CN103188052A - Space-selection-based self-feedback interference suppression method of same-frequency full-duplex MIMO (Multiple Input Multiple Output) system - Google Patents

Abstract

The invention discloses a space-selection-based self-feedback interference suppression method of a same-frequency full-duplex MIMO (Multiple Input Multiple Output) system. According to the self-feedback interference suppression method, a non-nonsingular self-feedback interference matrix is constructed by selecting one or more multipath self-feedback interference channels, and a sending filter or a receiving filter is designed for suppressing self-feedback interference in a space expanded by the non-nonsingular self-feedback interference matrix. According to the self-feedback interference suspension method, in terms of the designs of the sending filter and the receiving filter, a subspace of the space expanded by the self-feedback interference matrix at a signal receiving end or a self-feedback interference matrix at a signal sending end is selected, and the dimensionality of the subspace is smaller than, even equal to that of the parent space of the subspace; and then the self-feedback interference in the subspace is suppressed, and therefore, the limitation that the conventional space-domain suppression algorithm can not be applied when the self-feedback interference matrix is nonsingular is solved.

Description

The co-channel full duplex mimo system self feed back disturbance restraining method of choosing based on the space

Technical field

The invention belongs to wireless communication technology field, more specifically say, relate to a kind of co-channel full duplex mimo system self feed back disturbance restraining method of choosing based on the space.

Background technology

At wireless communication field, co-channel full duplex MIMO(Multiple-Input Multiple-Output, multiple-input and multiple-output) system mainly plays the effect of relaying amplifying signal, in voice scenes such as video conference, is used widely.Along with the development of 3G, 4G mobile radio system, relay station and junction network based on the co-channel full duplex mimo system have appearred especially.Because the co-channel full duplex mimo system is with the work of while frequently, the signal that transmitting antenna sends will be received antenna and receive, and this phenomenon is called as self feed back and disturbs.When transmitting antenna and reception antenna isolation are not enough, will cause self feed back interference effect message capacity even communication success rate.

The spatial domain cancellation technology is mainly by signal receiving filter in the design co-channel full duplex mimo system

And transmitting filter

Realize.Fig. 1 is that self feed back disturbs the spatial domain to suppress structural representation in the typical co-channel full duplex mimo system.As shown in Figure 1, N _RrxAnd N _RtxBe respectively co-channel full duplex mimo system reception antenna number and number of transmit antennas,

With

For receiving signal in the relay station through behind the receiving filter and send signal through the signal beam number before the transmitting filter, the dimension of C representing matrix.The source end to co-channel full duplex system mimo system channel is

The self feed back channel is

N _StxBe source end number of transmit antennas, L is the multipath bar number of self feed back interference signal time delay equal symbol cycle integral multiple.

For the co-channel full duplex mimo system receives signal,

For by the receiving filter signal,

Be the transmission signal before the process transmitting filter,

For sending signal.Then can obtain n during L=1 constantly: $\hat{r}\left[n\right]=G_{\mathrm{rx}}{H}_{\mathrm{SR}}r\left[n\right]+G_{\mathrm{rx}}{H}_{\mathrm{LI}}{G}_{\mathrm{tx}}\hat{t}\left[n\right],$ Wherein

Be the self feed back interference signal.

Existing co-channel full duplex mimo system self feed back disturbs the spatial domain cancellation technology to need the channel prior information, mainly contain ZF (Zero Forcing, ZF) algorithm, MMSE (Minimum Mean Square Error, least mean-square error) algorithm and BS (Beaming Selection, day line options) algorithm scheduling algorithm.But there are two big shortcomings in existing algorithm: 1) can not be applied to the self feed back channel matrix H _LIThe scene of full rank; 2) do not propose self feed back disturbance restraining method at the channel maximum multipath time delay is-greater-than symbol cycle, namely existing algorithm has only been considered the scene of L=1.

Summary of the invention

The objective of the invention is to overcome the deficiencies in the prior art, a kind of co-channel full duplex mimo system self feed back disturbance restraining method of choosing based on the space is provided, according to receiving signal end self feed back interference matrix design transmitting filter or receiving filter, during the cycle, part is made in the self feed back interference suppressed greater than signal code in self feed back interference matrix full rank and its multidiameter delay.

For achieving the above object, the present invention is based on the co-channel full duplex mimo system self feed back disturbance restraining method of choosing in the space, it is characterized in that may further comprise the steps:

(1), receives signal end self feed back interference matrix H _LIBe expressed as:

Wherein, H _Ij∈ C ^{1 * L}Expression is from co-channel full duplex mimo system j, 1≤j≤N _RtxThe root transmitting antenna is to i, 1≤i≤N _RrxThe subchannel vector of root reception antenna; N _RtxAnd N _RrxBe respectively co-channel full duplex mimo system number of transmit antennas and reception antenna number; H _Ij=[h _{Ij, 1}, h _{Ij, 2}..., h _{Ij, L}], h wherein _{Ij, k}Be the vectorial H of row _IjK column element value, k ∈ (1,2 ..., L), L is the multipath bar number of self feed back interference signal time delay equal symbol cycle integral multiple;

Calculate and receive signal end self feed back interference matrix H _LIOrder: R ₁=rank (H _LI), rank is that matrix is asked the order operator; If R ₁＜N _Rrx, H then _LINon-full rank enters step (9), otherwise enters step (2);

(2), hold self feed back interference matrix H to received signal _LIHandle, obtain the channel matrix of k bar multipath:

$H_{\mathrm{LI},k}=\left(\begin{array}{cccc}{h}_{11,k}& h_{12,k}& ...& h_{{1N}_{\mathrm{Rtx}},\mathrm{<figure-callout\; id="21"\; label="k\; h"\; filenames="HDA00002949924600012.png"\; state="\{\{state\}\}">k</figure-callout>}}& \\ h_{}{}_{21,\mathrm{<figure-callout\; id="22"\; label="k\; h"\; filenames="HDA00002949924600012.png"\; state="\{\{state\}\}">k</figure-callout>}}& h_{}{}_{22,k}& ...& h_{{2N}_{\mathrm{Rtx}},k}\\ .& .& .& .\\ .& .& .& .\\ .& .& .& .\\ h_{N_{\mathrm{Rtx}}1,k}& {\mathrm{<figure-callout\; id="2"\; label="h\; N\; Rtx"\; filenames="HDA00002949924600012.png,HDA00002949924600021.png"\; state="\{\{state\}\}">h</figure-callout>}}_{N_{\mathrm{Rtx}}}& ...& h_{N_{\mathrm{Rtx}}{N}_{\mathrm{Rtx}},k}\end{array}\right)$

Wherein, h _{Ij, k}Be the vectorial H of row _IjK column element value;

(3), initialization empty matrix set A, L multipath channel matrix H _LI,The matrix of non-full rank is formed set of matrices B among the k, and the current matrix element number of set A and set B is respectively M, N; If N=0 enters step (8), otherwise enter step (4);

(4), the x in the set A, 1≤x≤M matrix element is A _x, the y in the set B, 1≤y≤N matrix element is B _yAll matrix element B in the Ergodic Matrices set B _y, with A ₁, A ₂..., A _M, B _yThe splicing of going obtains N matrix X _y, at N rank (X _y) in find out less than N _RrxRank (X _y), with the matrix B of maximum correspondence wherein _yBe designated as

If there are a plurality of maximums, then choose the matrix B of a correspondence arbitrarily _yBe designated as

Enter step (5); If all rank (X _y) all be not less than N _Rrx, enter step (6);

(5), with matrix

Add set A, note is done And from set B, delete matrix

Note is done

Upgrade the element number of set A and B: M=M+1, N=N-1; If N=0 enters step (6), continue to upgrade set A, B otherwise return step (4);

(6), utilize all elements structure matrix in the set A:

$H_1=\left[\begin{array}{cccc}{H}_{\mathrm{LI},m_1}& H_{\mathrm{LI},{\mathrm{<figure-callout\; id="2"\; label="m"\; filenames="HDA00002949924600012.png,HDA00002949924600021.png"\; state="\{\{state\}\}">m</figure-callout>}}_2}& ...& H_{\mathrm{LI},m_M}\end{array}\right]=[A_1{\mathrm{<figure-callout\; id="2"\; label="A"\; filenames="HDA00002949924600012.png,HDA00002949924600021.png"\; state="\{\{state\}\}">A</figure-callout>}}_2...A_M]$

Wherein Be matrix H ₁T, 1≤t≤M element;

(7), increase receiving filter at co-channel full duplex mimo system signal link:

G _rx＝I-H ₁H ₁ ⁺＝G _rx,M-1G _rx,M-2...G _rx,1G _rx,0

Wherein:

$G_{\mathrm{rx},0}=I-H_{\mathrm{LI},m_1}{H}_{\mathrm{LI}{,m}_1}^{+}$

$G_{\mathrm{rx},1}=I-G_{\mathrm{rx},0}{H}_{\mathrm{LI},m_2}{\left(G_{\mathrm{rx},0}{H}_{\mathrm{Li},m_2}\right)}^{+}$

....

$G_{\mathrm{rx},M-1}=I-\underset{t^{\&prime;}=M-2}{\overset{0}{\mathrm{\&Pi;}}}{G}_{\mathrm{rx},t}{H}_{\mathrm{LI},m_M-1}{\left(\underset{t^{\&prime;}=M-2}{\overset{0}{\mathrm{\&Pi;}}}{G}_{\mathrm{rx},t}{H}_{\mathrm{LI},m_M-1}\right)}^{+}$

H wherein ₁ ⁺Be matrix H ₁The Moore-Penrose generalized inverse matrix, all the other matrix class are seemingly; I representation unit matrix;

(8), preferred matrix Z ₁Make 0＜rank (Z ₁H _{LI, k})＜N _Rrx, wherein k ∈ (1,2 ..., L) get arbitrary value, increase receiving filter: G at co-channel full duplex mimo system signal link _Rx=I-Z ₁H _{LI, k}(Z ₁H _{LI, k}) ⁺(Z wherein ₁H _{LI, k}) ⁺Be matrix Z ₁H _{LI, k}The Moore-Penrose generalized inverse matrix;

(9), increase receiving filter: G at co-channel full duplex mimo system signal link _Rx=I-H _LIH _LI ⁺, H wherein _LI ⁺Be matrix H _LIThe Moore-Penrose generalized inverse matrix.

For achieving the above object, the present invention is based on the co-channel full duplex mimo system self feed back disturbance restraining method of choosing in the space, it is characterized in that may further comprise the steps:

(1), receives signal end self feed back interference matrix H _LIBe expressed as:

To self feed back interference channel matrix H _LIHandle, obtain the channel matrix of k bar multipath:

Wherein, h _{Ij, k}Be the vectorial H of row _IjK column element value;

Structural matrix

H sends signal end self feed back interference matrix for the co-channel full duplex mimo system; R ₂=rank (H); If R ₂＜N _Rtx, namely the non-full rank of H enters step (8); Otherwise enter step (2);

(2), the initialization empty matrix is gathered C, L multipath channel matrix H _{LI, k}In the matrix of non-full rank form set of matrices D, set C and the current matrix element number of set D are respectively P, Q, if Q=0 enters step (7), otherwise enter step (3);

(3), the v among the note set C, 1≤v≤P matrix element is C _v, the w among the set D, 1≤w≤Q matrix element is D _wAll matrix element D among the Ergodic Matrices set D _w, will The splicing of going obtains Q matrix Y _w, at Q

In find out less than N _Rtx

With the matrix D of maximum correspondence wherein _wBe designated as

If there are a plurality of maximums, then choose a matrix D arbitrarily _wBe designated as

Enter step (4); If all

All be not less than N _Rtx, enter step (5);

(4), with matrix

Add set C, note is done

And from set D, delete matrix

Note is done Upgrade the element number of set C and D: P=P+1, Q=Q-1; If Q=0 enters step (5), continue to upgrade set C, D otherwise return step (3);

(5), utilize all elements structure matrix among the set C:

$H_2={\left[\begin{array}{cccc}{H}_{\mathrm{LI},n_1}^T& H_{\mathrm{LI},n_2}^T& ...& H_{\mathrm{LI},n_P}^T\end{array}\right]}^T={{[C}_1^T{C}_2^T...C_P^T]}^T$

Wherein

Be matrix H ₂R, 1≤r≤P element;

(6), in co-channel full duplex mimo system signal link, increase transmitting filter:

$G_{\mathrm{tx}}=I-H_2^{+}{H}_2=G_{\mathrm{tx},0}{G}_{\mathrm{tx},1}...G_{\mathrm{tx},P-2}{G}_{\mathrm{rx},P-1}$

Wherein:

$G_{\mathrm{tx},0}=I-H_{\mathrm{LI},n_1}^{+}{H}_{\mathrm{LI},n_1}$

$G_{\mathrm{tx},1}=I-{\left(H_{\mathrm{LI},n_2}{G}_{\mathrm{tx},0}\right)}^{+}{H}_{\mathrm{LI},n_2}{G}_{\mathrm{tx},0}$

....

$G_{\mathrm{tx},P-1}=I-{\left(H_{\mathrm{LI},n_P}\underset{r^{\&prime;}=0}{\overset{P-2}{\mathrm{\&Pi;}}}{G}_{\mathrm{tx},r^{\&prime;}}\right)}^{+}{H}_{\mathrm{LI},n_P}\underset{r^{\&prime;}=0}{\overset{P-2}{\mathrm{\&Pi;}}}{G}_{\mathrm{tx},r^{\&prime;}}$

H wherein ₂ ⁺Be matrix H ₂The Moore-Penrose generalized inverse matrix, all the other matrix class are seemingly; I representation unit matrix;

(7), preferred matrix Z ₂Make 0＜rank (Z ₂H _{LI, k})＜N _Rtx, wherein k ∈ (1,2 ..., L) get arbitrary value, increase transmitting filter: G at co-channel full duplex mimo system signal link _Tx=I-(Z ₂H _{LI, k}) ⁺Z ₂H _{LI, k}(Z wherein ₂H _{LI, k}) ⁺Be matrix Z ₂H _{LI, k}The Moore-Penrose generalized inverse matrix;

(8), increase transmitting filter: G at co-channel full duplex mimo system signal link _Tx=I-H ⁺H, wherein H ⁺Moore-Penrose generalized inverse matrix for matrix H.

Goal of the invention of the present invention is achieved in that

The present invention is based on the self feed back interference matrix of the co-channel full duplex mimo system self feed back disturbance restraining method chosen in the space non-full rank of self feed back interference channel structure by choosing one or more of multipaths, and design transmitting filter or receiving filter are suppressed at this non-full rank self feed back interference matrix and open into the self feed back interference space in.

The design of transmitting filter and receiving filter is at first by choosing by receiving signal end self feed back interference matrix H among the present invention _LIOr send signal end self feed back interference matrix H open into the subspace in space and this subspace dimension less than in addition equal its generating space, suppress the self feed back interference in this subspace then, solved self feed back interference matrix H _LIThe tradition spatial domain suppresses the restriction that algorithm can not be used during with the H full rank.

Description of drawings

Fig. 1 is that self feed back disturbs the spatial domain to suppress structural representation in the typical co-channel full duplex mimo system;

Fig. 2 is the performance schematic diagram of method one in the co-channel full duplex mimo system that the present invention is based on the co-channel full duplex mimo system self feed back disturbance restraining method proposition of choosing in the space;

Fig. 3 is the performance schematic diagram of method two in the co-channel full duplex mimo system that the present invention is based on the co-channel full duplex mimo system self feed back disturbance restraining method proposition of choosing in the space.

Embodiment

Below in conjunction with accompanying drawing the specific embodiment of the present invention is described, so that those skilled in the art understands the present invention better.What need point out especially is that in the following description, when perhaps the detailed description of known function and design can desalinate main contents of the present invention, these were described in here and will be left in the basket.

Embodiment

Fig. 1 is that self feed back disturbs the spatial domain to suppress structural representation in the typical co-channel full duplex mimo system.It is consistent with Fig. 1 that the self feed back that present embodiment adopts disturbs the spatial domain to suppress structure.Scene in this example adopts the wireless mobile communications relay station to set up the co-channel full duplex mimo system, and parameter is as follows: information source adopts Bernoulli Jacob's binary sequence, and its 0 and 1 probability is all 0.5, sampling period T _s=0.001s; Modulation system adopts BPSK; The number of transmit antennas N of source end _Stx=3, Space Time Coding speed is 3/4; The source end adopts the Rayleigh flat channel and adds white Gaussian noise to co-channel full duplex mimo system channel, and signal to noise ratio is expressed as SNR; The co-channel full duplex mimo system receives and number of transmit antennas N _Rrx=N _Rtx=3; The co-channel full duplex mimo system adopts Decoded-and-Forward mode processing signals, processing such as decoding and do processing such as Space Time Coding before the transmission signal when namely doing sky after receiving signal; The amplifier magnification ratio G=5dB of system; The self feed back channel adopts smooth Rayleigh channel, its fading channel multiple 0dB, and the maximum multipath bar is counted L=3.The present embodiment operation continues and performance statistics time T=50s.

The present invention is based on the co-channel full duplex mimo system self feed back disturbance restraining method of choosing in the space and proposed two kinds of methods, is that emphasis designs with transmitting filter and receiving filter respectively.In the present embodiment, the concrete implementation step of the co-channel full duplex mimo system self feed back disturbance restraining method of choosing based on the space one comprises:

Step 1: receive signal end self feed back interference matrix H _LIBe expressed as:

Receive signal end self feed back interference matrix H _LIBe co-channel full duplex mimo system feedback interference channel matrix.

Wherein, H _Ij∈ C ^{1 * L}Expression is from co-channel full duplex mimo system j, 1≤j≤N _RtxThe root transmitting antenna is to i, 1≤i≤N _RrxThe subchannel vector of root reception antenna; N _RtxAnd N _RrxBe respectively co-channel full duplex mimo system number of transmit antennas and reception antenna number; H _Ij=[h _{Ij, 1}, h _{Ij, 2}..., h _{Ij, L}], h wherein _{Ij, k}Be the vectorial H of row _IjK column element value, k ∈ (1,2 ..., L), L is the multipath bar number of self feed back interference signal time delay equal symbol cycle integral multiple.

Calculate and receive signal end self feed back interference matrix H _LIOrder: R ₁=rank (H _LI), rank is that matrix is asked the order operator; If R ₁＜N _Rrx, H then _LINon-full rank enters step 9, otherwise enters step 2.

In the present embodiment, receive signal end self feed back interference matrix H _LIPersonnel make up arbitrarily according to system parameters by enforcement, make its full rank or non-full rank.

Step 2: hold self feed back interference matrix H to received signal _LIHandle, obtain the channel matrix of k bar multipath:

$H_{\mathrm{LI},k}=\left(\begin{array}{cccc}{h}_{11,k}& h_{12,k}& ...& h_{{1N}_{\mathrm{Rtx}},\mathrm{<figure-callout\; id="21"\; label="k\; h"\; filenames="HDA00002949924600012.png"\; state="\{\{state\}\}">k</figure-callout>}}& \\ h_{}{}_{21,\mathrm{<figure-callout\; id="22"\; label="k\; h"\; filenames="HDA00002949924600012.png"\; state="\{\{state\}\}">k</figure-callout>}}& h_{}{}_{22,k}& ...& h_{{2N}_{\mathrm{Rtx}},k}\\ .& .& .& .\\ .& .& .& .\\ .& .& .& .\\ h_{N_{\mathrm{Rtx}}1,k}& {\mathrm{<figure-callout\; id="2"\; label="h\; N\; Rtx"\; filenames="HDA00002949924600012.png,HDA00002949924600021.png"\; state="\{\{state\}\}">h</figure-callout>}}_{N_{\mathrm{Rtx}}}& ...& h_{N_{\mathrm{Rtx}}{N}_{\mathrm{Rtx}},k}\end{array}\right)$

Wherein, h _{Ij, k}Be the vectorial H of row _IjK column element value.

Step 3: initialization empty matrix set A, L multipath channel matrix H _{LI, k}In the matrix of non-full rank form set of matrices B, the current matrix element number of set A and set B is respectively M, N, if N=0 enters step 8, otherwise enters step 4.

Step 4: the x in the note set A, 1≤x≤M matrix element is A _x, the y in the set B, 1≤y≤N matrix element is B _yAll matrix element B in the Ergodic Matrices set B _y, with A ₁, A ₂..., A _M, B _yThe splicing of going obtains N matrix X _y, at N rank (X _y) in find out less than N _RrxRank (X _y), with the matrix B of maximum correspondence wherein _yBe designated as

If there are a plurality of maximums, then choose the matrix B of a correspondence arbitrarily _yBe designated as

Enter step 5; If all rank (X _y) all be not less than N _Rrx, enter step 6.

Step 5: with matrix

Add set A, note is done And from set B, delete matrix

Note is done

Upgrade the element number of set A and B: M=M+1, N=N-1; If N=0 enters step 6, continue to upgrade set A, B otherwise return step 4.

Step 6: utilize all elements structure matrix in the set A:

$H_1=\left[\begin{array}{cccc}{H}_{\mathrm{LI},m_1}& H_{\mathrm{LI},{\mathrm{<figure-callout\; id="2"\; label="m"\; filenames="HDA00002949924600012.png,HDA00002949924600021.png"\; state="\{\{state\}\}">m</figure-callout>}}_2}& ...& H_{\mathrm{LI},m_M}\end{array}\right]=[A_1{\mathrm{<figure-callout\; id="2"\; label="A"\; filenames="HDA00002949924600012.png,HDA00002949924600021.png"\; state="\{\{state\}\}">A</figure-callout>}}_2...A_M]$

Wherein

Be matrix H ₁T, 1≤t≤M element.

Step 7: increase receiving filter at co-channel full duplex mimo system signal link:

G _rx＝I-H ₁H ₁ ⁺＝G _rx,M-1G _rx,M-2...G _rx,1G _rx,0

Wherein:

$G_{\mathrm{rx},0}=I-H_{\mathrm{LI},m_1}{H}_{\mathrm{LI}{,m}_1}^{+}$

$G_{\mathrm{rx},1}=I-G_{\mathrm{rx},0}{H}_{\mathrm{LI},m_2}{\left(G_{\mathrm{rx},0}{H}_{\mathrm{LI},m_2}\right)}^{+}$

....

$G_{\mathrm{rx},M-1}=I-\underset{t^{\&prime;}=M-2}{\overset{0}{\mathrm{\&Pi;}}}{G}_{\mathrm{rx},t}{H}_{\mathrm{LI},m_M-1}{\left(\underset{t^{\&prime;}=M-2}{\overset{0}{\mathrm{\&Pi;}}}{G}_{\mathrm{rx},t}{H}_{\mathrm{LI},m_M-1}\right)}^{+}$

Wherein () ⁺For asking the Moore-Penrose generalized inverse of matrix, H ₁ ⁺Be matrix H ₁The Moore-Penrose generalized inverse matrix, all the other matrix class are seemingly; Π () is for connecting multiplication symbol, I representation unit matrix.

Adopt this receiving filter, can be to H ₁The self feed back of the two-dimensional space of opening is disturbed and is suppressed.

Step 8: preferred matrix Z ₁Make 0＜rank (Z ₁H _{LI, k})＜N _Rrx, wherein k ∈ (1,2 ..., L) get arbitrary value, increase receiving filter: G at co-channel full duplex mimo system signal link _Rx=I-Z ₁H _{LI, k}(Z ₁H _{LI, k}) ⁺(Z wherein ₁H _{LI, k}) ⁺Be matrix Z ₁H _{LI, k}The Moore-Penrose generalized inverse matrix;

Step 9: increase receiving filter: G at co-channel full duplex mimo system signal link _Rx=I-H _LIH _LI ⁺, H wherein _LI ⁺Be matrix H _LIThe Moore-Penrose generalized inverse matrix.Adopt this receiving filter, can hold self feed back interference matrix H to received signal _LIIn all self feed backs disturb and suppress fully.

Fig. 2 is the performance schematic diagram of method one in the co-channel full duplex mimo system that the present invention is based on the co-channel full duplex mimo system self feed back disturbance restraining method proposition of choosing in the space.As shown in Figure 2, carry out emulation by present embodiment and obtain, when receiving signal end self feed back interference matrix H _LIDuring non-full rank, no self feed back disturbs the error rate of the co-channel full duplex mimo system that suppresses shown in curve 21, adopts the present invention to disturb the error rate that suppresses fully shown in curve 24 to self feed back; When receiving signal end self feed back interference matrix H _LIDuring full rank, no self feed back disturbs the ber curve of the co-channel full duplex mimo system that suppresses shown in curve 22, adopts the present invention to H ₁The self feed back of the two-dimensional space of opening disturbs the ber curve that suppresses shown in curve 23.As seen, adopt method one proposed by the invention, when self feed back channel maximum delay during greater than signal code cycle or self feed back interference matrix full rank, can realize effective inhibition that self feed back is disturbed.

In the present embodiment, the concrete implementation step of the co-channel full duplex mimo system self feed back disturbance restraining method of choosing based on the space two comprises:

Step 1: receive signal end self feed back interference matrix H _LIBe expressed as:

Wherein, H _Ij∈ C ^{1 * L}Expression is from co-channel full duplex mimo system j, 1≤j≤N _RtxThe root transmitting antenna is to i, 1≤i≤N _RrxThe subchannel vector of root reception antenna; H _Ij=[h _{Ij, 1}, h _{Ij, 2}..., h _{Ij, L}], h wherein _{Ij, k}Be the vectorial H of row _IjK column element value, k ∈ (1,2 ..., L), L is the multipath bar number of self feed back interference signal time delay equal symbol cycle integral multiple.

Hold self feed back interference matrix H to received signal _LIHandle, obtain the channel matrix of k bar multipath:

$H_{\mathrm{LI},k}=\left(\begin{array}{cccc}{h}_{11,k}& h_{12,k}& ...& h_{{1N}_{\mathrm{Rtx}},\mathrm{<figure-callout\; id="21"\; label="k\; h"\; filenames="HDA00002949924600012.png"\; state="\{\{state\}\}">k</figure-callout>}}& \\ h_{}{}_{21,\mathrm{<figure-callout\; id="22"\; label="k\; h"\; filenames="HDA00002949924600012.png"\; state="\{\{state\}\}">k</figure-callout>}}& h_{}{}_{22,k}& ...& h_{{2N}_{\mathrm{Rtx}},k}\\ .& .& .& .\\ .& .& .& .\\ .& .& .& .\\ h_{N_{\mathrm{Rtx}}1,k}& {\mathrm{<figure-callout\; id="2"\; label="h\; N\; Rtx"\; filenames="HDA00002949924600012.png,HDA00002949924600021.png"\; state="\{\{state\}\}">h</figure-callout>}}_{N_{\mathrm{Rtx}}}& ...& h_{N_{\mathrm{Rtx}}{N}_{\mathrm{Rtx}},k}\end{array}\right)$

Wherein, h _{Ij, k}Be the vectorial H of row _IjK column element value;

Structural matrix

H sends signal end self feed back interference matrix for the co-channel full duplex mimo system; R ₂=rank (H); If R ₂＜N _Rtx, namely the non-full rank of H enters step 8; Otherwise enter step 2.

In the present embodiment, receive signal end self feed back interference matrix H _LIPersonnel make up arbitrarily according to system parameters by enforcement, and making the transmission signal end self feed back interference matrix H that obtains is full rank or non-full rank.

Step 2: initialization empty matrix set C, L multipath channel matrix H _{LI, k}In the matrix of non-full rank form set of matrices D, set C and the current matrix element number of set D are respectively P, Q, if Q=0 enters step 7, otherwise enter step 3.

Step 3: the v among the note set C, 1≤v≤P matrix element is C _v, the w among the set D, 1≤w≤Q matrix element is D _wAll matrix element D among the Ergodic Matrices set D _w, will

The splicing of going obtains Q matrix Y _w, () ^TFor asking matrix transpose.At Q

In find out less than N _Rtx

With the matrix D of maximum correspondence wherein _wBe designated as

If there are a plurality of maximums, then choose a matrix D arbitrarily _wBe designated as

Enter step 4; If all

All be not less than N _Rtx, enter step 5.

Step 4: with matrix

Add set C, note is done

And from set D, delete matrix

Note is done

Upgrade the element number of set C and D: P=P+1, Q=Q-1; If Q=0 enters step 5, continue to upgrade set C, D otherwise return step 3;

Step 5: utilize all elements structure matrix among the set C:

${\mathrm{<figure-callout\; id="2"\; label="H"\; filenames="HDA00002949924600012.png,HDA00002949924600021.png"\; state="\{\{state\}\}">H</figure-callout>}}_2={\left[\begin{array}{cccc}{H}_{\mathrm{LI},n_1}^T& H_{\mathrm{LI},n_2}^T& ...& H_{\mathrm{LI},n_P}^T\end{array}\right]}^T={{[C}_1^T{C}_2^T...C_P^T]}^T$

Wherein Be matrix H ₂R, 1≤r≤P element.

Step 6: in co-channel full duplex mimo system signal link, increase transmitting filter:

$G_{\mathrm{tx}}=I-{\mathrm{<figure-callout\; id="2"\; label="H"\; filenames="HDA00002949924600012.png,HDA00002949924600021.png"\; state="\{\{state\}\}">H</figure-callout>}}_2^{+}{\mathrm{<figure-callout\; id="2"\; label="H"\; filenames="HDA00002949924600012.png,HDA00002949924600021.png"\; state="\{\{state\}\}">H</figure-callout>}}_2=G_{\mathrm{tx},0}{G}_{\mathrm{tx},1}...G_{\mathrm{tx},P-2}{G}_{\mathrm{rx},P-1}$

Wherein:

$G_{\mathrm{tx},0}=I-H_{\mathrm{LI},n_1}^{+}{H}_{\mathrm{LI},n_1}$

$G_{\mathrm{tx},1}=I-{\left(H_{\mathrm{LI},n_2}{G}_{\mathrm{tx},0}\right)}^{+}{H}_{\mathrm{LI},n_2}{G}_{\mathrm{tx},0}$

....

$G_{\mathrm{tx},P-1}=I-{\left(H_{\mathrm{LI},n_P}\underset{r^{\&prime;}=0}{\overset{P-2}{\mathrm{\&Pi;}}}{G}_{\mathrm{tx},r^{\&prime;}}\right)}^{+}{H}_{\mathrm{LI},n_P}\underset{r^{\&prime;}=0}{\overset{P-2}{\mathrm{\&Pi;}}}{G}_{\mathrm{tx},r^{\&prime;}}$

H wherein ₂ ⁺Be matrix H ₂The Moore-Penrose generalized inverse matrix, all the other matrix class are seemingly; I representation unit matrix.

Adopt this receiving filter, can be to H ₂The self feed back of the two-dimensional space of opening is disturbed and is suppressed.

Step 7: preferred matrix Z ₂Make 0＜rank (Z ₂H _{LI, k})＜N _Rtx, wherein k ∈ (1,2 ..., L) get arbitrary value, increase transmitting filter: G at co-channel full duplex mimo system signal link _Tx=I-(Z ₂H _{LI, k}) ⁺Z ₂H _{LI, k}(Z wherein ₂H _{LI, k}) ⁺Be matrix Z ₂H _{LI, k}The Moore-Penrose generalized inverse matrix;

Step 8: in co-channel full duplex mimo system signal link, increase transmitting filter: G _Tx=I-H ⁺H, wherein H ⁺Moore-Penrose generalized inverse matrix for matrix H.

Adopt this receiving filter, can be to sending signal end self feed back interference matrix H _LIIn all self feed backs disturb and suppress fully.

Fig. 3 is the performance schematic diagram of method two in the co-channel full duplex mimo system that the present invention is based on the co-channel full duplex mimo system self feed back disturbance restraining method proposition of choosing in the space.As shown in Figure 3, carry out emulation by present embodiment and obtain, when sending signal end self feed back interference matrix H full rank, no self feed back disturbs the error rate of the co-channel full duplex mimo system that suppresses shown in curve 31, adopts the present invention to H ₂The self feed back of the two-dimensional space of opening disturbs the error rate that suppresses shown in curve 34; When sending the non-full rank of signal end self feed back interference matrix H, no self feed back disturbs the error rate of the co-channel full duplex mimo system that suppresses shown in curve 32, adopts the present invention that self feed back is disturbed and suppresses fully shown in curve 33.As seen, adopt method two proposed by the invention, when self feed back channel maximum delay during greater than signal code cycle or self feed back interference matrix full rank, can realize effective inhibition that self feed back is disturbed.

Although above the illustrative embodiment of the present invention is described; so that those skilled in the art understand the present invention; but should be clear; the invention is not restricted to the scope of embodiment; to those skilled in the art; as long as various variations appended claim limit and the spirit and scope of the present invention determined in, these variations are apparent, all utilize innovation and creation that the present invention conceives all at the row of protection.

Claims (2)

1. co-channel full duplex mimo system self feed back disturbance restraining method of choosing based on the space is characterized in that may further comprise the steps:

(1), receives signal end self feed back interference matrix H _LIBe expressed as:

Wherein, H _Ij∈ C ^{1 * L}Expression is from co-channel full duplex mimo system j, 1≤j≤N _RtxThe root transmitting antenna is to i, 1≤i≤N _RrxThe subchannel vector of root reception antenna; H _Ij=[h _{Ij, 1}, h _{Ij, 2}..., h _{Ij, L}], h wherein _{Ij, k}Be the vectorial H of row _IjK column element value, k ∈ (1,2 ..., L);

Calculate and receive signal end self feed back interference matrix H _LIOrder: R ₁=rank (H _LI), rank is that matrix is asked the order operator; If R ₁＜N _Rrx, H then _LINon-full rank enters step (9), otherwise enters step (2);

(2), hold self feed back interference matrix H to received signal _LIHandle, obtain the channel matrix of k bar multipath:

$H_{\mathrm{LI},k}=\left(\begin{array}{cccc}{h}_{11,k}& h_{12,k}& ...& h_{{1N}_{\mathrm{Rtx}},k}\\ h_{21,k}& h_{22,k}& ...& h_{{2N}_{\mathrm{Rtx}},k}\\ .& .& .& .\\ .& .& .& .\\ .& .& .& .\\ h_{N_{\mathrm{Rtx}}1,k}& h_{N_{\mathrm{Rtx}}2,k}& ...& h_{N_{\mathrm{Rtx}}{N}_{\mathrm{Rtx}},k}\end{array}\right)$

(3), initialization empty matrix set A, L multipath channel matrix H _{LI, k}In the matrix of non-full rank form set of matrices B, the current matrix element number of set A and set B is respectively M, N; If N=0 enters step (8), otherwise enter step (4);

(4), the x in the set A, 1≤x≤M matrix element is A _x, the y in the set B, 1≤y≤N matrix element is B _yAll matrix element B in the Ergodic Matrices set B _y, with A ₁, A ₂..., A _M, B _yThe splicing of going obtains N matrix X _y, at N rank (X _y) in find out less than N _RrxRank (X _y), with the matrix B of maximum correspondence wherein _yBe designated as

If there are a plurality of maximums, then choose the matrix D of a correspondence arbitrarily _wBe designated as

Enter step (5); If all rank (X _y) all be not less than N _Rrx, enter step (6);

(5), with matrix

Add set A, note is done

And from set B, delete matrix

Note is done

Upgrade the element number of set A and B: M=M+1, N=N-1; If N=0 enters step (6), continue to upgrade set A, B otherwise return step (4);

(6), utilize all elements structure matrix in the set A:

$H_1=\left[\begin{array}{cccc}{H}_{\mathrm{LI},m_1}& H_{\mathrm{LI},m_2}& ...& H_{\mathrm{LI},m_M}\end{array}\right]=[A_1{A}_2...A_M]$

Wherein

Be matrix H ₁T, 1≤t≤M element;

(7), increase the reception traffic filter at co-channel full duplex mimo system signal link:

$G_{\mathrm{rx}}=I-H_1{H_1}^{+}=G_{\mathrm{rx},M-1}{G}_{\mathrm{rx},M-2}...G_{\mathrm{rx},1}{G}_{\mathrm{rx},0}$

Wherein:

$G_{\mathrm{rx},0}=I-H_{\mathrm{LI},m_1}{H}_{\mathrm{LI}{,m}_1}^{+}$

$G_{\mathrm{rx},1}=I-G_{\mathrm{rx},0}{H}_{\mathrm{LI},m_2}{\left(G_{\mathrm{rx},0}{H}_{\mathrm{LI},m_2}\right)}^{+}$

....

$G_{\mathrm{rx},M-1}=I-\underset{t^{\&prime;}=M-2}{\overset{0}{\mathrm{\&Pi;}}}{G}_{\mathrm{rx},t}{H}_{\mathrm{LI},m_M-1}{\left(\underset{t^{\&prime;}=M-2}{\overset{0}{\mathrm{\&Pi;}}}{G}_{\mathrm{rx},t}{H}_{\mathrm{LI},m_M-1}\right)}^{+}$

H wherein ₁ ⁺Be matrix H ₁The Moore-Penrose generalized inverse matrix, all the other matrix class are seemingly;

(8), preferred matrix Z ₁Make 0＜rank (Z ₁H _{LI, k})＜N _Rrx, wherein k ∈ (1,2 ..., L) get arbitrary value, increase receiving filter: G at co-channel full duplex mimo system signal link _Rx=I-Z ₁H _{LI, k}(Z ₁H _{LI, k}) ⁺

(9), increase receiving filter: G at co-channel full duplex mimo system signal link _Rx=I-H _LIH _LI ⁺, H wherein _LI ⁺Be matrix H _LIThe Moore-Penrose generalized inverse matrix.

2. co-channel full duplex mimo system self feed back disturbance restraining method of choosing based on the space is characterized in that drawing together following steps:

(1), receives signal end self feed back interference matrix H _LIBe expressed as:

To self feed back interference channel matrix H _LIHandle, obtain the channel matrix of k bar multipath:

$H_{\mathrm{LI},k}=\left(\begin{array}{cccc}{h}_{11,k}& h_{12,k}& ...& h_{{1N}_{\mathrm{Rtx}},k}\\ h_{21,k}& h_{22,k}& ...& h_{{2N}_{\mathrm{Rtx}},k}\\ .& .& .& .\\ .& .& .& .\\ .& .& .& .\\ h_{N_{\mathrm{Rtx}}1,k}& h_{N_{\mathrm{Rtx}}2,k}& ...& h_{N_{\mathrm{Rtx}}{N}_{\mathrm{Rtx}},k}\end{array}\right)$

Structural matrix

H sends signal end self feed back interference matrix for the co-channel full duplex mimo system; R ₂=rank (H); If R ₂＜N _Rtx, namely the non-full rank of H enters step (8); Otherwise enter step (2);

(2), the initialization empty matrix is gathered C, L multipath channel matrix H _{LI, k}In the matrix of non-full rank form set of matrices D, set C and the current matrix element number of set D are respectively P, Q; If Q=0 enters step (7), otherwise enter step (3);

(3), the v among the note set C, 1≤v≤P matrix element is C _v, the w among the set D, 1≤w≤Q matrix element is D _wAll matrix element D among the Ergodic Matrices set D _w, will

The splicing of going obtains Q matrix Y _w, at Q

In find out less than N _Rtx

With the matrix D of maximum correspondence wherein _wBe designated as

If there are a plurality of maximums, then choose a matrix D arbitrarily _wBe designated as

Enter step (4); If all

All be not less than N _Rtx, enter step (5);

(4), with matrix

Add set C, note is done

And from set D, delete matrix

Note is done

Upgrade the element number of set C and D: P=P+1, Q=Q-1; If Q=0 enters step (5), continue to upgrade set C, D otherwise return step (3);

(5), utilize all elements structure matrix among the set C:

$H_2={\left[\begin{array}{cccc}{H}_{\mathrm{LI},n_1}^T& H_{\mathrm{LI},n_2}^T& ...& H_{\mathrm{LI},n_P}^T\end{array}\right]}^T={{[C}_1^T{C}_2^T...C_P^T]}^T$

Wherein Be matrix H ₂R, 1≤r≤P element;

(6), in co-channel full duplex mimo system signal link, increase transmitting filter:

$G_{\mathrm{tx}}=I-H_2^{+}{H}_2=G_{\mathrm{tx},0}{G}_{\mathrm{tx},1}...G_{\mathrm{tx},P-2}{G}_{\mathrm{rx},P-1}$

Wherein:

$G_{\mathrm{tx},0}=I-H_{\mathrm{LI},n_1}^{+}{H}_{\mathrm{LI},n_1}$

$G_{\mathrm{tx},1}=I-{\left(H_{\mathrm{LI},n_2}{G}_{\mathrm{tx},0}\right)}^{+}{H}_{\mathrm{LI},n_2}{G}_{\mathrm{tx},0}$

....

$G_{\mathrm{tx},P-1}=I-{\left(H_{\mathrm{LI},n_P}\underset{r^{\&prime;}=0}{\overset{P-2}{\mathrm{\&Pi;}}}{G}_{\mathrm{tx},r^{\&prime;}}\right)}^{+}{H}_{\mathrm{LI},n_P}\underset{r^{\&prime;}=0}{\overset{P-2}{\mathrm{\&Pi;}}}{G}_{\mathrm{tx},r^{\&prime;}}$

H wherein ₂ ⁺Be matrix H ₂The Moore-Penrose generalized inverse matrix, all the other matrix class are seemingly; I representation unit matrix;

(7), preferred matrix Z ₂Make 0＜rank (Z ₂H _{LI, k})＜N _Rtx, wherein k ∈ (1,2 ..., L) get arbitrary value, increase transmitting filter: G at co-channel full duplex mimo system signal link _Tx=I-(Z ₂H _{LI, k}) ⁺Z ₂H _{LI, k}

(8), increase transmitting filter: G at co-channel full duplex mimo system signal link _Tx=I-H ⁺H.

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