CN102931893B - Soft switch control circuit for direct current motor - Google Patents
Soft switch control circuit for direct current motor Download PDFInfo
- Publication number
- CN102931893B CN102931893B CN201110227360.1A CN201110227360A CN102931893B CN 102931893 B CN102931893 B CN 102931893B CN 201110227360 A CN201110227360 A CN 201110227360A CN 102931893 B CN102931893 B CN 102931893B
- Authority
- CN
- China
- Prior art keywords
- signal
- reference voltage
- commutation
- motor
- circuit
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Active
Links
Abstract
The invention discloses a soft switch control circuit for a direct current motor. The soft switch control circuit is used for regulating a standard phase change time point defined by a standard phase change signal to control the phase change action of the direct current motor. The soft switch control circuit comprises an absolute value signal generation circuit, a reference voltage generation circuit and a comparison circuit, wherein the absolute value signal generation circuit generates an absolute value signal according to a pair of Hall sensing signals from the direct current motor; the reference voltage generation circuit receives the standard phase change signal and at least one terminal voltage from a coil of the direct current motor, and judges the coil current of the coil at the standard phase change time point according to the terminal voltages to regulate the level of a reference voltage; and the comparison circuit compares the absolute value signal with the reference voltage to generate a phase change regulation signal to regulate the standard phase change time point. The problem that a phase is easily changed early or lately in the conventional direct current motor switching technology is solved, and the aim of soft switch is fulfilled.
Description
Technical field
The present invention relates to a kind of control circuit for d.c. motor, particularly relate to a kind of soft switch control circuit for d.c. motor.
Background technology
Fig. 1 is the schematic diagram of a typical DC motor drive circuit.This d.c. motor drive circuit 180 has four switch element M1, M2, M3, M4 formation bridge circuit (H-bridge) and rotates with CD-ROM drive motor.Its running can divide into two different conduction phase (phase).Being the first conduction phase (phase I) when switch element M1 and M4 conducting, is the second conduction phase (phase II) when switch element M2 and M3 conducting.
This bridge circuit must switch alternately between the first conduction phase and the second conduction phase, to maintain its actuating force for motor.Fig. 2 control signal A of each switch element M1, M2, M3, M4 of bridge circuit, B, C, D and flow through the oscillogram of coil current I1 of motor coil for this reason, figure coil electric current I 1 stream of turning right is defined as positive current.
For motor coil and rotor, in close to commutation time point, because the relative position of motor coil and rotor moves closer to, can cause the change of induced electromotive force that coil current is increased; But, when commutation, switch element switching can cause again coil current to decline rapidly.The acute variation of this electric current is except producing noise, due to rotor magnetic pole close to motor coil time, the magnetic field that motor coil produces too not large help for revolution, therefore, when rotor magnetic pole is close to motor coil, coil current increase (as figure bend region indicate) obvious help can't be had for CD-ROM drive motor.The electric current of this part can be regarded as the idle current of motor driving, and its power consumption supervened and magnetic field are just as waste.
One typical processing method of the lower part display head it off of Fig. 2.As shown in FIG., first, the method produces absolute value signal Vabs according to hall signal H+ and H-.And then this absolute value signal Vabs and fixing reference voltage Vth are compared, to define fixing impulsive ahead of time.This does sth. in advance impulsive in order to adjustment control signal A originally, the sequential of B, C, D, to produce new control signal A1, B1, C1, D1, can make coil current discharge into zero ahead of time, avoids the generation of idle current.
This processing method adopts, in the face of different coil current, rotating speed and other Parameters variation, easily produce and too late problem fixing switching time ahead of time.Switching time, when shifting to an earlier date too many, can produce the interval of one section of Zero coil current, and cause motor without driving force near commutation point, only utilize the inertia of motor rotor to rotate, and cause motor rotor velocity of rotation not steady near commutation point.Switching time when shifting to an earlier date very little, then cannot reach the object of soft handover.
Summary of the invention
In view of this, main purpose of the present invention is the soft switch control circuit proposing a kind of d.c. motor, and the problem in the commutation avoiding Traditional DC motor handoff technique easily to produce too early or excessively evening, to reach the object of Sofe Switch.
For reaching above-mentioned purpose, the invention provides a kind of soft switch control circuit of d.c. motor.The standard commutation time point that this soft switch control circuit defines in order to adjust a standard commutation signal, to control the commutation action of a d.c. motor.This soft switch control circuit comprises an absolute value signal and produces circuit, a reference voltage generating circuit and a comparison circuit.Wherein, absolute value signal produces circuit according to a pair Hall detection signal from d.c. motor, produces an absolute value signal.Reference voltage generating circuit receives standard commutation signal and at least one terminal voltage from a coil of d.c. motor, and judges that aforementioned coil is in the coil current of standard commutation time point according to this terminal voltage, to adjust the level of a reference voltage.Comparison circuit compares absolute value signal and reference voltage, to produce a commutation adjustment signal adjustment standard commutation time point.
In one embodiment of this invention, motor control circuit, according to commutation adjustment signal and standard commutation signal, controls d.c. motor and carries out commutation action.
In one embodiment of this invention, this soft switch control circuit has a logical circuit, produces one revise commutation signal according to commutation adjustment signal and standard commutation signal, and this revises the sequential entirety in advance lead time of commutation signal compared to standard commutation signal.Motor control circuit is then carry out commutation action according to revising commutation signal control d.c. motor.
Can be further understood by following detailed Description Of The Invention and appended accompanying drawing about the advantages and spirit of the present invention.
Accompanying drawing explanation
Fig. 1 is the schematic diagram of a typical DC motor drive circuit;
Fig. 2 is in the bridge circuit of Fig. 1, each switch element control signal and the oscillogram of coil current, and the oscillogram of the control signal that produces of a typical soft Starting Technology and coil current;
Fig. 3 is the schematic diagram of DC motor drive device one of the present invention preferred embodiment;
Fig. 4 is the oscillogram of Fig. 3 Hall detection signal, absolute value signal and standard commutation signal;
Fig. 5 is the block schematic diagram of reference voltage generating circuit one of the present invention preferred embodiment;
Fig. 5 A is the schematic diagram of pulse signal generation unit one preferred embodiment in Fig. 5;
The oscillogram of the pulse signal that the pulse signal generation unit that Fig. 5 B is Fig. 5 A produces;
Fig. 5 C is the schematic diagram of reference voltage adjustment unit one preferred embodiment in Fig. 5;
Fig. 5 D is the schematic diagram of logical circuit one of the present invention preferred embodiment;
The logical circuit that Fig. 5 E is Fig. 5 D operates the oscillogram of the signal produced;
Fig. 5 F is the schematic diagram of another preferred embodiment of logical circuit of the present invention;
The logical circuit that Fig. 5 G is Fig. 5 F operates the oscillogram of the signal produced;
Fig. 6 is the block schematic diagram of SS (soft start) control circuit embodiment one of the present invention;
Fig. 6 A is the circuit diagram of the charge pump embodiment one of Fig. 6;
Fig. 6 B is the circuit diagram of the charge pump embodiment two of Fig. 6;
Fig. 7 is the block schematic diagram of SS (soft start) control circuit embodiment two of the present invention;
Fig. 7 A is the circuit diagram of D/A conversion circuit one preferred embodiment of Fig. 7;
Fig. 8 is the sequential chart of backward current preventing circuit of the present invention and motor drive one preferred embodiment;
Fig. 9 is that the present invention controls by the end-point voltage detecting motor coil the commutation flow process that motor control circuit carries out commutation.
[main element description of reference numerals]
Switch element M1, M2, M3, M4
Hall detector 110
Change-over circuit 130
Soft switch control circuit 200
SS (soft start) control circuit 300,400
Motor control circuit 160
Motor drive circuit 180
Hysteresis comparator 120
Motor coil 170
Absolute value signal produces circuit 240
Reference voltage generating circuit 230
Comparison circuit 260
Logical circuit 280,280 '
Pulse signal generation unit 232
Reference voltage adjustment unit 234
Electric capacity 236
First comparator 237
Second comparator 238
Leading edge pulse-generating circuit 2322,2324
First flip-flop 281
Second flip-flop 282
Flip-flop 287
With door 285
Or door 286
Frequency eliminating circuit 310
Charge pump 330,330 '
Comparator 350
Shift register 432
D/A conversion circuit 434
Backward current preventing circuit 190
First electric capacity C1
Second electric capacity C2
3rd electric capacity C3
Current source CS1, CS3, Iref
Embodiment
Fig. 3 is the schematic diagram of DC motor drive device one of the present invention preferred embodiment.As shown in FIG., this DC motor drive device has Hall detector 110, soft switch control circuit 200, SS (soft start) control circuit 300, motor control circuit 160 and a motor drive circuit 180.Wherein, Hall detector 110 detects the rotary state of motor, produces Hall detection signal H+, H-of corresponding to motor phase and switching.This Hall detection signal H+, H-, after hysteresis comparator 120 is changed, produce the standard commutation signal phase corresponding to motor actual rotation state.This standard commutation signal phase produces a motor rotation signal FG after a change-over circuit 130 is changed.
Soft switch control circuit 200 detects two terminal voltage Va, the Vb at motor coil 170 two ends, and revises standard commutation signal phase to produce a correction commutation signal nphase according to these two terminal voltage Va, Vb.Motor control circuit 160 revises commutation signal nphase according to this, and the standard commutation signal phase before non-modified, generation control signal A, B, C, D control switch element M1, M2, M3, M4 of motor drive circuit 180, and then control motor commutation.
As shown in FIG., this soft switch control circuit 200 has absolute value signal generation circuit 240, reference voltage generating circuit 230, comparison circuit 260 and a logical circuit 280.Wherein, absolute value signal produces circuit 240 according to Hall detection signal H+, H-from Hall detector 110, produces an absolute value signal Vabs.
Please refer to shown in Fig. 4 simultaneously, in figure, show the association of aforementioned Hall detection signal H+, H-, absolute value signal Vabs and standard commutation signal phase.As shown in FIG., absolute value signal Vabs is equivalent to the absolute value of the difference of Hall detection signal H+ and H-.Standard commutation signal phase is then a square-wave signal, and its cycle corresponds to revolution speed.
Reference voltage generating circuit 230 receives standard commutation signal phase and two terminal voltage Va, Vb from motor coil 170 two ends.This standard commutation signal phase defines a standard commutation time point as the judgement time point judging coil current.According to terminal voltage Va, Vb, reference voltage generating circuit 230 confirms that motor coil 170 flows through electric current, to adjust the level of a reference voltage V th in standard commutation time point.Specifically, if motor coil 170 exists in standard commutation time point flow through electric current, reference voltage generating circuit 230 will the current potential of padded reference voltage V th.Therefore, the current potential of the reference voltage V th of the present embodiment on-fixed, and can because the situation flowing through electric current of motor coil 170 adjust.
Comparison circuit 260 compares absolute value signal Vabs and reference voltage V th, to produce a commutation adjustment signal AA.In the present embodiment, the positive input terminal of comparison circuit 260 receives absolute value signal Vabs, and negative input end receives reference voltage V th; Therefore, along with reference voltage V th improves, the interval that reference voltage V th is greater than absolute value signal Vabs can be strengthened gradually.That is the interval that commutation adjustment signal AA is in electronegative potential can be strengthened gradually.For the setting in response to reference voltage V th, the level of this absolute value signal Vabs need higher than a default voltage level.With regard to a preferred embodiment, absolute value signal produces circuit 240 and has a voltage level shifter (levelshift), by the absolute value of the difference of Hall detection signal H+, H-upwards padded aforementioned default voltage level, to guarantee that the level of absolute value signal Vabs is higher than this default voltage level.Substantially, this default voltage level can the bottom boundary potential of benchmark voltage Vth set.
Logical circuit 280 receives standard commutation signal phase and commutation adjusts signal AA, and according to the commutation time point that commutation adjustment signal AA adjusts standard commutation signal phase, revises commutation signal nphase to produce.Substantially, the sequential that commutation adjustment signal AA falls within the interval of electronegative potential is the trough place corresponding to absolute value signal Vabs, and the sequential at the trough place of absolute value signal Vabs corresponds to the commutation time point of standard commutation signal phase.Logical circuit 280 falls within the duration in electronegative potential interval according to commutation adjustment signal AA, and the lead time length of adjustment standard commutation signal phase, revises commutation signal nphase to produce.That is, in the present embodiment, revise commutation signal nphase and standard commutation signal phase entirety is shifted to an earlier date a time span and obtains.
In the aforementioned embodiment, soft switch control circuit 200 produces the standard commutation signal phase revising commutation signal nphase and replace script, and motor control circuit 160 revises commutation signal nphase according to this to produce control signal A, B, C, D.But, the present invention is not limited to this.In practical application, motor control circuit 160 also can receive standard commutation signal phase simultaneously and aforementioned commutation adjusts signal AA, and produces control signal A, B, C, D according to this.In addition, motor control circuit 160 can only according to the sequential of commutation adjustment signal AA adjustment member control signal A, B, C, D, or only adjust control signal A, the rising edge (rising edge) of B, C, D or the sequential of falling edge (falling edge) according to commutation adjustment signal AA, as for other parts of control signal A, B, C, D, then can produce by establishing criteria commutation signal phase.For example, motor control circuit 160 can adjust signal AA according to commutation, in advance shutdown switch element M1 and M2.
Fig. 5 is the block schematic diagram of reference voltage generating circuit 230 1 of the present invention preferred embodiment.As shown in FIG., this reference voltage generating circuit 230 has pulse signal generation unit 232, reference voltage adjustment unit 234, electric capacity 236,1 first comparator 237 and one second comparator 238.Wherein, the first comparator 237 compares a terminal voltage Va from motor coil and reference voltage Vref, to produce one first comparison signal Vanza.Second comparator 238 compares other end voltage Vb from motor coil and reference voltage Vref, to produce one second comparison signal Vanzb.The level of the reference voltage Vref that aforementioned first comparator 237 and the second comparator 238 receive can adjust according to actual demand.These two comparators 237,238 are also not limited to adopt identical reference voltage Vref.
Secondly, the present embodiment utilizes two comparators 237,238 to compare terminal voltage Va, Vb and the reference voltage Vref of motor coil 170 respectively, to produce comparison signal Vanza, Vanzb.But, the present invention is not limited to this.The present invention also directly can compare terminal voltage Va, the Vb of motor coil 170, judges whether motor coil 170 exists electric current.For example, terminal voltage Va and Vb can be inputted positive input terminal and the negative input end of a comparator by the present invention respectively, if comparator exports high potential signal, namely represent that the current potential of terminal voltage Va is higher than terminal voltage Vb, coil current flows to the right.If otherwise comparator exports low-potential signal, then represent that coil current flows left.The output signal of this comparator, namely can be used as the reference of the current potential of adjustment reference voltage V th.
Pulse signal generation unit 232 receives standard commutation signal phase, and the standard commutation time point that establishing criteria commutation signal phase defines produces commutator pulse signal P_LH, P_HL, P_LHB, P_HLB that sequential is equal to standard commutation time point.Wherein, the sequential of pulse signal P_LH corresponds to standard commutation signal phase is switched to high potential time point by electronegative potential, and pulse signal P_LHB is then the reverse signal of pulse signal.Similarly, the sequential of pulse signal P_HL corresponds to standard commutation signal phase is switched to electronegative potential time point by high potential, and pulse signal P_HLB is then the reverse signal of pulse signal P_HL.Reference voltage V th results from the high-pressure side of electric capacity 236.Reference voltage adjustment unit 234 receives comparison signal Vanza, Vanzb and commutator pulse signal P_LH, P_HL, P_LHB, P_HLB, and passes through the discharge and recharge action of electric capacity 236, reaches the object of adjustment reference voltage V th.
Fig. 5 A is the schematic diagram of pulse signal generation unit 232 1 preferred embodiment in Fig. 5.Fig. 5 B is then the oscillogram of the pulse signal that this pulse signal generation unit 232 of display produces.As shown in FIG., standard commutation signal phase inputs a leading edge pulse-generating circuit 2322, to produce one first leading edge pulse signal P_LH, is switched to the sequential of high potential corresponding to standard commutation signal phase by electronegative potential.This standard commutation signal phase inputs another leading edge pulse-generating circuit 2324 after being converted to reverse standard commutation signal phaseb by a reverser simultaneously, to produce one second leading edge pulse signal P_HL.This second leading edge pulse signal P_HL corresponds to standard commutation signal phase is switched to electronegative potential sequential by high potential.Aforementioned first leading edge pulse signal P_LH is again by reverser conversion generation 1 a 3rd leading edge pulse signal P_LHB; Similarly, aforementioned second leading edge pulse signal P_HL is again by reverser conversion generation 1 a 4th leading edge pulse signal P_HLB.According to this, four different pulse signal P_LH, P_HL, P_LHB, P_HLB can be produced by establishing criteria commutation signal phase.
Previous embodiment utilizes leading edge pulse-generating circuit 2322,2324 to produce pulse signal P_LH, P_HL, P_LHB, P_HLB, and but, the present invention does not limit therewith.This pulse signal generation unit 232 also can utilize trailing edge pulse-generating circuit to produce pulse signal P_LH, P_HL, P_LHB, P_HLB, or mixing frontier and rear pulse-generating circuit, produces pulse signal P_LH, P_HL, P_LHB, P_HLB.
Fig. 5 C is the schematic diagram of reference voltage adjustment unit 234 1 preferred embodiment in Fig. 5.As shown in FIG., this reference voltage adjustment unit 234 has two charge paths and two discharge paths.Wherein, the first charge path has two switch elements, controlled by the first comparison signal Vanza and pulse signal P_LHB respectively.Second charge path has two switch elements, controlled by the second comparison signal Vanzb and pulse signal P_HLB respectively.First discharge path has two switch elements, controlled by the first comparison signal Vanza and pulse signal P_LH respectively.Second discharge path has two switch elements, controlled by the second comparison signal Vanzb and pulse signal P_HL respectively.
When the first comparison signal Vanza and pulse signal P_LHB is electronegative potential, the first charge path can be switched on.When the second comparison signal Vanzb and pulse signal P_HLB is electronegative potential, the second charge path can be switched on.When the first comparison signal Vanza and pulse signal P_LH is high potential, the first discharge path can be switched on.When the second comparison signal Vanzb and pulse signal P_HL is high potential, the second discharge path can be switched on.
According to this, when the first comparison signal Vanza is electronegative potential (namely the terminal voltage Va of motor coil is greater than reference voltage Vref), and pulse signal P_LHB is when being electronegative potential, first charge path is conducting state, current source CS1 is charged to electric capacity 236 by the first charge path, to promote the current potential of reference voltage V th.At the same time, the first discharge path can be interrupted.In addition, referring to Fig. 5 B, when pulse signal P_LHB is electronegative potential, pulse signal P_LH is high potential, and pulse signal P_HL is electronegative potential, and pulse signal P_HLB is high potential.Therefore, no matter being the second charge path or the second discharge path, is all be in interrupt status.
Similarly, when the second comparison signal Vanzb is electronegative potential (namely the terminal voltage Vb of motor coil is greater than reference voltage Vref), and pulse signal P_HLB is when being electronegative potential, second charge path is conducting state, current source CS1 is charged to electric capacity 236 by the second charge path, to promote the current potential of reference voltage V th.At the same time, the first charge path, the first discharge path and the second discharge path are then be in interrupt status.
Otherwise when the first comparison signal Vanza is high potential and pulse signal P_LH is high potential, the first discharge path is conducting state, and electric capacity 236 is discharged by the first discharge path, to downgrade the current potential of reference voltage V th.As for the second discharge path, the first charge path and the second charge path, be then be in interrupt status.Similarly, when the second comparison signal Vanzb is high potential and pulse signal P_HL is high potential, the second discharge path is conducting state, and electric capacity 236 is discharged by the second discharge path, to downgrade the current potential of reference voltage V th.As for the first discharge path, the first charge path and the second charge path, be then be in interrupt status.
To sum up state, switched to the standard commutation time point of high potential by electronegative potential corresponding to standard commutation signal, the i.e. time point of pulses generation in pulse signal P_LH and P_LHB, if the first comparison signal Vanza is electronegative potential, namely the terminal voltage Va of motor coil is higher than reference voltage Vref, and the current potential of reference voltage V th will improve, otherwise, if the first comparison signal Vanza is high potential, the current potential of reference voltage V th will reduce.Similarly, switched to the standard commutation time point of electronegative potential by high potential corresponding to standard commutation signal, the i.e. time point of pulses generation in pulse signal P_HL and P_HLB, if the second comparison signal Vanzb is electronegative potential, namely the terminal voltage Vb of motor coil is higher than reference voltage Vref, and the current potential of reference voltage V th will improve, otherwise, if the second comparison signal Vanzb is high potential, the current potential of reference voltage V th will reduce.
Whether previous embodiment is electronegative potential with the first comparison signal Vanza and pulse signal P_LHB, determines whether conducting first charge path.But, the present invention is not limited to this.By changing the type of switch element used, also can set with the first comparison signal Vanza as electronegative potential and pulse signal P_LH as high potential time, conducting first charge path.Secondly, also can set with the first comparison signal Vanza as high potential is to represent that the terminal voltage Va of motor coil is higher than reference voltage Vref, and be high potential with the first comparison signal Vanza and pulse signal P_LH, be set as the turn-on condition of the first charge path.As for each switch element on the second charge path, the first discharge path and the second discharge path, also similar adjustment can be done.In addition, control the whether conducting of the first charge path and the first discharge path if selected with pulse signal P_LH, and control the whether conducting of the second charge path and the second discharge path with pulse signal P_HL.Pulse signal generation unit 232 does not just need to produce pulse signal P_LHB and P_HLB in addition.
In addition, on each charge path of the reference voltage adjustment unit 234 of the present embodiment and discharge path, there are two switch elements respectively and control.But, the present invention does not limit therewith.Control the whether conducting of the first charge path and the first discharge path if selected with same pulse signal P_LH, then, in the first charge path and the first discharge path, the switch element that pulse signal P_LH controls thus can be shared.Similarly, the switch element controlled by pulse signal in the second charge path and the second discharge path also can be shared.
The reference voltage generating circuit 230 of the present embodiment is two terminal voltage Va, Vb of detecting motor coil 170, to adjust the current potential of reference voltage V th.But, the present invention does not limit therewith.This reference voltage generating circuit 230 also only can utilize a terminal voltage (for terminal voltage Va) of motor coil 170, adjusts the current potential of reference voltage V th.In the case, pulse signal generation unit 232 only needs to produce pulse signal P_LH, P_LHB, and reference voltage adjustment unit 234 only needs to set up the first charge path and the first discharge path, to adjust the current potential of reference voltage V th.
As aforementioned, terminal voltage Va, Vb due to soft switch control circuit 200 establishing criteria commutation signal phase of the present invention and motor coil adjust the commutation time point of motor drive circuit 180, thus in response to different coil currents, rotating speed and other Parameters variation, suitable commutation time point can be adjusted.Therefore, the problem that the adjustment traditional motor soft-switching process can being avoided easily to produce is excessive or adjustment is not enough.
Fig. 5 D is the schematic diagram of logical circuit 280 1 of the present invention preferred embodiment.Fig. 5 E is then the oscillogram that this logical circuit 280 operates the signal produced.As shown in FIG., this logical circuit 280 mainly by one first flip-flop (D flip flop) 281,1 second flip-flop 282, one and door (AND gate) 285 and one or door (OR gate) 286 formed.Wherein, first flip-flop 281 and the second flip-flop 282 receive commutation and adjust the reverse signal (reverse commutation adjusts signal AAb) of signal AA as clock signal (clock signal), first flip-flop 281 is simultaneously using standard commutation signal phase as replacement (reset) signal, and the second flip-flop 282 is using the reverse signal of standard commutation signal phase (reverse standard commutation signal phaseb) as replacement (reset) signal.The output signal GG ' of the inverse output terminal of the first flip-flop 281 carries out Logic judgment by one with door 285 with standard commutation signal phase, the output signal KK of this and the output signal of door 285 and the forward output of the second flip-flop 282 carries out Logic judgment by one or door 286 again, revises commutation signal nphase to export.
When reverse commutation adjustment signal AAb is switched to high potential by electronegative potential (in as figure time point t1), reverse standard commutation signal phaseb (not illustrating) is high potential, now, the output signal KK of the forward output of the second flip-flop 282 switches to high potential by electronegative potential.Subsequently, when reverse standard commutation signal phaseb is switched to electronegative potential by high potential (in as figure time point t2), the second flip-flop 282 is reset, and stops the output signal KK producing high potential.Subsequently, when reverse commutation adjustment signal AAb switches to high potential by electronegative potential again (in as figure time point t3), because reverse standard commutation signal phaseb still maintains electronegative potential, therefore, the output signal KK of the forward output of the second flip-flop 282 still maintains electronegative potential.But, at time point t3, when reverse commutation adjustment signal AAb switches to high potential by electronegative potential, because standard commutation signal phase is high potential, the output signal GG ' of the inverse output terminal of the first flip-flop 281 then can switch to electronegative potential by high potential.Subsequently, when standard commutation signal phase switches to electronegative potential (in as figure time point t4) by high potential, the first flip-flop 281 is reset, and the output signal GG ' of its inverse output terminal switches to high potential by electronegative potential.Next, when reverse commutation adjustment signal AAb switches to high potential by electronegative potential once again, because standard commutation signal phase maintains electronegative potential, therefore, the output signal GG ' of the inverse output terminal of the first flip-flop 281 still maintains high potential.
Time point t1 in the drawings, when reverse commutation adjustment signal AAb switches to high potential by electronegative potential, the forward output of the second flip-flop 282 exports the signal KK of high potential.Hereat, or door 286 can produce the correction commutation signal nphase of high potential.Subsequently, time point t2 in the drawings, when standard commutation signal phase switches to high potential by electronegative potential, the inverse output terminal of the first flip-flop 281 produces the output signal GG ' of high potential.Now, although the output signal KK of the forward output of the second flip-flop 282 switches to electronegative potential by high potential, but, due to the output signal of high potential can be produced with door 285, therefore, or the correction commutation signal nphase that exports of door 286 still maintain high potential.Next, at time point t3, when reverse commutation adjustment signal AAb switches to high potential by electronegative potential again, the inverse output terminal of the first flip-flop 281 can produce the output signal GG ' of electronegative potential, therefore, can produce the output signal of electronegative potential with door 285, or the correction commutation signal nphase that door 286 exports then can switch to electronegative potential by high potential.
Therefore this logical circuit 280 determines to revise the lead time length of commutation signal nphase relative to standard commutation signal phase according to commutation adjustment signal AA.That is the time span that commutation adjustment signal AA falls within electronegative potential is longer, and the lead time length revising commutation signal nphase is longer.In addition, although the time point revising the rising edge of commutation signal nphase shifts to an earlier date to some extent compared to standard commutation signal phase, revising commutation signal nphase does not have what to change in the duration of high potential compared to standard commutation signal phase.
Fig. 5 F is the schematic diagram of another preferred embodiment of logical circuit 280 ' of the present invention.Fig. 5 G is then the oscillogram that this logical circuit 280 ' operates the signal produced.As shown in FIG., this logical circuit 280 ' has a flip-flop 287.This flip-flop 287 receives the reverse signal (reverse commutation adjusts signal AAb) of commutation adjustment signal AA as clock signal, and the reverse signal (reverse standard commutation signal phaseb) simultaneously receiving standard commutation signal phase inputs as data.The output signal of the forward output of this flip-flop 287 is revises commutation signal nphase.
As depicted in fig. 5g, time point t5 in the drawings, when reverse commutation adjustment signal AAb switches to high potential by electronegative potential, reverse standard commutation signal phaseb is high potential, and therefore, the forward output of flip-flop 287 exports the correction commutation signal nphase of high potential.But, time point t6 in the drawings, when reverse commutation adjustment signal AAb rises to high potential by electronegative potential once again, reverse standard commutation signal phaseb is then electronegative potential.Now.The correction commutation signal nphase that flip-flop 287 exports can switch to electronegative potential by high potential originally.
Fig. 6 is the block schematic diagram of SS (soft start) control circuit 300 embodiment one of the present invention.As shown in FIG., this SS (soft start) control circuit 300 has frequency eliminating circuit 310, charge pump 330 and a comparator 350.Wherein, frequency eliminating circuit 310 receives a motor rotation signal FG, and produces a frequency signal CLK according to this.Charge pump 330 receiving frequency signals CLK, to produce a ramp signal Vramp.Comparator 350 receives the triangular signal Tri that this ramp signal Vramp and has a default frequency, to produce a PM signal Vpwm.Motor control circuit 160 received pulse modulating signal Vpwm, and the ON time of each switch element M1, M2, M3, M4 in motor drive circuit 180 is controlled according to this PM signal Vpwm, to adjust the charging interval of motor coil 170, and then governor motor drive circuit 180 is for the actuating force of motor, to reach the object of soft start.
Fig. 6 A is the circuit diagram of charge pump 330 embodiment one of Fig. 6.As shown in FIG., this charge pump 330 has one first electric capacity C1, one second electric capacity C2, one first switch element SW1, second switch element SW2 and a 3rd switch element SW3.Wherein, the capacitance of the first electric capacity C1 is greater than the capacitance of the second electric capacity C2.The on high-tension side output signal of the first electric capacity C1 is ramp signal Vramp.Whether first switch element SW1 conducting is controlled by frequency signal CLK.Second switch element SW2 conducting with otherwise be controlled by the reverse signal CLKB of frequency signal CLK.3rd switch element SW3 conducting with otherwise be controlled by an initialize signal RST.
When motor system starts, produce a pulse signal immediately and start this SS (soft start) control circuit 300 as initialize signal RST.Now, the 3rd switch element SW3 is switched on, and a starting voltage INI is stored to the initial value of the first electric capacity C1 as ramp signal Vramp.Subsequently, when frequency signal CLK is electronegative potential, switch element SW2 conducting, power supply AVDD charges to the second electric capacity C2.And when frequency signal CLK changes high potential into, switch element SW2 turns off, power supply AVDD stops charging to the second electric capacity C2; Meanwhile, switch element SW1 conducting, electric charge stored in the second electric capacity C2 then can charge to the first electric capacity C1.Capacitance due to the first electric capacity C1 is greater than the second electric capacity C2, and along with the alternately change of frequency signal CLK between high electronegative potential, the on high-tension side current potential of the first electric capacity C1 can be padded gradually, and produce ramp signal Vramp.
As aforementioned, due to the existence of frequency eliminating circuit 310, between the frequency of frequency signal CLK and motor rotation signal FG, there is a default scale and close.And alternately changing along with frequency signal CLK, the current potential of ramp signal Vramp can be padded gradually, and then the work period of PM signal Vpwm is increased gradually.Finally, the current potential of ramp signal Vramp can exceed the spike potential of triangular signal Tri.Now, the work period of the PM signal Vpwm that comparator 350 exports will reach 100%, and terminates soft start control cycle.According to this, SS (soft start) control circuit 300 of the present invention along with the increase of the revolution number of turns, can progressively increase the work period of PM signal Vpwm, to reach the object of soft start.
In the present embodiment, frequency eliminating circuit 310 receives motor rotation signal FG, and to produce a frequency signal CLK, in control charge pump 330, power supply AVDD is for the charge frequency of electric capacity C2.But, the present invention is not limited to this.Aforementioned motors turn signal FG can also replace by standard commutation signal phase or correction commutation signal nphase.In addition, if the frequency proportions of motor rotation signal FG and frequency signal CLK is set as 1: 1, the use of frequency eliminating circuit 310 can also be omitted.
Fig. 6 B is the circuit diagram of charge pump 330 ' embodiment two of the present invention.As shown in FIG., this charge pump 330 ' has a current source CS3, one the 4th switch element SW4, one the 5th switch element SW5 and the 3rd electric capacity C3.The on high-tension side output signal of the 3rd electric capacity C3 is ramp signal Vramp.The conducting state of the 4th switch element SW4 is then controlled by frequency signal CLK.The conducting state of the 5th switch element SW5 is then controlled by initialize signal RST, its concept and previous embodiment similar, do not repeat them here.When frequency signal CLK is high potential, the 4th switch element SW4 conducting, current source CS3 charges to the 3rd electric capacity C3, to improve its on high-tension side current potential.When frequency signal CLK is electronegative potential, the 4th switch element SW4 turns off, and current source CS3 then can stop charging to the 3rd electric capacity C3.According to this, along with the alternately change of frequency signal CLK between high electronegative potential, the current potential of ramp signal Vramp can be padded gradually.
Fig. 7 is the block schematic diagram of SS (soft start) control circuit 400 embodiment two of the present invention.As shown in FIG., the Main Differences of the embodiment of the present embodiment and earlier figures 6 is that the present embodiment replaces the charge pump 330 in Fig. 6 with a shift register 432 and a D/A conversion circuit 434.As shown in FIG., shift register 432 produces multiple digital signal b0, b1, b2...bn according to frequency signal CLK.Each digital signal b0, b1, b2...bn change between 1 and 0.D/A conversion circuit 434 produces a reference potential signal Vref1 according to digital signal b0, b1, b2...bn.
Fig. 7 A is the circuit diagram of D/A conversion circuit 434 1 preferred embodiment of Fig. 7.As shown in FIG., this D/A conversion circuit 434 has a current source Iref, multiple resistance R (0), R (1) ... R (n), Rx and multiple switch element SW (0), SW (1) ... SW (n).These resistance R (0), R (1) ... R (n), Rx connect bunchiness.One end of this resistance string is connected to constant current source Iref, other end ground connection.At least part of resistance R (0), R (1) ... R (n) is a switch element SW (0) in parallel, SW (1) respectively ... SW (n).These switch elements SW (0), SW (1) ... SW (n) controls its conducting state according to foregoing digital signals b0, b1, b2...bn.The junctional potential of current source Iref and resistance string is reference potential signal Vref1.
As shown in FIG., the current potential height of reference potential signal Vref1 can be subject to each switch element SW (0), SW (1) ... the impact of the conducting state of SW (n).Furthermore, digital signal b0, b1, b2...bn control switch element SW (0), SW (1) ... during SW (n) conducting, electric current will flow through this switch element SW (0), SW (1) ... the current path that SW (n) is formed, and can not flow through corresponding resistance R (0), R (1) ... R (n).Switch element SW (0), SW (1) ... the quantity of SW (n) conducting is more, the resistance R (0) that electric current flows through, R (1) ... R (n) is fewer, the current potential of reference potential signal Vref1 is also lower.According to this, by digital signal b0, b1, b2...bn control switch element SW (0), SW (1) ... the conducting number of SW (n), i.e. the current potential height of the reference potential signal Vref1 that exports of this D/A conversion circuit 434 of adjustable.
In the present embodiment, shift register 432 can along with the alternately change of frequency signal, gradually increase export high potential digital signal b0, b1, b2...bn quantity, to adjust switch element SW (0), SW (1) ... the conducting number of SW (n).For example, when frequency signal CLK display revolution one is enclosed, shift register 432 only exports the digital signal b0 of high potential, and to interrupt its corresponding switch element SW (0), all the other digital signal b1, b2...bn maintain the state of electronegative potential.Next, when frequency signal CLK display motor rotates a circle again, shift register 432, except exporting the digital signal b0 of high potential, increases again the digital signal b1 exporting high potential, again to interrupt its corresponding switch element SW (1).Continue according to this, the current potential of reference potential signal Vref1 can be made to raise gradually along with the rotation number of turns of motor.
In motor drive shown in Fig. 3, except soft switch control circuit 200, the present embodiment also has the issuable backward current of conduction phase handoff procedure that a backward current preventing circuit 190 prevents motor drive circuit 180.
As shown in FIG., motor control circuit 160 controls revolution by motor drive circuit 180.This motor drive circuit 180 has four switch elements M1, M2, M3, M4, forms bridge circuit (H-bridge) with CD-ROM drive motor.Its running can divide into two different conduction phase (phase), is the first conduction phase (phase I) when switch element M1 and M4 conducting, is the second conduction phase (phase II) when switch element M2 and M3 conducting.
When first conduction phase is switched to the second conduction phase, because the inductive of motor coil 170, the electric current of switch element M2, M3 conducting moment still remains on saturation current value, and toward the right flowing in figure, thus can produce backward current to recharge to power end Vm, and power end Vm voltage rise may be made to exceed withstand voltage and cause circuit burnout.In order to head it off, DC motor drive device of the present invention has backward current preventing circuit 190, by detecting terminal voltage Va, the Vb at motor coil 170 two ends, and according to the difference of these two terminal voltage Va and Vb, judge the conducting time point of switch element M1, M2, M3, M4.
Fig. 8 is the timing waveform of each signal of backward current preventing circuit 190 of the present invention and motor drive circuit 180.In figure, control signal A, B, C, D represent the gate control signal of each switch element M1, M2, M3, M4 respectively, coil current i (motor) represents the coil current of motor, and current i (M1), i (M2), i (M3), i (M4) represent the electric current flowing through each switch element M1, M2, M3, M4 respectively.Terminal voltage Va represents the voltage of the contact VA of switch element M1 and M3, and terminal voltage Vb represents the voltage of the contact VB of switch element M2 and M4, and terminal voltage Va and terminal voltage Vb also represents the terminal voltage at motor two ends.
Fig. 9 is then to carry out the schematic flow sheet of commutation by the ON time of this backward current preventing circuit 190 control switch element M1, M2, M3, M4.Please refer to shown in Fig. 8, when the first conduction phase, control signal A is electronegative potential, and control signal D is high potential simultaneously, respectively control switch element M1 and M4 conducting.Now, coil current i (motor) flows (this sense of current is just defined as) to the right by the left side in figure.
During the first conduction phase at the end, control signal A switches to high potential closing switch element M1, and control signal C switches to high potential turn-on switch component M3, and enters interdischarge interval.Now, power end Vm stops coil power supply, but, due to the inductance characteristic of motor coil 170, coil current i (motor) continues to flow to switch element M4, and makes the terminal voltage Va of the left end point VA of motor coil 170 be negative, and the terminal voltage Vb of right endpoint VB is just.Therefore, the voltage difference (Va-Vb) at motor coil 170 two ends is negative, and the voltage difference (Va-Vb) at motor coil 170 two ends can be close toward zero along with the discharging action of motor coil 170.
When the absolute value of voltage difference (Va-Vb) is less than one first default reference voltage, backward current preventing circuit 190 produces a discharge control signal Discharge.After motor control circuit 160 receives this discharge control signal Discharge, switched to by control signal B electronegative potential with turn-on switch component M2, and switched to by control signal D electronegative potential with closing switch element M4, to switch to the second conduction phase.
During the second conduction phase at the end, control signal B switches to high potential closing switch element M2, and control signal D switches to high potential turn-on switch component M4, and enters interdischarge interval.Now, power end Vm stops coil power supply, but, due to the inductance characteristic of motor coil 170, coil current i (motor) continues to flow to switch element M3, and makes the terminal voltage Va of the left end point VA of motor coil 170 be that just the terminal voltage Va of right endpoint VB is negative.Therefore, the voltage difference (Va-Vb) at motor coil 170 two ends is just, and the voltage difference (Va-Vb) at motor coil 170 two ends can be close toward zero along with the discharging action of motor coil 170.
When the absolute value of voltage difference (Va-Vb) is less than one second default reference voltage, backward current preventing circuit 190 produces a discharge control signal Discharge.After motor control circuit 160 receives this discharge control signal Discharge, switched to by control signal A electronegative potential with turn-on switch component M1, and switched to by control signal C electronegative potential with closing switch element M3, to switch to the first conduction phase.
In the aforementioned embodiment, be switched in the process of interdischarge interval by during the first conduction phase, the closedown of switch element M1 and the conducting of switch element M3 are carried out simultaneously.But, short circuit is produced, as shown in Figure 9, with regard to a preferred embodiment, during the first conduction phase and during a dead band can being inserted between interdischarge interval (dead time) in order to avoid switch element M1 and switch element M3 conducting simultaneously.That is before turn-on switch component M3, first closing switch element M1.Similarly, short circuit is produced, during a dead band can being inserted between during interdischarge interval and the second conduction phase (dead time) in order to avoid switch element M4 and switch element M2 conducting simultaneously.That is before turn-on switch component M2, first closing switch element M4.
Secondly, with regard to a preferred embodiment, backward current preventing circuit 190 of the present invention can be a comparator with two default reference voltages.Terminal voltage Va, the Vb of this comparator detecting motor coil 170 two-end-point VA and VB, and when the absolute value (voltage difference (Va-Vb) for negative time) of voltage difference (Va-Vb) is less than one first default reference voltage or when voltage difference (Va-Vb) (voltage difference (Va-Vb) is timing) is less than one second default reference voltage, produce discharge control signal Discharge, notice motor control circuit 160 carries out commutation action.But, the present invention is not limited to this, and this comparator also only can have a default reference voltage.When the absolute value (no matter voltage difference (Va-Vb) is just or is negative) of voltage difference (Va-Vb) is less than a default reference voltage, namely produce discharge control signal Discharge.
But; the foregoing is only preferred embodiment of the present invention; when not limiting protection range of the invention process with this, i.e. all simple equivalence changes of doing according to the claims in the present invention and description of the invention content and amendment, all still belongs in protection range that patent of the present invention contains.Any embodiment of the present invention or claim can not reach whole object disclosed by the present invention or advantage or feature in addition.In addition, specification digest part and denomination of invention are only used to the use of auxiliary patent document retrieval, are not used for limiting the scope of the invention.
Claims (13)
1. a soft switch control circuit for d.c. motor, by adjusting the standard commutation time point that a standard commutation signal defines, control the commutation action of a d.c. motor, it is characterized in that, soft switch control circuit comprises:
One absolute value signal produces circuit, according to a pair Hall detection signal from this d.c. motor, produces an absolute value signal;
One reference voltage generating circuit, receives this standard commutation signal and at least one terminal voltage from a coil of this d.c. motor, and judges that this coil is in the coil current of this standard commutation time point, to adjust the level of a reference voltage according to this terminal voltage; And
One comparison circuit, compares this absolute value signal and this reference voltage, adjusts this standard commutation time point to produce a commutation adjustment signal.
2. the soft switch control circuit of d.c. motor as claimed in claim 1, is characterized in that, according to this terminal voltage, this reference voltage generating circuit judges that this coil is in this standard commutation time point whether coil current, to adjust the level of this reference voltage.
3. the soft switch control circuit of d.c. motor as claimed in claim 1, is characterized in that, this absolute value signal produces circuit and has a voltage level shifter, to guarantee the bottom boundary potential of the level of this absolute value signal higher than this reference voltage.
4. the soft switch control circuit of d.c. motor as claimed in claim 1, is characterized in that, more comprise a logical circuit, adjusts this standard commutation signal, to produce a correction commutation signal in order to control the commutation action of this d.c. motor according to this commutation adjustment signal.
5. the soft switch control circuit of d.c. motor as claimed in claim 4, is characterized in that, the sequential of this standard commutation signal entirety, according to this commutation adjustment signal, is shifted to an earlier date a lead time, to produce this correction commutation signal by this logical circuit.
6. the soft switch control circuit of d.c. motor as claimed in claim 1, is characterized in that, this commutation adjustment signal drives in order to adjustment in a bridge circuit of this d.c. motor, the conducting time point of at least one control switch.
7. the soft switch control circuit of d.c. motor as claimed in claim 1, it is characterized in that, this reference voltage generating circuit comprises:
One pulse signal generation unit, receives this standard commutation signal, to produce at least one commutator pulse signal;
One electric capacity, in order to produce this reference voltage; And
One reference voltage adjustment unit, in the adjustment time point that this commutator pulse signal defines, carries out discharge and recharge behavior according to this terminal voltage to this electric capacity, to adjust the level of this reference voltage.
8. the soft switch control circuit of d.c. motor as claimed in claim 7, it is characterized in that, this reference voltage generating circuit more comprises a comparator, in order to compare this terminal voltage and a reference voltage, to produce a comparison signal, this reference voltage adjustment unit carries out discharge and recharge according to this comparison signal to this electric capacity.
9. the soft switch control circuit of d.c. motor as claimed in claim 8, it is characterized in that, this reference voltage adjustment unit has a charge path and a discharge path, respectively in order to carry out discharge and recharge to this electric capacity, the conducting state of this charge path and this discharge path is by this comparison signal and this corresponding commutator pulse signal co-controlling.
10. the soft switch control circuit of d.c. motor as claimed in claim 7, it is characterized in that, this pulse signal generation unit comprises a leading edge pulse-generating circuit, this leading edge pulse-generating circuit produces one first commutator pulse signal according to this standard commutation signal, and produces one second commutator pulse signal according to a reverse signal of this standard commutation signal.
The soft switch control circuit of 11. d.c. motors as claimed in claim 7, is characterized in that, this reference voltage generating circuit receives a first end voltage and one second terminal voltage at these coil two ends, and this reference voltage generating circuit more comprises:
One first comparator, compares this first end voltage and one first reference voltage, to produce one first control signal; And
One second comparator, compares this second terminal voltage and one second reference voltage, to produce one second control signal;
Wherein, this reference voltage adjustment unit carries out discharge and recharge according to this first control signal and this second control signal to this electric capacity.
The soft switch control circuit of 12. d.c. motors as claimed in claim 11, it is characterized in that, this first reference voltage is identical with the current potential of this second reference voltage.
The soft switch control circuit of 13. d.c. motors as claimed in claim 1, is characterized in that, this Hall detection signal, after a hysteresis comparator conversion, produces this standard commutation signal.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201110227360.1A CN102931893B (en) | 2011-08-09 | 2011-08-09 | Soft switch control circuit for direct current motor |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201110227360.1A CN102931893B (en) | 2011-08-09 | 2011-08-09 | Soft switch control circuit for direct current motor |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN102931893A CN102931893A (en) | 2013-02-13 |
| CN102931893B true CN102931893B (en) | 2015-03-11 |
Family
ID=47646625
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN201110227360.1A Active CN102931893B (en) | 2011-08-09 | 2011-08-09 | Soft switch control circuit for direct current motor |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN102931893B (en) |
Families Citing this family (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| WO2018119238A1 (en) * | 2016-12-21 | 2018-06-28 | Dana Automotive Systems Group, Llc | Hall-effect sensor signal offset correction in phase commutation |
| CN107769629B (en) * | 2017-12-07 | 2020-05-22 | 绍兴光大芯业微电子有限公司 | Steady flow driving system and method of single-coil fan motor |
| TWI692195B (en) * | 2019-09-11 | 2020-04-21 | 茂達電子股份有限公司 | Motor driving device and method thereof |
| TWI748768B (en) * | 2020-11-27 | 2021-12-01 | 威剛科技股份有限公司 | Motor driving system |
Family Cites Families (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| KR100258434B1 (en) * | 1996-09-02 | 2000-06-01 | 윤종용 | Driving dircuit for a 3-phase bldc motor using 1-hall signal |
| JP3711102B2 (en) * | 2002-10-30 | 2005-10-26 | 三洋電機株式会社 | Single-phase motor driving device, single-phase motor driving method, and integrated circuit |
| JP2007006563A (en) * | 2005-06-22 | 2007-01-11 | Renesas Technology Corp | Single-phase motor driving circuit |
| CN101800511B (en) * | 2009-02-11 | 2012-07-25 | 晶致半导体股份有限公司 | Single-phase motor-driving device with energy saving module |
| TWI394362B (en) * | 2009-09-11 | 2013-04-21 | Anpec Electronics Corp | Method of driving dc motor and related circuit for avoiding reverse current |
| JP2011151997A (en) * | 2010-01-22 | 2011-08-04 | Sanyo Electric Co Ltd | Motor drive circuit |
-
2011
- 2011-08-09 CN CN201110227360.1A patent/CN102931893B/en active Active
Also Published As
| Publication number | Publication date |
|---|---|
| CN102931893A (en) | 2013-02-13 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN105453412B (en) | For the controller of brushless motor | |
| US5294877A (en) | Circuit and method for detecting deceleration rates of a polyphase DC motor | |
| CN101753074B (en) | Control circuit for a brushless DC motor and method therefor | |
| US5929577A (en) | Brushless DC motor controller | |
| CN101790838A (en) | Method for driving an electrical converter and associated apparatus | |
| CN102931893B (en) | Soft switch control circuit for direct current motor | |
| KR100416865B1 (en) | Brushless motor drive circuit having low noise and high efficiency | |
| US20130043818A1 (en) | Soft-switching control circuit for dc motor | |
| US20120326643A1 (en) | Position Corrected Pulse Width Modulation for Brushless Direct Current Motors | |
| TWI410035B (en) | Electric power conversion apparatus, and triangular wave voltage generating circuit | |
| US20020048180A1 (en) | Interleaved power converters incorporating bang-bang control | |
| CN100574085C (en) | The single-phase motor drive unit | |
| EP1433248B1 (en) | Stepper motor controller | |
| CN101599707A (en) | Automobile battery-charging generator and rectifying device thereof | |
| CN105474530A (en) | Method of controlling brushless permanent-magnet motor | |
| TW201210186A (en) | A Pulse Amplitude Modulation method for the brushless DC motor | |
| CN102088266A (en) | Brushless motor stepless speed change controller based on FPGA (Field Programmable Gate Array) digitization control | |
| CN102377381A (en) | Pulse and amplitude adjusting method for direct-current brushless motor | |
| TWI435532B (en) | Soft-switching control citcuit for dc motor | |
| JP2015527050A (en) | Electronic circuit and method for automatically adjusting the phase of a drive signal applied to an electric motor according to zero current detected in the winding of the electric motor and for detecting zero current | |
| CN104009627B (en) | Multiphase switching controller | |
| TWI749948B (en) | Motor controller | |
| US20220166362A1 (en) | Motor controller, motor system and method for controlling motor | |
| CN201904749U (en) | FPGA (field programmable gate array) digital control based variable speed controller for brushless motor | |
| CN212086064U (en) | Current mode charge pump device |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| C06 | Publication | ||
| PB01 | Publication | ||
| C10 | Entry into substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| C14 | Grant of patent or utility model | ||
| GR01 | Patent grant |