Summary of the invention
The technical problem that (one) will solve
The technical problem to be solved in the present invention is: how a kind of MIMO detection method and device are provided, with according to actual channel quality and communication system conditions of demand flexible complexity and detection performance, realize the detection performance of varying level with the detection complexity of different brackets.
(2) technical scheme
For solving the problems of the technologies described above, the invention provides a kind of MIMO detection method, it comprises step:
A: r carries out linearity test to received signal, obtains the first estimated value of corresponding transmitted signal
B: according to predetermined iterations to received signal r carry out non-linear detection, obtain the estimated value of counterpart transmitted signal
C: according to described the first estimated value
Estimated value with described part transmitted signal
The residue transmitted signal that does not obtain estimated value among the described step B is carried out the bit inversion operation, obtain the estimated value of corresponding residue transmitted signal
D: the estimated value that merges described part transmitted signal
Estimated value with described residue transmitted signal
Obtain the second estimated value of corresponding transmitted signal
E: according to described the first estimated value
With described the second estimated value
Obtain vector space R, r carries out Maximum Likelihood Detection to received signal in described vector space R, obtains distance and receives the nearest signal vector of signal r as the final estimated value of corresponding transmitted signal
Wherein, in the described steps A, described the first estimated value
Computing formula as follows:
Wherein, g is filtering matrix.
Wherein, the computing formula of described filtering matrix g is as follows:
G=(H
HH)
-1H
HPerhaps,
g=(H
HH+σ
2I)
-1H
H;
Wherein, H represents channel matrix, σ
2The expression noise power.
Wherein, among the described step B, according to predetermined iterations to received signal r to carry out the detailed process of non-linear detection as follows:
Initialization: i=1, G
1=F (H);
Iterative process:
i=i+1;
Wherein, i is less than or equal to predetermined iterations N
Iterr
iReception signal when representing the i time iteration, r
1Equal initial described reception signal r; G
iThe expression filtering matrix, F (H) and
Expression calculation of filtered matrix G
iFunction, H represents channel matrix; (G
i)
jExpression filtering matrix G
iJ capable, s
iRepresent filtering matrix G in the i time iteration
iThe capable subscript of 2-Norm minimum in the row vector;
Expression according to planisphere to detection signal
Carry out hard decision,
S in the expression transmitted signal
iThe estimated value of individual symbol;
The s of expression channel matrix H
iRow turn order;
The s of expression signaling channel matrix H
1, s
2..., s
iClassify 0 matrix that obtains as.
Wherein, adopt zero forcing algorithm or least-mean-square error algorithm calculation of filtered matrix G
i
Wherein, described predetermined iterations is according to the signal to noise ratio setting of communication system.
Wherein, described step C specifically comprises step:
C1: determine every kind of probability of happening that variation mode is corresponding according to the signal to noise ratio of communication system;
C2: according to the estimated value of described part transmitted signal
Do not obtained the location index of the residue transmitted signal of estimated value;
C3: according to every kind of probability of happening that variation mode is corresponding, the transmitted signal that described location index is corresponding is carried out the bit inversion operation, obtain the estimated value of corresponding residue transmitted signal
Wherein, in the described step e, the formula of Maximum Likelihood Detection is as follows:
Wherein, H represents channel matrix; X is all possible vector in the vector space R;
The final estimated value that represents corresponding transmitted signal.
The present invention also provides a kind of MIMO checkout gear, and described device comprises:
The linearity test unit is used for to received signal that r carries out linearity test, obtains the first estimated value of corresponding transmitted signal
Non-linear detection unit, be used for according to predetermined iterations to received signal r carry out non-linear detection, obtain the estimated value of counterpart transmitted signal
Detecting unit is estimated in variation, is used for according to every kind of probability of happening that variation mode is corresponding, according to described the first estimated value
Estimated value with described part transmitted signal
The residue transmitted signal that does not obtain estimated value among the described step B is carried out the bit inversion operation, obtain the estimated value of corresponding residue transmitted signal
Merge cells is for the estimated value that merges described part transmitted signal
Estimated value with described residue transmitted signal
Obtain the second estimated value of corresponding transmitted signal
The Maximum Likelihood Detection unit is used for according to described the first estimated value
With described the second estimated value
Obtain vector space R, r carries out Maximum Likelihood Detection to received signal in described vector space R, obtains distance and receives the nearest signal vector of signal r as the final estimated value of corresponding transmitted signal
Wherein, described device also comprises:
The complexity control unit is used for determining predetermined iterations according to the signal to noise ratio of communication system;
The variance control unit is used for determining every kind of probability of happening that variation mode is corresponding according to the signal to noise ratio of communication system.
(3) beneficial effect
The described MIMO detection method of the embodiment of the invention and device, can and detect performance according to actual channel quality and communication system conditions of demand flexible complexity, realize the detection performance of varying level with the detection complexity of different brackets, be with a wide range of applications.
Embodiment
Below in conjunction with drawings and Examples, the specific embodiment of the present invention is described in further detail.Following examples are used for explanation the present invention, but are not used for limiting the scope of the invention.
For the MIMO(multiple-input and multiple-output) communication system, need to carry out the transmission data that MIMO detects to obtain transmitting terminal at receiving terminal.The invention provides method and the device of the adjustable realization MIMO input of a kind of complexity, can and detect performance according to actual channel quality and system requirements situation flexible complexity, and in conjunction with linear MIMO detect, non-linear partial MIMO detects, linear MIMO testing result carried out meristic variation, realizes the detection performance of varying level with the detection complexity of different brackets.
Fig. 1 is the structural representation of MIMO communication system, and as shown in Figure 1, described MIMO communication system has N at transmitting terminal
tThe root antenna, receiving terminal has N
rThe root antenna; Then receive signal and transmitted signal and satisfy following relation:
r=H×x+n;
Wherein, r is for receiving signal, and its dimension is N
r* 1, N
rBe the reception antenna number.
R '
1, r '
2 Be respectively the reception signal of every reception antenna; X is transmitted signal, and its dimension is N
t* 1, N
tBe the transmitting antenna number.
x
1, x
2 Be respectively the transmitted signal of every transmitting antenna; H represents channel matrix, and its dimension is N
r* N
tN represents noise jamming, and its dimension is N
r* 1.
Fig. 2 is the described MIMO detection method of embodiment of the invention flow chart, and as shown in Figure 2, described method comprises step:
A: r carries out linearity test to received signal, obtains the first estimated value of corresponding transmitted signal
In steps A, receiving terminal to received signal r carries out linearity test, obtains the first estimated value to transmitted signal
Concrete formula is as follows:
Wherein,
Be N
t* 1 dimension, N
tBe the transmitting antenna number, g is filtering matrix;
Wherein, can adopt in the present embodiment but be not limited to ZF (ZF) algorithm or least mean-square error (MMSE) algorithm calculates described filtering matrix g.
When adopting zero forcing algorithm, g=(H
HH)
-1H
H
When adopting least-mean-square error algorithm, g=(H
HH+ σ
2I)
-1H
H
Wherein, H is channel matrix, can be obtained by channel estimating σ
2Be noise power.
B: according to predetermined iterations to received signal r carry out non-linear detection, obtain the estimated value of counterpart transmitted signal
In step B, the predetermined iterations according to the indication of complexity control unit carries out non-linear detection to received signal, obtains the estimated value to the part transmitted signal
Concrete grammar is as follows:
The complexity control unit determines the iterations N of non-linear detection
Iter, and N
Iter<N
t, N wherein
tBe the transmitting antenna number.The complexity control unit is regulated iterations N automatically according to the communication system signal to noise ratio snr
Iter
Table one is N
t=N
r=4, when adopting the 16QAM modulation, the iterations N of complexity control unit output
IterRule change relation table with signal to noise ratio snr.
Table 1 iterations N
IterRule change relation table with signal to noise ratio snr
Need to prove, in actual applications, iterations N
IterBe not limited to shown in the table one with the relation of signal to noise ratio snr, those skilled in the art can be according to flexible adjustment form one data such as actual conditions and system configuration, to average out between detection complexity and detection performance.
Determine iterations N at the complexity control unit according to signal to noise ratio snr
IterAfterwards, non-linear detection unit is carried out N
IterInferior iterative detection.MIMO iterative detection process is specific as follows:
Initialization: i=1, G
1=F (H);
Iterative process:
i=i+1;
Wherein, i is less than or equal to predetermined iterations N
Iterr
iReception signal when representing the i time iteration, r
1Equal initial described reception signal r; G
iThe expression filtering matrix, F (H) and
Expression calculation of filtered matrix G
iFunction, H represents channel matrix; (G
i)
jExpression filtering matrix G
iJ capable, s
iRepresent filtering matrix G in the i time iteration
iThe capable subscript of 2-Norm minimum in the row vector;
Expression according to planisphere to detection signal
Carry out hard decision,
S in the expression transmitted signal
iThe estimated value of individual symbol;
The s of expression channel matrix H
iRow turn order;
The s of expression signaling channel matrix H
1, s
2..., s
iClassify 0 matrix that obtains as.Need to prove, the interference elimination in the above-mentioned algorithm sequentially is that the energy of the generalized inverse matrix reception column vector signal of the each iteration of basis sorts, and guarantees like this N under the control of complexity control unit
IterThe detected value of inferior iteration is local optimum.
Wherein, can adopt in the present embodiment but be not limited to ZF ordering interference cancellation algorithm or least mean-square error ordering interference cancellation algorithm is come calculation of filtered matrix G
i
Therefore in step B, non-linear detection unit will be according to the iterations N of complexity control unit decision
IterExport the estimated value to the part transmitted signal
Dimension be N
t* 1, but owing to not carrying out completely iterative detection, wherein only have N
IterIndividual symbol has value, and all the other the unknowns are 0.
C: according to described the first estimated value
Estimated value with described part transmitted signal
The residue transmitted signal that does not obtain estimated value among the described step B is carried out the bit inversion operation, obtain the estimated value of corresponding residue transmitted signal
In step C, iterative detection among the step B do not estimated the transmitted signal that obtains, by the variance control unit controls, detect according to the steps A neutral line and to obtain
Respective symbol is carried out the bit variation, thereby produce the estimated value of corresponding receiving symbol
Concrete grammar is as follows:
For the signal that uses M contrast system, its each constellation symbol has log
2M bit number, possible variation kind has log
2The M kind.For example modulate for 16QAM, each constellation symbol is made of 4 bit binary code, then have the possibility of 4 kinds of variations: 1 bit makes a variation ... 4 bits make a variation, the bit that variation is corresponding position in this bit group carries out negate (0 change 1,1 becomes 0), the variance control unit is used for determining the probability of happening of every kind of variation when generating estimate symbol.The purpose of variance control unit is to make this sign estimation value to have may equal actual value greatlyr, is a kind of local best practice.The variance control unit can be regulated automatically according to the communication system signal to noise ratio snr.
Table two is N
t=N
rDuring=4,16QAM modulation, the probability of happening of every kind of variation mode of variance control unit output and the relation of SNR.
The relation table of table 2 variation mode, probability of happening and SNR
Need to prove, in actual applications, the probability of happening of every kind of variation mode of variance control unit output and the relation of SNR are not limited to shown in the table one, and those skilled in the art can be according to flexible adjustment form two data such as actual conditions and system configuration.
The estimated value of the part transmitted signal that obtains among the step B
Dimension be N
t* 1, owing to not carrying out completely iterative detection, wherein only have N
IterIndividual symbol has value, and all the other positions are 0, and obtaining the position is the location index index=[index of 0 signal
1, index
2Index
n], n=N wherein
t-N
IterSteps A is carried out linearity test to received signal, obtains the first estimated value to whole transmitted signals
Dimension be N
t* 1.According to the indication of index vector index and variance control unit, right
In the symbol corresponding with index vector index carry out the bit inversion operation, generate new Vector Groups
Dimension be N
t* 1, wherein only have n=N
t-N
IterIndividual symbol has value, and all the other are 0.
D: the estimated value that merges described part transmitted signal
Estimated value with described residue transmitted signal
Obtain the second estimated value of corresponding transmitted signal
In step D, to step B and step C testing result
And
Merge.
With
Be N
t* 1 dimensional vector, and
In N is arranged
IterIndividual symbol has value,
In n=N is arranged
t-N
IterIndividual symbol has value, and
With
It is complementary relationship that middle symbol has the location index of value.Then right
With
Merge, obtain the second estimated value to transmitted signal
Dimension be N
t* 1.
E: according to described the first estimated value
With described the second estimated value
Obtain vector space R, r carries out Maximum Likelihood Detection to received signal in described vector space R, obtains distance and receives the nearest signal vector of signal r as the final estimated value of corresponding transmitted signal
In step e, by the steps A testing result
With step D testing result
Consist of new vector space R, the dimension of new vector space R is N
t* 2.
The search signal vector nearest with receiving signal r carries out the maximum likelihood input in vector space R, obtains final estimated value
Concrete formula is as follows:
Wherein, H is channel matrix, and r is for receiving signal, and x is all possible vector in vector space R, and in the present embodiment, the size of vector space R is
N
tBe the transmitting antenna number.
Be the final estimated value to transmitted signal.
Fig. 3 is the modular structure schematic diagram of the described MIMO checkout gear of the embodiment of the invention, and as shown in Figure 3, this MIMO checkout gear comprises:
Linearity test unit 100 is used for to received signal that r carries out linearity test, obtains the first estimated value of corresponding transmitted signal
Non-linear detection unit 200, be used for according to predetermined iterations to received signal r carry out non-linear detection, obtain the estimated value of counterpart transmitted signal
Detecting
unit 300 is estimated in variation, is used for according to every kind of probability of happening that variation mode is corresponding, according to described the first estimated value
Estimated value with described part transmitted signal
The residue transmitted signal that does not obtain estimated value among the described step B is carried out the bit inversion operation, obtain the estimated value of corresponding residue transmitted signal
Merge
cells 400 is for the estimated value that merges described part transmitted signal
Estimated value with described residue transmitted signal
Obtain the second estimated value of corresponding transmitted signal
Maximum
Likelihood Detection unit 500 is used for according to described the first estimated value
With described the second estimated value
Obtain vector space R, r carries out Maximum Likelihood Detection to received signal in described vector space R, obtains distance and receives the nearest signal vector of signal r as the final estimated value of corresponding transmitted signal
Complexity control unit 600 is used for determining predetermined iterations according to the signal to noise ratio of communication system;
Variance control unit 700 is used for determining every kind of probability of happening that variation mode is corresponding according to the signal to noise ratio of communication system.
The described MIMO detection method of the embodiment of the invention and device, can and detect performance according to actual channel quality and communication system conditions of demand flexible complexity, realize the detection performance of varying level with the detection complexity of different brackets, be with a wide range of applications.
Above execution mode only is used for explanation the present invention; and be not limitation of the present invention; the those of ordinary skill in relevant technologies field; in the situation that do not break away from the spirit and scope of the present invention; can also make a variety of changes and modification; therefore all technical schemes that are equal to also belong to category of the present invention, and scope of patent protection of the present invention should be defined by the claims.