CN102790995A - Information channel gain estimation method based on cognitive radio - Google Patents

Information channel gain estimation method based on cognitive radio Download PDF

Info

Publication number
CN102790995A
CN102790995A CN2012102908464A CN201210290846A CN102790995A CN 102790995 A CN102790995 A CN 102790995A CN 2012102908464 A CN2012102908464 A CN 2012102908464A CN 201210290846 A CN201210290846 A CN 201210290846A CN 102790995 A CN102790995 A CN 102790995A
Authority
CN
China
Prior art keywords
prime
gamma
user
main
signal
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Granted
Application number
CN2012102908464A
Other languages
Chinese (zh)
Other versions
CN102790995B (en
Inventor
赵国栋
张蔺
武刚
陈智
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
University of Electronic Science and Technology of China
Original Assignee
University of Electronic Science and Technology of China
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by University of Electronic Science and Technology of China filed Critical University of Electronic Science and Technology of China
Priority to CN201210290846.4A priority Critical patent/CN102790995B/en
Publication of CN102790995A publication Critical patent/CN102790995A/en
Application granted granted Critical
Publication of CN102790995B publication Critical patent/CN102790995B/en
Expired - Fee Related legal-status Critical Current
Anticipated expiration legal-status Critical

Links

Images

Landscapes

  • Mobile Radio Communication Systems (AREA)

Abstract

The invention discloses an information channel gain estimation method based on cognitive radio. By the adoption of the method, a cognitive user actively serves as a relay of a main user to transfer a main user signal after being received and amplified as a detection signal to a main user receiving end, a closed-loop power control of the main user is triggered via increasing a signal to noise ratio of the main user receiving end, finally, according to an observed change of the signal to noise ratio of the main user signal, the cognitive user can estimate the information channel gain of two crossed information channels, and can also estimate the information channel gain of a main user information channel, thus the average information channel content among cognitive users is enabled to be remarkably increased by the information, and meanwhile since the main user signal after being amplified is utilized by the cognitive user as the detection signal in the method, the disturbance on the main user from the cognitive user during a detection process is avoided on an average meaning according to the method.

Description

Channel gain method of estimation based on cognitive radio
Technical field
The invention belongs to the cognitive radio technology field, be specifically related to a kind of in cognitive radio networks in order to realize the coexistence of main user and cognitive user, improve the channel gain method of estimation of cognitive user ergodic capacity.
Background technology
Cognitive radio (CR, Cognitive Radio) is a kind of at the rare effective technology of following wireless communication field solution frequency spectrum resource.If cognitive user (CU; Cognitive User) can be to main user (PU; Primary User) cause disturb or cognitive user to main user's interference in the receivable scope of main user; This technology allows cognitive user to insert certain section frequency spectrum of having distributed to main user, realizes frequency spectrum share, thereby improves the availability of frequency spectrum.Cognitive user can insert target band through dual mode, and a kind of is that the opportunistic frequency spectrum inserts (OSA, Opportunistic Spectrum Access), and another kind is frequency spectrum share (SS, Spectrum Sharing).Under opportunistic frequency spectrum access way, cognitive user detects main user's operating state, if main user is in idle condition, cognitive user can insert target band; In case it is in running order to detect main user, cognitive user will discharge target band.Therefore in the opportunistic frequency spectrum inserted, in fact cognitive user had utilized main user on target band, to use the space, and cognitive user and main user can not be that identical frequency band is used in time or different location like this; But in the frequency spectrum share mode, if the interference that cognitive user causes main user is lower than the receivable interference threshold of main user, cognitive user still can be used target band in same place with main user simultaneously so.Therefore the frequency spectrum share mode can be utilized more spectrum opportunities with respect to the opportunistic access way.
In the frequency spectrum share mode, channel condition information (CSI, Channel State Information) is the key that realizes cognitive user and main user coexistence.According to the channel condition information that cognitive user obtains, cognitive user can coexist with main user under different restrictive conditions, thereby reaches different channel capacities.Fig. 1 is a typical cognitive user and main user's symbiotic system model, and this model has been considered two cognitive user and two main users, wherein, and PU 1And PU 2Represent two main users, CU 1And CU 2Represent two cognitive user, h PpRepresent two main user PU 1And PU 2Between channel, h CcRepresent two cognitive user CU 1And CU 2Between channel, h CpExpression cognitive user CU 1To main user PU 2Between channel, h PcRepresent main user PU 1To cognitive user CU 2Between channel.
From information-theoretical angle, knowing under the situation of all channel condition informations that the transmitting power of cognitive user only is subject to the interference (IC, Interference Control) to main user, at this moment cognitive user can reach maximum channel capacity.But the estimation of channel condition information is very challenging in cognitive radio system, because in actual cognitive radio system, main user is unwilling even can not carry out information exchange with cognitive user.In Fig. 1, although cognitive user can directly obtain cognitive channel h CcChannel condition information, but obtain other channel condition information be very the difficulty.If obtain cross-channel h PcChannel condition information, cognitive user need obtain main user's training sequence so; If obtain another one cross-channel h CpChannel condition information, so main user need obtain the training sequence of cognitive user, and in real system, these conditions obviously are impossible satisfy, and for main subscriber channel h Pp, owing to have only main user to estimate to it, therefore if obtain h PpChannel condition information, this system need set up the based on feedback link between a main user and the cognitive user, main user is with h PpChannel condition information feed back to cognitive user through based on feedback link, if there is not based on feedback link, cognitive user possibly obtain h hardly PpChannel condition information.It is thus clear that in cognitive radio system, to two cross-channel h Pc, h Cp, and main subscriber channel h PpBe estimated for realize main user and cognitive user the coexistence bottleneck, wherein to main subscriber channel h PpObtaining of state information is the most difficult.
To the problems referred to above, some documents are studied the estimation of three channel condition informations of model shown in Figure 2, wherein, and main user PU 1And PU 2Have a transmit receive antenna respectively and be operated in tdd mode, CU 1One transmit antennas and a reception antenna are arranged.Existing research method is based on the principle of active perception study; In the method, main user job is in that (under the effect of closed power control, main user's transmitting terminal is according to the signal to noise ratio (SNR of receiving terminal feedback under the condition of closed power control; Signal Noise Ratio) change information is adjusted transmitting power automatically; Guarantee that receiving terminal can receive the desired signal of constant signal to noise ratio, thereby guarantee the constant data rate transmission, so this technology is widely used in the current cognitive radio system); Cognitive user is through initiatively sending interfere information to main user's receiving terminal; Reduce the signal to noise ratio of main user's receiving terminal, thereby trigger main user's closed power control, the adjustment of the main user emission power that last cognitive user basis observes is to two cross-channel h PcOr h CpChannel gain estimate, obtain the gain of two cross-channel after, the transmit power limited of cognitive user when carrying out transfer of data is in the maximum interference power (ITC that main user allowed; Interference Temperture Control); But concrete list of references: R.Zhang, on active learning and supervised transmission of spectrum sharing based cognitive radios by exploiting hidden primary radio feedback, IEEE Trans.Commun.vol.58; No.10; Pp.2960-2970, Oct.2010 and I.Bajaj, and Y.Gong; Cross-channel estimation using supervised probing and sensing in cognitive radio networks; In Proc.IEEE Int.Conmun.Conf. (ICC), Jun.2011, pp.1-5.The problem of the existence of this method is: in detection process, cognitive user can temporarily reduce main user's communications performance to the interference signal that main user sends; In addition, this detection method can only estimate cross-channel h PcAnd h CpChannel gain, promptly
Figure BDA00002018101600021
With
Figure BDA00002018101600022
Can not estimate main subscriber channel h PpChannel gain, promptly
Figure BDA00002018101600023
Summary of the invention
The objective of the invention is to send the problem that interference signal can reduce main telex network performance and can not estimate main subscriber channel gain to main user, proposed a kind of channel gain method of estimation based on active probe in order to solve cognitive user in the existing channel gain estimation method.
Technical scheme of the present invention is: a kind of channel gain method of estimation based on cognitive radio specifically comprises the steps:
Step 1: first time slot, cognitive user are measured the main subscriber signal signal to noise ratio γ that the first main user sends C1, cognitive user is with amplitude gain G simultaneously 2The main subscriber signal that amplification receives from the first main user, and transmit with amplitude gain G to the second main user 2Main subscriber signal after the amplification;
Step 2: second time slot, cognitive user are measured the main subscriber signal signal to noise ratio γ that the second main user sends C2, cognitive user is with amplitude gain G simultaneously 1The main subscriber signal that amplification receives from the second main user, and transmit with amplitude gain G to the first main user 1Main subscriber signal after the amplification;
Step 3: the 3rd time slot, cognitive user are measured the main subscriber signal signal to noise ratio γ ' that the first main user sends C1, cognitive user is with amplitude gain G ' simultaneously 2The main subscriber signal that amplification receives from the first main user, and transmit with amplitude gain G ' to the second main user 2Main subscriber signal after the amplification;
Step 4: the 4th time slot, cognitive user are measured the main subscriber signal signal to noise ratio γ ' that the second main user sends C2
Step 5: the 5th time slot, cognitive user are measured the main subscriber signal signal to noise ratio γ that the first main user sends " C1
Step 6: cognitive users were calculated, and the first primary user channel gain
Figure BDA00002018101600031
cognitive user and the second main user channel gain
Figure BDA00002018101600032
The first and second main primary user user channel increased
Figure BDA00002018101600033
h 2 2 = γ c 1 ′ γ c 1 G 2 2 σ c 2 ( 1 + G 2 Δ ) 2 σ 2 2 - σ 2 2 G 2 2 σ c 2 ,
h 1 2 = γ c 2 ′ γ c 2 G 1 2 σ c 2 ( 1 + G 1 Δ ) 2 σ 1 2 - σ 1 2 G 1 2 σ c 2 ,
h 0 2 = h 1 2 h 2 2 Δ 2 ,
Wherein, Δ = ( G 2 γ r 1 ′ ′ - G 2 ′ γ r 1 ′ ) ± γ r 1 ′ γ r 1 ′ ′ ( G 2 - G 2 ′ ) 2 + γ r 1 ( γ r 1 ′ - γ r 1 ′ ′ ) ( G 2 ′ 2 - G 2 2 ) G 2 G 2 ′ ( γ r 1 ′ - γ r 1 ′ ′ ) .
Beneficial effect of the present invention: the present invention has obtained main subscriber channel gain
Figure BDA000020181016000310
in the system of cognitive user and main user coexistence when obtaining two cross-channel gains
Figure BDA00002018101600038
and
Figure BDA00002018101600039
, this information makes the ergodic capacity between the cognitive user that more significantly raising arranged.In the method for the invention; Cognitive user is initiatively served as main user's relaying; Main subscriber signal after receiving, amplifying is transmitted to main user's receiving terminal as detectable signal; Recently trigger main user's closed power through the noise that improves main user's receiving terminal and control, last cognitive user changes the channel gain that can not only estimate two cross-channel according to the signal to noise ratio of the main subscriber signal that observes, and can also estimate the channel gain of main subscriber channel.Therefore method of the present invention has also avoided in the detection process cognitive user to main user's interference on average meaning.
Description of drawings
Fig. 1 is existing a kind of cognitive user and main user's symbiotic system model sketch map.
Fig. 2 is the system model sketch map that the inventive method adopts.
Fig. 3 is the time slot schematic flow sheet of the inventive method.
Fig. 4 is cognitive user estimated performance sketch map to main subscriber channel gain under the different capacity restrictive condition.
Fig. 5 be unknown main subscriber channel gain
Figure BDA00002018101600041
with known should the value situation under channel capacity probability density function (CDF) curve between the cognitive user contrast sketch map.
Embodiment
To combine accompanying drawing below, provide specific embodiment of the present invention.
Describe content of the present invention for ease, at first employed term among the present invention defined:
Definition 1: time division multiplexing (TDD, Time Division Duplex): communicating pair communicates on the different time sheet in same frequency.
Definition 2: time slot (Slot) a: timeslice of time division multiplexing.
Definition 3: signal to noise ratio: the ratio of signal power and noise power (user is used as all interference beyond the desired signal as noise processed).
Definition 4: closed power control (CLPC, Closed Loop Power Contro1): the power of transmitting terminal is according to the variation adjustment of receiving terminal signal to noise ratio, thus the quality of reception of assurance receiving terminal.
The model that adopts in the face of the present invention is down introduced:
As shown in Figure 2, considered two main user PU in the model that the present invention adopts 1, PU 2With a cognitive user CU 1, in order to express easily, main subscriber channel h Pp, two cross-channel h PcAnd h CpUse h respectively 0, h 1And h 2Expression, corresponding channel gain is expressed as
Figure BDA00002018101600042
With
Figure BDA00002018101600043
Definition signal is from main user PU simultaneously 1To PU 2Direction be the fl transmission direction, be the reverse transfer direction on the contrary.
In the model, two main users use the f frequency range at main subscriber channel h 0The mode that goes up with TDD intercoms mutually, and cognitive user also attempts to insert the f frequency range simultaneously, the interference that when communicating by letter main user is caused in order to be controlled at, and cognitive user need be according to main subscriber channel h 0, cross-channel h 1And h 2Variation adjust transmitting power in real time.Use n in the model respectively 1, n 2And n cExpression PU 1, PU 2And CU 1The white Gaussian noise at place, obeying average respectively is 0, variance does
Figure BDA00002018101600051
With Gaussian distribution, promptly
Figure BDA00002018101600053
With
Figure BDA00002018101600054
Introduce content of the present invention according to the time slot flow chart of Fig. 3 below; Wherein, laterally be time orientation, unit is a time slot; Vertically be respectively the operating state of direct link (Direct link) and repeated link (Relay link), 5 cycles that time slot is estimated as a channel gain.
First and third, five time slots: on the fl transmission direction, main user PU 1With power p 1(milliwatt is mw) to PU 2Send signal
Figure BDA00002018101600055
The sampling sequence number of k expression signal satisfies 1≤k≤K, and wherein, K representes maximum hits, p 1Satisfy
p 1 = γ T 2 σ 2 2 h 0 2 , - - - ( 1 )
Wherein, γ T2Expression PU 2Target signal to noise ratio.
Cognitive user CU 1The main subscriber signal that receives is respectively with corresponding signal to noise ratio
y c 1 ( k ) = h 1 p 1 x p 1 ( k ) + n c ( k ) , - - - ( 2 )
With
γ c 1 = p 1 h 1 2 σ c 2 , - - - ( 3 )
CU 1When receiving main subscriber signal with amplitude gain G 2Amplify this signal, the main subscriber signal after will amplifying then as detectable signal to PU 2Transmit, detectable signal can be expressed as:
x c 1 ( k ) = G 2 y c 1 ( k ) = G 2 ( h 1 p 1 x p 1 ( k ) + n c ( k ) ) , - - - ( 4 )
Therefore, at first time slot, PU 2Signal that the place receives and corresponding signal to noise ratio are:
Figure BDA000020181016000510
With
γ 2 = p 1 ( h 0 + G 2 h 1 h 2 ) 2 G 2 2 h 2 2 σ c 2 + σ 2 2 , - - - ( 6 )
Under closed power control, at the second time slot PU 2The change information of local signal to noise ratio is passed to PU through based on feedback link 1, PU 1The transmitting power that will adjust signal at the 3rd time slot does
p 1 ′ = γ T 2 ( G 2 2 h 2 2 σ c 2 + σ 2 2 ) ( h 0 + G 2 h 1 h 2 ) 2 , - - - ( 7 )
Therefore at the 3rd time slot CU 1Can observe the signal to noise ratio of a main subscriber signal after the renewal:
γ c 1 ′ = h 1 2 p 1 ′ σ c 2 , - - - ( 8 )
At the 3rd time slot, if CU 1With amplitude gain G ' 2Amplify the main subscriber signal that receives and transmit the signal after amplifying, at the 5th time slot, CU 1Can observe the signal to noise ratio of a main subscriber signal after the renewal once more:
γ c 1 ′ ′ = h 1 2 p 1 ′ ′ σ c 2 , - - - ( 9 )
Wherein, p " 1For at the 5th time slot PU 1Transmitting power, this power satisfies:
p 1 ′ ′ = γ T 2 ( G 2 ′ 2 h 2 2 σ c 2 + σ 2 2 ) ( h 0 + G 2 ′ h 1 h 2 ) 2 , - - - ( 10 )
The second, four time slots: with the similar process of fl transmission direction, in the reverse transfer direction, if at the second time slot CU 1With amplitude gain G 1Amplify PU 2The signal that sends is also transmitted the signal after amplifying, CU 1Will observe the signal to noise ratio of main subscriber signal at second, four time slots respectively:
γ c 2 = h 2 2 p 2 σ c 2 , - - - ( 11 )
With
γ c 2 ′ = h 2 2 p 2 ′ σ c 2 , - - - ( 12 )
Wherein, p 2, p ' 2Be respectively PU 2In the transmitting power of second time slot and the 4th time slot, satisfy respectively
p 2 = γ T 1 σ 1 2 h 0 2 , - - - ( 13 )
With
p 2 ′ = γ T 1 ( G 1 2 h 1 2 σ c 2 + σ 1 2 ) ( h 0 + G 1 h 1 h 2 ) 2 , - - - ( 14 )
Wherein, γ T1Expression PU 1The target signal to noise ratio at place.
Through above-mentioned active probe operation, CU 1Just obtained to comprise channel gain
Figure BDA00002018101600071
With
Figure BDA00002018101600072
Information, provide CU below 1Information through these acquisitions is right With
Figure BDA00002018101600074
Estimation procedure.
Obtain through (3)/(8), (3)/(9)
p 1 ′ = γ c 1 ′ γ c 1 p 1 , - - - ( 15 )
With
p 1 ′ ′ = γ c 1 ′ ′ γ c 1 p 1 , - - - ( 16 )
Abbreviation (7) and (10) obtain:
γ T 2 ( G 2 2 h 2 2 σ c 2 + σ 2 2 ) = p 1 ′ h 0 2 + G 2 2 p 1 ′ h 1 2 h 2 2 + 2 G 2 p 1 ′ h 0 h 1 h 2 , - - - ( 17 )
With
γ T 2 ( G 2 ′ 2 h 2 2 σ c 2 + σ 2 2 ) = p 1 ′ ′ h 0 2 + G 2 ′ 2 p 1 ′ ′ h 1 2 h 2 2 + 2 G 2 ′ p 1 ′ ′ h 0 h 1 h 2 , - - - ( 18 )
Obtain through
Figure BDA00002018101600079
:
G 2 ′ 2 γ T 2 ( G 2 2 h 2 2 σ c 2 + σ 2 2 ) = G 2 ′ 2 ( p 1 ′ h 0 2 + G 2 2 p 1 ′ h 1 2 h 2 2 + 2 G 2 p 1 ′ h 0 h 1 h 2 ) , - - - ( 19 )
Figure BDA000020181016000711
G 2 2 γ T 2 ( G 2 ′ 2 h 2 2 σ c 2 + σ 2 2 ) = G 2 2 ( p 1 ′ ′ h 0 2 + G 2 ′ 2 p 1 ′ ′ h 1 2 h 2 2 + 2 G 2 ′ p 1 ′ ′ h 0 h 1 h 2 ) , - - - ( 20 )
Obtain through (19)-(20):
( G 2 ′ 2 - G 2 2 ) γ T 2 σ 2 2 = G 2 ′ 2 p 1 ′ h 0 2 - G 2 2 p 1 ′ ′ h 0 2 + G 2 ′ 2 G 2 2 p 1 ′ h 1 2 h 2 2 - G 2 2 G 2 ′ 2 p 1 ′ ′ h 1 2 h 2 2 + , ( 21 )
2 G 2 ′ 2 G 2 p 1 ′ h 0 h 1 h 2 - 2 G 2 2 G 2 ′ p 1 ′ ′ h 0 h 1 h 2
Obtain through changing (21):
( G 2 ′ 2 - G 2 2 ) γ T 2 σ 2 2 = G 2 ′ 2 p 1 ′ h 0 2 - G 2 2 p 1 ′ ′ h 0 2 + G 2 ′ 2 G 2 2 p 1 ′ h 0 2 h 1 2 h 2 2 h 0 2 - G 2 2 G 2 ′ 2 p 1 ′ ′ h 0 2 h 1 2 h 2 2 h 0 2 , ( 22 )
+ 2 G 2 ′ 2 G 2 p 1 ′ h 0 h 1 h 2 h 0 - 2 G 2 2 G 2 ′ p 0 ′ ′ h 0 h 1 h 2 h 0
(22) are brought in (15) and (16) to be obtained:
( G 2 ′ 2 - G 2 2 ) γ T 2 = G 2 ′ 2 γ c 1 ′ p 1 h 0 2 γ c 1 σ 2 2 - G 2 2 γ c 1 ′ ′ p 1 h 0 2 γ c 1 σ 2 2 + G 2 ′ 2 G 2 2 γ c 1 ′ p 1 h 0 2 h 1 2 h 2 2 γ c 1 h 0 2 σ 2 2 , ( 23 )
- G 2 2 G 2 ′ 2 γ c 1 ′ ′ p 1 h 0 2 h 1 2 h 2 2 γ c 1 h 0 2 σ 2 2 + 2 G 2 ′ 2 G 2 γ c 1 ′ p 1 h 0 h 1 h 2 γ c 1 h 0 σ 2 2 - 2 G 2 2 G 2 ′ γ c 1 ′ ′ p 1 h 0 h 1 h 2 γ c 1 h 0 σ 2 2
(23) are brought in (1) to be obtained:
γ T 2 ( G 2 ′ 2 - G 2 2 ) = G 2 ′ 2 γ c 1 ′ γ T 2 γ c 1 - G 2 2 γ c 1 ′ ′ γ T 2 γ c 1 + G 2 ′ 2 G 2 2 γ c 1 ′ h 1 2 h 2 2 γ T 2 γ c 1 h 0 2 , ( 24 )
- G 2 2 G 2 ′ 2 γ c 1 ′ ′ h 1 2 h 2 2 γ T 2 γ c 1 h 0 2 + 2 G 2 ′ 2 G 2 γ c 1 ′ h 1 h 2 γ T 2 γ c 1 h 0 - 2 G 2 2 G 2 ′ γ c 1 ′ ′ h 1 h 2 γ T 2 γ c 1 h 0
(24) both members is simultaneously divided by γ T2Obtain:
G 2 ′ 2 - G 2 2 = G 2 ′ 2 γ c 1 ′ γ c 1 - G 2 2 γ c 1 ′ ′ γ c 1 + G 2 ′ 2 G 2 2 γ c 1 ′ h 1 2 h 2 2 γ c 1 h 0 2 - G 2 2 G 2 ′ ′ 2 γ c 1 ′ ′ h 1 2 h 2 2 γ c 1 h 0 2 , ( 25 )
+ G 2 ′ 2 G 2 γ c 1 ′ h 1 h 2 γ c 1 h 0 - 2 G 2 2 G 2 ′ γ c 1 ′ ′ h 1 h 2 γ c 1 h 0
Abbreviation (25) obtains:
G 2 ′ 2 G 2 2 ( γ c 1 ′ - γ c 1 ′ ′ ) h 1 2 h 2 2 h 0 2 + 2 G 2 ′ G 2 ( G 2 ′ γ c 1 ′ - G 2 γ c 1 ′ ′ ) h 1 h 2 h 0 + G 2 ′ 2 γ c 1 ′ - G 2 ′ 2 γ c 1 + G 2 2 γ c 1 = 0 , - - - ( 26 )
Make
Figure BDA00002018101600088
(26) to be write as:
G 2 ′ 2 G 2 2 ( γ c 1 ′ - γ c 1 ′ ′ ) Δ 2 + 2 G 2 ′ G 2 ( G 2 ′ γ c 1 ′ - G 2 γ c 1 ′ ′ ) Δ + G 2 ′ 2 γ c 1 ′ - G 2 2 γ c 1 ′ ′ - G 2 ′ 2 γ c 1 + G 2 2 γ c 1 = 0 , - - - ( 27 )
Separating (27) obtains:
Δ = ( G 2 γ c 1 ′ ′ - G 2 ′ γ c 1 ′ ) ± ( G 2 γ c 1 ′ ′ - G 2 ′ γ c 1 ′ ) 2 - ( γ c 1 ′ - γ c 1 ′ ′ ) ( G 2 ′ 2 γ c 1 ′ - G 2 2 γ c 1 ′ ′ + G 2 2 γ c 1 - G 2 ′ 2 γ c 1 ) G 2 G 2 ′ ( γ c 1 ′ - γ c 1 ′ ′ ) , - - - ( 28 )
Abbreviation (28) obtains:
Δ = ( G 2 γ c 1 ′ ′ - G 2 ′ γ c 1 ′ ) ± γ c 1 ′ γ c 1 ′ ′ ( G 2 - G 2 ′ ) 2 + γ c 1 ( γ c 1 ′ - γ c 1 ′ ′ ) ( G 2 ′ 2 - G 2 2 ) G 2 G 2 ′ ( γ c 1 ′ - γ c 1 ′ ′ ) , - - - ( 29 )
Therefore, CU 1Can obtain:
h 1h 2=Δh 0, (30)
The h here 0, h 1And h 2Be appreciated that and be channel h 0, h 1And h 2Channel coefficients.
(17) are brought in (30) can be obtained:
γ T 2 ( G 2 2 h 2 2 σ c 2 + σ 2 2 ) = γ c 1 ′ γ c 1 p 1 h 0 2 + G 2 2 Δ 2 γ c 1 ′ γ c 1 p 1 h 0 2 + 2 G 2 Δ γ c 1 ′ γ c 1 p 1 h 0 2 , - - - ( 31 )
Equality (31) two ends can be obtained divided by
Figure BDA000020181016000813
simultaneously:
γ T 2 ( G 2 2 h 2 2 σ c 2 σ 2 2 + 1 ) = γ c 1 ′ γ c 1 p 1 h 0 2 σ 2 2 + G 2 2 Δ 2 γ c 1 ′ γ c 1 p 1 h 0 2 σ 2 2 + 2 G 2 Δ γ c 1 ′ γ c 1 p 1 h 0 2 σ 2 2 , - - - ( 32 )
Bring equality (1) into (31), can obtain:
G 2 2 h 2 2 σ c 2 σ 2 2 + 1 = γ c 1 ′ γ c 1 ( 1 + G 2 2 + 2 G 2 Δ ) , - - - ( 33 )
Abbreviation (32) can obtain:
h 2 2 = γ c 1 ′ γ c 1 G 2 2 σ c 2 ( 1 + G 2 Δ ) 2 σ 2 2 - σ 2 2 G 2 2 σ c 2 , - - - ( 34 )
In like manner, after obtaining Δ, if consider reverse transfer, cognitive user can obtain so:
h 1 2 = γ c 2 ′ γ c 2 G 1 2 σ c 2 ( 1 + G 1 Δ ) 2 σ 1 2 - σ 1 2 G 1 2 σ c 2 , - - - ( 35 )
Can obtain through (29), (30), (33) and (34):
h 0 2 = h 1 2 h 2 2 Δ 2 , - - - ( 36 )
Through aforesaid operations, cognitive user has just obtained
Figure BDA00002018101600095
and
Figure BDA00002018101600096
Steps summarize with the inventive method is following at last:
Step 1: first time slot, CU 1Measure PU 1The main subscriber signal signal to noise ratio γ that sends C1, while CU 1With amplitude gain G 2Amplification is from PU 1The main subscriber signal that receives, and to PU 2Forwarding is with amplitude gain G 2Main subscriber signal after the amplification.
Step 2: second time slot, CU 1Measure PU 2The main subscriber signal signal to noise ratio r that sends C2, while CU 1With amplitude gain G 1Amplification is from PU 2The main subscriber signal that receives, and to PU 1Forwarding is with amplitude gain G 1Main subscriber signal after the amplification.
Step 3: the 3rd time slot, CU 1Measure PU 1The main subscriber signal signal to noise ratio γ ' that sends C1, while CU 1With amplitude gain G ' 2Amplification is from PU 1The main subscriber signal that receives, and to PU 2Forwarding is with amplitude gain G ' 2Main subscriber signal after the amplification.
Step 4: the 4th time slot, CU 1Measure PU 2The main subscriber signal signal to noise ratio γ ' that sends C2
Step 5: the 5th time slot, CU 1Measure PU 1The main subscriber signal signal to noise ratio γ that sends " C1
Step 6: calculate h 2 2 = γ c 1 ′ γ c 1 G 2 2 σ c 2 ( 1 + G 2 Δ ) 2 σ 2 2 - σ 2 2 G 2 2 σ c 2 , h 1 2 = γ c 2 ′ γ c 2 G 1 2 σ c 2 ( 1 + G 1 Δ ) 2 σ 1 2 - σ 1 2 G 1 2 σ c 2 With h 0 2 = h 1 2 h 2 2 Δ 2 , Wherein, Δ = ( G 2 γ r 1 ′ ′ - G 2 ′ γ r 1 ′ ) ± γ r 1 ′ γ r 1 ′ ′ ( G 2 - G 2 ′ ) 2 + γ r 1 ( γ r 1 ′ - γ r 1 ′ ′ ) ( G 2 ′ 2 - G 2 2 ) G 2 G 2 ′ ( γ r 1 ′ - γ r 1 ′ ′ ) .
Need to prove,, thereby can define amplitude gain G according to Power Limitation here because each node has Power Limitation 1, G 2, G ' 2, the G of theoretic optimum 1, G 2, G ' 2Be inaccessible in actual power limit, those skilled in the art can choose according to actual conditions.In addition, because CU 1The sum of errors amplitude gain G of the main user's signal to noise ratio that observes 2, G ' 2Non-positive root or imaginary number root may appear in inappropriate choosing, (29), this time CU 1Think and estimate failure, then estimate next time; On the contrary, CU 1An arithmetic number root that obtains is regarded as once successfully estimating.In addition, if occur two arithmetic number roots, CU simultaneously 1Will one of them root of random choose proceed the estimation of channel gain, emulation proves that the method for estimation of this suboptimum still can reach preferable performance.
Principle of the present invention: under the effect of closed power control, if the signal to noise ratio of receiving terminal reduces, transmitting terminal will increase transmitting power at next transmission time slot so; On the contrary, if the signal to noise ratio of receiving terminal increases, transmitting terminal will reduce transmitting power at next transmission time slot so.Cognitive user changes the change information that can obtain main user's transmitting terminal power through the signal to noise ratio of the main subscriber signal that receives.Be transmitted as example with forward direction, can know CU from (7) and (8) 1The signal to noise ratio that receives has comprised h 0, h 1And h 2Information, i.e. γ ' C1=f (h 0, h 1, h 2), therefore, CU 1Utilize the main user's signal to noise ratio that is observed to channel gain
Figure BDA00002018101600101
With Estimate it is feasible.
Can find out the necessary condition of estimating main subscriber channel gain the present invention from top step:
1. main user job is under tdd mode.
2. the main subscriber signal after cognitive user needs to amplify is transmitted to main user's receiving terminal as detectable signal.
Consider the system model among Fig. 2, wherein, cognitive user CU 1Be positioned at two main user PU 1And PU 2Between, get PU 1And PU 2Distance be 0.25km, represent CU with d 1To PU 1Distance, represent CU with 0.25-d 1To PU 2Distance.Electromagnetic wave is propagated the influence that receives shadow fading and free space decline in wireless channel, wherein, shadow fading obedience average is 10 logarithm normal distribution, and free space decline model is:
P L(dB)=128.1+37.6log 10(l)l≥0.035km,(37)
Wherein, l representes the distance of electromagnetic wave propagation.
Consider main user PU in the instance 1Target received signal to noise ratio γ T1=15dB, main user PU 2Target received signal to noise ratio γ T2=5dB, main user PU 1, PU 2With cognitive user CU 1The noise energy at place is respectively
Figure BDA00002018101600103
Figure BDA00002018101600104
With
Figure BDA00002018101600105
Further consider main user PU 1And PU 2Max power constraint be respectively P Max 1 = 20 DBm With P Max 2 = 10 DBm .
Fig. 4 has provided cognitive user CU 1Be respectively in Power Limitation
Figure BDA00002018101600108
With
Figure BDA00002018101600109
Estimated performance contrast under two kinds of situation, wherein, left vertical is represented the evaluated error of channel gain, and right vertical representes to be estimated power, and ε representes average evaluated error relatively, is defined as
Figure BDA00002018101600111
Figure BDA00002018101600112
Expression
Figure BDA00002018101600113
Estimated value;
Figure BDA00002018101600114
Average success rate, N are estimated in expression mExpression overall estimate number of times, N fThe frequency of failure is estimated in expression;
Figure BDA00002018101600115
Expression cognitive user CU 1Max power constraint; D representes cognitive user CU 1Apart from main user PU 1Distance.
From figure, can clearly see; During as
Figure BDA00002018101600116
; Because the variation of cognitive user position; Average evaluated error minimum relatively can be low to moderate 1.5%, and average success rate is up to 90%; During as
Figure BDA00002018101600117
; Average evaluated error minimum relatively can be low to moderate 2%; Average success rate is higher than 85%, and visible, this method of estimation has shown estimated performance preferably; And cognitive user maximum constraints power is high more, and estimated performance is good more.
Below, in the system of cognitive user and main user coexistence, cross-channel gain that the main subscriber channel that utilizes the present invention to obtain gains and cross-channel gains with respect to only obtain can improve the ergodic capacity of cognitive user more significantly through the emulation proof.
As shown in Figure 1, consider that 4 users lay respectively at elongated four summits of square of 100m that are, main user PU 1With cognitive user CU 1Max power constraint all be 20dBm, main user PU 1And PU 2Average data rate be 4.65Mbps, the average interrupt rate is 4%, the maximum interruption rate that main user allows is 5%.
If cognitive user can only obtain cross-channel h CpAnd h PcChannel gain, cognitive user can only limit at interference temperature under (ITC) condition and work so.Fig. 5 provided unknown main subscriber channel gain
Figure BDA00002018101600118
and known should the value situation under channel capacity probability density function (CDF) curve comparison diagram between the cognitive user; Wherein, C representes channel capacity; Unit is bits per second (bps), and Mbps representes MBPS.Can learn that from Fig. 5 in this case, the ergodic capacity of cognitive user only is 0.056Mbps; Yet; Under the same conditions, if cognitive user can reach 1.17Mbps through the ergodic capacity of the present invention's acquisition
Figure BDA00002018101600119
and
Figure BDA000020181016001110
cognitive user.It is thus clear that in the system of cognitive user and main user coexistence, the present invention can improve the ergodic capacity of cognitive user near 20dB.
Above instance is merely preferred example of the present invention, and use of the present invention is not limited to this instance, and is all within spirit of the present invention and principle, any modification of being made, is equal to replacement, improvement etc., all should be included within protection scope of the present invention.

Claims (1)

1. the channel gain method of estimation based on cognitive radio specifically comprises the steps:
Step 1: first time slot, cognitive user are measured the main subscriber signal signal to noise ratio γ that the first main user sends C1, cognitive user is with amplitude gain G simultaneously 2The main subscriber signal that amplification receives from the first main user, and transmit with amplitude gain G to the second main user 2Main subscriber signal after the amplification;
Step 2: second time slot, cognitive user are measured the main subscriber signal signal to noise ratio γ that the second main user sends C2, cognitive user is with amplitude gain G simultaneously 1The main subscriber signal that amplification receives from the second main user, and transmit with amplitude gain G to the first main user 1Main subscriber signal after the amplification;
Step 3: the 3rd time slot, cognitive user are measured the main subscriber signal signal to noise ratio γ ' that the first main user sends C1, cognitive user is with amplitude gain G ' simultaneously 2The main subscriber signal that amplification receives from the first main user, and transmit with amplitude gain G ' to the second main user 2Main subscriber signal after the amplification;
Step 4: the 4th time slot, cognitive user are measured the main subscriber signal signal to noise ratio γ ' that the second main user sends C2
Step 5: the 5th time slot, cognitive user are measured the main subscriber signal signal to noise ratio γ ' that the first main user sends C1
Step 6: cognitive users were calculated, and the first primary user channel gain
Figure FDA00002018101500011
cognitive user and the second main user channel gain
Figure FDA00002018101500012
The first and second main primary user user channel increased
Figure FDA00002018101500013
h 2 2 = γ c 1 ′ γ c 1 G 2 2 σ c 2 ( 1 + G 2 Δ ) 2 σ 2 2 - σ 2 2 G 2 2 σ c 2 ,
h 1 2 = γ c 2 ′ γ c 2 G 1 2 σ c 2 ( 1 + G 1 Δ ) 2 σ 1 2 - σ 1 2 G 1 2 σ c 2 ,
h 0 2 = h 1 2 h 2 2 Δ 2 ,
Wherein, Δ = ( G 2 γ r 1 ′ ′ - G 2 ′ γ r 1 ′ ) ± γ r 1 ′ γ r 1 ′ ′ ( G 2 - G 2 ′ ) 2 + γ r 1 ( γ r 1 ′ - γ r 1 ′ ′ ) ( G 2 ′ 2 - G 2 2 ) G 2 G 2 ′ ( γ r 1 ′ - γ r 1 ′ ′ ) .
CN201210290846.4A 2012-08-16 2012-08-16 Information channel gain estimation method based on cognitive radio Expired - Fee Related CN102790995B (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
CN201210290846.4A CN102790995B (en) 2012-08-16 2012-08-16 Information channel gain estimation method based on cognitive radio

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
CN201210290846.4A CN102790995B (en) 2012-08-16 2012-08-16 Information channel gain estimation method based on cognitive radio

Publications (2)

Publication Number Publication Date
CN102790995A true CN102790995A (en) 2012-11-21
CN102790995B CN102790995B (en) 2014-09-10

Family

ID=47156274

Family Applications (1)

Application Number Title Priority Date Filing Date
CN201210290846.4A Expired - Fee Related CN102790995B (en) 2012-08-16 2012-08-16 Information channel gain estimation method based on cognitive radio

Country Status (1)

Country Link
CN (1) CN102790995B (en)

Cited By (9)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN104486268A (en) * 2014-12-30 2015-04-01 电子科技大学 Cross channel gain estimation method
CN104796995A (en) * 2014-01-21 2015-07-22 上海贝尔股份有限公司 Distributed channel detection method and distributed channel detection and sequential access system
CN105071879A (en) * 2015-08-28 2015-11-18 电子科技大学 Detection method for judging area of cognitive user in cross-channel gain estimation
CN105682210A (en) * 2016-03-08 2016-06-15 电子科技大学 SNR estimation method for PU receiver in cognitive radio system
CN106130937A (en) * 2016-07-08 2016-11-16 电子科技大学 Information channel gain estimation method between main system transceiver based on median criterion
CN106209702A (en) * 2016-07-08 2016-12-07 电子科技大学 Information channel gain estimation method between main system transceiver based on maximum-likelihood criterion
CN107969031A (en) * 2017-10-20 2018-04-27 宁波大学 A kind of main channel gain and cross-channel gain combined estimation method
CN108736982A (en) * 2017-04-24 2018-11-02 腾讯科技(深圳)有限公司 Acoustic communication processing method, device and electronic equipment
CN113660049A (en) * 2021-08-17 2021-11-16 电子科技大学 Design method of event trigger control and wireless communication combined system

Citations (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN101437295A (en) * 2008-12-09 2009-05-20 重庆邮电大学 Method for detecting perception radio collaboration frequency spectrum based on SNR compare
CN101662321A (en) * 2008-08-25 2010-03-03 上海无线通信研究中心 Method for sending secondary pre-code based on zero subspace technology in cognitive radio MIMO system

Patent Citations (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN101662321A (en) * 2008-08-25 2010-03-03 上海无线通信研究中心 Method for sending secondary pre-code based on zero subspace technology in cognitive radio MIMO system
CN101437295A (en) * 2008-12-09 2009-05-20 重庆邮电大学 Method for detecting perception radio collaboration frequency spectrum based on SNR compare

Non-Patent Citations (2)

* Cited by examiner, † Cited by third party
Title
GUODONG ZHAO等: "Proactive Detection of Spectrum Opportunities in Primary Systems with Power Control", 《IEEE TRANSACTIONS ON WIRELESS COMMUNICATIONS》 *
RUI ZHANG: "On Active Learning and Supervised Transmission of Spectrum Sharing Based Cognitive Radios by Exploiting Hidden Primary Radio Feedback", 《IEEE TRANSACTIONS ON COMMUNICATIONS》 *

Cited By (14)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN104796995A (en) * 2014-01-21 2015-07-22 上海贝尔股份有限公司 Distributed channel detection method and distributed channel detection and sequential access system
CN104486268A (en) * 2014-12-30 2015-04-01 电子科技大学 Cross channel gain estimation method
CN104486268B (en) * 2014-12-30 2017-12-19 电子科技大学 A kind of cross-channel gain estimation method
CN105071879B (en) * 2015-08-28 2017-06-09 电子科技大学 The detection method of cognitive user region is judged in cross-channel gain estimation
CN105071879A (en) * 2015-08-28 2015-11-18 电子科技大学 Detection method for judging area of cognitive user in cross-channel gain estimation
CN105682210A (en) * 2016-03-08 2016-06-15 电子科技大学 SNR estimation method for PU receiver in cognitive radio system
CN106209702A (en) * 2016-07-08 2016-12-07 电子科技大学 Information channel gain estimation method between main system transceiver based on maximum-likelihood criterion
CN106130937A (en) * 2016-07-08 2016-11-16 电子科技大学 Information channel gain estimation method between main system transceiver based on median criterion
CN106130937B (en) * 2016-07-08 2019-03-15 电子科技大学 Information channel gain estimation method between main system transceiver based on median criterion
CN108736982A (en) * 2017-04-24 2018-11-02 腾讯科技(深圳)有限公司 Acoustic communication processing method, device and electronic equipment
CN107969031A (en) * 2017-10-20 2018-04-27 宁波大学 A kind of main channel gain and cross-channel gain combined estimation method
CN107969031B (en) * 2017-10-20 2020-10-27 宁波大学 Main channel gain and cross channel gain joint estimation method
CN113660049A (en) * 2021-08-17 2021-11-16 电子科技大学 Design method of event trigger control and wireless communication combined system
CN113660049B (en) * 2021-08-17 2022-04-22 电子科技大学 Design method of event trigger control and wireless communication combined system

Also Published As

Publication number Publication date
CN102790995B (en) 2014-09-10

Similar Documents

Publication Publication Date Title
CN102790995B (en) Information channel gain estimation method based on cognitive radio
US6941113B2 (en) Transceiver capable of adaptively selecting a modulation method based on the transmission power and channel condition
Boulogeorgos et al. A distance and bandwidth dependent adaptive modulation scheme for THz communications
Si et al. On the performance of cognitive relay networks under primary user's outage constraint
JP5038924B2 (en) Relay transmission system, base station, relay station and method
US10555263B2 (en) Uplink signal transmit power control
US8605644B2 (en) Transmission power control for sounding signal for wireless networks
US8862051B2 (en) Determining the repeater gain in dependence of interference
KR20010013848A (en) Radio communication device and method of controlling transmission rate
EP1139685B1 (en) Wireless communication device and transmission power control method
US11265802B2 (en) Wireless communication system and wireless communication method
CN101399579A (en) Uplink (reverse link) power control method for radio communication system
CN112218360A (en) Method, apparatus and system for wireless communication in wireless communication system
CN103037490A (en) Method and corresponding device for controlling uplink control channel power
US9402235B2 (en) Non-cooperative power control for large-scale antenna systems
CN102497641A (en) Method for improving communication quality of wireless sensor network
CN111132263B (en) Full-duplex destination-end scrambled untrusted energy acquisition relay transmission method and system
EP2045930B1 (en) Decentralized C/I power control for TDD
US6539234B1 (en) Radio communication terminal and transmission power control method
KR101652861B1 (en) Apparatus and method for signal reception using multiple antennas
Zhang et al. Proactive channel gain estimation for coexistence between cognitive and primary users
CN104486268B (en) A kind of cross-channel gain estimation method
Kyritsi et al. Measurement based investigation of cooperative relaying
CN112601286B (en) User scheduling method based on channel estimation error
Ferdi Wireless powered cooperative relaying systems with non-orthogonal multiple access

Legal Events

Date Code Title Description
C06 Publication
PB01 Publication
C10 Entry into substantive examination
SE01 Entry into force of request for substantive examination
C14 Grant of patent or utility model
GR01 Patent grant
CF01 Termination of patent right due to non-payment of annual fee

Granted publication date: 20140910

Termination date: 20150816

EXPY Termination of patent right or utility model