CN1025093C - Complementary common-mode current-stable compound emitter voltage follower - Google Patents
Complementary common-mode current-stable compound emitter voltage follower Download PDFInfo
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- CN1025093C CN1025093C CN 93100353 CN93100353A CN1025093C CN 1025093 C CN1025093 C CN 1025093C CN 93100353 CN93100353 CN 93100353 CN 93100353 A CN93100353 A CN 93100353A CN 1025093 C CN1025093 C CN 1025093C
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Abstract
The present invention relates to a composite emitter voltage follower with complementary common mode steady current. The composite emitter voltage follower is suitable for output parts of transistor audio power amplifiers of an A class and a B class. The composite emitter voltage follower is composed of two composite transistors, two current samplers, an AND circuit, a variable bias device and a phase corrector, wherein the two composite transistors are composed of two transistors. Three transistors are one group, and are symmetrical corresponding to member transistors in full complementation. The two current samplers are connected to a final-stage or penultimate-stage transistor collector loop. Only one BE node is arranged between a base electrode and an emitting electrode of each composite transistor, and the resistance of direct current between the emitting electrode and a load is zero. The composite emitter voltage follower has the advantage that the output resistance is small; the distortion is small; the composite emitter voltage follower has no need of using large loop negative feedback to realize the high-fidelity audio power amplification.
Description
The present invention relates to the voltage follower that the audio frequency push-pull power amplifier is used, especially a kind of complementary common-mode current-stable compound emitter voltage follower.
Existing transistor class AB audio power amplifier output is the composite voltage follower of usefulness mostly, and generally the multiple tube of being made up of two or three transistors is served as.Between base stage of this multiple tube (B) and the emitter (E), generally there is the transistorized BE knot of member (PN junction) of two or three series connection; Also existing between the emitter of multiple tube and the load loud speaker stablizes and the emitter resistance R of setting its multiple tube static working current
EThis just makes the output voltage U of compound follower
oWith input voltage U
iBetween differ AC voltage drop and resistance R of two or three BE knot
EOn the AC voltage drop sum.Because each BE knot, especially the voltage-current characteristic of the BE of power output pipe knot is nonlinear, so output voltage U
oWith input voltage U
iCompare, difference harmonic distortion more in other words is bigger.The output resistance of this follower is also bigger in addition.
The composite voltage follower that Figure 63, Figure 66 addressed in the Chinese patent publication number " CN1035214A technique of low distorsion amplification " for example, equivalent electric circuit for the sound signal that is exaggerated, all as shown in Figure 1, this is the representative compound emitter follower in the existing general audio power amplifier.As can be seen from Figure 1, the positive half cycle with signal is an example:
U
o＝U
i-（μ
BE1+U
BE3+U
RE）
It is output voltage U
oWith input voltage U
iBetween differ in the following formula bracket three.U wherein
BE1It is transistor T
1BE make friends with the stream voltage drop; U
BE3It is the final stage transistor T
3BE make friends with the stream voltage drop; U
REBe multiple tube emitter resistance R
EOn AC voltage drop.Because U
BE3Numerical value do not allow to ignore and be non-linear, so U
oAnd U
iIt is bigger to compare distortion.Output resistance is at least greater than R in addition
EResistance, unlikely provide enough dampings to loud speaker.For distortion that improves above-mentioned compound follower itself and the output resistance that reduces itself, usually need to use big loop negative feedback measure, thereby also just may bring the degenerative various harmful side effects of big loop, for example various dynamic intermodulation distortion and interface intermodulation distortion or the like.
In view of the aforementioned technical background, the purpose of this invention is to provide a kind of complementary common-mode current-stable compound emitter voltage follower, its part comprises:
Two by six transistors with three be one group, corresponding member manages the Darlington that complete complementary symmetry constitutes separately, its connection method is that two transistorized base stages of prime connect the signal source collector electrode and connect penultimate stage two transistor bases, emitters respectively and connect penultimate stage and transistorized collector electrode of final stage and output, its penultimate stage transistor emitter connects final stage two transistor base stage respectively, and its final stage two transistor emitter connects positive source and negative pole respectively;
Two current samplers according to the difference of this follower common mode current control section current sampling point, are serially connected in the above-mentioned final stage transistor collector loop, in the perhaps above-mentioned penultimate stage transistor collector loop;
A phase place correcting apparatus, be serially connected between two current sampler common junction in the above-mentioned final stage transistor collector loop and above-mentioned front stage transistor emitter, the penultimate stage transistor collector electrode, perhaps be serially connected between two current sampler common junction in above-mentioned final stage transistor collector and the penultimate stage transistor collector loop, the front stage transistor emitter;
One be connected between two transistor bases of above-mentioned prime, its mid point connects signal source and the variable bias device control of its bias voltage numerical value controlled terminal;
A "AND" circuit that is connected between above-mentioned two current sampler outputs and the above-mentioned variable bias device control end.
From the present invention forms, be not difficult to find out that it is worked in the positive and negative half cycle of signal respectively by two Darlingtons, has only a BE knot (PN junction) between base stage of every Darlington (B) and the emitter (E), and the corresponding separately member in two multiple tubes manages, and complete complementary symmetry connects, the emitter (E) of multiple tube and the D.C. resistance between the load be null value, the transistorized signal code of its final stage be by its collector electrode output stream to load, and the working point electric current of this follower is stable by the complementary common-mode Current Negative Three-Point Capacitance.
Advantage of the present invention is that very little, the distortion of itself output resistance own is very little, can adopt big loop negative-feedback technology just can realize the power amplification of high-fidelity audio frequency, thereby can eliminate or alleviate all kinds of harmful side effect that big loop negative feedback brings greatly.
Below in conjunction with accompanying drawing the present invention is described in detail.
The composite voltage follower circuit figure that Fig. 1, Fig. 2 mostly use for existing transistor class AB audio power amplifier output.
Fig. 3 is the circuit diagram of two Darlingtons among the present invention and the present invention equivalent circuit diagram to sound signal.
Fig. 4 is the circuit diagram and the specification digest accompanying drawing of the embodiment of the invention 1.
Fig. 5 is the circuit diagram of the embodiment of the invention 2.
Fig. 6 is a current sampler among Fig. 4
Circuit diagram.
Fig. 7 is a current sampler among Fig. 4
Circuit diagram.
Fig. 8 is a "AND" circuit among Fig. 4, Fig. 5
Circuit diagram.
Fig. 9 is a variable bias device among Fig. 4, Fig. 5
Circuit diagram.
Figure 10 is a phase corrector among Fig. 4, Fig. 5
Circuit diagram.
Figure 11 is a current sampler among Fig. 5
Circuit diagram.
With reference to Fig. 3, know just among the present invention that two Darlingtons are is one group of (T by six transistors with three
1, T
3, T
5, T
2, T
4, T
6), corresponding member manages complete complementary symmetry and is formed by connecting separately, transistor T wherein
1, T
4, T
6Be NPN transistor, T
3, T
5, T
2Be the PNP transistor, its connection method is two transistor Ts of prime
1, T
2The base stage number of connecing source U
i, collector electrode connects two transistor Ts of penultimate stage respectively
3, T
4Base stage, emitter connect two transistor Ts of penultimate stage
3, T
4With the final stage transistor T
5, T
6Collector electrode and output V
o, its penultimate stage transistor T
3, T
4Emitter connect two transistor Ts of final stage respectively
5, T
6Base stage, two transistor Ts of its final stage
5, T
6Emitter meet positive source+E and negative pole-E respectively.
In Fig. 3, for the multiple tube (top dashed rectangle) of positive half cycle work, transistor T
1Base stage as the base stage (B) of this multiple tube, transistor T
1Emitter as the emitter (E) of this multiple tube, transistor T
5Emitter as the collector electrode (C) of this multiple tube.At the multiple tube of negative half period work (below dashed rectangle) roughly the same.
As can be seen from Figure 4, the circuit of embodiment of the present invention one is the final stage transistor T at 3 circuit
5, T
6Two current samplers of serial connection in the collector loop
(Fig. 6 and Fig. 7): at current sampler
Common junction and front stage transistor (T
1, T
2) emitter, penultimate stage transistor T
3, T
4Be connected to a phase corrector between the collector electrode
(Figure 10); At current sampler
Output and variable bias device
Control end between be connected to a "AND" circuit
(Fig. 8); At two transistor Ts of prime
1, T
2Base stage between be connected to a variable bias box
(Fig. 9), its mid point V
iConnect signal source, its bias voltage numerical value can be by control terminal K
1, K
2Control.
As can be seen from Figure 5, the circuit of embodiment of the present invention two is consistent basically with its scheme one circuit, and its difference is at its circuit penultimate stage transistor T
3, T
4Be serially connected with two current samplers that structure is identical in the collector loop
(Figure 11); At its final stage transistor T
5, T
6Collector electrode and current sampler
Common junction, front stage transistor T
1, T
2Between the emitter, be serially connected with a phase corrector
(Figure 10).
In Fig. 4, current sampler
Circuit, as shown in Figure 6, it is by resistance R
7With voltage-stabiliser tube D
1Be formed in parallel D
1Negative pole be called Q
1End connects transistor T
5Collector electrode, D
1Negative pole double as also
Output q
1, D
1Positive pole be called Q
2, meet the output V of this compound emitter follower
o, resistance R
7Resistance is selected 10-50 Ω for use.D
1Zener voltage select V for use
2=1～3V, D
1Current capacity greater than transistor T
5Maximum current.
Current sampler
Circuit, as shown in Figure 7, by resistance R
8With voltage-stabiliser tube D
2Be formed in parallel D
2Negative pole be Q
3End meets output V
o, D
2Just very Q
4End connects transistor T
6Collector electrode, D
2Positive pole go back double as
Output q
4, R wherein
8=R
7, D
2With D
1Same model.
Current sampler
Output voltage and the relation between the sampled electric current be non-linear.
"AND" circuit
(Fig. 8) by a NPN small-power silicon transistor T
7With a PNP small-power silicon transistor T
8And four resistance R
3R
4R
5R
6Form R
7Emitter meet R
3An end, T
8Emitter meet R
3The other end, R
7Base stage meet R
4An end meet R again
5An end, T
8Base stage meet R
4The other end meet R again
6An end, R
5The other end claim Y
1End connects current sampler
Q
1End, R
6The other end claim Y
2, connect current sampler
Q
4End, transistor T
7Collector electrode claim C
7End connects the variable bias device
B
1End (Fig. 9), transistor T
8Collector electrode claim C
8End connects the variable bias device
B
2End, wherein R
3=10-20 Ω, R
4=0.5-1k Ω, R
5=R
6, R
6Value should satisfy following formula:
（ (V
2R
4)/2.4 - 1/2 R
4）＜R
6＜（V
2R
4-0.6R
4）/1.2
This is a kind of complementary differential amplifier of modification originally, borrows now to claim that it is a "AND" circuit, and be because following reason: if NPN pipe T
7Base potential just become and PNP pipe T
8Base potential to become negative the existence simultaneously (be T
7With T
8Input is all arranged), T so
7, T
8Collector current will increase together.
Variable bias device in Fig. 4 circuit
, as shown in Figure 9, by dc constant current power supply I
1, I
2And resistance R
1, R
2Be composed in series, the order of series connection is followed successively by I
1, R
1, R
2, I
2, R
1On also be parallel with capacitor C
1, R
2On also be parallel with capacitor C
2, I wherein
1, R
1, C
1Tie point be called terminal b
1, I
2, R
2, C
2Tie point be called terminal b
1, R
1, R
2, C
1, C
2Tie point be called terminal V
i, constant-current source I
1Electric current flow into termination power positive pole, constant-current source I
2Electric current flows out termination power cathode, wherein I
1=I
2=2-6mA, R
1=R
2=(0.6V)/((I
1-/m
A) C
1=C
2=100-500 μ F.
The variable bias device
Terminal b
1Transistor T in map interlinking 4. circuit
1Base stage, its b
2Termination transistor T
2Base stage, its V
iTermination signal source U
ib
1End and b
2End is also distinguished double as variable bias device
Control terminal K
1And K
2
Phase-correcting circuit
, as shown in figure 10, by an inductance L and resistance R
9Be formed in parallel, one of them terminal is called J, and another terminal is called J ', and wherein L=1-5 μ H and its D.C. resistance are zero, R
9=3 Ω-15 Ω.Its terminal J connects transistor T
1, T
2Emitter, transistor T
3, T
4Collector electrode, its another terminal J ' meets output V
oBecause phase corrector
D.C. resistance be zero, so transistor T
1, T
2Emitter to load R
1Between D.C. resistance also be null value.
Current sampler in Fig. 5 circuit
With
Circuit, as shown in figure 11.They are by the resistance R of a 20-100 Ω
10With a voltage-stabiliser tube D
3Compose in parallel D
3Zener voltage be 1-3V, as long as current capacity is greater than transistor T
3Maximum collector current get final product.
Phase corrector in Fig. 4 circuit
In audio range, can be considered short circuit, current sampler
During work sound signal is presented very little resistance, and they are connected on transistor T
5Or T
6In the collector loop, and the collector electrode output resistance is higher comparatively speaking, seemingly is equivalent to small resistor of constant-current source series connection so nearby, still is original constant-current source for the effect of sound signal.
Variable bias device in this circuit
Resistance R
1, R
2, its resistance value ratio transistor T
1, T
2The little several magnitude of input resistance resistance, can ignore, so draw transistor T
1, T
3, T
5For the sound signal that is exaggerated positive half cycle formed a NEW TYPE OF COMPOSITE pipe, shown in the dotted line block diagram above among Fig. 3; Transistor T
2, T
4, T
6The negative half period of sound signal has been formed another multiple tube, shown in the dashed rectangle below Fig. 3.Has only a PN junction between the base stage of every NEW TYPE OF COMPOSITE pipe and the emitter of this multiple tube, be exactly transistor T
1Or T
2BE knot: the emitter of every multiple tube and load R
LBetween D.C. resistance be zero.With the positive half cycle of sound signal, output voltage U
oWith input voltage U
iBetween only differ transistor T
1BE make friends with stream voltage drop U
BE1That is: U
o=U
i-U
BE1
Owing to flow through transistor T during the amplifier operate as normal
1The alternating current very little (microampere order) of BE knot, so transistor T
1BE make friends with stream voltage drop U
BE1Also very little, U
BE1Can be less than U
oOne thousandth to tens thousand of/one, can ignore U in other words
BE1And obtain: U
o=U
iIt is output voltage U
oBe similar to very much input voltage U
i, distortion is very little in other words.During negative half period by transistor T
2, T
4, T
6The multiple tube work of forming, they respectively and transistor T
1, T
3, T
5Complete complementary symmetry connects, and operation principle roughly the same repeats no more.
The output resistance of this follower is also little of the milliohm level, to loud speaker R
LEnough dampings are arranged.
Phase corrector
Effect be to prevent self-excitation, it also is the indispensable significant element of this follower.
The quiescent point electric current of this follower is assigned to keep and stablize by the control part of common mode current, and its principle is to work as transistor T
5During conducting, current sampler
Just have voltage output, work as transistor T
6During conducting, current sampler
Just have voltage output; When
With
There is output signal to deliver to "AND" circuit simultaneously
The time,
Just there is output signal to remove to adjust the variable bias device
Bias voltage numerical value.
For the sound signal that is exaggerated, transistor T
5Conducting, transistor T
6Just end; Transistor T
6Conducting, transistor T
5Just end, so current sampler
With
Can there be output signal to send into "AND" circuit simultaneously
,
Just not having output signal removes the dried variable bias device that gives
For quiescent bias current, transistor T
5And T
6Conducting simultaneously promptly has one " common mode current " to flow through transistor T
5And T
6This a pair of complementary power tube (if this ' common mode current " can not be controlled and will burn pipe).So current sampler
With
Can there be output to deliver to "AND" circuit simultaneously
If this " common mode current " our undesirable increase occurs or when reducing,
Will readjust the variable bias device
Bias voltage numerical value, thereby " common mode current " (quiescent current) of whole compound follower got back on the correct numerical value.
Like this, current sampler
With
And "AND" circuit
Co-operation, just the difference of signal code and common mode current is come, and only removes to adjust biasing circuit, thereby keep and stablized the necessary common mode current of compound emitter follower operate as normal (quiescent point electric current) according to the size of common mode current.
In fact, because the degenerative effect of this common mode current, the power output pipe all can not end on any time of one-period fully, is always keeping a common mode current (for example 10-100mA) and is flowing through transistor T simultaneously
5And T
6, this helps to overcome the switch distortion of efferent duct.Obviously this dynamic current stabilization method obviously is better than tradition quiescent current bias method commonly used.
In Fig. 5 circuit, the current sampling of common mode current control section point is arranged on penultimate stage, so the stable electric current of common mode current negative feedback is the quiescent current of penultimate stage, has also just stablized the quiescent current of final stage power tube simultaneously indirectly.All the other operation principles of this circuit are identical with Fig. 4 circuit, no longer repeat.
Fig. 4, Fig. 5 circuit are compared, and the advantage of Fig. 5 circuit is a current sampler
With
In voltage-stabiliser tube D
3Current capacity can be smaller; Shortcoming is that the final stage power tube thermal stability that might enter complete cut-off region and final stage quiescent current is also so good not as Fig. 4 circuit.
Transistor in the follower of the present invention is silicon transistor.
Comparing with the compound follower of class of compound emitter follower of the present invention and prior art has following advantage:
1, the power amplifier complete machine needn't re-use big loop negative-feedback and just can obtain very low distortion. Such as the THD of 100 watts of model machines＜0.01%(test condition: 20-20KH, 0.1W-100W).
2, has very little output resistance. The damped coefficient of 100 watts of model machines is much larger than 100.
3, transient response is good, and the output voltage climbing speed is fast. The output voltage climbing speed of 100 watts of model machines is greater than 50V/ μ S, if necessary, and the leeway that still is much improved.
4, subjective sense of hearing is fabulous, and the clear soft smoothness of high pitch especially far surpasses general traditional power amplifier.
5, owing to having cancelled big loop negative-feedback, lower to the frequency characteristic requirement of final stage high power valve, be conducive to reduce cost and improve reliability.
6, circuit is uncomplicated, and the cost that only increases seldom just can make existing power amplifier performance commonly used be significantly improved.
7, the present invention also can be integrated, if it is used in the integrated audio power amplifier exclusive disjunction amplifier, can increase substantially their performance.
Usage of the present invention: small-power Class A voltage amplifier and the present invention with a low distortion combine, and just can consist of the novel degenerative high-fidelity audio frequency of no big loop power amplifier.
Claims (3)
1, a kind of complementary common-mode current-stable compound emitter voltage follower is characterized in that its composition comprises:
A, two by six transistors with three be one group, corresponding member manages the Darlington that complete complementary symmetry constitutes separately, its connection method is that two transistorized base stages of prime connect signal source, collector electrode and connect penultimate stage two transistorized base stages, emitters respectively and connect penultimate stage and transistorized collector electrode of final stage and output, and the emitter of penultimate stage transistor connects two transistor bases of final stage respectively, two transistorized emitters of final stage connect positive source and negative pole respectively;
B, two current samplers according to the difference of this follower common mode current control section current sampling point, are serially connected in the above-mentioned final stage transistor collector loop or are serially connected in the above-mentioned penultimate stage transistor collector loop;
C, a phase corrector, be serially connected between two current sampler common junction in the above-mentioned final stage transistor collector loop and above-mentioned front stage transistor emitter, the penultimate stage transistor collector electrode, perhaps be serially connected between two current sampler common junction in above-mentioned final stage transistor collector and the penultimate stage transistor collector loop, the above-mentioned front stage transistor emitter;
D, one be connected between two transistor bases of above-mentioned prime, its mid point connects signal source and variable bias device its bias voltage numerical value controlled terminal control;
E, a "AND" circuit that is connected between above-mentioned two current sampler outputs and the above-mentioned variable bias device control end.
2, according to the follower of claim 1 regulation, have only between the base stage (B) that it is characterized in that its every Darlington and the emitter (E) BE tie D.C. resistance between (PN junction), its emitter (E) and the load be null value, the transistorized signal code of its final stage by its collector electrode output stream to load;
3,, it is characterized in that its working point electric current is stable by the complementary common-mode Current Negative Three-Point Capacitance according to the follower of claim 1 regulation.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN 93100353 CN1025093C (en) | 1993-01-19 | 1993-01-19 | Complementary common-mode current-stable compound emitter voltage follower |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN 93100353 CN1025093C (en) | 1993-01-19 | 1993-01-19 | Complementary common-mode current-stable compound emitter voltage follower |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN1076564A CN1076564A (en) | 1993-09-22 |
| CN1025093C true CN1025093C (en) | 1994-06-15 |
Family
ID=4982969
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN 93100353 Expired - Fee Related CN1025093C (en) | 1993-01-19 | 1993-01-19 | Complementary common-mode current-stable compound emitter voltage follower |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN1025093C (en) |
Families Citing this family (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102545802A (en) * | 2012-02-21 | 2012-07-04 | 长沙学院 | Power tube complementary power amplifier |
| CN104977450B (en) | 2014-04-03 | 2019-04-30 | 深圳市中兴微电子技术有限公司 | A kind of current sampling circuit and method |
| CN105207632B (en) * | 2014-06-01 | 2018-07-20 | 李凤朝 | A kind of power amplification circuit |
| CN104682352B (en) * | 2015-03-05 | 2017-06-16 | 深圳市九洲电器有限公司 | A kind of improved electric power controller |
-
1993
- 1993-01-19 CN CN 93100353 patent/CN1025093C/en not_active Expired - Fee Related
Also Published As
| Publication number | Publication date |
|---|---|
| CN1076564A (en) | 1993-09-22 |
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