CN102468759B - Resonant converter, and resetting method and device thereof - Google Patents
Resonant converter, and resetting method and device thereof Download PDFInfo
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- CN102468759B CN102468759B CN201010538319.1A CN201010538319A CN102468759B CN 102468759 B CN102468759 B CN 102468759B CN 201010538319 A CN201010538319 A CN 201010538319A CN 102468759 B CN102468759 B CN 102468759B
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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Abstract
The invention provides a resonant converter, and a resetting method and a resetting device thereof. The resetting method and the resetting device are used for limiting or eliminating residual energy in a resonant network before the resonant converter is restarted. According to the idea of the invention, an energy resetting module is assembled to the resonant converter and is used for limiting peak current generated in a switching circuit by resetting the residual energy in a resonant circuit of the closed resonant converter after the resonant converter is closed.
Description
Technical field
The present invention relates to a kind of remapping method and device thereof, particularly relate to a kind of remapping method and the device thereof that are applied to resonant converter.
Background technology
Due to the concern for environment and energy resource consumption day by day, consumer constantly seeks the product having more energy efficiency, the designer of electronic product utilizes the flexible topology that switches to improve the usefulness of electronics and electric equipment products, and these products can be run with higher frequency.But switch cost but becomes the obstacle saving power supply, especially when carrying out high frequency and running.For this reason, resonant converter (resonantconverter) can in order to provide zero voltage switching technology, reducing the switch cost that electronic equipment occurs when opening or cut out conversion, can run in higher switching frequency compared to other transducers so as to making it.Resonant converter includes switch element and resonant inductor capacitor network.
Basic switch element by one include with a diode and a transistor parallel connection and the electronic component obtained, as typical power metal oxide semiconductor field-effect transistor (MOSFET).Specifically, resonant converter switches this switch element when switch element is in zero current or no-voltage point, to reduce the stress of switch element and to reduce radio interference.Zero voltage switching (zero-voltage switching, ZVS) refer to the magnitude of voltage when switching on switch be zero or one close to zero low voltage value, just can reduce the consume in Circuits System thus.
Resonant converter is led to when being controlled by the switching frequency changing its switch element.It similarly is that DC turns high frequency AC inverter, resonant mode dc-dc, resonant mode inverter or produces the rectifier, resonant mode AC-DC converter, resonant mode AC-AC transducer etc. of line frequency (line-frequency) AC that common resonant converter comprises.Common application, for example, comprises PC, server, telecommunication system, mobile phone, automobile, Medical Devices, game electronic game and industrial equipment etc.
In some application example, as when this resonant converter restarts, switch element flows through a large peak current.The infringement switch element but this large peak electricity fails to be convened for lack of a quorum, and this peak current is after this resonant converter is closed, by the energy person of causing residual in the resonant network of this resonant converter.
Technological deficiency " known technology summary of the invention
In view of restriction and the defect of known technology, the present invention proposes one " remapping method of resonant converter and device thereof ", with before resonant converter restarts, the rudimental energy limiting or prevent in resonant network, and then solve the insurmountable problem of known technology.
This part outline some feature of the present invention, other features will be described in follow-up paragraph.The present invention is by the definition of additional claim, and it is herein incorporated paragraph as a reference.
Main purpose of the present invention is for providing a kind of remapping method and device of resonant converter, and by before resonant converter restarts, the rudimental energy first limiting or prevent in resonant network, avoids it to cause damage to element in this resonant converter.
For reaching above-mentioned purpose, a better embodiment of the present invention is for providing a kind of remapping method being applied to resonant converter, and it comprises step: close a resonant converter; And by being refitted in the rudimental energy of closing in a resonant circuit of resonant converter, to limit the peak current generated in a switching circuit of this resonant converter.
For reaching above-mentioned purpose, another better embodiment of the present invention is for providing a kind of reset apparatus being applied to a resonant converter, this resonant converter comprises a switching circuit and a resonant circuit, this reset apparatus comprises a control module, be coupled to this switching circuit, and be closed this switching circuit of rear control in this resonant converter, with by being refitted in rudimental energy in buttoned-up resonant converter, and limit the peak current generated in this resonant converter.
For reaching above-mentioned purpose, another better embodiment of the present invention, for providing a resonant converter, comprises a switching circuit, receives an input voltage; One resonant circuit, is coupled to this switching circuit, and comprises a resonant inductance, a resonant capacitance and a magnetizing inductance and to be one another in series connection; One transformer, is coupled to this resonant circuit and receives the output of this resonant circuit; One rectification circuit, is coupled to this transformer, receives the output of also this transformer of rectification to produce the output of this resonant converter; And a driver, being coupled to this switching circuit and controlling this switching circuit, after being closed with this resonant converter, by being refitted in rudimental energy in buttoned-up resonant converter, and limiting the peak current generated in this switching circuit.
The present invention can avoid the problem of the peak current of contactor when restarting, and reaches low consumed effect.
The present invention is illustrated by following accompanying drawing and embodiment, makes clearer understanding.
Accompanying drawing explanation
Fig. 1: it discloses example embodiment assembly of the present invention has energy to reset the block diagram of the resonant converter of module;
Fig. 2 A: it discloses the circuit diagram of the LLC serial-resonant transducer resetting module controls in example embodiment of the present invention with energy;
Fig. 2 B: the waveform schematic diagram that its resonant converter disclosing example embodiment of the present invention runs in a normal mode;
Fig. 2 C: it discloses the waveform amplification schematic diagram of resonant capacitor voltage and resonant inductance electric current in this real example embodiment resonant converter;
Fig. 3 A: it discloses the equivalent circuit diagram of resonant network in example embodiment of the present invention;
Fig. 3 B: it discloses condenser type and switches acquired results schematic diagram;
Fig. 4 A: it discloses the operational flowchart of example embodiment of the present invention;
Fig. 4 B: it discloses in example embodiment of the present invention relative to the operational illustration yet driving flow process in Fig. 4 A;
Fig. 4 C: to disclose in each embodiment mains switch at different drain current (I
d) to draining to source voltage (V
d) operator scheme schematic diagram in pattern;
Fig. 4 D: it discloses the operator scheme schematic diagram of arbitrary switch Q1 ~ Q4 in example embodiment of the present invention;
Fig. 4 E: it discloses the equivalent circuit diagram of example embodiment breaker in middle circuit of the present invention and resonant network;
Fig. 4 F: it discloses the operation chart of reset system when t0=t1 in example embodiment of the present invention;
Fig. 4 G: it discloses the operation chart of reset system when t2=t3 in example embodiment of the present invention;
Fig. 5: it discloses the flow chart limiting or eliminate rudimental energy in resonant network before this resonant converter in example embodiment of the present invention resets;
Fig. 6 A: it discloses tool serial-resonant transducer and energy in example embodiment of the present invention and resets the resonant converter reset system circuit diagram of module;
Fig. 6 B: it discloses this energy in example embodiment of the present invention and resets the element waveform schematic diagram of module;
Fig. 6 C: it discloses the grid voltage waveform schematic diagram of this serial-resonant converter switch under different Dead Time operation in example embodiment of the present invention;
Fig. 7 A: it discloses in another example embodiment of the present invention the resonant converter reset system circuit diagram with a series connection resonant converter and energy replacement module;
Fig. 7 B: it discloses this energy in another example embodiment of the present invention and resets the element waveform schematic diagram of module;
Fig. 7 C: it discloses the voltage waveform view of this serial-resonant converter switch under different R1 operation in another example embodiment of the present invention;
Fig. 8 A: it discloses the resonant converter reset system circuit diagram of tool serial-resonant transducer in example embodiment of the present invention;
Fig. 8 B: it discloses the operating system schematic diagram of the system circuit diagram of Fig. 8 A in example embodiment of the present invention.
Description of reference numerals in above-mentioned accompanying drawing is as follows:
100: resonant converter block diagram
101: resonant converter
103: switch element
105: resonant network
107: energy resets module
200: serial-resonant transducer
201: switching circuit
203: resonant network
205: transformer
207: rectification circuit
220: waveform schematic diagram
240: waveform schematic diagram
300: resonant network equivalent circuit diagram
301: rectangular wave inputs
310: resonant network equivalent circuit diagram
311: rectangular wave inputs
320: resonant network equivalent circuit diagram
330: condenser type switches schematic diagram
400: drive flow process
401: start-up period
403: operated in saturation
405: linear operation
407: drive singal produces
410: operational illustration yet
420: operator scheme schematic diagram
430: operator scheme schematic diagram
431: linear (switch) pattern
433: saturation mode
440: equivalent electric circuit
441: symmetrical rectangular wave input
450: operation chart
460: operation chart
500: flow chart
501 ~ 507: step
600: reset system circuit diagram
610: serial-resonant transducer
620: energy resets module
621: driver
623: control module
625: single end
627: Enable Pin
630: waveform schematic diagram
640: grid voltage waveform schematic diagram
700: reset system circuit diagram
710: serial-resonant transducer
720: energy resets module
721: driver
723: control module
725: single end
727: Enable Pin
729: amplifier
730: waveform schematic diagram
740: voltage waveform view
800: reset system circuit diagram
820: operating system schematic diagram
Cin: input capacitance
Cd: electric capacity
Co: output capacitance
Cr: resonant capacitance
Cs: electric capacity
IQ3: electric current
I
d: drain current
Ir: electric current
Im: electric current
Lm: magnetizing inductance
Lr: resonant inductance
MOSFET: mos field effect transistor
Q1 ~ Q4: mains switch
Q5 ~ Q6: synchronous rectification switch
Qd: switch
Qs: switch
R: resistance
R1 ~ R3: resistance
RL: load
Rd: resistance
Ro: resistance
V
d: source voltage
V
iN: input voltage
V
dS: voltage
V
gS: voltage
V
t: voltage
V
oUT: output voltage
Vc: voltage
Vcc: accessory power supply supply voltage
Vcc_ref: reference voltage
Vcr: initial voltage
Vo: output voltage
Vth: voltage
S1: drive singal
S2: drive singal
T: transformer
T1: Dead Time
T2: Dead Time
ZVS: zero voltage switching
N
2rL: load
T0 ~ t3: time point
T0 ' ~ t2 ': time point
Embodiment
Some exemplary embodiments embodying feature & benefits of the present invention describe in detail in the explanation of back segment.Be understood that the present invention can have various changes in different modes, it does not depart from the scope of the present invention, and explanation wherein and accompanying drawing are in itself when the use explained, and is not used to limit the present invention.
Fig. 1 discloses example embodiment assembly of the present invention has energy to reset the block diagram of the resonant converter of module (energy resetting module), and it in order to consume the dump energy of this transducer before restarting this resonant converter.As shown in the figure, resonant converter 101 is a kind of power supply changeover device being applied to electronic equipment.In one embodiment, this resonant converter 101 includes switch element 103, resonant network 105 and energy replacement module 107.This resonant converter 101 receives input voltage VIN, produce output voltage VO UT, and use the electric capacity of resonant network 105 and inductance whole by the given electric current of switch element 103 or a waveform for voltage to mould, wherein this switch element 103 can be Mosfet, the elements such as IGBT.This resonant network 105 is also referred to as a resonant circuit (resonant circuit) or a resonant slots (resonant tank).In theory, when restarting after this resonant converter 101 is closed, if circuit energy is completely absorbed no current or voltage by this switch element 103.But, as previously mentioned, after this resonant converter 101 of closedown, in this resonant network 105, still remaining energy may be had.And this energy resets the dump energy that namely module 107 is used to consume before this resonant converter 101 starts or replacement remains in this resonant network 105, to limit the peak current of this switch element 103.This energy resets alternative output drive signal S1 and S2 of module 107 to this switch element 103 and/or this resonant network 105 again.
Fig. 2 A discloses the circuit diagram resetting module controls LLC serial-resonant transducer in example embodiment of the present invention with energy.As shown in Figure 2 A, this LLC serial-resonant transducer 200 includes the switching circuit be made up of mains switch Q1 ~ Q4 201, resonant network 203, transformer T 205, and a rectification circuit 207.Wherein, LLC refers in a resonant circuit and includes a resonant inductance Lr, a resonant capacitance Cr, and a magnetizing inductance Lm is one another in series connection.And this resonant converter 200 also includes an input capacitance Cin.This transformer 205 by the secondary side coil of a primary side coil and two series connection by this switching circuit 201 and this resonant network 203 isolated with this rectification circuit 207.In one embodiment, this rectification circuit 207 comprises a pair synchronous rectification switch Q5 ~ Q6, and it is connected to an an output capacitance Co and load RL.In fig. 2, this switch Q5 and Q6 can adopt as MOSFET implements.The source terminal of this switch Q5 and Q6 is connected to the negative electrode (cathode) of this electric capacity Co, and the drain electrode end of the drain electrode end of this switch Q5 and this switch Q6 is connected to this secondary side coil.The common connecting point of two secondary coils is then connected to the anode (anode) of this electric capacity Co and the positive pole of an output voltage Vo.
This resonant converter 200 receives an input voltage vin, and produces an output voltage Vo.This resonant converter 200 has a parameter designing and opereating specification with under guaranteeing that this switch Q1 ~ Q4 works in a zero voltage switching (zero-voltage switching, ZVS) state; Even make this rectifier switch Q5 ~ Q6 work in zero current and switch (zero current switching, ZCS) state.The main function of zero voltage switching makes switch element before opening, guarantees that the voltage on this switch is zero, and then reduces switching losses.
The waveform schematic diagram that the resonant converter 200 that Fig. 2 B discloses example embodiment of the present invention runs in a normal mode.In fig. 2b, a drive singal of S1 representation switch Q1 and Q4, a drive singal of S2 representation switch Q2 and Q3, ir and im then represents the electric current flowing through this resonant inductance Lr and this magnetizing inductance Lm respectively.When switch Q1 and Q2 is closed, im value is respectively Im and-Im.Vc is the voltage of this resonant capacitance Cr.The reference direction of ir, im and Vc is then disclosed in Fig. 2 A.Difference between ir and im is the primary side current of this transformer T.In A and B of region, energy is sent to primary side by primary side.In addition, this exciting curent im is more or less the same under a light-load conditions and a heavy load condition.
At time point t0 ', because primary side current ir is contrary in its reference direction, switch Q1/Q4 opens under zero voltage condition.And the interval between time point t0 ' and t1 ', rectifier switch Q6 conducting, does not therefore participate in resonance at this magnetizing inductance, so this exciting curent im linearly increases.Due to the resonance between Lr and Cr, presented with quasi sine (quasi-sine) waveform by the current i Q6 of Q6.Close at time point t1 ', Q6, because switch periods is longer than the harmonic period between Lr and Cr, make before Q1/Q4 is closed, ir falls progressively to im.Then, Cr, Lr and Lm participate in resonance.In order to simplify parsing, suppose Lm > > Lr, then Ir in t1 ' to t2 ' between about in a straight line.Close at time point t2 ', Q1/Q4.And in time point t3 ', Q2/Q3 then no-voltage unlatching.In the interval of the interval of t3 ' to t4 ' and t4 ' to t5 ', also can as front parsing.The mode of operation of electric current I Q5 and waveform are all identical with IQ6.IQ5 and iQ6 forms output rectified current.Three shut-in times that waveform schematic diagram 220 in Fig. 2 B also discloses when this resonant converter is closed put t1, t2 and t3.Certainly this resonant converter can be put in any time and be closed.
In fig. 2, opening and turning off produce a rectangular wave between A point and B point by switch Q1 ~ Q4, and be provided to resonant circuit 203.If circuit working is at resonant frequency point, then the electric current of this resonant circuit 203 is then close to a sine curve.Between A point and B point, this sinusoidal current waveform lags behind voltage waveform between this A point and B point, so when voltage waveform reaches its zero crossing, current value is still negative value, thus reaches zero voltage switching.
Fig. 2 C discloses the waveform amplification schematic diagram 240 of resonant capacitor voltage and resonant inductance electric current in example embodiment resonant converter 200 of the present invention.When this resonant converter 200 (i.e. transducer after t0 ' not to its load conveying capacity) after time point t0 ' (shut-in time point 241) closes, restart (i.e. transducer after t1 ' again to its load conveying capacity) in time point t1 ' (replacement time point 243).Certainly, this resonant converter can be restarted immediately after closedown, i.e. time point t0 '=t1 ', makes time interval 245 be zero.And it is poor to there is the regular hour between the time point restarted in typical circumstances and shut-in time point, i.e. t1 ' > t0 '.After time point t1 ', the voltage Vc of resonant capacitance Cr then vibrates along oscillation center 247, and decays by a certain magnitude of voltage and in several duty cycle, decay to zero, as being down to 0v from 120v.Fig. 2 C is labeled with the first duty cycle 249.As shown in Figure 2 C, no matter when this resonant converter 200 is being closed (as at time point t0 '), in resonant network 203, has rudimental energy stay.This rudimental energy be present in this Cr and/or Lr cannot be consumed fast.Therefore, this resonance current Ir has a direct current biasing (DC bias).If this resonant converter 200 restarts between time interval t1 '-t2 ', then the direct current biasing because of ir is produced high current peak and causes circuit to damage by switch Q1/Q4 or Q2/Q3.Therefore, before this resonant converter 200 of replacement, be necessary first to solve this special problem.
Fig. 3 A discloses the equivalent circuit diagram of resonant network in example embodiment of the present invention.The equivalent electric circuit 300 of this resonant network 203 is in order to analyze this operation of resonant network 203 between time interval t1 and t2.This circuit 300 has one and to be produced by this switching circuit 201 and to have the symmetrical rectangular wave input 301 of certain value (as +/-400v).For simulating the operation of this resonant network 203, this equivalent electric circuit 300 can be further divided into two equivalent electric circuits 310 and 320.This circuit 310 has a symmetrical rectangular wave input 311, but without the initial voltage Vcr of this resonant capacitance and the initial current Ir of this resonant inductance.On the other hand, this circuit 320 has initial voltage Vcr or initial current Ir, but does not have input signal.In circuit 320, this initial voltage Vcr and initial current Ir can be reset within the switching manipulation time.The resonance current of circuit 300 then comprises the reset current of circuit 320 and the switching current of this circuit 310.
This circuit 310 and 320, by general business software, as the SIMULINK in MATLAB, provides the simulation waveform of this voltage Vcr and this electric current I r.In the simulation, this resonant converter 200 restarts in time point t1 '.Fig. 2 C discloses in example embodiment of the present invention, the resonant capacitor voltage Vcr of this resonant converter 200 and the waveform 240 of resonant inductance electric current I r.After time point t1 ', this voltage Vcr is vibrated by a certain magnitude of voltage (as 120v) and declines, and this electric current I r has a direct current biasing in this process.Due to the direct current biasing of this electric current I r, this switch Q1-Q4 need bear capacitive switch result.Fig. 3 B then discloses the schematic diagram 330 that capacitive switches.For example, when Q1 opens, the body diode of Q3 just flows through electric current.Again because Q1, Q3 are in same brachium pontis, therefore, capacitive switching result makes meeting circuit for generating short circuit and produces very large loss in this condition, and this may damage switch Q1 ~ Q4.As shown in Figure 3 B, namely the simulated current peak value of the simulation of this electric current I Q3 may be greatly increased (as more than 20A) in a short time.
For solving this problem, the driving flow process 400 that an energy resets module 107 is imported into first reset this resonant network energy before restarting this resonant converter 200.As shown in Figure 4 A, it discloses the operational flowchart of example embodiment of the present invention.In particular, drive flow process 400 by a start-up period 401, and judge whether to close this resonant converter 200.If judge, this resonant converter 200 is by maintenance work state (as before time point t0), then this driving flow process 400 can make this transducer work in a linear working state 405.If judge, this resonant converter 200 is closed (as between time interval t1 ~ t2), then this driving flow process 400 can make this transducer work in a saturated 403, to consume the energy of resonant network.Then, step 407 according to step 403 or 405 Output rusults, produce drive singal S1 and S2 to Q1 ~ Q4.Fig. 4 B discloses the operational illustration yet 410 relative to Fig. 4 A flow process 400 in example embodiment of the present invention.Work in saturation condition in step 403 (between time interval t1-t2) switch Q1 ~ Q4, and work in linear condition with switch Q1 ~ Q4 in step 405 (place of time point < t0 and > t3).
Fig. 4 C is the drain current (I of a switch (as MOSFET) in each embodiment
d) and drain to source voltage (V
dS) relation schematic diagram 420.Linearly the boundary of (ohm) pattern and saturation mode is with the bending parabola (V of a rising
dS=V
gS-V
t) represented by.In linear model, when this MOSFET is in conducting state, this MOSFET is as a very little resistance (in full to hundreds of m Ω).
Linear model: work as V
gS> Vth and VDS < (VGS-Vth).
And under being in saturation mode, when MOSFET conducting, it is just as a rheostat (rheostat), being controlled by its gate-source voltage, it has very large resistance (in full to hundreds of or thousands of Ω).
Saturation mode: work as V
gS> Vth and V
dS> (V
gS-Vth).
Fig. 4 D discloses the operator scheme schematic diagram 430 of arbitrary switch Q1 ~ Q4.In linear (switch) pattern 431, for example, Q3, as a switch application, is controlled its turn-on and turn-off by the drive singal in its gate-source, and Q3 has very little conduction resistance value (in full to hundreds of m Ω).And in a saturation mode 433, Q3 as a rheostat, by the horizontal V of different gate-source voltage
gS(as 2-20V) control its conduction resistance value, and there is large resistance value (as being greater than dozens of Ω).For the simulation operation of Q1 ~ Q4 under saturation mode 433, this switching circuit 201 and resonant network 203 change and represent with the equivalent electric circuit 440 shown in Fig. 4 E, and as shown in the figure, this equivalent electric circuit 440 includes a load Q1/Q2, a load Q3/Q4, and a load n
2rL, wherein this load Q1/Q2 or Q3/Q4 represents Q1 ~ Q4 resistance value in a saturated mode.This equivalent electric circuit 440 has the symmetrical rectangular wave produced by switching circuit 201 and inputs 441.Under saturated, Q1 ~ Q4 with the pattern of such as large resistance by V
gScontrolling run, but not run as switch.Therefore, saturation mode can limit the electric current flowing through Q1 ~ Q4, and consumes resonant energy as resistance.This flow process 400 just can be avoided generation current spike problem on switch had previously been discussed.
Any time point after saturation operation mode (step 403) between time interval t1 to t2 can put t0 in the shut-in time and between restarting before time point t3 occurs.Fig. 4 F discloses the operation chart 450 of system 400 when t0=t1 in example embodiment of the present invention.In this embodiment, this resonant converter 200 is opened at once immediately and is entered saturation operation mode after time point t0 is closed.Fig. 4 G then discloses the operation chart 460 of system 400 when t2=t3 in example embodiment of the present invention.In this embodiment, this resonant converter 200 works in saturation mode with the energy consumed in circuit and is reopened at time point t3 (t2) between time interval t1 to t2 (t3).After the t3 moment, this resonant converter 200 can be restarted under zero initial condition, and the problem not having capacitive to switch produces.
Fig. 5 discloses the flow chart 500 limiting or eliminate rudimental energy in resonant network before this resonant converter in example embodiment of the present invention resets.For example, this flow process 500 can reset module 107 by energy and performs.Such as, in step 501, this energy resets module 107 and closes a resonant converter.In step 503, this energy resets module 107 and limits by the rudimental energy reset in this resonant converter resonant circuit the peak current betided in this resonant converter switching circuit.This energy resets module 107 and consumes rudimental energy by being controlled in one or more resistance in this resonant converter.In one embodiment, in this resonant converter, controlled one or more resistance is included in a saturation mode the one or more switches (as Q1 ~ Q4) operated.This one or more switch element is driven (by a driver) by providing a drive singal and goes to control this switch in saturation mode by the duty ratio controlling this drive singal, and wherein the duty ratio of the drive singal of this switch element is in a saturated mode than little under normal mode (as when under transducer is operated in linear model).This one or more switch element is also gone operation control to work in saturation mode by reducing a driving voltage by driving, wherein in a saturated mode this driving voltage belonging to switch element circuit lower than running in a normal mode.In another embodiment, in this resonant circuit, one or more resistance also can be removed consumed energy by control.The embodiment that can disclose see Fig. 8 A.This one or more resistance is connected into resonant network with after a switch element parallel connection, makes resistant series enter resonant network to consume the residual amount of energy of resonant network by controlling the shutoff of this switch element.Last in step 505, this energy resets module 107 and opens this resonant converter after rudimental energy in resetting to have closed in resonant circuit.
And aforesaid flow process causes Q1 ~ Q4 to be able to run in a saturated mode between time interval t1 to t2, and will be described in further detail in rear.Fig. 6 A discloses tool serial-resonant transducer and energy in example embodiment of the present invention and resets the circuit diagram of the resonant converter reset system 600 of module.This serial-resonant transducer 610 has the element that resonant converter 200 is identical as shown in Figure 2 A, this energy reset module 620 then according to as in Fig. 4 A to Fig. 4 G the identical process flow operation that discloses.This energy resets module 620 and has driver 621, resonant converter control module 623 and an accessory power supply Vcc, and wherein this driver 621 drives Q1 (Q4) and drive singal S2 to go to drive Q2 (Q3) in order to provide a drive singal S1 to go.Before restarting this serial-resonant transducer 610, the drive singal that this energy replacement module 620 provides a little duty ratio works in saturation mode with control Q1 ~ Q4.Especially, a single input (one-shot pin) 625 of this control module 623 removes control one Dead Time (deadtime), and an Enable Pin 627 of this control module 623 removes the magnitude of voltage of control Vcc.For example, by ON
manufactured MC33607 can as the use of this resonant converter control module 623.
Fig. 6 B discloses this energy in example embodiment of the present invention and resets the waveform schematic diagram 630 of module 620.At this serial-resonant transducer 610 after time point t0 closes, an enable voltage Ven is provided to this control module 623 by this Enable Pin 627.This Enable Pin 627 is connected to the grid of a switch Qd by a resistance Rd and an electric capacity Cd.This accessory power supply Vcc is then connected to Qd and Qs by a resistance R1.
Acting as of this single end 625 makes output signal S1 and S2 be in low level simultaneously, to provide the Dead Time between S1 and S2.This single end 625 is connected in parallel to ground wire by a resistance Ro, an electric capacity Co and an electric capacity Cs (contacting with Qs).
Fig. 6 B discloses the waveform of an enable voltage, switch Qs grid voltage and switch Qd grid voltage in the embodiment of the present invention.In linear mode operation, this single terminal voltage is controlled to provide a normal Dead Time, and the output switch of enabling signal S1 and S2, namely main electrical current starts to be reversed before change polarity simultaneously.For no-voltage mode of resonance, this converter switch cycle is set and is equal to or more than this single cycle.
Under working in saturation mode for making this switch Q1 ~ Q4, Qs opens between time interval t0-t1, and the Co of Ro and parallel connection, Cs determine a Dead Time T2, and it is greater than a normal Dead Time T1.Fig. 6 C discloses the grid voltage waveform schematic diagram 640 of this serial-resonant transducer 610 switch Q1 ~ Q4 under different Dead Time operation in example embodiment of the present invention.Under the situation of identical operating frequency, larger Dead Time T2 makes the duty ratio of output signal S1 and S2 be less than the duty ratio under normal Dead Time T1 situation, thus makes driving voltage value at S1, S2 at larger Dead Time to the magnitude of voltage level (as 12v) lower than (i.e. normal Dead Time T1) under normally working.Therefore, lower driving voltage (as ~ 4v) make Q1 ~ Q4 enter this saturation mode.After time point t1, Qs closes, and the Dead Time T1 under the given normal condition of Ro and Co, this normal Dead Time T1 make the magnitude of voltage of signal S1 and S2 be in a normal voltage levvl (as 12v).Whereby, after reopening, the electric current I Q1 of the switch Q1 of this serial-resonant transducer 610 has a small leak electric current, and as a peak current value is less than 10A, it is caused by large T2 dead time (i.e. a little driving load).In other words, previous embodiment makes this peak current IQ1 be reduced to a smaller value (as being less than 10A) by a high value (as being greater than 20A) by the larger Dead Time of configuration one.
Fig. 7 A discloses in another embodiment of the present invention the resonant converter reset system circuit diagram 700 with a series connection resonant converter and energy replacement module.This serial-resonant transducer 710 has the element that resonant converter 200 is identical as shown in Figure 2 A.This energy reset module 720 then according to as in Fig. 4 A to Fig. 4 G the identical process flow operation that discloses.This energy resets module 720 and has driver 721, resonant converter control module 723 and an accessory power supply Vcc, and wherein this driver 721 drives Q1 (Q4) and drive singal S2 to go to drive Q2 (Q3) in order to provide a drive singal S1 to go.Disclose different being from Fig. 6, the energy in Fig. 7 A resets module 720 and borrows control Vcc voltage and directly reduce the driving voltage of Q1 ~ Q4 drive singal and make Q1 ~ Q4 work in saturation mode.Especially, before restarting this serial-resonant transducer 710, this energy resets module 720 controlling resistance R1 and removes control Vcc voltage.
Fig. 7 B discloses this energy in another example embodiment of the present invention and resets the waveform schematic diagram 730 of module 720.At this serial-resonant transducer 710 after time point t0 closes, an enable voltage Ven is provided to this control module 723 by an Enable Pin 727.This Enable Pin 727 is connected to the grid of a switch Qd by a resistance Rd and an electric capacity Cd.One single end 725 is connected in parallel to ground by a resistance Ro and an electric capacity Co.Between time interval t0 to t1, the Dead Time in saturated mode operation remains identical with Dead Time T1 normal in linear mode operation.This accessory power supply Vcc is then connected to the inverting input of an amplifier 729 by a resistance R3, and reference voltage Vcc_ref is then connected to amplifier 729 in-phase input end.Fig. 7 C discloses the voltage waveform view 740 of this serial-resonant transducer 710 switch Q1 ~ Q4 under different R1 operating and setting in example embodiment of the present invention.Before time point t0, Qd conducting makes R1 be shorted, and accordingly, Vcc is determined by R2 and R3.And between time interval t0 to t1, Qd turns off, Vcc is determined by R1, R2 and R3.For example:
When Qd conducting,
Vcc＝Vcc_ref*(R2+R3)/R2＝12v (1)
When Qd turns off,
Vcc＝Vcc_ref*(R2+R3+R1)/(R2+R1)＝4v (2)
Because S1 and S2 voltage peak between time interval t0 to t1 is only 4v, switch Q1 ~ Q4 will run to consume resonant slots energy as resistance.Due to lower driving voltage effect, the peak current value of its breaker in middle (as Q1) is lowered as reduced to lower than 10A.The peak current of switch Q1 ~ Q4 also can be reduced to a smaller value (as being less than 10A) by a higher value (as being greater than 20A) by above-described embodiment.
Fig. 8 A discloses the resonant converter reset system circuit diagram 800 in example embodiment of the present invention with serial-resonant transducer.Because this embodiment does not need special converter control method, the control system (not shown) of any existence all combining to serial-resonant transducer.One large resistance is added into this serial-resonant transducer to consume resonant slots energy.For example, a resistance R and this resonant slots 203 are connected in series, and a switch Qs is then in parallel with this resistance R.This resistance R can be made up of one or more resistance.Fig. 8 B discloses the operating system schematic diagram 820 of the system circuit diagram 800 of Fig. 8 A in example embodiment of the present invention.In this embodiment, this serial-resonant transducer circuitry 800 includes a driver, and this driver also includes a control module and is coupled to this resistance R and switch Qs.Between time interval t1 to t2, (1), when Q1/Q4 closes, Q3/Q2 is unlocked; Or (2) when Q3/Q2 closes, Q1/Q4 is unlocked.Meanwhile, this switch Qs is closed (namely opening a way (open)) by this control module, and this resistance R consumes resonant slots energy under Q1 ~ Q4 is in normal operating state.After the t3 moment restarts this resonant converter, Qs start by control module (i.e. closed circuit (close)) with by this resistance R short circuit.
The demonstration system of disclosed discussion and application technology consume the short-cut method of resonant converter circuit interior resonance groove energy before can being provided in restart resonant converter.Reset module 107 by this resonant circuit 101 of assembly and an energy, this resonant converter can before restarting, the energy that restriction or elimination remain in resonant network.Therefore, example embodiment of the present invention meet change frequency scope with design consider under, the problem of the peak current of contactor can be avoided when restarting, and reach low consumed effect.
Aforesaid advantage all can be overlapped in the assembly for resonant converter, comprises as LLC, LCC, parallel connection, series connection, series parallel resonance and combination person thereof, but is not limited to this.Moreover, be described in reset before resonant converter at this and control the DC current gain of resonant converter to consume the program of the resonant slots energy of resonant converter, more further by software, hardware, firmware or can perform in conjunction with software and/or firmware and/or hardware.By this program, namely the rudimental energy in resonant network is effectively limited and is eliminated before replacement resonant converter.And also can application specific integrated circuit (Application Specific Integrated Circuit in the program described in this, ASIC) and field programmable gate array (FieldProgrammable Gate Array, FPGA) etc. reach.
The technology of the present invention has practicality, novelty and progressive, files an application in accordance with the law.Even if the present invention has been described in detail by the above embodiments and can have been appointed by those skilled in the art and execute craftsman and to think and for modifying as all, but de-as the scope of attached claim institute for protecting.
Claims (17)
1. be applied to a remapping method for resonant converter, it comprises step:
Close a resonant converter; And
The rudimental energy of closing in a resonant circuit of resonant converter is refitted in by controlling one or more resistance in this resonant converter, to limit the peak current generated in a switching circuit of this resonant converter, wherein be closed period at this resonant converter, this resonant converter stops transmitting energy to load end.
2. remapping method as claimed in claim 1, wherein controls one or more resistance in this resonant converter and also comprises the following step:
One or more switch elements of this switching circuit are worked in a saturation mode.
3. remapping method as claimed in claim 2, wherein make one or more switch elements of this switching circuit run in a saturation mode also to comprise the following step at least one of them:
There is provided a drive singal of this switching circuit, when making it run in a saturation mode, the duty ratio of this drive singal is less than the duty ratio of this drive singal when running in a normal mode; And
Reduce the driving voltage delivering to this switching circuit, when running in a saturation mode to make this switching circuit, this driving voltage is less than driving voltage when it runs in a normal mode.
4. remapping method as claimed in claim 1, also comprises step:
After being refitted in the rudimental energy of closing in resonant circuit, reset this resonant converter.
5. be applied to a reset apparatus for a resonant converter, this resonant converter comprises a switching circuit and a resonant circuit, and this reset apparatus comprises:
One control module, be coupled to this switching circuit, and be closed this switching circuit of rear control in this resonant converter, with by being refitted in rudimental energy in buttoned-up resonant converter, and limit the peak current generated in this resonant converter, wherein be closed period at this resonant converter, this resonant converter stops transmitting energy to load end;
Wherein this control module is by controlling in this resonant converter one or more resistance to consume this rudimental energy.
6. reset apparatus as claimed in claim 5, in this resonant converter of wherein said control, one or more resistance also comprises the following step:
One or more switch elements that this control module controls in this switching circuit run in a saturation mode.
7. reset apparatus as claimed in claim 5, wherein this resonant circuit also comprises one or more resistance, an electric capacity, an inductance and a switch element, wherein this resistance is connected with this electric capacity and this inductance, this switch element and this resistor coupled in parallel, this control module is closed this switch element of rear control in this resonant converter, to reset rudimental energy in buttoned-up resonant converter.
8. reset apparatus as claimed in claim 6, wherein this control module assembly makes one or more switch elements of this switching circuit run in a saturation mode, its through the following steps at least one of them:
There is provided a drive singal of this switching circuit, when making it run in a saturation mode, the duty ratio of this drive singal is less than the duty ratio of this drive singal when running in a normal mode; And
Reduce the driving voltage delivering to this switching circuit, when running in a saturation mode to make it, this driving voltage is less than driving voltage when running in a normal mode.
9. reset apparatus as claimed in claim 5, this resonant converter also comprises:
One transformer, is coupled to this resonant circuit and receives the output of this resonant circuit; And
One rectification circuit, is coupled to this transformer, receives the output of also this transformer of rectification to produce the output of this resonant converter.
10. reset apparatus as claimed in claim 5, wherein this resonant converter is one or its combination of a LLC resonant converter, a LCC resonant converter, a resonant converter in parallel, a series connection resonant converter.
11. 1 resonant converters, comprise:
One switching circuit, receives an input voltage;
One resonant circuit, is coupled to this switching circuit, and receive the square-wave signal that this switching circuit produces, wherein this resonant circuit comprises at least one resistance;
One transformer, is coupled to this resonant circuit and receives the output of this resonant circuit;
One rectification circuit, is coupled to this transformer, receives the output of also this transformer of rectification to produce the output of this resonant converter; And
One driver, be coupled to this switching circuit and this resonant circuit and control this switching circuit or this resonant circuit, with after this resonant converter is closed, by being refitted in rudimental energy in buttoned-up resonant converter, and limit the peak current generated in this switching circuit, wherein be closed period at this resonant converter, this resonant converter stops transmitting energy to load end, wherein this driver comprises a control module, and this control module is by controlling this at least one resistance in this resonant converter to consume this rudimental energy.
12. resonant converters as claimed in claim 11, wherein this control module controls this switching circuit, and is closed this switching circuit of rear drive in this resonant converter, makes it run in a saturation mode.
13. resonant converters as claimed in claim 12, wherein this control module controls a drive singal of this switching circuit, by controlling a Dead Time of the drive singal of this switching circuit, and short when when this resonant converter is run in a saturation mode, the duty ratio of this drive singal works in a normal mode than this transducer.
14. resonant converters as claimed in claim 12, wherein this control module controls to a driving voltage of this switching circuit, little when working at a normal mode than this transducer to make its this driving voltage when a saturation mode.
15. resonant converters as claimed in claim 11, wherein this resonant circuit also includes:
One resonant inductance, is connected with this at least one resistant series;
One resonant capacitance;
At least one switch, is connected with this at least one resistor coupled in parallel; And
Wherein this control module is coupled to this at least one resistance and this at least one switch.
16. resonant converters as claimed in claim 15, wherein this control module is after this resonant converter is closed, and closes this at least one switch, makes the energy in this this resonant circuit of at least one resistance consumption; And this control module opens this at least one switch, with under one zero initial conditions, restart a normal running.
17. resonant converters as claimed in claim 11, wherein this resonant converter is a LLC resonant converter, a LCC resonant converter, a resonant converter in parallel, a series connection resonant converter one or a combination set of.
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| US5712772A (en) * | 1995-02-03 | 1998-01-27 | Ericsson Raynet | Controller for high efficiency resonant switching converters |
| US6344979B1 (en) * | 2001-02-09 | 2002-02-05 | Delta Electronics, Inc. | LLC series resonant DC-to-DC converter |
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| EP2176944B1 (en) * | 2007-07-04 | 2016-10-19 | Nxp B.V. | Standby operation of a resonant power converter |
| EP2201669B1 (en) * | 2007-09-18 | 2017-06-21 | Nxp B.V. | Control method for a half bridge resonant converter for avoiding capacitive mode |
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| US5712772A (en) * | 1995-02-03 | 1998-01-27 | Ericsson Raynet | Controller for high efficiency resonant switching converters |
| US6344979B1 (en) * | 2001-02-09 | 2002-02-05 | Delta Electronics, Inc. | LLC series resonant DC-to-DC converter |
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