CN102215192B - Analog-digital mixed channel selection filter - Google Patents
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- CN102215192B CN102215192B CN201110122850.5A CN201110122850A CN102215192B CN 102215192 B CN102215192 B CN 102215192B CN 201110122850 A CN201110122850 A CN 201110122850A CN 102215192 B CN102215192 B CN 102215192B
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Abstract
The invention provides an analog-digital mixed channel selection filter in the technical field of digital communication. The analog-digital mixed channel selection filter comprises an amplification receiving module positioned in an analog domain, a frequency conversion module, a low-pass and analog-to-digital conversion module and a digital processing module which is positioned in a digital domain, wherein an input end of the amplification receiving module receives a radio frequency input signal and outputs the amplified radio frequency input signal to the frequency conversion module; the frequency conversion module outputs an analog baseband signal and is connected with an input end of the low-pass and analog-to-digital conversion module; the input end of the low-pass and analog-to-digital conversion module receives the analog baseband signal and outputs a baseband digital signal to the digital processing module; and the digital processing module outputs the digital baseband signal. In the invention, by using a simple low-order RC (Radio Control) low-pass filter as an analog filter, the dimension of a chip is effectively reduced, the power consumption is reduced and design and process requirements of the analog filter are largely simplified.
Description
Technical field
What the present invention relates to is a kind of device of digital communication technology system, specifically a kind of analog-digital mixed channel selection filter.
Background technology
Radio digital communication system, particularly as digital tv ground broadcasting, is the information for transmission broadband, High Data Rate coding.In concrete digital television broadcasting application, for example United States of america digital television standard A TSC broadcast, the DVB-T of the broadcast standard of Europe Digital Television, Europe digital TV hand-held broadcast standard DVB-H, China Digital TV terrestrial broadcasting standard CTTB, and China Mobile multimedia broadcasting standard C MMB, various standard definitions various channel width, as ATSC, DVB-T, DVB-H, CTTB, CMMB, the channel width of different system is not from 2MHz to 8MHz etc.And in most standard, digital television signal particularly, no matter in VHF frequency range or at uhf band, channel division is continuous.Therefore, the channel of required use always has adjacent channel to exist, and adjacent channel power may be better than used channel.Therefore, need a channel selection filter to carry out the outer interference signal of filtering band.
In direct conversion tuner, conventional low pass filter completes channel and selects to filter.A lot of utilization resistance and electric capacity are before built multistage simulation low-pass filter.If need compatible different bandwidth, also need resistance and the capacitance of many groups, thereby arrive by switching over the cut-off frequency that different groups change filter.Meanwhile, due to the otherness of CMOS technique, even the filter of same bandwidth, its actual bandwidth also difference slightly in Different Individual, therefore also needs to adopt collimation technique conventionally.So-called calibration, is exactly first to generate the test tone that a frequency is filter cutoff frequency, is input to this filter, and then measures in the output of filter, thereby determine that the actual frequency of this filter responds.If test result has difference with designing requirement, also need to switch between adjacent resistance or capacitor value with switch, to meet the accurate requirement to filter cutoff frequency.
There are a lot of problems in such method, first, due to the consideration of the size of chip, the exponent number of simulation low-pass filter is usually very limited, thereby therefore the performance that neighboring trace suppresses is also restricted; Secondly in design, the existence of large electric capacity makes the overall dimensions of chip larger, and power consumption is corresponding increasing also; In addition, calibration process normal signal need to be interrupted, so this method be not suitable for the occasion becoming when any; The demand of different bandwidth and the introducing of calibration process have also increased extra chip area greatly.
Through the retrieval of prior art is found, Chinese patent literature CN100379146C, Granted publication day 2008-4-2, recorded a kind of " tuner that comprises selective filter ", this technology has been used the filter of dual resonance frequency in tuner, object is better to eliminate the residual frequency content of the channel adjacent with selected channel, and keeps band internal linear frequency response preferably.But remaining, this technology only passes through simulation means, for example by building RC filter, complete frequency and select, and in order to reach better filtering performance, for example, the filter of design dual resonance frequency, bringing cost is larger chip size, and higher power consumption, and also inevasible meeting is simultaneously subject to the conforming impact of chip fabrication technique.
Further retrieval is found, US Patent No. 20080214137 " Receiver for Wireless Communications ", proposed a kind of in receiver the method for converting from radio frequency to baseband signal.This invention is in order to realize under multi-mode, multiband, meet simultaneously the strict of performance such as flatness in the selectivity of radio-frequency filter, band are met, employing multiple branch circuit has been proposed in parallel, and the implementation structure of tunable optic filter, a plurality of radio-frequency filter and low noise amplifier series connection.Although connect and reduce the selectivity requirement to single filter by a plurality of radio-frequency filters, but be certainly to cause the increase of insertion loss and the deterioration of the interior performance of band, and the raising of price, power consumption, even if therefore all propose the instruction suggestion of " radio-frequency filter should not over 4 " in this article; Although the interpolation of low noise amplifier can reduce because filter inserts the deterioration of making an uproar mutually, has also increased cost and power consumption; Being added on of tunable optic filter also can only be selected to be operated in several fixing frequency ranges to a certain extent.Therefore can find out that the limitation of this invention is apparent.First contrast with the present invention, this invention is operated under multiband, multi-mode in order to realize, required a plurality of radio-frequency filter, tunable optic filter series connection, and a plurality of branch circuit parallel connections, the performance improvement bringing is little, and flexibility is not high, but cost, circuit design and heat radiation difficulty all increase greatly, performance also can be subject to the circumscribed restriction of analogue device itself, and consistency is difficult to be protected.The more important thing is, contrast with the present invention, this invention relies on analog domain, complete filtered signal completely, digital signal processor (DSP) is only for to branch road or tunable optic filter transmit button selection instruction (switch), do not utilize high accuracy, two-forty and the Digital Signal Processing advance of digital signal processor, the advantage of maturity to assist filtering work at all, improve signal quality.Therefore just combination and a variation based on existing pure analog filtering technology.
Summary of the invention
The present invention is directed to prior art above shortcomings, a kind of analog-digital mixed channel selection filter is provided, for the channel width at the automatic compatible multistandard of direct conversion tuner, at analog domain and numeric field, complete mixed channel selection filtering simultaneously; By adopting simple low order RC low pass filter as analog filter, and numeric field adopts is high-order, have the digital filter of cut-off frequency accurately, realize, can effectively reduce the size of chip, reduce power consumption, Design of Analog Filter and technological requirement are simplified greatly, can also bring performance and Out-of-band rejection in better band, and more accurate filtering cut-off frequency.
The present invention is achieved by the following technical solutions, the present invention includes: the amplification receiver module that is positioned at analog domain, frequency-variable module, low pass and analog-to-digital conversion module and the digital signal processing module that is positioned at numeric field, wherein: amplify the input received RF input signal of receiver module and export the radio-frequency input signals after amplifying to frequency-variable module, frequency-variable module is exported analog baseband signal and is connected with the input of low pass and analog-to-digital conversion module, the input of low pass and analog-to-digital conversion module receives analog baseband signal and exports baseband digital signal to digital signal processing module, digital signal processing module output digital baseband signal.
Described amplification receiver module comprises: low noise amplifier and received signal strength indicator device, wherein: low noise amplifier received RF input signal and output connect respectively received signal strength indicator device and frequency-variable module, thus S meter receives and monitors the radio-frequency (RF) signal strength after amplifying and feed back to low noise amplifier and carries out enlargement ratio control.
Described frequency-variable module comprises: local oscillator, phase shifter and frequency mixer, wherein: the output of local oscillator is connected with phase shifter and exports in-phase component signal and orthogonal component signal, the input of frequency mixer is connected and received RF input signal with the output that amplifies receiver module respectively, the phase terminal of frequency mixer is connected with phase shifter and receives respectively in-phase component signal and orthogonal component signal, and the output of frequency mixer connects low pass and analog-to-digital conversion module.
Described low pass and analog-to-digital conversion module comprise: low pass filter, variable gain amplifier and analog and digital signal transducer, wherein: the input of low pass filter is connected and exports the baseband signal after filtering image spectra to variable gain amplifier with the analog baseband signal of frequency-variable module output, variable gain amplifier exports the baseband signal after gain process analog and digital signal transducer to and exports in digital form digital signal processing module to.
Described digital signal processing module comprises: high-order digit filter, optional strip width controller and digital gain controller, wherein: high-order digit filter receives low pass and the output of D/A converter module and the control signal of optional strip width controller, complete after the frequency selectivity filtering that current channel width is required, the signal after output filtering is to digital gain controller module.Digital gain controller module completes to be controlled the automatic gain of filtered digital signal, then by the signal output of level constant.
Compared with prior art, the invention has the advantages that:
1, in analog domain, only need filter simple, general, low order (as RC filter), be responsible for original, there is the Out-of-band rejection that comprises image frequency to a certain degree, to guarantee that ADC has enough good inband signaling dynamic range.The selectivity of analog filter is required greatly to reduce.And because the Out-of-band rejection of filter exists balance with being with the performance index such as interior performance, therefore reduce analog filter and optionally require to contribute to better design to guarantee the performances such as inband flatness of filter, thereby further guarantee to enter the signal quality of digital signal processor.
2, because the selectivity requirement to analog filter is low, so the exponent number of filter does not need very high.Under different mode different bandwidth more without changing different filters, thereby its volume, price, power consumption all can reduce greatly, are more conducive to system and cost control.
3, utilize high-speed, low-cost, the high accuracy of digital signal processor, and the advance of Digital Signal Processing, maturity, by finally completing the accurate filtering to signal at numeric field design digital filter.The exponent number of digital filter increases, and default many group filters are parallel, substantially do not bring any extra cost to increase (logic unit numbers based on digital signal processor and the maturity of handling property), and existing advance and the maturity of Digital Signal Processing, performance in the accurate cut-off frequency of assurance digital filter that can be fabulous, good Out-of-band rejection and band.Thus, digital simulation territory is in conjunction with filtering, even if need to be operated under the different bandwidth of different mode, the required pressure major part of analog domain filter is transferred on digital filter in the past, when having reduced the requirement of analog domain and cost, guaranteed again performance.Therefore the mode of this digital-to-analogue combination can realize performance performance best under minimum cost.
4, the direct conversion tuner of current main flow, as the Max3580 of Maxim, by its databook, learn, when bandwidth is 7MHz, its baseband frequency spectrum Out-of-band rejection during 1.5MHz (distance center frequency 5MHz) beyond band shoulder also can only be accomplished 30 decibels of left and right.And the channel selection filter that the present invention proposes, test by existing platform represents, the different bandwidth (2MHz～8MHz) that not only well the broadcast standard of the current all main flows of compatibility brings, and take 8MHz bandwidth as example, at band shoulder 0.2MHz (distance center frequency 0.2MHz), locate, realize at the Out-of-band rejection (band matches) that is not less than 40 decibels.Have be simultaneously not less than 40 decibels band stray and ± inband flatness of 0.5 decibel.With respect to prior art, improve a lot, be enough to well meet the demand of digital broadcasting.
Accompanying drawing explanation
Fig. 1 is structural representation of the present invention.
Fig. 2 is for amplifying receiver module structural representation.
Fig. 3 is the Q line structure schematic diagram in digital signal processor.
Embodiment
Below embodiments of the invention are elaborated, the present embodiment is implemented take technical solution of the present invention under prerequisite, provided detailed execution mode and concrete operating process, but protection scope of the present invention is not limited to following embodiment.
As shown in Figure 1, the present embodiment comprises: be positioned at amplification receiver module 1, frequency-variable module 2, low pass and the analog-to-digital conversion module 3 of analog domain and the digital signal processing module 4 that is positioned at numeric field, wherein: amplify the input received RF input signal of receiver module 1 and export the radio-frequency input signals after amplifying to frequency-variable module 2, frequency-variable module 2 is exported analog baseband signals and is connected with the input of low pass and analog-to-digital conversion module 3, and the input of low pass and analog-to-digital conversion module 3 receives analog baseband signal and also exports baseband digital signal to digital signal processing module 4.
Described amplification receiver module 1 comprises: low noise amplifier 101 and received signal strength indicator device 102 (RSSI), wherein: low noise amplifier 101 received RF input signals, its output connects respectively received signal strength indicator device 102 (RSSI) and frequency-variable module.S meter 102 (RSSI) thus receive and monitor the radio-frequency (RF) signal strength after amplifying and feed back to low noise amplifier 101 and carry out enlargement ratio control, thereby realize best noise factor and minimum distortion.
Described frequency-variable module comprises: local oscillator 106, phase shifter 105 and frequency mixer 103, wherein: the output of local oscillator 106 is connected with phase shifter 105 and exports 0 of characteristic frequency and spend phase place (in-phase component) and 90 degree phase place (quadrature component) signals, the input of frequency mixer 103 is connected and received RF input signal with the output that amplifies receiver module respectively, the phase terminal of frequency mixer 103 is connected with phase shifter 105 and receives respectively 0 degree phase place (in-phase component) and 90 degree phase place (quadrature component) signals, the output of frequency mixer 103 connects low pass and analog-to-digital conversion module.
The sine wave signal of the characteristic frequency that is input as local oscillator 106 generations of described phase shifter 105, it is output as 0 degree phase place (in-phase component) and 90 degree phase place (quadrature component) signals outputs of this frequency.
Described local oscillator 106 is output as the sine wave signal of characteristic frequency, these local oscillator 106 VCXOs, compensation crystal oscillator, constant-temperature crystal oscillator; The required frequency that the frequency that the above-mentioned oscillator of described sine wave signal produces obtains after several times frequency multiplication or frequency division.
Described low pass and analog-to-digital conversion module comprise: low pass filter 107,108, variable gain amplifier 109,110 and analog and digital signal transducer 111,112, wherein: the input of low pass filter 107,108 is connected and exports the baseband signal after filtering image spectra to variable gain amplifier 109,110 with the analog baseband signal of frequency-variable module output, variable gain amplifier 109,110 exports the baseband signal after gain process analog and digital signal transducer 111,112 to and exports in digital form digital signal processing module to.
The RC filter of described low pass filter 107,108 low orders, for example (but being not limited to) is 3 rank or 5 rank RC filters.Its role is to the Out-of-band rejection that comprises image frequency to a certain degree, to guarantee that ADC has enough good inband signaling dynamic range.The present invention, due to the processing mode that adopts digital-to-analogue to mix, just can meet the compatible requirement to different channels bandwidth communication standard without building many group simulation low-pass filters in analog domain.Also greatly reduce the requirement to analog filter exponent number and manufacture craft simultaneously.The assurance of high-performance, meticulous cut-off frequency guarantees the digital filter by numeric field.
Thereby described variable gain amplifier 109,110 change feedback resistances or input resistance are realized the operational amplifier of change in gain, to guarantee that filtered signal is at a suitable level range.
Described digital signal processing module comprises: high-order digit filter, optional strip width controller and digital gain controller, wherein: high-order digit filter receives the output of low pass and D/A converter module, and the control signal of optional strip width controller, complete after the frequency selectivity filtering that current channel width is required, the signal after output filtering is to digital gain controller module.Digital gain controller module completes to be controlled the automatic gain of filtered digital signal, then by the signal output of level constant.As shown in Figure 2, wherein I road has with the on all four processing structure in Q road, so in figure, only take Q road as example.
The control signal of described optional strip width controller, can be manual setting, can be also to draw by extra demodulating information, its role is to determine the cut off band width of current needed filter.
Described digital filter, can be finite impulse response filter (FIR), can be also infinite impulse response filter (IIR) structure, or can also be both combinations.This digital filter can be independent I or Q road real filter, can be also the complex filter structure that I, Q mix.Digital filter is current very ripe technology, the raising of its performance is only limited to the hardware capabilities of Contemporary Digital signal processor, therefore can design high-order, there is in good band performance and the digital filter of cut-off frequency accurately, fabulous assurance the effect of selective filter.For realizing the compatible requirement to different channels bandwidth, this filter can be variable tap digital filter, definite indicated current channel width of control signal of being exported by optional strip width controller of its tap coefficient is determined, also can be pre-stored many group different bandwidth filter parameters, where the control signal of being exported by optional strip width controller selection application organizes filter parameter be exported.
Described digital gain controller device comprises: multiplier, amplitude power calculator, integrator, subtracter and loop filter, wherein: multiplier is connected with reception control signal with the output of digital filter and the output of loop filter respectively, the output of multiplier is exported the I/Q two paths of signals after adjusting range as digital signal processor, and deliver to amplitude power calculator, amplitude power calculator calculates respectively and exports integrator to after the amplitude of I/Q two paths of signals or power and obtain average amplitude or average power, integrator subtracts each other by subtracter the input that the difference obtaining exports loop filter to by average amplitude or average power and preset value.
Claims (1)
1. an analog-digital mixed channel selection filter, it is characterized in that, comprise: the amplification receiver module that is positioned at analog domain, frequency-variable module, low pass and analog-to-digital conversion module and the digital signal processing module that is positioned at numeric field, wherein: amplify the input received RF input signal of receiver module and export the radio-frequency input signals after amplifying to frequency-variable module, frequency-variable module is exported analog baseband signal and is connected with the input of low pass and analog-to-digital conversion module, the input of low pass and analog-to-digital conversion module receives analog baseband signal and exports baseband digital signal to digital signal processing module, digital signal processing module output digital baseband signal,
Described digital signal processing module comprises: high-order digit filter, optional strip width controller and digital gain controller, wherein: high-order digit filter receives low pass and the output of D/A converter module and the control signal of optional strip width controller, complete after the frequency selectivity filtering that current channel width is required, signal after output filtering is to digital gain controller module, digital gain controller module completes to be controlled the automatic gain of filtered digital signal, then by the signal output of level constant;
Described amplification receiver module comprises: low noise amplifier and received signal strength indicator device, wherein: low noise amplifier received RF input signal and output connect respectively received signal strength indicator device and frequency-variable module, thus S meter receives and monitors the radio-frequency (RF) signal strength after amplifying and feed back to low noise amplifier and carries out enlargement ratio control;
Described frequency-variable module comprises: local oscillator, phase shifter and frequency mixer, wherein: the output of local oscillator is connected with phase shifter and exports in-phase component signal and orthogonal component signal, the input of frequency mixer is connected and received RF input signal with the output that amplifies receiver module respectively, the phase terminal of frequency mixer is connected with phase shifter and receives respectively in-phase component signal and orthogonal component signal, and the output of frequency mixer connects low pass and analog-to-digital conversion module;
Described local oscillator adopts VCXO, compensation crystal oscillator or constant-temperature crystal oscillator;
Described low pass and analog-to-digital conversion module comprise: low pass filter, variable gain amplifier and analog and digital signal transducer, wherein: the input of low pass filter is connected and exports the baseband signal after filtering image spectra to variable gain amplifier with the analog baseband signal of frequency-variable module output, variable gain amplifier exports the baseband signal after gain process analog and digital signal transducer to and exports in digital form digital signal processing module to;
Described low pass filter adopts 3 rank or 5 rank RC filters;
The control signal of described optional strip width controller is transmitted by manual setting or by extraneous solution adjusting information;
Described high-order digit filter adopts two single channel real numbers or an I-Q to mix plural finite impulse response filter, infinite impulse response filter or its combination.
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| US9093955B2 (en) * | 2013-03-21 | 2015-07-28 | Tektronix, Inc. | Asynchronous time-interleaved waveform generator using harmonic mixing |
| US10862504B2 (en) * | 2018-08-29 | 2020-12-08 | Mediatek Singapore Pte. Ltd. | Radio frequency bandpass delta-sigma analog-to-digital converters and related methods |
| CN110426064B (en) * | 2019-07-18 | 2021-07-20 | 东南大学 | Wireless passive sensor and wireless passive sensing method |
Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN1035031A (en) * | 1988-12-17 | 1989-08-23 | 邮电部武汉邮电科学研究院 | Signal receiver |
| CN101192840A (en) * | 2006-11-24 | 2008-06-04 | 鼎芯通讯（上海）有限公司 | Channel receiver |
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Patent Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN1035031A (en) * | 1988-12-17 | 1989-08-23 | 邮电部武汉邮电科学研究院 | Signal receiver |
| CN101192840A (en) * | 2006-11-24 | 2008-06-04 | 鼎芯通讯（上海）有限公司 | Channel receiver |
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