CN102106068A - Method of forming a switching regulator and structure therefor - Google Patents
Method of forming a switching regulator and structure therefor Download PDFInfo
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- CN102106068A CN102106068A CN2008801304613A CN200880130461A CN102106068A CN 102106068 A CN102106068 A CN 102106068A CN 2008801304613 A CN2008801304613 A CN 2008801304613A CN 200880130461 A CN200880130461 A CN 200880130461A CN 102106068 A CN102106068 A CN 102106068A
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
- H02M3/33523—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters with galvanic isolation between input and output of both the power stage and the feedback loop
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0003—Details of control, feedback or regulation circuits
- H02M1/0016—Control circuits providing compensation of output voltage deviations using feedforward of disturbance parameters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0003—Details of control, feedback or regulation circuits
- H02M1/0025—Arrangements for modifying reference values, feedback values or error values in the control loop of a converter
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y10—TECHNICAL SUBJECTS COVERED BY FORMER USPC
- Y10T—TECHNICAL SUBJECTS COVERED BY FORMER US CLASSIFICATION
- Y10T29/00—Metal working
- Y10T29/49—Method of mechanical manufacture
- Y10T29/49002—Electrical device making
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
Abstract
In one embodiment, a power supply controller is configured to receive a sense signal having a negative value that is proportional to the input voltage. The power supply controller uses the sense signal to limit the switch current through the switch responsively to the value of the input voltage.
Description
Technical field
The present invention is broadly directed to electronic device, especially relates to the method for semiconductor structure and formation semiconductor device.
Background technology
In the past, semi-conductor industry utilizes the whole bag of tricks and structure to form the switch mode power controller, and this switch mode power controller is used to form the power supply of the output voltage that adjustment is provided.Favourable feature is in response to the power output that the electric current by the mains switch of power supply comes limit switch formula power supply.The example of this configuration is at United States Patent (USP) the 7th, 215, is described in No. 107, and this patent was issued by people such as Djenguerian on May 8th, 2007.Usually exist from electric current arrive time of expectation peak value and switching response in electric current by the propagation delay of actual time of closing, this propagation delay causes the big actual peak current of peak value than expectation.In some embodiments, change to the amount of required time of second value and limit electric current from first value based on electric current.Yet, determine that the time interval and rate of change need increase the complicated circuit of the cost of power-supply controller of electric.In addition, it is difficult accurately determining to cause the time interval of the inaccuracy of output voltage.
Therefore, need a kind of limit transport more accurately to the power of load and have the power-supply controller of electric of lower cost.
Description of drawings
Fig. 1 has schematically illustrated the execution mode of the part of power-supply system, and this system comprises the exemplary execution mode according to the part of power-supply controller of electric of the present invention.
Fig. 2 has schematically illustrated some signals that formed by the operation according to the power-supply system of Fig. 1 of the present invention.
Fig. 3 has schematically illustrated the more detailed part according to the execution mode of another part of the power-supply controller of electric of Fig. 1 of the present invention.
Fig. 4 has schematically illustrated the execution mode of the part of another power-supply system, and this system comprises the illustrative embodiments of the part of another power-supply controller of electric, and this controller is the optional execution mode according to the power-supply controller of electric of Fig. 1 of the present invention.
Fig. 5 shows the plane graph of the amplification of semiconductor device, and this device comprises the power-supply controller of electric according to Fig. 1 of the present invention.
Simple and clear for what illustrate, the element among the figure not necessarily in proportion, and the same numeral among the different figure is represented components identical.In addition, description and the details of simply having omitted well-known step and element in order to describe.The current-carrying electrode means the device element of carrying by the electric current of device as used herein, as source electrode or the emitter of drain electrode or bipolar transistor or the negative electrode or the anode of collector electrode or diode of MOS transistor; Control electrode means the device element of the electric current of carrying by device, as the base stage of the grid or the bipolar transistor of MOS transistor.Although this paper is interpreted as certain N-passage or P-passage device with device; Or some N-type or P-type doped region, those of ordinary skill in the art it should be understood that it also is possible replenishing device according to the present invention.Those skilled in the art will be appreciated that, the word that relates to circuit operation used herein " during (during) ", " at (while) ", " as (when) " are not the accurate term that is meant that action takes place immediately when starting the action beginning, but may some is little but reasonably postpone, as by the propagation delay between the reaction that starts action launching.The value that word " approximately " or " basically's " use means element has expectation extremely near the parameter of set point or position.Yet, as known in the art, always have little variation prevention value or position accurately as regulation.This area confirms that up to ten (10%) at least percent the variation of (and for doping content of semiconductor up to 20 (20%) percent) is the reasonable change that departs from definitely dreamboat as described.
Embodiment
Fig. 1 has schematically illustrated the execution mode of the part of power-supply system 10, and this power-supply system 10 comprises the illustrative embodiments of power-supply controller of electric 35.System 10 is received in the power between voltage input end 11 and the common reference terminal 12, and is provided at output 13 and exports the voltage that returns between 14.Be often referred to the common reference voltage that on terminal 12, forms at the input voltage that receives between terminal 11 and 12.Usually output voltage is adjusted to desired value or desired value in the scope of the value about desired value.For example, described desired value can be five volts (5V), and the scope of value can be positive and negative (5%) 5 percent about in the of five volts.System 10 generally include have primary coil 17, the transformer 16 of secondary coil 18 and ancillary coil 19.Mains switch (for example transistor 27) is used for the value of the switching current 30 of control flows coils 17 and transistor 27, so that regulate the value of output voltage.Current sensing element (for example sense resistor 28) is used to form current sense (CS) signal, this signal representation switch electric current 30.Person of skill in the art will appreciate that other known current sensing element can be used for substitutional resistance device 28.Electric current 30 determines to be provided for the amount of the output current of load, and this load is included in output 13 and returns capacitor 21 and the load 15 that connects between 14.As will further seeing hereinafter, power-supply controller of electric 35 is configured to the value of sensing input voltage and controls peak value by the electric current 30 of mains switch in response to the value of input voltage, therefore, control offers the peak value of the output current of the load that comprises capacitor 21 and load 15.This control of the peak value of electric current 30 also causes providing to output 13 value of the substantial constant of power at the set-point of feedback signal, even the value of this input voltage may change.
Diode 20 is connected in coil 18 with in output 13 with return 14 and help to form output voltages with capacitor 21 usually.Feedback circuit 29 provides feedback (FB) signal of the value of representing output voltage.Feedback circuit 29 can be any optical coupler for example in the various known feedback circuits, and it is provided at the primary and secondary side of transformer 16 and the isolation between the system 10.Use ancillary coil 19 by being used for the boost voltage of operation control 35.Diode 23, capacitor 24 and resistor 22 help the voltage and current from sensed coil 19 to form boost voltage.The ancillary coil circuit that is formed by coil 19, diode 23 and capacitor 24 is known auxiliary winding supply circuit.
Fig. 2 is the figure with curve, and these curves are illustrated in some signals that operating period of controller 35 forms in system 10.The value of the increase of signal shown in abscissa express time and ordinate are represented.Curve 66 is illustrated in the specified waveform of the switching drive signal that forms in the output 41.Curve 56 illustrates the rated value of electric current 30, and curve 59 is illustrated in the rated value with respect to the sensing signal (SS) of the common reference voltage on terminal 12 that receives in the input 43.Curve 80 illustrates the rated value of the compensating signal (CSS) that is formed by circuit 51.This specification is with reference to figure 1 and Fig. 2.
In the operating period of controller 35, ON-OFF control circuit 45 make as the switching drive signal of curve 66 shown in the time T 0 effectively (assert) to start transistor 27.This switching drive signal is high during the ON time part in cycle of the switching drive signal shown in curve 66 usually.Start transistor 27 and make electric current 30 flowing through coil 17, transistor 27 and resistor 28.The electric current 30 of flowing through coil 17 attempts to induce electric current 33 with flowing through coil 19.Yet diode 23 stops flowing of electric current 33, and electric current 33 induces voltage at node 32, and this voltage is born with respect to the common reference voltage on terminal 12.Absolute value at the negative voltage on the node 32 is proportional with respect to the value of terminal 12 and the input voltage on terminal 11.This ratio is roughly relevant by the turn ratio between coil 17 and 19. Resistor 25 and 26 resitstance voltage divider form the voltage as the sensing signal (SS) in input 43, as by shown in the curve 59.Sensing signal (SS) is proportional with input voltage, thereby represents this input voltage, but bears with respect to the common reference voltage on terminal 12.
Use the peak value of current compensation circuit 51, so that the maximum of the power that provides by system 10 is provided in response to the value Control current 30 of input voltage.Under the situation that does not have circuit 51, if the value of input voltage increases, the slope of electric current 30 will increase and the peak value of electric current 30 can increase before circuit 45 can stop electric current 30 and above rated peak.Configuration circuit 51 is with the duration in response to the ON time part of the value controlling and driving signal of input voltage, so that in response to the peak value of the value restriction electric current 30 of input voltage.Circuit 51 receives sensing signal (SS) and current sense (CS) signal, and uses sensing signal to regulate or compensate the peak value of the switching current 30 that passes through mains switch in response to the value of input voltage.Exemplary execution mode shown in Figure 1 comprises adder circuit 50, comparator 48 and with reference to generator or reference circuit or with reference to 46.In the configuration of this illustrative embodiments, adder circuit 50 will be sued for peace to form compensating signal (CSS) with the reference voltage that comes self-reference 46 from the sensing signal (SS) of input 43.With the value comparison of the value of compensating signal (CSS) and current sense (CS) signal with invalid (disable) signal in the output that is formed on comparator 48.When the value of current sense (CS) signal becomes value than compensating signal (CSS) when bigger, the output of comparator 48 uprises.As further seeing hereinafter, ON-OFF control circuit 45 these invalid signals of use come the ON time part in the cycle of terminating switch drive signal, disable transistor 27 and termination circuit 30 thus.
Typically, select the value of resistor 25 and 26, make the sensing signal (SS) that in input 43, forms have rated value, and provide expectation or rated peak at the electric current shown in curve 56 30 at the rated value place of input voltage.For example, system 10 can be designed such that between terminal 11 and 12 rated value of the input voltage that receives is about 325 volts (325V) and can have the high value of about 375 volts (375V) and an about hectovolt spy's (100V) low value.The corresponding rated value of sensing signal can be about negative 260 millivolts (260mV), and high value can for negative approximately 300 millivolts (300mV) and low value can for negative approximately 80 millivolts (80mV).When transistor 27 is activated and input voltage during at the rated value place, resistor 25 and 26 set point value are formed on the sensing signal at rated value place, and it is born with respect to common reference voltage, shown in curve 59.Add to the reference voltage of self-reference 46 to form the rated value of compensating signal (CSS) this rated value of sensing signal.Because the value of sensing signal (SS) is born, it is lower than as curve 80 for example in the value of the reference voltage shown in the time T 0 compensating signal (CSS).When the value of sensing signal (CS) reaches the value of compensating signal (CSS), the output of comparator 48 uprises and circuit 45 stop drive signals (as in time T 1 by shown in the curve 66) the ON time part of current cycle, stop electric current 30 thus at the rated peak place, as by curve 56 shown in the time T 1.
When transistor 27 was under an embargo, the energy-sensitive of storage went out at the positive voltage at node 32 places with from the electric current that pass through diode 23 of terminal 12, to give capacitor 24 chargings and formation boost voltage in coil 17.Form the sensing signal that has positive voltage with respect to the value of the common reference voltage on the terminal 12 at the positive voltage at node 32 places, as in time T 1 back by shown in the curve 59.Because circuit 45 has invalid transistor 27, being somebody's turn to do on the occasion of the operation for circuit 45 of compensating signal do not influence.
When transistor 27 is activated and input voltage when being higher than rated value (high value), electric current 30 with bigger speed therefore with steeper slope increase, as by shown in the imaginary curve 57.Because the value of input voltage increases, the absolute value of sensing signal is greater than the value at rated value, therefore, sensing signal is more negative, as by shown in the imaginary curve 61.Therefore, circuit 51 has formed the compensating signal (CSS) with value lower than the rated value of compensating signal (CSS), shown in imaginary curve 81.Because the value of compensating signal reduces, current sense (CS) signal is crossed in the cycle of drive signal the value of the compensating signal in stage early, this drive signal terminates in drive signal ON time part of the drive signal in stage early in the cycle, transistor 27 rated value stage more early at the comparison input voltage in the cycle is under an embargo, shown in imaginary curve 67.Because the slope of electric current 30 is steeper, signal value that form, that be used to begin to stop the reference signal of electric current 30 reduces the rated value that makes electric current 30 thereby peak value that produce be substantially equal to peak current by way of compensation.Under the situation of the value that does not change reference signal in response to input voltage, the steeper slope of electric current 30 will cause this peakedness ratio rated peak bigger.Therefore, the peak response of Control current 30 is in the value of the increase of input voltage and Be Controlled.Because because the value of input voltage is bigger, electric current 30 increases with faster rate, the amount with the power that the rated value of input voltage is carried is identical basically to be transported to the amount of power of output 13.
When transistor 27 is activated and input voltage during less than rated value, electric current 30 increases with speed slowly, therefore also increase with less slope, shown in imaginary curve 58.This forms the absolute value of sensing signal, and it is less than as the value by the rated value place shown in the imaginary curve 60.Because sensing signal is born, the value of the reduction of sensing signal makes the rated value of compensating signal greater than the compensating signal shown in imaginary curve 82.Because the value of compensating signal increases, the value that current sensing signal (CS) is crossed compensating signal in the middle and later periods in cycle of drive signal, this drive signal terminates in the ON time part of the drive signal of middle and later periods in drive signal cycle, and transistor 27 was under an embargo in the stage of the rated value that is being compared to the input voltage shown in imaginary curve 68 in the cycle after more.Because the lower slope of electric current 30, the increase of value that is used to begin to stop the reference signal of electric current 30 makes the consequent peak value of electric current 30 be substantially equal to the rated value of peak current.Under the situation of the value that does not change reference signal in response to input voltage, the littler slope of electric current 30 causes the peakedness ratio rated peak littler.Therefore, configuration circuit 51 is with the peak value in response to the variation by-pass cock electric current of input voltage, for the set-point of feedback signal the peak value of the substantial constant of electric current 30 is provided to output 13.Because electric current 30 increases with lower speed, the amount that is transported to the power of output 13 is substantially equal to the rated value of input voltage.
Fig. 3 has schematically illustrated the illustrative embodiments of the part of ON-OFF control circuit 45.In this illustrative embodiments, error amplifier 62 receiving feedback signals of ON-OFF control circuit 45 and formation error signal (ES), this error signal is represented the difference between the actual value of the desired value of input voltage and input voltage.As known in the art, error amplifier 62 generally comprises and is used to controller 35 formed closed control loops that frequency compensated frequency compensation assembly, for example impedance Z are provided.Comparator 63 compares error signal and circuits sense signal, so that the operation of oxide-semiconductor control transistors 27 in normal operation.Or door 65 receives compensating signal (CSS) and make latch 64 reset with disable transistor 27 and stop electric current 30, to limit the peak value of electric current 30 in response to the value of input voltage.
Clear for what illustrate, explained the operation preferred embodiment of controller 35, yet other execution mode should provide similar operation.Person of skill in the art will appreciate that other realization can be used for circuit 45.For example, error amplifier 62 can be in the outside of controller 35, and the output of error amplifier can substitute the FB signal.In another embodiment of optional execution mode, the current sensing signal that enters circuit 45 can use the ramp signal that is produced by the ramp generator circuit to replace.
Fig. 4 has schematically illustrated the execution mode of power-supply system 70, and this system is the optional execution mode of power-supply system 10, and system 10 is explained in the execution mode of Fig. 1～Fig. 4.System 70 is similar to system 10, except diode 71 and capacitor 72 are used to help to be formed on sensing signal in the input 43.In addition, the controller in system's 70 use power-supply controller of electric 75 alternate figures 1.Controller 75 is similar to controller 35, but controller 75 comprises power switch, and for example power transistor 77, and it is formed ON-OFF control circuit 45 and circuit 51 on same semiconductor chip.In addition, controller 75 comprises current sensing circuit 78, shunt regulator for example, and its value that is used for current sensor 30 is to form current sensing signal.This current sensing element is known for those skilled in the art.
In optional execution mode, and because controller 75 is integrated to comprise mains switch and current sensing circuit 78, using constant negative voltage may be favourable to substitute sensing signal.Constant negative voltage makes controller 75 that the peak value of electric current 30 is controlled to fixing basically value.
Fig. 5 shows on semiconductor chip 86 plane graph of amplification of a part of the execution mode of the semiconductor device that forms or integrated circuit 85.Controller 35 or controller 75 form on chip 86.Chip 86 also can comprise circuit not shown in Figure 5 (in order to simplify accompanying drawing).Controller 35 and device or integrated circuit 85 form on chip by the known semiconductor fabrication of those skilled in the art.
In view of above-mentioned full content, the application discloses a kind of new device and method obviously.Except further feature, also comprise and form power-supply controller of electric to receive the negative sensing voltage of representing input voltage and the peak value that limits the electric current of process mains switch in response to the value of input voltage.Adopt negative voltage to be convenient to adopt the voltage compensation current sensing signal, and the electric current that needn't produce input voltage is to voltage transitions.This provides accuracy by eliminating at least one electric current to voltage conversion circuit.And, having used less assembly and circuit, this has reduced the cost of power-supply controller of electric.Do not adopt input voltage, form negative voltage from the signal of representing input voltage and directly reduced the amount that forms the employed power of circuit of sensing signal.Less assembly has also improved accuracy, even this causes the input voltage variation also the peak-limitation of electric current 30 to be arrived amount value basically.Adopt voltage to form sensing function and improved accuracy to current conversion without voltage.
Although theme of the present invention is described with specific preferred implementation, clearly a lot of replacements and variation are tangible for the technical staff of semiconductor applications.Clear for what describe, word " is connected " and is used in the text, yet it is defined as " to be coupled " with word has identical implication.Therefore, " be connected " and should be interpreted as comprising direct connection and be connected indirectly.Although the illustrative embodiments of using fixed frequency instead to swash power-supply controller of electric is described the present invention, the present invention is applicable to other power configuration.
Claims (17)
1. switching regulaor comprises:
First circuit, it is configured to be formed for the switching drive signal of console switch, so that control flows is through the switching current of described switch, so that output voltage is adjusted to desired value, wherein said output voltage is to be formed by following input voltage, described input voltage with respect to the common reference value of described input voltage have on the occasion of;
Current compensation circuit;
First input of described current compensation circuit is configured to receive the current sensing signal of the described switching current of representing the described switch of flowing through;
Second input of described current compensation circuit is configured to receive and the proportional sensing voltage of described input voltage, and wherein said sensing voltage is negative with respect to the described common reference value of described input voltage; And
Described switching regulaor is configured to use described sensing voltage to come in response to described input voltage the peak value of described switching current to be controlled to the value of substantial constant.
2. switching regulaor according to claim 1, wherein said current compensation circuit is configured to the summation of described sensing voltage and reference voltage forming compensating signal, and wherein said current compensation circuit uses described compensating signal to form to be used for the control signal of the ON time part that stops described switching drive signal.
3. switching regulaor according to claim 2 also comprises described compensating signal is compared to form described control signal with described current sensing signal.
4. switching regulaor according to claim 1, wherein said current compensation circuit comprise sues for peace described sensing voltage and reference voltage to form the summing circuit of compensating signal.
5. switching regulaor according to claim 4, wherein said current compensation circuit comprises comparator, and described comparator is coupled into and receives described compensating signal and described current sensing signal and form the ON time control signal partly that is used for stopping described switching drive signal responsively.
6. switching regulaor according to claim 1, also comprise the feedback signal that described switching regulaor is configured to receive the described output voltage of representative, use described feedback signal to form the error voltage of the deviation of representative described output voltage and described desired value and the switching current of described error voltage and described compensating signal being compared the described switch of restricted passage.
7. switching regulaor according to claim 1, wherein said current sensing signal is a voltage.
8. method that forms switching regulaor comprises:
Dispose described switching regulaor to be formed for the switching drive signal of console switch, and control flows is through the switching current of described switch, so that output voltage is adjusted to desired value, wherein said output voltage is formed by input voltage, described input voltage with respect to the common reference value of described input voltage have on the occasion of;
Dispose described switching regulaor to receive sensing signal, described sensing signal and described input voltage are proportional, and wherein said sensing signal is negative with respect to the described common reference value of described input voltage; And
The described switching regulaor that operationally is coupled to limit in response to described input voltage the peak value of described switching current to use described sensing signal.
9. method according to claim 8, the described switching regulaor that wherein operationally is coupled comprises to use described sensing signal: dispose described switching regulaor and regulate the ON time duration partly in the cycle of described switching drive signal to use described sensing signal.
10. method according to claim 9, the described switching regulaor that wherein operationally is coupled comprises to use described sensing signal: dispose described switching regulaor with the summation of described sensing signal and reference signal forming the compensation sensing signal, and limit the peak value of described switching current in response to described compensation sensing signal.
11. method according to claim 10 wherein disposes described switching regulaor so that described sensing signal summation is also comprised: the described switching regulaor that operationally is coupled is to compare described compensation sensing signal with the current sensing signal of the described switching current of representative.
12. method according to claim 11, the described switching regulaor that wherein operationally is coupled comprises to use described sensing signal: the feedback signal that described switching regulaor is configured to receive the described output voltage of representative, use described feedback signal to form the error signal of the deviation of representative described output voltage and desired value, and described error signal is compared with described compensation sensing signal.
13. a switching regulaor comprises:
Described switching regulaor is configured to form and is used for the switching drive signal of console switch, wherein said switch be configured to receive with respect to common reference have on the occasion of input voltage, and wherein said switching drive signal is formed with the switching current of control flows through described switch, so that output voltage is adjusted to desired value, wherein said output voltage is formed by described input voltage;
First circuit of described switching regulaor, described first circuit operationally are coupled to receive the current sensing signal of the described switching current of representative;
The described common reference that described first circuit arrangement becomes to receive with respect to described input voltage is negative sensing signal; And
Described switching regulaor is configured to use described sensing signal to control in response to described sensing signal the peak value of described switching current.
14. switching regulaor according to claim 13, the absolute value of wherein said sensing signal and the value of described input voltage are proportional.
15. switching regulaor according to claim 13, wherein said first circuit arrangement become described sensing signal and reference signal summation are compensated sensing signal to form.
16. switching regulaor according to claim 15, wherein said first circuit arrangement one-tenth is compared described compensation sensing signal and is formed control signal with described current sensing signal.
17. switching regulaor according to claim 16, the pwm circuit of wherein said switching regulaor are configured to use described control signal to form the duration of described switching drive signal.
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| PCT/US2008/070874 WO2010011219A2 (en) | 2008-07-23 | 2008-07-23 | Method of forming a switching regulator and structure therefor |
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| Publication Number | Publication Date |
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| CN102106068A true CN102106068A (en) | 2011-06-22 |
| CN102106068B CN102106068B (en) | 2014-08-27 |
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| CN200880130461.3A Expired - Fee Related CN102106068B (en) | 2008-07-23 | 2008-07-23 | Method of forming a switching regulator and structure therefor |
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| Country | Link |
|---|---|
| US (1) | US8432147B2 (en) |
| CN (1) | CN102106068B (en) |
| HK (1) | HK1153578A1 (en) |
| TW (1) | TWI448062B (en) |
| WO (1) | WO2010011219A2 (en) |
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| CN102545631A (en) * | 2012-01-09 | 2012-07-04 | 绍兴光大芯业微电子有限公司 | Constant current control device for switching power supply |
| CN104767384A (en) * | 2014-01-08 | 2015-07-08 | 半导体元件工业有限责任公司 | Method of forming a power supply controller and structure therefor |
| CN105450005A (en) * | 2014-09-19 | 2016-03-30 | 株式会社村田制作所 | Power overload protection using hiccup mode |
| CN109843579A (en) * | 2017-09-25 | 2019-06-04 | 法国圣戈班玻璃厂 | Means of transport glass, means of transport and the method for manufacture |
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| CN109843579A (en) * | 2017-09-25 | 2019-06-04 | 法国圣戈班玻璃厂 | Means of transport glass, means of transport and the method for manufacture |
| CN109843579B (en) * | 2017-09-25 | 2023-10-20 | 法国圣戈班玻璃厂 | Vehicle window, vehicle and method for manufacturing |
Also Published As
| Publication number | Publication date |
|---|---|
| US20110110124A1 (en) | 2011-05-12 |
| CN102106068B (en) | 2014-08-27 |
| TW201027894A (en) | 2010-07-16 |
| HK1153578A1 (en) | 2012-03-30 |
| WO2010011219A3 (en) | 2010-04-15 |
| US8432147B2 (en) | 2013-04-30 |
| WO2010011219A2 (en) | 2010-01-28 |
| TWI448062B (en) | 2014-08-01 |
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