CN102035779A - Demodulation module, signal analysis device and signal analysis method - Google Patents
Demodulation module, signal analysis device and signal analysis method Download PDFInfo
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- CN102035779A CN102035779A CN200910178522XA CN200910178522A CN102035779A CN 102035779 A CN102035779 A CN 102035779A CN 200910178522X A CN200910178522X A CN 200910178522XA CN 200910178522 A CN200910178522 A CN 200910178522A CN 102035779 A CN102035779 A CN 102035779A
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Abstract
The invention discloses a demodulation module, a signal analysis device and a signal analysis method. The signal analysis device comprises a relativity calculating device, a symbol boundary detection device and a carrier frequency shift estimation device. The relativity calculating device is used for receiving an input signal, delaying the input signal according to a plurality of different retardation to obtain a plurality of delayed signals, calculating the relativity of the delayed signals and a prearranged virtual noise sequence to obtain a plurality of relativity calculated results, and generating a relativity sequence according to the relativity calculated result. The symbol boundary detection device is used for detecting a sample point with a maximal relativity according to the relativity sequence, and generating a symbol boundary indication signal according to a relativity numerical value of the sampling point. The carrier frequency shift estimation device is used for estimating the carrier frequency shift quantity according to the symbol boundary indication signal.
Description
Technical field
The present invention relates to a kind of method of estimation of carrier frequency drift, particularly relate to a kind of carrier frequency drift method of estimation that is applicable to the multi-path transmission channel.
Background technology
In wireless telecommunication system, because concussion frequency inaccuracy and Doppler effect (DopplerEffect), thereby between transmission end and receiving terminal, may produce the carrier frequency drift problem of (CarrierFrequency Offset is called for short CFO).Especially in OFDM (Orthogonalfrequency division multiplexing is called for short OFDM) system, the influence that the carrier frequency drift is produced is even more serious.Because the transmission system of OFDM is a multicarrier system, very responsive for the carrier frequency drift, carrier frequency drift meeting destroys the orthogonality between the ofdm system sub-carriers, thereby caused between subcarrier and interfered with each other (Inter-Carrier Interference, be called for short ICI), make problems such as the system effectiveness variation of ofdm system and the rate increase that makes a mistake.Therefore, how exactly the estimating carrier frequency drift interferes with each other (ICI) and becomes the ofdm system utmost point and need the important topic that be solved to solve intercarrier.
Summary of the invention
According to one embodiment of the invention, a kind of demodulation module comprises analog-to-digital converter, fundamental frequency frequency mixer, time sequence reply device, signal analysis device and decoder.Analog-to-digital converter is changed an analog if signal, to export a digital medium-frequency signal.The fundamental frequency frequency mixer receives this digital medium-frequency signal, and according to this digital medium-frequency signal of carrier frequency frequency reducing to produce a fundamental frequency signal, wherein this fundamental frequency frequency mixer is also adjusted this carrier frequency according to one first back coupling control signal, to compensate the carrier frequency drift of this carrier frequency.The time sequence reply device is feedback control signal this fundamental frequency signal of resampling according to one second.Signal analysis device receives this fundamental frequency signal, the correlation of analyzing this fundamental frequency signal and a predetermined virtual noise sequence is to obtain a plurality of correlation results, and strengthen described correlation results producing a correlation sequence, and produce this according to this correlation sequence and first feedback control signal and this second feedback signal.Decoder is in order to decipher an output signal of this time sequence reply device, to produce a decoding output signal.
According to another embodiment of the present invention, a kind of signal analysis device comprises correlation calculations device, the marginal checkout gear of symbol (symbol) and carrier frequency drift estimation unit.The correlation calculations device receives an input signal, postpone this input signal to obtain a plurality of inhibit signals according to a plurality of different retardations, and calculate the correlation of a described inhibit signal and a predetermined virtual noise sequence, obtaining a plurality of correlativity calculation result, and produce a correlation sequence according to described correlativity calculation result.Symbol limit checkout gear has a sampling point of maximum correlation according to this correlation Sequence Detection, and produces symbol limit index signal according to a correlation values of this sampling point.Carrier frequency drift estimation unit is estimated a carrier frequency drift amount according to this symbol limit index signal.
According to another embodiment of the present invention, a kind of signal analysis method comprises: receive an input signal, wherein this input signal comprises a data information and a virtual noise sequence at least; Postpone this input signal according to a plurality of different retardations, to obtain a plurality of inhibit signals; Calculate the correlation of a described inhibit signal and a predetermined virtual noise sequence, to obtain a plurality of correlativity calculation result; Produce a correlation sequence according to described correlativity calculation result; And according to a carrier frequency drift amount of this this input signal of correlation sequencal estimation.
Description of drawings
Fig. 1 a-1b shows the data structure of digital television broadcasting data.
Fig. 2 shows the correlation operation result of received signal in the multi-path transmission channel environment.
Fig. 3 a-3b shows the estimation and the corresponding compensation result of carrier frequency drift in the multi-path transmission channel environment.
Fig. 4 shows according to the described receiver of one embodiment of the invention.
Fig. 5 a-5c shows described in the correlativity calculation result of multi-path transmission channel environment according to one embodiment of the invention.
Fig. 6 shows according to the described correlation calculations device of one embodiment of the invention.
Fig. 7 shows according to the described signal analysis method of one embodiment of the invention.
The reference numeral explanation
100,101～data;
201～the item of asking;
202～error items;
400～receiver;
401～tuner;
402～demodulation module;
403～analog-to-digital converter;
404～fundamental frequency frequency mixer;
405～time sequence reply device;
406～equalizer;
407～decoder;
408～signal analysis device;
411,611～correlation calculations device;
412～symbol limit checkout gear;
413～sequential mistake estimation unit;
414～carrier frequency drift estimation unit;
612,613～computing module;
621,631,624,634, FIFO～first-in first-out register;
622, a plurality of unit of 632～conjugation;
623,633～multiplier;
625,635～correlation calculations unit;
Corr (n), Corr_D1 (n), CorrAD2 (n)～correlation;
D～delay;
Data～data information;
PN, PN code, Pre PN, Post PN～virtual noise sequence;
S-
B, S-
C, S-
IND, S-
OUT, S
RF, S-
T～signal.
Embodiment
For manufacturing of the present invention, method of operation, target and advantage can be become apparent, several preferred embodiments cited below particularly, and be described with reference to the accompanying drawings as follows:
Embodiment:
The digital television broadcasting system specification that digital ground multimedia/television broadcasting (Digital terrestrial multimedia/televisionbroadcasting is called for short DTMB) system comes out for new development in recent years.The technology of DTMB comprises to be inserted known virtual noise (Pseudo Noise, be called for short PN) sequence in the guard interval, in order to the protected data signal, and can be further in order to the original position of Identification Data data.Fig. 1 a-1b shows the data structure of DTMB.As shown in the figure, data 100 and 101 are the data of the DTMB of a frame (frame), and wherein data 101 are that data 100 are postponed the result of D sampling point.Data 100 and 101 comprise the part of PN sequence (being denoted as PN code) and the part of data information (being denoted as Data) respectively, wherein PN sequence tail end partly can be repeated to make an addition to the head (being denoted as Pre PN) of PN sequence again, and the head of PN sequence can be repeated to make an addition to the tail end (being denoted as Post PN) of PN sequence again.For example, DTMB can use the PN420 specification, wherein can add 420 PN sequence before the data information altogether, comprise 255 complete PN sequences, and adding wherein, 82 first halfs in the PN sequence form Pre PN part, and add wherein at 83, so formation length totally 420 sequence in latter half of the formations Post PN part of PN sequence.
Because the content of the PN sequence that the known transmission end of receiving terminal is inserted, therefore after a plurality of by the conjugation of the DTMB data that receiver is received (data 100 for example shown in Figure 1) and result's (data 101 for example shown in Figure 1) of D sampling point of DTMB data delay carry out mutually multiplication, again that operation result and receiver local side is stored PN sequence is carried out the computing of correlation (correlation), finds out the sampling point max (Corr with maximum correlation
D(n)), synchronous to reach data information.Wherein, on behalf of the stored PN sequence of local side, the sampling point with maximum correlation mate the most in this sampling point and the DTMB data that receive, in case the coupling of PN sequence is finished, can obtain the original position of PN sequence in the received signal, then, just can pick out the data information original position by the position of PN sequence, it is synchronous to reach data information.Calculate the example of correlation can be further with reference to by people such as Ling-LongDai in November, 2008 at (the Institute of Electrical andElectronic Engineers of the Institute of Electrical and Electronics Engineers, be called for short IEEE) communication system international conference (International Conferenceon Communications Systems, be called for short ICCS) technical literature delivered, title is " in the time-domain synchronous orthogonal frequency-division multiplexing system new frequency synchronization algorithm " (A new frequencysynchronization algorithm in the TDS-OFDM systems).
Except the sequential that reaches data information was synchronous, receiver can further utilize resulting maximum correlation result of calculation max (Corr
D(n)) the carrier frequency drift Δ f that estimates transmission channel and produced, wherein the method for estimation of carrier frequency drift Δ f is as follows:
Wherein fs is a sampling frequency (Fig. 4, the sampling frequency of analog-to-digital converter 403).
Yet, in the transmission channel environment of multi-path (multi-path), because the received signal of receiving terminal can comprise the DTMB data from an above transmission path, therefore when carrying out correlation operation, except the institute that should have maximum correlation in theory asks (Desired term), also can additionally produce the no small error items of a plurality of correlations (False term), even the correlation of error items is asked item quite or bigger with institute.Ask the sampling point (having maximum correlation) that mates the most for PN sequence in theory, the multiplied result of a plurality of delay versions with the DTMB data of the conjugation of the DTMB data that just receive in theory carries out should having after the correlation operation sampling point of maximum correlation again with the PN sequence of local side, representing at this sampling point, PN sequence in the PN sequence of local side and the DTMB data that receive reaches synchronously, and other sampling point then is an error items.Fig. 2 shows the correlation operation result of received signal in the multi-path transmission channel environment, wherein transverse axis is represented sampling point, the longitudinal axis is represented the result of calculation of correlation, suppose that transmission channel comprises 2 paths, so the result of calculation of correlation should comprise that in theory two stronger institutes of correlation ask item 201.Yet, in case the correlation of error items 202 can cause at the sampling point max (Corr that seeks maximum correlation because of the effect that channel response produced of multi-path thereby when being higher than institute and asking
D(n)) obtain wrong result the time, thus, the data information that not only makes the mistake is synchronous, and the carrier frequency drift estimated result that also leads to errors.
Fig. 3 a-3b is presented at the estimation and the corresponding compensation result of carrier frequency drift in the multi-path transmission channel environment, transverse axis representative frame index (frame index) wherein, the longitudinal axis are represented according to carrying out carrier frequency drift results estimated Δ f suc as formula (1) described method.In more detail, Fig. 3 a is according to ask an estimating carrier frequency drift, the result who compensates, and Fig. 3 b is according to the drift of error items estimating carrier frequency, the result who compensates.Shown in Fig. 3 a, if can find the correct item of asking, the carrier frequency drift Δ f that then can estimate exactly, in this example, frame index is 0 o'clock, according to ask a carrier frequency drift of the reality of estimation be 100kHz.Then come compensating carrier frequency, after compensation after a while, can make actual carrier frequency drift converge on 0kHz according to the carrier frequency drift delta f that estimates.Yet,, be unable to estimate out actual carrier frequency drift Δ f if carry out the estimation of carrier frequency drift according to error items.That is to say that if the carrier frequency drift Δ f that estimates according to error items compensates, then Shi Ji carrier frequency drift then can't converge on 0kHz.Shown in Fig. 3 b, frame index is 0 o'clock, the carrier frequency drift of estimating according to error items is 200kHz (but not actual carrier frequency drift 100kHz), if compensate according to this carrier frequency drift 200kHz, after compensation after a while, make actual carrier frequency drift be-100kHz, but not converge on 0kHz.In view of this, the present invention proposes a kind of new carrier frequency drift method of estimation accurately to estimate the correct item of demanding, this carrier frequency drift method of estimation is not only applicable to single path transmission channel environment, more be applicable to multi-path transmission channel environment, synchronous in order to accurately to finish data information, and accurately estimate the carrier frequency drift.
Fig. 4 shows according to the described receiver 400 of one embodiment of the invention.Receiver 400 comprises a tuner (tuner) 401 and a demodulation module 402.Tuner 401 will be by the RF signal S that antenna received
RFBe converted to the intermediate-freuqncy signal of simulation.Demodulation module 402 can be integrated into a demodulator IC, receives the intermediate-freuqncy signal of simulating in order to self-tuner 401, and this signal of demodulation is to produce output signal S-
OUT(Transport Stream).
According to one embodiment of the invention, demodulation module 402 can comprise analog-to-digital converter (Analog to digital converter is called for short ADC) 403, fundamental frequency frequency mixer 404, time sequence reply device 405, equalizer 406, decoder 407 and signal analysis device 408.Analog-to-digital converter 403 is in order to (formula (1), the fs) intermediate-freuqncy signal of sampling simulation is with the output digital medium-frequency signal according to a sampling frequency.Fundamental frequency frequency mixer 404 carries out down converted according to a carrier frequency with digital medium-frequency signal, to produce digital baseband signal S
B Signal analysis device 408 is in order to analyze digital baseband signal S
BIn the characteristic of virtual noise sequence, and produce respectively according to the characteristic of virtual noise sequence and to feedback control signal S
CWith S
TTo fundamental frequency frequency mixer 404 and time sequence reply device 405, wherein fundamental frequency frequency mixer 404 is according to feedbacking control signal S respectively
CThe information that is provided changes the frequency of carrier wave, and in order to compensating carrier frequency offset, and time sequence reply device 405 is according to feedbacking control signal S
TThe sequential synchronizing information that the is provided digital baseband signal S that resamples
B, in order to signal is returned back to the sequential synchronous with the transmission end.The output signal of equalizer 406 balanced time sequence reply devices 405 is in order to the frequency response of compensation transmission channel, to remove the influence that transmission channel is caused.Equalizer 406 is inessential assembly in this embodiment.The balanced signals of crossing of the last decoding of decoder 407, the signal S-that deciphered with output signal
OUT
According to one embodiment of the invention, signal analysis device 408 can comprise a correlation calculations device 411, symbol limit checkout gear 412, sequential mistake estimation unit 413 and carrier frequency drift estimation unit 414.The digital baseband signal S of correlation calculations device 411 in order to obtaining from fundamental frequency frequency mixer 404
BConjugation a plurality of with digital baseband signal S
BThe version that postpones of difference carry out behind the phase multiplication to obtain a plurality of operation results, again PN sequence stored in these a plurality of operation results and the correlation calculations device 411 is carried out the computing of correlation (correlation) respectively, obtaining a plurality of correlativity calculation result, and produce correlation sequence C orr (n) according to a plurality of correlativity calculation result.Checkout gear 412 autocorrelation calculation elements 411 in symbol limit receive the correlation sequence, detect to have the maximum correlation sampling point in each frame, and note down the correlation values and the position of this sampling point, to produce symbol limit index signal S-
INDSequential mistake estimation unit 413 is coupled to symbol limit checkout gear 412, in order to according to symbol limit index signal S-
INDThe position of the indicated sampling point with maximum correlation and correlation values information such as (that is the amplitudes of this sampling point) produces back coupling control signal S
T, make that time sequence reply device 405 can be according to feedbacking control signal S
TWith digital baseband signal S
BResample, in order to return back to the sequential synchronous with the transmission end.Carrier frequency drift estimation unit 414 is coupled to symbol limit checkout gear 412 equally, in order to according to symbol limit index signal S-
INDThe correlation values of the indicated sampling point with maximum correlation (that is, the amplitude of this sampling point) is passed through suc as formula the drift of (1) described method estimating carrier frequency, and produces back coupling control signal S
C, make that fundamental frequency frequency mixer 404 can be according to feedbacking control signal S
CThe carrier frequency drift estimated value Δ f compensating carrier frequency offset that is provided.
As mentioned above, because the signal that receives in the transmission channel environment of multi-path can produce the error items (as shown in Figure 2) with big correlation when calculating correlation, thereby cause at the sampling point max (Corr that seeks maximum correlation
D(n)) obtain wrong result the time, the data information that makes the mistake is synchronous, and wrong carrier frequency drift estimated result (as shown in Figure 3).Therefore, according to one embodiment of the invention, correlation calculations device 411 is further strengthened the correlation of the item of asking when calculating correlation, make and in the correlativity calculation result that obtains, ask item can have maximum correlation values, can find out the position that institute asks exactly in is-symbol limit checkout gear 412, and then sequential mistake estimation unit 413 and carrier frequency drift estimation unit 414 can correctly obtain the estimated value of sequential synchronizing information and carrier frequency drift.
Fig. 5 a-5c shows described in the correlativity calculation result of multi-path transmission channel environment according to one embodiment of the invention.Can know by Fig. 5 a-5c and to understand that one embodiment of the invention are described strengthens the notion that institute asks item.After Fig. 5 a shows that the version of a delay D1 sampling point (as shown in Figure 1) of and DTMB data a plurality of according to the conjugation of the DTMB data that receive carries out mutually multiplication, the resulting result of computing of again that this operation result and receiver local side is stored PN sequence execution correlation (correlation).As shown in the figure, suppose sampling point n2 and n4 by being asked item, just the sampling point that mates the most of PN sequence in theory is positioned at sampling point n1, n3 and n5 and then is error items.Can find out by Fig. 5 a, because the effect that channel response produced of multi-path, make the correlation of the error items be positioned at sampling point n1 ask the correlation of item quite approaching with the institute that is positioned at sampling point n2, even greater than a correlation of being asked that is positioned at sampling point n4, therefore be very to find out institute exactly to ask (in a sampling point n2 and a n4) to carry out the synchronous and Frequency offset estimation of sequential as if the correlativity calculation result of basis shown in Fig. 5 a, thereby make a mistake.Fig. 5 b shows another correlation operation result, this result is after the version of a delay D2 sampling point (shown in the 1st figure) of and DTMB data a plurality of according to the conjugation of the DTMB data that receive carries out mutually multiplication, the resulting result of computing of again that this operation result and receiver local side is stored PN sequence execution correlation (correlation).Can find out by Fig. 5 b, because the effect that channel response produced of multi-path, the feasible correlation that is positioned at the error items of sampling point n5 is positioned at the correlation of the item of asking of sampling point n2 greatly, and, thereby can't tell institute and ask (in a sampling point n2 and a n4) greater than the correlation of item of asking that is positioned at sampling point n4.Therefore if carry out the synchronous and Frequency offset estimation of sequential, then can make a mistake according to the correlativity calculation result shown in Fig. 5 b.
Yet, shown in Fig. 5 a and Fig. 5 b, the position that takes place owing to error items can change along with the length variations that postpones D, and a position that takes place of asking can't change along with the difference that postpones D, therefore according to one embodiment of the invention, use the different resulting correlativity calculation result that postpone by adding up, strengthen the correlation of the item of asking, the feasible item of asking can significantly separate with the error items generation in the correlativity calculation result that obtains, shown in Fig. 5 c, the correlation of a n2 and the n4 of asking after adding up and error items produce and significantly separate, thus, signal analysis device 408 can be exactly be found out a tram of being asked according to the correlativity calculation result of strengthening, and then obtains accurately sequential synchronously and the estimated value of carrier frequency drift.
Fig. 6 shows according to the described correlation calculations device of one embodiment of the invention.According to one embodiment of the invention, correlation calculations device 611 can comprise two groups or more computing module.For clear elaboration notion of the present invention, Fig. 6 shows two groups of computing modules 612 and 613.It should be noted that the present invention also can use two groups of above computing modules; be not to be defined in to use two groups of computing modules; those skilled in the art can do some changes and retouching under the premise without departing from the spirit and scope of the present invention, so protection scope of the present invention is as the criterion with claim of the present invention.
According to embodiments of the invention, each computing module can comprise two groups of first in first out (First InFirst Out is called for short FIFO) register respectively.The length of first group of first-in first-out register designs according to different delay requirements respectively, and for example the length of first-in first-out register 621 can be designed to D1, in order to the digital baseband signal S with input
BPostpone D1 sampling point, and the length of first-in first-out register 631 can be designed to D2, in order to digital baseband signal S with input
BPostpone D2 sampling point.Digital baseband signal S in the process a plurality of unit of conjugation (conjugator abbreviates conj as) 622 and 632 with input
BAfter doing conjugation a plurality of (complex conjugate) conversion, digital baseband signal S
BThe version of a plurality of meetings of conjugation and its delay D1 (or D2) multiply each other by multiplier 623 and 633.Result after multiplying each other can further input to second group of first-in first-out register 624 and 634.Second group of first-in first- out register 624 and 634 lays respectively in correlation calculations unit 625 and 635, and in order to the computing of additional related, so its length can design with C2 according to required correlation length C 1 respectively.Digital baseband signal S
BConjugation a plurality of with postpone result after version multiplies each other and in correlation calculations unit 625 and 635, multiply each other with the stored PN sequence pointwise of receiver local side respectively, and the multiplied result and then obtain correlativity calculation result Corr_D1 (n) and Corr_D2 (n) of adding up respectively by second group of first-in first-out register 624 and 634.At last, by correlativity calculation result Corr_D1 (n) and Corr_D2 (n) that adder 614 adds up and obtains, the correlation of the item of asking in order to further to strengthen is with output correlation sequence C orr (n).
Shown in Fig. 5 a-5c, the position that takes place owing to error items can change along with the length variations that postpones D, and a position that takes place of asking can't change along with the difference that postpones D, use the different resulting correlativity calculation result that postpone through adding up, can strengthen the correlation of the item of asking, make the correlation of in resulting correlation sequence, asking item to produce and significantly separate with error items.Therefore symbol limit checkout gear 421 sampling point with maximum correlation that can find exactly, and produce as mentioned above and feedback control signal S
CWith S-
TTo fundamental frequency frequency mixer 404 and time sequence reply device 405, to carry out carrier frequency drift estimation and time sequence reply.
Fig. 7 shows according to the described signal analysis method of one embodiment of the invention.At first, receive an input signal (step S701), wherein this input signal can be a DTMB signal as shown in Figure 1a, comprises virtual noise sequence (PN Code) and data information (Data), and this input signal can be through the fundamental frequency signal after the fundamental frequency frequency mixer 404 execution down converted.Then, postpone this input signal (step S702), for example, postpone this input signal, to obtain having the input signal of different retardations respectively according to two or more different retardations according to a plurality of different retardations.Then, calculate the described input signal with described different retardation and the correlation of a virtual noise sequence, to obtain a plurality of correlativity calculation result (step S703).Then, produce a correlation sequence (step S704) according to described correlativity calculation result.At last, according to the original position and a carrier frequency drift amount (step S705) of this correlation sequencal estimation one data information.With reference to as shown in Figure 6 correlation calculations apparatus structure, wherein step S702 can also comprise with step S703: the described input signal conjugation of this input signal is a plurality of and that have different retardations multiplies each other, to obtain a plurality of multiplied result; And calculate this virtual noise sequence and correlation described multiplied result, to obtain described correlativity calculation result, retardation D1 for example shown in Figure 6 and D2, and correlativity calculation result Corr_D1 (n) and Corr_D2 (n).In step S704, by the Corr_D1 that adds up (n) and Corr_D2 (n) to produce correlation sequence C orr (n).
In addition, with reference to correlation calculations apparatus structure as shown in Figure 4, step S705 can also comprise: detect a sampling point that has maximum correlation among the correlation sequence C orr (n); A position and a correlation values according to this sampling point with maximum correlation produce symbol limit index signal S-
INDAnd an original position and a carrier frequency drift amount of estimating this data information according to this symbol limit index signal.
Though the present invention discloses as above with preferred embodiment; so it is not in order to limit scope of the present invention; those skilled in the art can do some changes and retouching under the premise without departing from the spirit and scope of the present invention, so protection scope of the present invention is as the criterion with claim of the present invention.
Claims (15)
1. demodulation module comprises:
One analog-to-digital converter is changed an analog if signal, to export a digital medium-frequency signal;
One fundamental frequency frequency mixer, receive this digital medium-frequency signal, and to produce a fundamental frequency signal, wherein this fundamental frequency frequency mixer is also adjusted this carrier frequency according to one first back coupling control signal, to compensate the carrier frequency drift of this carrier frequency according to this digital medium-frequency signal of carrier frequency frequency reducing;
One sequential return mechanism is feedback control signal this fundamental frequency signal of resampling according to one second;
One signal analysis device, receive this fundamental frequency signal, the correlation of analyzing this fundamental frequency signal and a predetermined virtual noise sequence is to obtain a plurality of correlation results, and strengthen described correlation results producing a correlation sequence, and produce this according to this correlation sequence and first feedback control signal and this second feedback signal; And
One decoder is in order to decipher an output signal of this time sequence reply device, to produce a decoding output signal.
2. demodulation module as claimed in claim 1 also comprises;
One equalizer, before this decoder is decoded this output signal of this time sequence reply device, this output signal of balanced this time sequence reply device, wherein an output signal of this this equalizer of decoder for decoding.
3. demodulation module as claimed in claim 1, wherein this signal analysis device comprises:
One correlation calculations device, receive this fundamental frequency signal, postpone this fundamental frequency signal to obtain described inhibit signal according to a plurality of different retardations, and calculate described inhibit signal and be somebody's turn to do the correlation of being scheduled to the virtual noise sequence, obtaining described correlativity calculation result, and the described correlativity calculation result that adds up is to obtain this correlation sequence;
One symbol limit checkout gear has a sampling point of maximum correlation according to this correlation Sequence Detection, and produces the marginal index signal of a symbol according to a position of this sampling point with a correlation values;
One carrier frequency drift estimation unit is estimated a carrier frequency drift amount according to this symbol limit index signal, and is given birth to this first feedback signal according to this carrier frequency drift volume production; And
One sequential mistake estimation unit produces this second feedback signal according to this symbol limit index signal.
4. demodulation module as claimed in claim 3, wherein this carrier frequency drift estimation unit is estimated this carrier frequency drift amount according to this correlation values of this sampling point.
5. demodulation module as claimed in claim 3, wherein this sequential mistake estimation unit produces this second feedback signal according to this position and this correlation values of this sampling point.
6. demodulation module as claimed in claim 3, wherein this correlation calculations device comprises:
A plurality of computing modules, wherein each computing module comprises:
One first-in first-out register is in order to deposit this fundamental frequency signal of a set retardation;
The a plurality of unit of one conjugation are in order to do this fundamental frequency signal a plurality of conversions of conjugation;
One multiplier is coupled to this first-in first-out register and a plurality of unit of this conjugation, carries out multiplying in order to the output and an output of these a plurality of unit of conjugation of advancing to go out earlier register according to this, to obtain a multiplied result; And
One correlation calculations unit is in order to calculate this multiplied result and the correlation that should be scheduled to the virtual noise sequence, to obtain this correlativity calculation result; And
One adder is in order to add up this correlativity calculation result of described computing module output, to produce this correlation sequence.
7. signal analysis device in order to the estimating carrier frequency drift, comprising:
One correlation calculations device, receive an input signal, postpone this input signal to obtain a plurality of inhibit signals according to a plurality of different retardations, and calculate the correlation of a described inhibit signal and a predetermined virtual noise sequence, obtaining a plurality of correlativity calculation result, and produce a correlation sequence according to described correlativity calculation result;
One symbol limit checkout gear has a sampling point of maximum correlation according to this correlation Sequence Detection, and produces symbol limit index signal according to a correlation values of this sampling point; And
One carrier frequency drift estimation unit is estimated a carrier frequency drift amount according to this symbol limit index signal.
8. signal analysis device as claimed in claim 7, wherein this correlation calculations device adds up described correlativity calculation result to produce this correlation sequence.
9. signal analysis device as claimed in claim 7, this symbol limit checkout gear wherein, also the position according to this sampling point produces this symbol limit index signal, also comprises:
One sequential mistake estimation unit is estimated the original position of a data information of this input signal according to this symbol limit index signal.
10. signal analysis device as claimed in claim 7, wherein this correlation calculations device comprises:
A plurality of computing modules, wherein each computing module comprises:
One first-in first-out register is in order to deposit this input signal of a set retardation;
The a plurality of unit of one conjugation are in order to do this input signal a plurality of conversions of conjugation;
One multiplier is coupled to this first-in first-out register and a plurality of unit of this conjugation, carries out multiplying in order to the output and an output of these a plurality of unit of conjugation of advancing to go out earlier register according to this, to obtain a multiplied result; And
One correlation calculations unit is in order to calculate this multiplied result and the correlation that should be scheduled to the virtual noise sequence, to obtain this correlativity calculation result; And
One adder is in order to add up this correlativity calculation result of described computing module output, to produce this correlation sequence.
11. a signal analysis method in order to the estimating carrier frequency drift, comprising:
Receive an input signal, wherein this input signal comprises a data information and a virtual noise sequence at least;
Postpone this input signal according to a plurality of different retardations, to obtain a plurality of inhibit signals;
Calculate the correlation of a described inhibit signal and a predetermined virtual noise sequence, to obtain a plurality of correlativity calculation result;
Produce a correlation sequence according to described correlativity calculation result; And
Carrier frequency drift amount according to this this input signal of correlation sequencal estimation.
12. signal analysis method as claimed in claim 11, wherein the generation step of this correlation sequence comprises that the described correlativity calculation result that adds up is to produce this correlation sequence.
13. signal analysis method as claimed in claim 11, wherein the estimating step of this carrier frequency drift amount comprises:
A sampling point that has maximum correlation according to this correlation Sequence Detection; And
Estimate this carrier frequency drift amount according to a correlation values of this sampling point.
14. signal analysis method as claimed in claim 13 also comprises:
The original position of estimating this data information according to a position and this correlation values of this sampling point.
15. signal analysis method as claimed in claim 11, the calculation procedure of wherein said correlativity calculation result also comprises:
A plurality of and the described inhibit signal of one conjugation of this input signal is multiplied each other, to obtain a plurality of multiplied result; And
Calculate this predetermined virtual noise sequence and correlation described multiplied result, to obtain described correlativity calculation result.
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| Publication number | Priority date | Publication date | Assignee | Title |
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| CN107105222A (en) * | 2016-02-23 | 2017-08-29 | 晨星半导体股份有限公司 | Symbol detection circuit and method |
| CN112242967A (en) * | 2020-09-11 | 2021-01-19 | 北京邮电大学 | Multi-carrier complementary code single code cyclic shift multiple access method |
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| US6683924B1 (en) * | 1999-10-19 | 2004-01-27 | Ericsson Inc. | Apparatus and methods for selective correlation timing in rake receivers |
| US7359314B2 (en) * | 2001-12-26 | 2008-04-15 | Hitachi, Ltd. | Signal transmission system for transmitting a signal with a guard interval and a demodulation method thereof |
| CN101227443A (en) * | 2007-01-19 | 2008-07-23 | 华为技术有限公司 | Apparatus and method for generating training symbol and estimating bias of training symbol |
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Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
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| CN107105222A (en) * | 2016-02-23 | 2017-08-29 | 晨星半导体股份有限公司 | Symbol detection circuit and method |
| CN112242967A (en) * | 2020-09-11 | 2021-01-19 | 北京邮电大学 | Multi-carrier complementary code single code cyclic shift multiple access method |
| CN112242967B (en) * | 2020-09-11 | 2021-11-23 | 北京邮电大学 | Multi-carrier complementary code single code cyclic shift multiple access method |
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