CN101682601A - Frequency domain interpolation based receiver for multicarrier signals - Google Patents
Frequency domain interpolation based receiver for multicarrier signals Download PDFInfo
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- CN101682601A CN101682601A CN200880017844A CN200880017844A CN101682601A CN 101682601 A CN101682601 A CN 101682601A CN 200880017844 A CN200880017844 A CN 200880017844A CN 200880017844 A CN200880017844 A CN 200880017844A CN 101682601 A CN101682601 A CN 101682601A
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L25/00—Baseband systems
- H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
- H04L25/0202—Channel estimation
- H04L25/0224—Channel estimation using sounding signals
- H04L25/0228—Channel estimation using sounding signals with direct estimation from sounding signals
- H04L25/023—Channel estimation using sounding signals with direct estimation from sounding signals with extension to other symbols
- H04L25/0232—Channel estimation using sounding signals with direct estimation from sounding signals with extension to other symbols by interpolation between sounding signals
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L25/00—Baseband systems
- H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
- H04L25/0202—Channel estimation
- H04L25/0212—Channel estimation of impulse response
- H04L25/0216—Channel estimation of impulse response with estimation of channel length
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L25/00—Baseband systems
- H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
- H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
- H04L25/03006—Arrangements for removing intersymbol interference
- H04L25/03159—Arrangements for removing intersymbol interference operating in the frequency domain
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L25/00—Baseband systems
- H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
- H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
- H04L25/03006—Arrangements for removing intersymbol interference
- H04L2025/0335—Arrangements for removing intersymbol interference characterised by the type of transmission
- H04L2025/03375—Passband transmission
- H04L2025/03414—Multicarrier
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L25/00—Baseband systems
- H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
- H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
- H04L25/03006—Arrangements for removing intersymbol interference
- H04L2025/03433—Arrangements for removing intersymbol interference characterised by equaliser structure
- H04L2025/03439—Fixed structures
- H04L2025/03522—Frequency domain
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- H—ELECTRICITY
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- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L25/00—Baseband systems
- H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
- H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
- H04L25/03006—Arrangements for removing intersymbol interference
- H04L2025/03433—Arrangements for removing intersymbol interference characterised by equaliser structure
- H04L2025/03535—Variable structures
- H04L2025/03547—Switching between time domain structures
- H04L2025/03566—Switching between time domain structures between different tapped delay line structures
- H04L2025/03585—Modifying the length
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- H04L25/00—Baseband systems
- H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
- H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
- H04L25/03006—Arrangements for removing intersymbol interference
- H04L2025/03777—Arrangements for removing intersymbol interference characterised by the signalling
- H04L2025/03783—Details of reference signals
- H04L2025/03796—Location of reference signals
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L25/00—Baseband systems
- H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
- H04L25/0202—Channel estimation
- H04L25/022—Channel estimation of frequency response
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/26—Systems using multi-frequency codes
- H04L27/2601—Multicarrier modulation systems
- H04L27/2647—Arrangements specific to the receiver only
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L5/00—Arrangements affording multiple use of the transmission path
- H04L5/0001—Arrangements for dividing the transmission path
- H04L5/0003—Two-dimensional division
- H04L5/0005—Time-frequency
- H04L5/0007—Time-frequency the frequencies being orthogonal, e.g. OFDM(A), DMT
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L5/00—Arrangements affording multiple use of the transmission path
- H04L5/003—Arrangements for allocating sub-channels of the transmission path
- H04L5/0048—Allocation of pilot signals, i.e. of signals known to the receiver
- H04L5/0051—Allocation of pilot signals, i.e. of signals known to the receiver of dedicated pilots, i.e. pilots destined for a single user or terminal
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- Engineering & Computer Science (AREA)
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- Computer Networks & Wireless Communication (AREA)
- Signal Processing (AREA)
- Noise Elimination (AREA)
Abstract
A receiver apparatus (1) for receiving a signal over a fading channel comprises a frequency domain interpolation unit (16) with a filter unit (10), a power comparison unit (20), and a processing unit(21). The filter unit (10) comprises a first filter element (11), which is a reference filter, and a second filter element (12). The first filter element (11) is arranged as large-band filter. The power comparison unit (20) compares the power of the signal filtered with said second filter element (12) with the power of the signal filtered with said first filter element (11). The processing unit (21) determines an appropriate filter length for a third filter element (13) of the filter unit (10) on the basis of this comparison. Thereby, a trade-off is made between an additional power received due to a long echo and an additional Gaussian noise power. The signal filtered with the third filter element (13) is sent to a signal processing unit (22) for further signal processing and then output at said output (4) of the receiver apparatus (1).
Description
Technical field
The present invention relates to a kind of receiver device of received signal on fading channel, a kind of wireless network and a kind of method of transmitting data that comprises this receiver device of being used for.More specifically, the present invention relates to based on the wireless network that for example in DVB-T or DVB-H, uses as OFDM modulation techniques such as (OFDM).
Background technology
EP 0 838 928 A2 have described a kind of equipment that is used to receive the digital signal of transmitting as OFDM multicarrier symbol sequence on transmission channel.Thereby such transmission signals is included in the reference symbol of each predetermined OFDM symbols place transmission.Known equipment comprises and is used for by the fundametal component after the demodulation of the OFDM symbol that will before receive producing the device of the estimation of channel transfer functions divided by at equilibrium, forward error correction, recompile with the corresponding estimation of the identical previous transmission symbol that obtains after remapping.In addition, by the respective component of the component after the demodulation that will be scheduled to the OFDM reference symbol, obtain the initial estimation of channel transfer functions divided by the identical traffic symbol of in receiver, storing.This known equipment comprises frequency domain filter, be used for greater than protection at interval duration but the equivalence " bandwidth " of time gap between the periodicity repetition of the channel impulse response that causes less than sub-sampling owing to frequency domain come filtering is carried out in the estimation of channel transfer functions.
Be that from the shortcoming of the known equipment of EP 0 838 928 A2 the implementation complexity has by the very long feedback control loop of Viterby decoder to channel estimating.In addition, for the channel with fast-changing impulse response, the signal quality that receives may be degenerated.
Summary of the invention
The purpose of this invention is to provide a kind of receiver device, wireless network and transmit the method for data with improved performance, especially the channel to impulse response with variation has improved adaptive.
This purpose is the receiver device that limited by claim 1, realizes by wireless network that claim 8 limited and by the method that claim 9 limited.Mentioned favourable improvement of the present invention in the dependent claims.
It should be noted that first filter element, second filter element and the 3rd filter element not necessarily will be embodied as different elements.For example, filter cell can provide general filter element.This general filter element can be carried out the operation of first filter element, second filter element and the 3rd filter element respectively.
Advantageously, power comparison module is calculated as fractional value with power ratio, the molecule of described fractional value is the power that utilizes the signal of second filter filtering, denominator is the power that utilizes the signal of first filter filtering, and processing unit recently is that the 3rd filter element is determined suitable filter length based on this power.This advantage that has is, can carry out determining of suitable filter length with reference to relative value, and described relative value is utilized the intensity of the signal of second filter filtering with reference to the intensity measurement that utilizes the signal of first filter filtering.
In addition, advantageously, processing unit changes the filter length of second filter element, makes power ratio at least near 100%, so that provide good reception aspect the noise to received signal at received signal power.Equal at the most at the filter length of second filter under the situation of filter length of first filter, power ratio is at most 100%.In this case, processing unit can change the filter length of second filter element, so that realize suitable power ratio.
Therefore, additional advantage is, receives a large amount of signal powers, and the power of the noise that receives simultaneously is less relatively.Therefore, advantageously, use the shortest filter length of second filter element, for this length, power ratio is at least near 100%.
Advantageously, processing unit changes the filter length of second filter element, so that the long echo of detection signal at least, as long as the power of this long echo surpasses certain threshold level.This makes can receive a large amount of utilizable signal powers.
Therefore, must between the secondary power of the reception of the additional long echo of signal and the noise that adds owing to the increase of filter length, weigh.Therefore, advantageously, the secondary power of the noise (especially Gaussian noise) that processing unit adds based on the power of long echo and owing to the increase of filter length is determined suitable filter length, so that receive long echo.
Advantageously, first filter element is big band filter.This advantage that has be can reference signal power total amount.
In addition, advantageously, first filter element is can be with narrow band filter for referencial use.This advantage that has is, power that can the reference signal major part.Therefore, can dynamically reduce the filter length of the 3rd filter by the disappearance that detects long echo, this length is the bandwidth of equalization filter.
By reference embodiment described below, these and other aspects of the present invention will become apparent and be illustrated.
Description of drawings
According to below with reference to the accompanying drawing description of the preferred embodiment of the present invention, the present invention's easy to understand that will become, in the accompanying drawing:
Fig. 1 shows the schematic diagram according to the receiver device of the wireless network of the embodiment of the invention; And
Fig. 2 shows the block diagram of the frequency domain interpolation unit of receiver device shown in Figure 1.
Embodiment
Fig. 1 shows the receiver device 1 of wireless network 2.Receiver device 1 comprises input 3 and output 4.Input 3 is connected with antenna 5.Wireless network 2 also comprises transmitter 6 and antenna 7.Wireless network 2 can also be based on the standard that adopts as the modulation scheme of OFDM (OFDM) and so on.In such standard, signal comprises the pilot signal that places the characteristic frequency place, and described pilot signal allows to obtain the correct estimation of channel, so that handle the echo problems under the mobile environment easily.In the standard of DVB-T and so on, some pilot signals only turn in the process of data of other symbols effectively at some symbols.These pilot signals are arranged to the pilot signal of dispersion, are used for channel estimating and equilibrium.Yet receiver device 1 of the present invention and wireless network 2 can also be used for other situations, especially adopt the situation of other modulation schemes.
In order to obtain channel estimating, all the pilot signal of disperseing is carried out interpolation in time domain and frequency domain at each subcarrier of each OFDM symbol.In frequency domain, the strategy that suppresses the maximum possible noise is to use the narrowest possible interpolation filter about channel impulse response.Yet under mobile environment, the bandwidth of filter may not be selected as even as big as the emergent long echo of balanced possibility.
With reference to figure 2 frequency domain interpolation unit 16 is described in more detail.
Fig. 2 shows the schematic block diagram of frequency domain interpolation unit 16.Frequency domain interpolation unit 16 comprises input 17, to import the estimation to pilot positions after DFT.Frequency domain interpolation unit 16 is with respect to frequency domain, at the channel estimating after each symbol (especially data symbol) output interpolation.
Can use Gaussian noise model to be described in the noise that to the process of receiver device 1 transmission, is added into signal from transmitter 6.Such Gaussian noise has been added specific noise energy to this signal, and this noise energy depends on the filter cell 10 employed filter lengths of receiver device 1.Filter cell 10 comprises first filter element 11, second filter element 12 and the 3rd filter element 13.In an embodiment of the present invention, the filter length of first filter element 11 be fix or in long-time relatively, be set to fixed value at least.In addition, the filter length of first filter element 11 is selected as making win filter element 11 to be broadband filter.The filter length of second filter element 12 is variable.In addition, advantageously, the filter length of second filter element 12 less than or equal the filter length of first filter element 11 at the most, this is because the filter length of first filter element 11 is longer relatively.
The filter length that it should be noted that second filter element 12 also can be variable, and the fixed filters length that makes the filter element 11 of winning is in the scope of the filter length of second filter element 12.In this case, advantageously, the filter length of first filter element 11 should be not long.Alternative as another, the filter length of first filter element 11 can be chosen as shorter relatively.Then, this first filter element 11 is arranged to narrow band filter.In this case, advantageously, the filter length of second filter element 12 is equal to or greater than the length of first filter element 11.
Hereinafter, suppose that first filter element 11 is arranged to broadband filter, the filter length of second filter element 12 is equal to or less than the length of first filter element 11.Correspondingly, can derive other situations.
Although the huge interference that may suffer in the channel of land, yet Gaussian noise remains one of restrictive noise of tool usually, influences each function restriction.Because acting in the balancing procedure of Gaussian noise is particularly crucial, a kind of method of considering that the interpolation filter bandwidth reduces noisiness only is the bandwidth that reduces interpolation filter.This can improve performance, especially under the situation that does not detect long echo.Then, can use narrower bandwidth, and this narrower bandwidth provides more much better performance aspect noise suppressed.Yet when long echo occurring, the power that detects new long echo relatively apace is necessary.Otherwise when the filter that has a bandwidth that reduces when use suppressed more noises, equalizer possibly can't carry out equilibrium, and the data of many equilibriums will be degenerated.
Making according to the receiver device 1 of the embodiment of the invention can the new at least long echo of fast detecting, make and to determine that suitable filter length carries out signal and receives (especially balanced), and with the filter length of this filter length as the 3rd filter element 13, described the 3rd filter element 13 is used for the signal that is sent to output 4 is carried out filtering.
The selection that it should be noted that the suitable filter length of the 3rd filter element 13 is the additional signal power that receiving when this filter length increases and the balance between the additive noise power.Therefore, advantageously, when power determining unit 14 when definiteness shows that needs switch back big frequency band interpolation filter really, power comparison module 20 switches back bigger filter length, to avoid making balanced data degradation.This is reducing to suppress a kind of possibility mode of Gaussian noise of protection interpolation filter bandwidth.
If first filter element 11 is big band filters, and the filter length of second filter element 12 less than or equal the filter length of first filter element 11 at the most, then the power of power determining unit 14 determined power (being the power that utilizes the signal of first filter element, 11 filtering) specific power determining unit 15 outputs all the time is big, and this is because it comprises more Gaussian noise.Yet, if the output of power determining unit 15 surpasses specific threshold value with the ratio of the output of power determining unit 14, show that then this power of crossing volume of decaying by the narrow band filter of employed second filter element 12 is because echo out of balance causes.
It should be noted that use at the narrow band filter of first filter element 11 as a reference, can also be applied to receiver device detect by the disappearance that detects long echo the possibility of the bandwidth of dynamic reduction the 3rd filter element 13.
When in the 3rd filter element 13, being provided with and having determined the suitable filter length of the 3rd filter element 13, carry out filtering to the received signal and send it to output 18 by the 3rd filter element 13.
9 pairs of these signals of decoder element are decoded and are exported decoded signal to signal processing unit 22 to carry out further signal processing.After further signal processing, in output 4 place's output signals of receiver device 1.
Although disclose example embodiment of the present invention, yet to those skilled in the art apparently, under the premise without departing from the spirit and scope of the present invention, can carry out various changes and modification to the present invention, these changes and modification will realize some advantages in the advantage of the present invention.This modification to the present invention's design should be contained by claims, in the claims the scope that reference marker should be construed as limiting the invention.In addition, in specification and claims, the implication of " comprising " should not be understood that to get rid of other elements or step." one " does not get rid of a plurality ofly in addition, and the function of the described multiple arrangement of claim can be realized in single processor or other unit.
Claims (10)
1, a kind of receiver device (1) that is used for received signal on fading channel, wherein, symbol is modulated onto on the sub-carrier frequencies channel, pilot signal is placed in some the sub-carrier frequencies channel places in the described sub-carrier frequencies channel, described receiver device comprises the frequency domain interpolation unit (16) that is used at described sub-carrier frequencies channel place described pilot signal being carried out interpolation, described frequency domain interpolation unit (16) comprises and is used at frequency domain the described signal that receives being carried out filter filtering unit (10), and power comparison module (20), described filter cell (10) comprises first filter element (11), second filter element (12) and at least the three filter element (13), the length of described second filter element (12) is with respect to the variable-length of described first filter element (11), described power comparison module (20) will utilize the signal power of the described signal of described second filter element (12) filtering to compare with the signal power of the described signal that utilizes described first filter element (11) filtering, processing unit (21) determines suitable filter length for described the 3rd filter element (13) based on the output of described power comparison module (20), described the 3rd filter element (13) carries out filtering to the described signal that receives, and the filter length of described the 3rd filter element (13) is configured to determined described suitable filter length.
2, receiver device according to claim 1, it is characterized in that, described power comparison module (20) is calculated as fractional value with power ratio, the molecule of described fractional value is the described power that utilizes the described signal of described second filter element (12) filtering, denominator is the described power that utilizes the described signal of described first filter element (11) filtering, and described processing unit (21) is recently determined described suitable filter length for described the 3rd filter element (13) based on described power.
3, receiver device according to claim 2 is characterized in that, described processing unit (21) changes the described filter length of described second filter element (12), makes described power ratio at least near 100%.
4, receiver device according to claim 3, it is characterized in that, described processing unit (21) is defined as the described suitable filter length of described the 3rd filter element (13) the shortest filter length of described second filter element (12), for the shortest described filter length, described power ratio is at least near 100%.
5, receiver device according to claim 2, it is characterized in that, described processing unit (21) changes the described filter length of described second filter element (12), to detect the long echo of described signal at least, described processing unit (21) is determined described suitable filter length, make that the described long echo of described signal is within described suitable filter length when the power of described long echo surpasses certain threshold level.
6, receiver device according to claim 5, it is characterized in that, the secondary power of the Gaussian noise that described processing unit (21) adds based on the described power of described long echo and owing to the increase of filter length is determined described suitable filter length, to receive described long echo.
7, a kind of wireless network (2), comprise transmitter (6) and receiver device (1) at least, wherein, described transmitter (6) sends signal to described receiver device (1) on attenuation channel, described signal comprises the transmission symbol that is modulated onto on the sub-carrier frequencies channel, and described receiver device (1) is arranged according to claim 1.
8, a kind of from the method for transmitter (6) to receiver device (1) transmission data, wherein, symbol is modulated onto on the sub-carrier frequencies channel, and pilot signal is placed in some the sub-carrier frequencies channel places in the described sub-carrier frequencies channel, said method comprising the steps of:
Utilize first filter length that the received signal that comprises pilot signal of sub-carrier frequencies channel is carried out filtering at frequency domain;
At described frequency domain utilization at least the second filter length described received signal is carried out filtering;
Compare with the signal power of the described received signal of utilizing the described second filter length filtering utilizing the signal power of the described received signal of the described first filter length filtering;
Based on the described suitable filter length that relatively is identified for described received signal is carried out filtering; And
Utilize described suitable filter length to come described received signal is carried out filtering at described frequency domain.
9, method according to claim 8 is characterized in that, filter length is big band filter length at least.
10, method according to claim 8 is characterized in that, filter length is narrow band filter length at least.
Applications Claiming Priority (3)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| EP07290676 | 2007-05-30 | ||
| EP07290676.1 | 2007-05-30 | ||
| PCT/IB2008/052075 WO2008146242A2 (en) | 2007-05-30 | 2008-05-27 | Frequency domain interpolation based receiver for multicarrier signals |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN101682601A true CN101682601A (en) | 2010-03-24 |
| CN101682601B CN101682601B (en) | 2012-10-03 |
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ID=40075620
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN200880017844XA Active CN101682601B (en) | 2007-05-30 | 2008-05-27 | Frequency domain interpolation based receiver for multicarrier signals |
Country Status (4)
| Country | Link |
|---|---|
| US (1) | US8571156B2 (en) |
| EP (1) | EP2156628A2 (en) |
| CN (1) | CN101682601B (en) |
| WO (1) | WO2008146242A2 (en) |
Family Cites Families (11)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| IT1288778B1 (it) | 1996-10-25 | 1998-09-24 | Rai Radiotelevisione Italiana | Procedimento e apparato di ricezione di segnali numerici in multiplex codificato e divisione di frequenze. |
| DE19929178C2 (en) * | 1999-06-25 | 2002-10-24 | Infineon Technologies Ag | Phase locked loop system |
| CN1114296C (en) * | 2000-07-18 | 2003-07-09 | 华为技术有限公司 | Bandwidth-variable channel estimation method for frequency-selective channel and its device |
| JP4071468B2 (en) * | 2001-09-28 | 2008-04-02 | 株式会社東芝 | OFDM receiver |
| DE10155179B4 (en) * | 2001-11-12 | 2006-11-23 | Andrew Wireless Systems Gmbh | Digital repeater with bandpass filtering, adaptive pre-equalization and suppression of self-oscillation |
| US7085315B1 (en) * | 2002-04-15 | 2006-08-01 | Vixs, Inc. | Digital demodulation utilizing frequency equalization |
| US7085317B2 (en) * | 2003-02-18 | 2006-08-01 | Qualcomm, Inc. | Communication receiver with an adaptive equalizer length |
| KR100590354B1 (en) * | 2003-12-15 | 2006-06-15 | 삼성탈레스 주식회사 | An Apparatus and Method for compensation for residual frequency offset in OFDM system |
| US7738655B2 (en) * | 2006-04-12 | 2010-06-15 | Texas Instruments Incorporated | Interference canceller tap sharing in a communications transceiver |
| CN1866945A (en) * | 2006-05-11 | 2006-11-22 | 上海交通大学 | RLS channel estimating method based on variable forgetting factor in OFDM system |
| US7961806B2 (en) * | 2007-01-23 | 2011-06-14 | Mediatek Inc. | Power adaptive channel estimation for a multi-path receiving |
-
2008
- 2008-05-27 EP EP08763117A patent/EP2156628A2/en not_active Withdrawn
- 2008-05-27 CN CN200880017844XA patent/CN101682601B/en active Active
- 2008-05-27 WO PCT/IB2008/052075 patent/WO2008146242A2/en active Application Filing
- 2008-05-27 US US12/599,697 patent/US8571156B2/en active Active
Also Published As
| Publication number | Publication date |
|---|---|
| WO2008146242A3 (en) | 2009-05-28 |
| CN101682601B (en) | 2012-10-03 |
| EP2156628A2 (en) | 2010-02-24 |
| WO2008146242A2 (en) | 2008-12-04 |
| US20100303161A1 (en) | 2010-12-02 |
| US8571156B2 (en) | 2013-10-29 |
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