CN101631096B - Transmitter, receiver and adjusting method for reducing in-phase/quadrature phase mismatching - Google Patents
Transmitter, receiver and adjusting method for reducing in-phase/quadrature phase mismatching Download PDFInfo
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- CN101631096B CN101631096B CN200810131522XA CN200810131522A CN101631096B CN 101631096 B CN101631096 B CN 101631096B CN 200810131522X A CN200810131522X A CN 200810131522XA CN 200810131522 A CN200810131522 A CN 200810131522A CN 101631096 B CN101631096 B CN 101631096B
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Abstract
The invention provides a transmitter, a receiver and an adjusting method for reducing the in-phase/quadrature phase mismatching, which can reduce the phase error related with the frequency. The method comprises the following steps: receiving a first in-phase signal and a first quadrature phase signal; adjusting a set of parameters so as to reduce the in-phase/quadrature phase mismatching related with the first in-phase signal and the first quadrature phase signal; receiving a second in-phase signal and a second quadrature phase signal, wherein one of the frequency and the phase of the second in-phase signal is different from the first in-phase signal; adjusting the set of parameters to reduce the in-phase/quadrature phase mismatching related with the second in-phase signal and the second quadrature phase signal; and according to the adjusting result, selecting final value of the set of parameters so as to reduce the second in-phase signal and a second quadrature phase signal related with different frequencies.
Description
Technical field
The present invention relates to a kind of transmitter, receiver and method of adjustment, particularly relate to a kind of be used to reduce the mutually unmatched transmitter of inphase/orthogonal, receiver and method of adjustment.
Background technology
Consult Fig. 1 and Fig. 2, known direct raising frequency formula (direct up-conversion) transmitter comprises 13,14, two frequency mixers of 11,12, two low pass filters of two-digit to analog converter 15,16, a summer 17, a power amplifier 18 and an antenna 19.On homophase (in-phase) path, the homophase fundamental frequency signal BBI of a numeral
tCarry out numeral to analog-converted in regular turn, low pass filtered involves and a homophase local oscillated signal LOI
tMixing is to produce the homophase radiofrequency signal RFI of a simulation
t, and on quadrature phase (quadrature-phase) path, the quadrature phase fundamental frequency signal BBQ of a numeral
tCarry out numeral to analog-converted in regular turn, low pass filtered involves and quadrature local oscillated signal LOQ mutually
tMixing is to produce an analog orthogonal phase radiofrequency signal RFQ
tThese two radiofrequency signal RFI
t, RFQ
tCarry out totalling and power amplification again, to be transmitted into the external world.
One known direct frequency-reducing type (direct down-conversion) receiver comprises an antenna 21,25,26 and two analog-to- digital converters 27,28 of 23,24, two low pass filters of 22, two frequency mixers of a low-noise amplifier (LNA).The radiofrequency signal of one simulation is carried out on in-phase path and a homophase local oscillated signal LOI after reception and amplifying in regular turn
rMixing, low pass filtered involve to be simulated to digital translation, to produce the homophase fundamental frequency signal BBI of a numeral
r, and on the quadrature phase path, carry out in regular turn and quadrature local oscillated signal LOQ mutually
rMixing, low pass filtered involve to be simulated to digital translation, to produce the quadrature phase fundamental frequency signal BBQ of a numeral
r
Can there be amplitude error and phase error between the square on square on the in-phase path and the quadrature phase path; This phenomenon is called that inphase/orthogonal does not match (I/Q mismatch) mutually or inphase/orthogonal uneven (I/Q imbalance) mutually; Signal to noise ratio (snr) can be reduced, and data loss maybe be caused.Developed at present and many mutually unmatched technology of inphase/orthogonal that are used to reduce; And these known technologies are all treated as phase error and in signal band, are fixed value (constant value), reduce phase error and only once adjust to certain CF.
Consulting Fig. 2 and Fig. 3, is example with receiver shown in Figure 2, if exist colony to postpone (group delay) error (in Fig. 2 with τ between the local oscillated signal input of frequency mixer 23,24
1Represent), the phase error that is then caused is at signal band-f
m-f
mIn be fixed value, shown in Fig. 3 (a), in this case, known technology can effectively reduce fixing phase error; Yet, if exist colony's delay error between the output of frequency mixer 23,24 (in Fig. 2 with τ
2Represent), the phase error that is then caused is at signal band-f
m-f
mIn with the linear ratio of frequency, shown in Fig. 3 (b), in this case, known technology can't effectively reduce the phase error with frequency dependence.
Summary of the invention
Therefore, the object of the invention promptly in that a kind of mutually unmatched method of adjustment of inphase/orthogonal that is used to reduce is provided, can reduce the phase error with frequency dependence.
So the present invention is used to reduce the mutually unmatched method of adjustment of inphase/orthogonal and is applicable to a transmitter.The method includes the steps of:
Receive one first in-phase signal and one first quadrature-phase;
Adjusting one group of parameter does not match with this first in-phase signal and the relevant inphase/orthogonal of this first quadrature-phase to reduce mutually;
Receive one second in-phase signal and one second quadrature-phase, wherein, this second in-phase signal one is different from this first in-phase signal in frequency and phase place;
Adjusting this group parameter does not match with this second in-phase signal and the relevant inphase/orthogonal of this second quadrature-phase to reduce mutually; And
According to aforesaid adjustment result, select the end value of this group parameter, do not match mutually to reduce the inphase/orthogonal relevant with different frequency.
The present invention is used to reduce the mutually unmatched method of adjustment of inphase/orthogonal and is applicable to a receiver.The method includes the steps of:
Receive one first radiofrequency signal, wherein, this first radiofrequency signal produces from one first in-phase signal and one first quadrature-phase;
Adjusting one group of parameter does not match to reduce the inphase/orthogonal relevant with this first radiofrequency signal mutually;
Receive one second radiofrequency signal, wherein, this second radiofrequency signal produces from one second in-phase signal and one second quadrature-phase, and this second in-phase signal one is different from this first in-phase signal in frequency and phase place;
Adjusting this group parameter does not match to reduce the inphase/orthogonal relevant with this second radiofrequency signal mutually; And
According to aforesaid adjustment result, select the end value of this group parameter, do not match mutually to reduce the inphase/orthogonal relevant with different frequency.
And another object of the present invention is promptly providing a kind of transmitter and a kind of receiver, can reduce the phase error with frequency dependence.
So transmitter of the present invention comprises a transmitter module, a detecting unit and an adjustment unit.An in-phase signal and the quadrature-phase of this transmitter module to receiving carried out phase place and amplitude compensation according to one group of parameter, and carries out homophase and the mixing of quadrature phase respectively, and carries out totalling, to produce a radiofrequency signal.This detecting unit is according to this radiofrequency signal, produces do not match the mutually detection signal of degree of a reaction inphase/orthogonal.When this adjustment unit receives one first in-phase signal and one first quadrature-phase at this transmitter module; Do not match mutually with this first in-phase signal and the relevant inphase/orthogonal of this first quadrature-phase to reduce according to this this group parameter of detection signal adjustment; And when this transmitter module receives one second in-phase signal and one second quadrature-phase; Do not match mutually with this second in-phase signal and the relevant inphase/orthogonal of this second quadrature-phase to reduce according to this this group parameter of detection signal adjustment; And according to aforesaid adjustment result, select the end value of this group parameter, do not match mutually to reduce the inphase/orthogonal relevant with different frequency.Wherein, this second in-phase signal one is different from this first in-phase signal in frequency and phase place.
Receiver of the present invention comprises a receiver module, a detecting unit and an adjustment unit.This receiver module carries out homophase and the mixing of quadrature phase, and carries out phase place and amplitude compensation according to one group of parameter, to produce two fundamental frequency signals the radiofrequency signal that receives.This detecting unit is according to these two fundamental frequency signals, produces do not match the mutually detection signal of degree of a reaction inphase/orthogonal.When this adjustment unit receives one first radiofrequency signal at this receiver module; Do not match mutually to reduce the inphase/orthogonal relevant according to this this group parameter of detection signal adjustment with this first radiofrequency signal; And when this receiver module receives one second radiofrequency signal; Do not match mutually to reduce the inphase/orthogonal relevant according to this this group parameter of detection signal adjustment with this second radiofrequency signal; And according to aforesaid adjustment result, select the end value of this group parameter, do not match mutually to reduce the inphase/orthogonal relevant with different frequency.Wherein, This first radiofrequency signal produces from one first in-phase signal and one first quadrature-phase; This second radiofrequency signal produces from one second in-phase signal and one second quadrature-phase, and this second in-phase signal one is different from this first in-phase signal in frequency and phase place.
Description of drawings
Fig. 1 is the calcspar of a known transmitter;
Fig. 2 is the calcspar of a known receiver;
Fig. 3 (a)-(b) is the sketch map that concerns between explanation phase error and frequency;
Fig. 4 is the calcspar of the embodiment of transmitter of the present invention;
Fig. 5 is the flow chart of the mutually unmatched method of adjustment of the employed reduction inphase/orthogonal of Fig. 4 embodiment;
Fig. 6 (a)-(1) is the sketch map that one of key diagram 4 embodiment implement aspect;
Fig. 7 (a)-(1) is the sketch map of another enforcement aspect of key diagram 4 embodiment;
Fig. 8 is the calcspar of the embodiment of receiver of the present invention; And
Fig. 9 is the flow chart of the mutually unmatched method of adjustment of the employed reduction inphase/orthogonal of Fig. 8 embodiment.
The reference numeral explanation
4 transmitter modules, 6 receiver modules
40,67 compensating units, 401,674 delay-level
41,42 digital to analog converters, 48,68 detecting units
482 variable gain amplifiers, 484,681 fast fourier transformer
49,69 adjustment units, 65,66,483 analog-to-digital converters
43,44,63,64 low pass filters
45,46,61,62,481 frequency mixers
47,404,673 summer
402,403,671,672 gain stages
51-55,71-75 step
Embodiment
About addressing other technologies content, characteristics and effect before the present invention, in below in conjunction with detailed description, can clearly appear with reference to two graphic embodiment.
Consult Fig. 4, the embodiment of transmitter of the present invention comprises a transmitter module 4, a detecting unit 48 and an adjustment unit 49.This transmitter module 4 comprises a compensating unit 40,43,44, two frequency mixers 45,46 of 41,42, two low pass filters of two-digit to analog converter and a summer 47.
This compensating unit 40 is according to the fundamental frequency signal BBI of one group of parameter to two-digit
t, BBQ
tCarry out phase place and amplitude compensation.In the present embodiment, this group parameter comprises a variable delay time τ
tAnd two variable gain X
t, Y
t, this variable delay time τ
tBe used for and the proportional phase compensation of frequency these two variable gain X
t, Y
tBe used for fixing the compensation of amplitude compensation and stationary phase, and this compensating unit 40 comprises a delay-level 401, two gain stages 402,403 and summer 404.This delay-level 401 is with this fundamental frequency signal BBI
tPostpone this variable delay time τ
tThis gain stage 402 with the output signal times of this delay-level 401 with this variable gain X
t, with an output signal as this compensating unit 40.This gain stage 403 with the output signal times of this delay-level 401 with this variable gain Y
tThis summer 404 is with this fundamental frequency signal BBQ
tWith the output signal totalling of this gain stage 403, with another output signal as this compensating unit 40.
This two-digit to analog converter 41,42 carries out numeral to analog-converted to the output signal of this gain stage 402 and this summer 404 respectively.These two low pass filters 43,44 carry out LPF to the output signal of this two-digit to analog converter 41,42 respectively.This frequency mixer 45 is with the output signal and a homophase local oscillated signal LOI of this low pass filter 43
tMixing is to produce a homophase radiofrequency signal RFI
t, and this frequency mixer 46 is with the output signal of this low pass filter 44 and quadrature local oscillated signal LOQ mutually
tMixing is to produce a quadrature phase radiofrequency signal RFQ
tThe output signal of 47 pairs of these two frequency mixers 45,46 of this summer carries out totalling.
This detecting unit 48 is according to the output signal of this summer 47, produces do not match the mutually detection signal of degree of a reaction inphase/orthogonal that is positioned at fundamental frequency.In the present embodiment; This detecting unit 48 comprises a frequency mixer 481, a variable gain amplifier 482, an analog-to-digital converter 483 and a fast fourier transformer 484; In regular turn the output signal of this summer 47 is carried out with self mixing, amplification, simulates to digital translation and fast fourier transform, produce this detection signal.As these two fundamental frequency signal BBI
t, BBQ
tBe that string ripple signal and its frequency are F
BBnThe time, the output signal of this frequency mixer 481 has at 2F
BBnThe spectrum component at place, and its spectrum analysis can demonstrate the mutually unmatched degree of inphase/orthogonal.In another embodiment, this frequency mixer 481 also can be replaced by an envelope detector, and in other embodiments, this variable gain amplifier 482 also can be omitted.
49 adjustment of this adjustment unit and select should group parameter (i.e. this variable delay time τ
tAnd these two variable gain X
t, Y
t), do not match mutually to reduce inphase/orthogonal (detailed action is in hereinafter describing).
It should be noted that this delay-level 401 also can be arranged on other position, for example: between this low pass filter 43 and this frequency mixer 45, perhaps between this low pass filter 44 and this frequency mixer 46, and not as limit.
Consult Fig. 5, present embodiment is employed to be used to reduce the mutually unmatched method of adjustment of inphase/orthogonal and to comprise following steps:
Implement in the aspect at one of present embodiment, this first in-phase signal is cos (2 π F
BB1T), this first quadrature-phase is sin (2 π F
BB1T), this second in-phase signal is cos (2 π F
BB2T), this second quadrature-phase is sin (2 π F
BB2T), the frequency F of this second in-phase signal
BB2Be different from the frequency F of this first in-phase signal
BB1, and this homophase local oscillated signal LOI
tBe cos (2 π F
LOT), this quadrature phase local oscillated signal LOQ
tBe-sin (2 π F
LOT).
Before this transmitter was adjusted, shown in Fig. 6 (a), the output signal of this summer 47 had at F
LO+ F
BBnThe required spectrum component at place, and at F
LO-F
BBnMirror image (image) spectrum component at place, even the power of required spectrum component can be with frequency shift, the power of image spectra composition also may be with frequency shift, and shown in Fig. 6 (b), the output signal of this frequency mixer 481 has at 2F
BBnThe spectrum component at place, and this spectrum component may be with frequency shift.
After this transmitter carry out step 51, shown in Fig. 6 (c), the output signal of this summer 47 had at F
LO+ F
BB1The required spectrum component at place, and at F
LO-F
BB1The image spectra composition at place, and shown in Fig. 6 (d), the output signal of this frequency mixer 481 has at 2F
BB1The spectrum component at place, and its spectrum analysis can demonstrate the inphase/orthogonal mutually unmatched degree relevant with this first in-phase signal and this first quadrature-phase.
After this transmitter carry out step 52, shown in Fig. 6 (e), the output signal of this summer 47 had at F
LO+ F
BB1The required spectrum component at place, and at F
LO-F
BB1The image spectra composition at place, and the power of image spectra composition has been lowered, and shown in Fig. 6 (f), the output signal of this frequency mixer 481 has at 2F
BB1The spectrum component at place, and the power of this spectrum component has been lowered.
After this transmitter carry out step 53, shown in Fig. 6 (g), the output signal of this summer 47 had at F
LO+ F
BB2The required spectrum component at place, and at F
LO-F
BB2The image spectra composition at place, and shown in Fig. 6 (h), the output signal of this frequency mixer 481 has at 2F
BB2The spectrum component at place, and its spectrum analysis can demonstrate the inphase/orthogonal mutually unmatched degree relevant with this second in-phase signal and this second quadrature-phase.
After this transmitter carry out step 54, shown in Fig. 6 (i), the output signal of this summer 47 had at F
LO+ F
BB2The required spectrum component at place, and at F
LO-F
BB2The image spectra composition at place, and the power of image spectra composition has been lowered, and shown in Fig. 6 (j), the output signal of this frequency mixer 481 has at 2F
BB2The spectrum component at place, and the power of this spectrum component has been lowered.
After this transmitter carry out step 55, shown in Fig. 6 (k), the output signal of this summer 47 had at F
LO+ F
BBnThe required spectrum component at place, and at F
LO-F
BBnThe image spectra composition at place, and the power of image spectra composition all is minimized at different frequency, and in known technology, the image spectra composition only is minimized in certain frequency, and shown in Fig. 6 (1), the output signal of this frequency mixer 481 has at 2F
BBnThe spectrum component at place, and the power of this spectrum component all is minimized at different frequency, and in known technology, this spectrum component only is minimized in certain frequency.
In another enforcement aspect of present embodiment, this first in-phase signal is cos (2 π F
BB1T), this first quadrature-phase is sin (2 π F
BB1T), this second in-phase signal is sin (2 π F
BB1T), this second quadrature-phase is cos (2 π F
BB1T), the phase place of this second in-phase signal is different from the phase place of this first in-phase signal, and this homophase local oscillated signal LOI
tBe cos (2 π F
LOT), this quadrature phase local oscillated signal LOQ
tBe-sin (2 π F
LOT).
Before this transmitter was adjusted, shown in Fig. 7 (a), the output signal of this summer 47 had at F
LO+ F
BBnThe required spectrum component at place, and at F
LO-F
BBnThe image spectra composition at place, even the power of required spectrum component can be with frequency shift, the power of image spectra composition also may be with frequency shift, and shown in Fig. 7 (b), the output signal of this frequency mixer 481 has at 2F
BBnThe spectrum component at place, and this spectrum component may be with frequency shift.
After this transmitter carry out step 51, shown in Fig. 7 (c), the output signal of this summer 47 had at F
LO+ F
BB1The required spectrum component at place, and at F
LO-F
BB1The image spectra composition at place, and shown in Fig. 7 (d), the output signal of this frequency mixer 481 has at 2F
BB1The spectrum component at place, and its spectrum analysis can demonstrate the inphase/orthogonal mutually unmatched degree relevant with this first in-phase signal and this first quadrature-phase.
After this transmitter carry out step 52, shown in Fig. 7 (e), the output signal of this summer 47 had at F
LO+ F
BB1The required spectrum component at place, and at F
LO-F
BB1The image spectra composition at place, and the power of image spectra composition has been lowered, and shown in Fig. 7 (f), the output signal of this frequency mixer 481 has at 2F
BB1The spectrum component at place, and the power of this spectrum component has been lowered.
After this transmitter carry out step 53, shown in Fig. 7 (g), the output signal of this summer 47 had at F
LO-F
BB1The required spectrum component at place, and at F
LO+ F
BB1The image spectra composition at place, and shown in Fig. 7 (h), the output signal of this frequency mixer 481 has at 2F
BB1The spectrum component at place, and its spectrum analysis can demonstrate the inphase/orthogonal mutually unmatched degree relevant with this second in-phase signal and this second quadrature-phase.
After this transmitter carry out step 54, shown in Fig. 7 (i), the output signal of this summer 47 had at F
LO-F
BB1The required spectrum component at place, and at F
LO+ F
BB1The image spectra composition at place, and the power of image spectra composition has been lowered, and shown in Fig. 7 (j), the output signal of this frequency mixer 481 has at 2F
BB1The spectrum component at place, and the power of this spectrum component has been lowered.
After this transmitter carry out step 55, shown in Fig. 7 (k), the output signal of this summer 47 had at F
LO+ F
BBnThe required spectrum component at place, and at F
LO-F
BBnThe image spectra composition at place, and the power of image spectra composition all is minimized at different frequency, and in known technology, the image spectra composition only is minimized in certain frequency, and shown in Fig. 7 (1), the output signal of this frequency mixer 481 has at 2F
BBnThe spectrum component at place, and the power of this spectrum component all is minimized at different frequency, and in known technology, this spectrum component only is minimized in certain frequency.
It should be noted that; In this enforcement aspect, can be to produce this second in-phase signal and this second quadrature-phase, for example: utilize a switching unit according to this first in-phase signal and this first quadrature-phase; In step 53, this first in-phase signal is delivered to this fundamental frequency signal BBQ
tInput, with as this second quadrature-phase, this first quadrature-phase is delivered to this fundamental frequency signal BBI
tInput, with as this second in-phase signal, perhaps for example: utilize a delay cell; In step 53; This first in-phase signal is postponed a period of time,, this first quadrature-phase is postponed a period of time to produce this second quadrature-phase; Producing this second in-phase signal, and not as limit.
Consult Fig. 8, the embodiment of receiver of the present invention comprises a receiver module 6, a detecting unit 68 and an adjustment unit 69.This receiver module 6 comprises 63,64, two analog-to- digital converters 65,66 of 61,62, two low pass filters of two frequency mixers and a compensating unit 67.
This frequency mixer 61 is with the radiofrequency signal and a homophase local oscillated signal LOI of a simulation
rMixing, producing a fundamental frequency signal, and this frequency mixer 62 is with this radiofrequency signal and quadrature local oscillated signal LOQ mutually
rMixing is to produce another fundamental frequency signal.These two low pass filters 63,64 carry out LPF to the output signal of these two frequency mixers 61,62 respectively.These two analog-to- digital converters 65,66 are simulated to digital translation the output signal of these two low pass filters 63,64 respectively.
This compensating unit 67 carries out phase place and amplitude compensation according to one group of parameter to the output signal of these two analog-to-digital converters 65,66.In the present embodiment, this group parameter comprises two variable gain X
r, Y
rAn and variable delay time τ
r, these two variable gain X
r, Y
rBe used for fixing the compensation of amplitude compensation and stationary phase, this variable delay time τ
rBe used for and the proportional phase compensation of frequency, and this compensating unit 67 comprises two gain stages 671,672, a summer 673 and a delay-level 674.This gain stage 671 with the output signal times of this analog-to-digital converter 65 with this variable gain X
rThis gain stage 672 with the output signal times of this analog-to-digital converter 66 with this variable gain Y
rThis summer 673 is with the output signal totalling of these two gain stages 671,672.This delay-level 674 is with this variable delay time of output signal delay τ of this summer 673
r, to export a homophase fundamental frequency signal BBI
rThis compensating unit 67 is directly exported the output signal of this analog-to-digital converter 66, as a quadrature phase fundamental frequency signal BBQ
r
This detecting unit 68 is according to these two fundamental frequency signal BBI
r, BBQ
r, produce do not match the mutually detection signal of degree of a reaction inphase/orthogonal.In the present embodiment, this detecting unit 68 comprises a fast fourier transformer 681.This fast fourier transformer is with these two fundamental frequency signal BBI
r, BBQ
rBe regarded as a complex signal BBI
r+ jBBQ
r, carry out fast fourier transform, to produce this detection signal.When this radiofrequency signal is one when not having the mutually unmatched signal of inphase/orthogonal, for example: when this radiofrequency signal is that adjusted this transmitter produces, and these two fundamental frequency signal BBI
t, BBQ
tThe frequency that is string ripple signal and its etc. is F
BBnThe time, these two fundamental frequency signal BBI
r, BBQ
rHave at-F
BBnThe spectrum component at place, and its spectrum analysis can demonstrate the mutually unmatched degree of inphase/orthogonal.
69 adjustment of this adjustment unit and select should group parameter (i.e. this two variable gain X
r, Y
rAnd this variable delay time τ
r), do not match mutually to reduce inphase/orthogonal (detailed action is in hereinafter describing).
It should be noted that this delay-level 674 also can be arranged on other position, for example: between this frequency mixer 61 and this low pass filter 63, perhaps between this frequency mixer 62 and this low pass filter 64, and not as limit.
Consult Fig. 9, present embodiment is employed to be used to reduce the mutually unmatched method of adjustment of inphase/orthogonal and to comprise following steps:
Implement in the aspect at one of present embodiment, this first in-phase signal is cos (2 π F
BB1T), this first quadrature-phase is s in (2 π F
BB1T), this second in-phase signal is cos (2 π F
BB2T), this second quadrature-phase is sin (2 π F
BB2T), the frequency F of this second in-phase signal
BB2Be different from the frequency F of this first in-phase signal
BB1, and this homophase local oscillated signal LOI
rBe cos (2 π F
LOT), this quadrature phase local oscillated signal LOQ
rBe-sin (2 π F
LOT).
In another enforcement aspect of present embodiment, this first in-phase signal is cos (2 π F
BB1T), this first quadrature-phase is sin (2 π F
BB1T), this second in-phase signal is sin (2 π F
BB1T), this second quadrature-phase is cos (2 π F
BB1T), the phase place of this second in-phase signal is different from the phase place of this first in-phase signal, and this homophase local oscillated signal LOI
rBe cos (2 π F
LOT), this quadrature phase local oscillated signal LOQ
rBe-sin (2 π F
LOT).
It should be noted that and in the embodiment of this transmitter and this receiver, also can carry out parameter adjustment more frequently, and select final argument, do not exceed with secondary according to these adjustment result.
The above is merely embodiments of the invention, can not limit the scope that the present invention implements with this, and all simple equivalent of doing according to claim of the present invention and invention description change and modify, and all still belong to the scope that patent of the present invention contains.
Claims (8)
1. one kind is used to reduce the mutually unmatched method of adjustment of inphase/orthogonal, is applicable to a transmitter, and the method includes the steps of:
Receive one first in-phase signal and one first quadrature-phase;
Adjusting one group of parameter does not match with this first in-phase signal and the relevant inphase/orthogonal of this first quadrature-phase to reduce mutually;
Receive one second in-phase signal and one second quadrature-phase, wherein, this second in-phase signal one is different from this first in-phase signal in frequency and phase place;
Adjusting this group parameter does not match with this second in-phase signal and the relevant inphase/orthogonal of this second quadrature-phase to reduce mutually; And
According to aforesaid adjustment result, select the end value of this group parameter, do not match mutually to reduce the inphase/orthogonal relevant with different frequency,
Wherein, this group parameter comprises the variable delay time, be used for and the proportional phase compensation of frequency,
And wherein, this group parameter also comprises two variable gains, is used for fixing the compensation of amplitude compensation and stationary phase.
2. according to the described method of claim 1, wherein, at least one of which and this first in-phase signal of this second in-phase signal on frequency or phase place is different.
3. according to the described method of claim 1, wherein, be inphase/orthogonal not to be matched mutually reduce a preset value in fact.
4. one kind is used to reduce the mutually unmatched method of adjustment of inphase/orthogonal, is applicable to a receiver, and the method includes the steps of:
Receive one first radiofrequency signal, wherein, this first radiofrequency signal produces from one first in-phase signal and one first quadrature-phase;
Adjusting one group of parameter does not match to reduce the inphase/orthogonal relevant with this first radiofrequency signal mutually;
Receive one second radiofrequency signal, wherein, this second radiofrequency signal produces from one second in-phase signal and one second quadrature-phase, and this second in-phase signal one is different from this first in-phase signal in frequency and phase place;
Adjusting this group parameter does not match to reduce the inphase/orthogonal relevant with this second radiofrequency signal mutually; And
According to aforesaid adjustment result, select the end value of this group parameter, do not match mutually to reduce the inphase/orthogonal relevant with different frequency,
Wherein, this group parameter comprises the variable delay time, be used for and the proportional phase compensation of frequency,
And wherein, this group parameter also comprises two variable gains, is used for fixing the compensation of amplitude compensation and stationary phase.。
5. according to the described method of claim 4, wherein, at least one of which and this first in-phase signal of this second in-phase signal on phase place or frequency is different.
6. according to the described method of claim 4, wherein, be inphase/orthogonal not to be matched mutually reduce a preset value in fact.
7. transmitter comprises:
One transmitter module to an in-phase signal and a quadrature-phase that receives, carries out phase place and amplitude compensation according to one group of parameter, and carries out homophase and the mixing of quadrature phase respectively, and carries out totalling, to produce a radiofrequency signal;
One detecting unit according to this radiofrequency signal, produces do not match the mutually detection signal of degree of a reaction inphase/orthogonal; And
One adjustment unit; When this transmitter module receives one first in-phase signal and one first quadrature-phase; Do not match mutually with this first in-phase signal and the relevant inphase/orthogonal of this first quadrature-phase to reduce according to this this group parameter of detection signal adjustment; And when this transmitter module receives one second in-phase signal and one second quadrature-phase, do not match mutually with this second in-phase signal and the relevant inphase/orthogonal of this second quadrature-phase to reduce, and according to aforesaid adjustment result according to this this group parameter of detection signal adjustment; Select the end value of this group parameter, do not match mutually to reduce the inphase/orthogonal relevant with different frequency;
Wherein, this second in-phase signal one is different from this first in-phase signal in frequency and phase place,
Wherein, this group parameter comprises the variable delay time, be used for and the proportional phase compensation of frequency,
And wherein, this group parameter also comprises two variable gains, is used for fixing the compensation of amplitude compensation and stationary phase.
8. receiver comprises:
One receiver module to the radiofrequency signal that receives, carries out homophase and the mixing of quadrature phase, and carries out phase place and amplitude compensation according to one group of parameter, to produce two fundamental frequency signals;
One detecting unit according to these two fundamental frequency signals, produces do not match the mutually detection signal of degree of a reaction inphase/orthogonal; And
One adjustment unit; When this receiver module receives one first radiofrequency signal; Do not match mutually to reduce the inphase/orthogonal relevant according to this this group parameter of detection signal adjustment with this first radiofrequency signal; And when this receiver module receives one second radiofrequency signal, do not match mutually to reduce the inphase/orthogonal relevant, and according to aforesaid adjustment result with this second radiofrequency signal according to this this group parameter of detection signal adjustment; Select the end value of this group parameter, do not match mutually to reduce the inphase/orthogonal relevant with different frequency;
Wherein, This first radiofrequency signal produces from one first in-phase signal and one first quadrature-phase; This second radiofrequency signal produces from one second in-phase signal and one second quadrature-phase, and this second in-phase signal one is different from this first in-phase signal in frequency and phase place
Wherein, this group parameter comprises the variable delay time, be used for and the proportional phase compensation of frequency,
And wherein, this group parameter also comprises two variable gains, is used for fixing the compensation of amplitude compensation and stationary phase.
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| CN104717164A (en) * | 2013-12-11 | 2015-06-17 | 瑞昱半导体股份有限公司 | Signal correction method and signal correction device |
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| TWI466506B (en) | 2012-02-22 | 2014-12-21 | Realtek Semiconductor Corp | Method for compensating mismatch of in-phase signal and quadrature signal of transmitter/receiver |
| CN103297070B (en) * | 2012-02-28 | 2016-07-06 | 瑞昱半导体股份有限公司 | Compensate in-phase signal and the unmatched method of orthogonal signalling in conveyer/receptor |
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