CN101563809A - High frequency filter with closed circuit coupling - Google Patents
High frequency filter with closed circuit coupling Download PDFInfo
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- CN101563809A CN101563809A CNA2007800470999A CN200780047099A CN101563809A CN 101563809 A CN101563809 A CN 101563809A CN A2007800470999 A CNA2007800470999 A CN A2007800470999A CN 200780047099 A CN200780047099 A CN 200780047099A CN 101563809 A CN101563809 A CN 101563809A
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
- H01P1/00—Auxiliary devices
- H01P1/20—Frequency-selective devices, e.g. filters
- H01P1/201—Filters for transverse electromagnetic waves
- H01P1/205—Comb or interdigital filters; Cascaded coaxial cavities
- H01P1/2053—Comb or interdigital filters; Cascaded coaxial cavities the coaxial cavity resonators being disposed parall to each other
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
- H01P1/00—Auxiliary devices
- H01P1/20—Frequency-selective devices, e.g. filters
- H01P1/213—Frequency-selective devices, e.g. filters combining or separating two or more different frequencies
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
- H01P1/00—Auxiliary devices
- H01P1/20—Frequency-selective devices, e.g. filters
- H01P1/201—Filters for transverse electromagnetic waves
- H01P1/205—Comb or interdigital filters; Cascaded coaxial cavities
-
- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
- H01P1/00—Auxiliary devices
- H01P1/20—Frequency-selective devices, e.g. filters
- H01P1/213—Frequency-selective devices, e.g. filters combining or separating two or more different frequencies
- H01P1/2136—Frequency-selective devices, e.g. filters combining or separating two or more different frequencies using comb or interdigital filters; using cascaded coaxial cavities
Abstract
The invention relates to an improved high frequency filter having the following features: the high frequency filter has a transmission behavior with a coupling impedance resonance with at least one null point at a frequency (fs), wherein the null point at the frequency (fs) can be set by specifying and/or preselecting a defined capacitive (12/') and inductive (12/'') coupling between two coaxial resonators (15) directly following one another on a signal path (10).
Description
Technical field
The present invention relates to a kind of high frequency filter with the coupling of bandreject filtering loop as described in the preamble as claimed in claim 1.
Background technology
High frequency filter is using in the extensive fields very much.
For example in the digital mobile radio technology, communicating by letter between mobile subscriber and the base station undertaken by the sending-receiving antenna that is arranged in the base station.In this worth expectation is only a shared antenna to be used for sending and received signal.
At this, send signal and use different frequency ranges with received signal.The antenna that is adopted must be applicable in two frequency ranges and send and receive.Send signal and received signal in order to separate, need carry out suitable frequency filtering, this frequency filtering guarantees that sending signal only is transmitted to antenna (rather than on direction of receiver) by transmitter on the one hand, and received signal only is transmitted to receiver by this antenna on the other hand.
Can adopt a pair of high frequency filter, these two high frequency filters all allow frequency band specific, that just expect separately by (band pass filter) for this reason.But also can adopt the high frequency filter of a pair of prevention frequency band specific, that just do not expect separately, be called band stop filter at this.In addition, can also adopt a pair of high frequency filter, comprise allowing to be lower than first filter (low pass filter) that passes through between the frequency of frequency between transmission frequency band and the frequency acceptance band and stoping to be lower than allowing to be higher than second filter that passes through between the frequency that sends frequency between frequency band and the frequency acceptance band between the frequency that sends frequency between frequency band and the frequency acceptance band.Here this second filter is so-called high pass filter.Also can adopt by other combination that described filter type is formed.
At this, the transmission in the base station-frequency acceptance band separates normally with duplexing directional filter to be carried out, and this duplex directional filter has being mentioned of task, just will send-RX path has as far as possible together with feeding back and is not connected on the described shared antenna.By the band pass filter of two interconnection, just so-called transmitting filter (TX band pass filter) and reception bandpass filter (RX band pass filter) are formed, wherein setting is respectively applied for the terminal of separation of the antenna of receiving branch, transmitting branch and described shared connection to the duplex directional filter at this.
Therefore, the band pass filter that uses in duplexing directional filter has on the one hand be used to interconnect transmitting filter and the needed selection of reception bandpass filter (TX/RX) (just necessary supression wave band decay), the useful signal of should decaying as small as possible on the other hand in its corresponding free transmission range.
The logical structure of the band that uses in duplexing directional filter (for example GSM/UMTS) in mobile wireless frequency range commonly used mainly is made of coaxial resonator.
The structure of coaxial resonator and type of action are open by prior art, for example referring to " IanHunter:Theory and Design of Microwave Filters ", IEEElectromagnetic Waves Series, No.48,1.Microwave filters, 197 pages.
Have transmission zero in the stopband range band pass filter (so-called Cauer band pass filter) of (the so-called resistance utmost point) has been described in filter theory.This filter type is often realized in combination by so-called cross-couplings (cross-over connection coupling) and coaxial resonator.At this, intercouple (just not being the continuous resonators in direct front and back in signal change procedure) condenser type of non-conterminous resonator in the logical structure of band or induction type, make by Signal Separation and the ensuing elimination that has the merging of phase shift and in transmission characteristic, produce amplitude.This cross-couplings technology for example is described in IEEE Transactions on microwave theory andtechniques, Vol.51, No.4, in April, 2004 " Cross-Coupling in CoaxialCavity Filters-A Tutorial Overview ", J.Brain Thomas, the 1368-1376 page or leaf.
But there is following shortcoming in so-called cross-couplings, and necessary coupling needs non-conterminous resonator, not directly front and back setting continuously of these resonators just.Also need to realize mechanically the filter topologies logic of this coupling thus.
Owing to be applicable to the limited amount that cross-linked resonator is right, therefore can only produce the resistance utmost point of limited quantity.
The high frequency filter of especially realizing with duplexing directional filter form with the coupling of bandreject filtering loop is according to the rules disclosed by WO2004/100305A1 in principle.This high frequency filter is a kind of high frequency filter with a plurality of resonators, and these resonators are arranged between 3 terminals, just is arranged on the terminal that is used to send branch, is used to receive the terminal of branch and is used between the terminal of common antenna.
According to prior art according to the rules, in order to improve this duplexing directional filter, stipulate that the resonator that this duplex directional filter has at least one mutual close coupling is right, wherein mutually the resonator of close coupling under couple state with two coupled resonance hunting of frequencys that depart from mutually, that the resonator itself that these two coupled resonance frequencies are different from two close couplings is had in the frequency range between transmission frequency band and frequency acceptance band respectively when observing separately or resonator be tuned to resonance frequency.
Thereby for example disclose measure under coaxial high frequency filter situation, can differently regulate two couplings between the adjacent resonators thus by WO02/054527A2.For example on the dividing plate between two inner wires two adjacent coaxial resonators, the coupling tuned cell is set for this reason, above this dividing plate on form coupling window between the wave guide wall, described coupling tuned cell can be conditioned to change this coupling.
Similarly solution is also open by JP09-199906A on the principle at present, and the document has been described and adopted two regulating loops between the resonator to change this coupling.
According to US4216448, on the coupling circuit that comprises 4 coaxial resonators, the resonance performance of correspondingly regulating filter by DRIVE SCREWS (on the axially-extending line of inner wire).In addition, in the disclosure document, be not provided with coupling (just not being between two resonators adjacent before and after on the transmission path) between first resonator and last resonator of transmission path, and by additional coupling window and in this upwardly extending projection in additional coupling window side.
At last, also will be with reference to high frequency filter according to US5389903A, this high frequency filter comprises the T shape inner wire with socket cap, this socket cap has the bigger diameter of inner wire than this socket cap of carrying below it.This socket cap moves prejudicially with respect to the inner wire post.The resonance frequency of also regulating each resonator with the similar mode of above-mentioned prior art in addition by screw.Resonator formula or the condenser type ground coupling that interacts, wherein this induction type or capacitive coupling mainly can by change and the inner wire post between the distance and the ratio of the distance dependent between the inner wire head adjusted.In order to carry out meticulous adjusting, also between each resonator, use set screw in addition.
All these all show at the open source literature that illustrate of beginning, the intercoupling and change and the coupling of differently regulating these resonators is complete known of each coaxial resonator.
But, if especially in the structure of band pass filter, produce stopband with transmission zero position (so-called resistance utmost point), then up to the present need with two mutually not the resonators of direct neighbor (just on signal transmission path be not directly before and after continuous resonators) intercouple by additional measure condenser type ground or induction type ground, make by Signal Separation and subsequently have the synthetic of phase shift and elimination generation amplitude in transmission characteristic (transmission zero or hinder the utmost point).This carries out in the scope of the so-called coupling technique that beginning is mentioned.
Summary of the invention
Correspondingly, the technical problem to be solved in the present invention provides a kind of improved high frequency filter, this high frequency filter has improved passband and/or stopband effect at the frequency that can be scheduled to or frequency range, wherein should filter topology not limited as much as possible.
The present invention is correspondingly solved by the feature that provides in the claim 1.Preferred implementation of the present invention provides in the dependent claims.
Thrillingly be, verified can differing in the centre frequency with band filter less than producing at least one under ± 50% the frequency restrained point (at least one resistance utmost point just), and the corresponding coupling of the coaxial resonator by two direct neighbor settings on signal path produces.
According to the present invention, this improvement that is better than prior art realizes basically like this: to the high frequency filter of the coaxial resonator that comprises electromagnetic coupled about at least one selected coaxial resonator to distributing preliminary election and/or preregulated coupling impedance especially, right two coaxial resonators direct neighbor ground in transmission path of this coaxial resonator is provided with, and the size of this coupling impedance is set so that the combination results based on capacitive couplings and induction type coupling has the coupling impedance resonance that defines blanketing frequency.Restrain point owing to produce in such transmission characteristic that is coupling in high frequency filter, therefore also this coupling is called the coupling of bandreject filtering loop below.
In other words, within the scope of the invention, this bandreject filtering loop is coupled, just blanketing frequency is configured such that this bandreject filtering loop coupling is positioned at outside the free transmission range of HF filter on the one hand, is positioned at the stopband range of HF filter on the other hand.
Preferably, blanketing frequency is at first come given in advance by the parameter of change and/or adjusting and/or two main influences of preliminary election or definite blanketing frequency.Marginally at this be the capacitive couplings that except the induction type resonator coupling of definition, also defines.The induction type of definition is coupling in this and for example can comes adjusted by the distance between the resonator to be coupled.On the contrary, desired capacitive couplings for example can be by realizing in lip-deep vertical expansion for the treatment of coupled resonators.Even the change of arbitrary parameter also can affect to corresponding another parameter in two described parameters, but can change the expectation coupling of adjacent resonators by induction type given in advance coupling and capacitive couplings, make the decay of expectation be positioned at outside the free transmission range of HF filter and within the stopband range of HF filter.
Therefore in scope of the present invention, can realize following important advantage:
-adjacent the resonator that can be coupled at first now makes to produce the supression point by this coupling.This provides following significant advantage: when realizing high frequency filter filter topology not have to look like in the prior art restriction, just to the arrangement of coaxial resonator without limits.In the prior art, have following major defect, promptly (just under the situation that produces the cross-over connection coupling) can not carry out necessary coupling between adjacent resonator in so-called " cross-couplings ".This needs special filter topology fully thus, so that can produce coupling between non-conterminous two resonators.
-owing to can produce coupling between two adjacent resonators in scope of the present invention, therefore also providing in principle will a plurality of adjacent selections of resonator to intercoupling arbitrarily.In scope of the present invention, under the situation of n resonator even can produce n-1 and restrain point, just far away more than the cross-couplings of routine.
-in scope of the present invention,, make these two inner wires on their surface, have radially and extend for the coupling of control capacittance formula correspondingly can reduce two distances between the inner wire.This can also be used to reduce the general construction height of filter.
Description of drawings
Explain the present invention in detail by accompanying drawing below.Specifically illustrate:
Fig. 1 illustrates the schematic construction of high frequency filter under the situation of duplexing directional filter with the schematic diagram of signal;
Fig. 2 illustrates the diagrammatic top view of the high frequency filter with a signal path;
Fig. 3 illustrates the signal axial, cross-sectional view of the line segment III-III in Fig. 2;
Fig. 4 illustrates the replacement circuit figure that relates to according to the embodiment of Fig. 2 and Fig. 3;
Fig. 5 illustrates the band-pass behavior that is used to reproduce the band pass filter that the present invention is used for duplexing directional filter and the diagram of fade performance; And
Fig. 6 a to Fig. 6 f illustrates the difference diagram at the different settings of coupling capacitance and coupling inductance.
Embodiment
The high frequency filter of the form of duplexing directional filter 3 is shown with schematic diagram in Fig. 1, wherein high frequency filter 1 comprises 3 terminals 5,7,9, just terminal TX, RX and be used for the terminal of antenna port AP, thereby send signal and can go to antenna port AP (port of common antenna) from sending terminal 5 by first signal path, the signal that is received by antenna can cause by antenna port AP (terminal 9) and receive terminal 7 conversely.
Duplex directional filter 3 comprises corresponding band pass filter 11 and 13 respectively for this reason in two signal paths, this band pass filter has necessary selection (just restraining decay), can not have signal to arrive the receiving branch from sending terminal thus.On the other hand, free transmission range should be decayed as small as possible for useful signal.
In Fig. 2, for example the high frequency filter 1 with signal path 10 is shown with the vertical view of illustrating (under the situation of the cover plate on omit) for this reason, this signal path is for example from terminal 5 to terminal 9, just from sending terminal, and comprise 6 coaxial resonators 15 at this to antenna port terminal (branch road of duplexing directional filter just only is shown).
Thus, each coaxial resonator 15 all has one and wherein in related shell wall 17c coupling opening 23 is set along signal path around its shell wall 17c all around, and promptly so-called ripple door screen forms window thus, and seeing through this window can propagation of electromagnetic waves.
On coaxial terminal 5 and 9, with known manner inner wire 5a and 9a are set respectively, these inner wires extend in the corresponding resonator cavity 19, and for example in flat unit 5b that conducts electricity and 9b, stop, utilize in the related coaxial resonator 15 corresponding inner wire to be coupled into electric field at terminal 5 places by the electric capacity of such formation thus and terminal 9 these electric fields of place's decoupling (wherein the signal that is for example received by antenna conversely is coupled into the corresponding resonator that is arranged on the secondary signal path by the flat unit 9b of conduction, and causes the terminal 7 that is not shown specifically among Fig. 2 by the secondary signal path).The schematic sectional view of a fragment of the band pass filter 11 that is provided with for transmitting branch for example only is shown in Fig. 3 thus, wherein can inserts the signal path of second receiving branch that is used for duplexing directional filter not shown in Figure 3 by the ripple door screen 23a in Fig. 3 left side.
9 the signal path from terminal 5 to terminal as for having explained intercouples 6 coaxial resonators 15.1 to 15.6 in this way.
Corresponding replacement circuit figure is shown in Figure 4, and has from terminal 5 to terminal a signal path 10 of 9,6 resonators 11 are as parallel oscillation loop 111 shown in it, an output head grounding in this parallel oscillation loop, another relative output is connected to signal path 10 according to corresponding order.This parallel oscillation loop 24 characterizes by capacitor and inductance with known manner at this.If the coupling of the routine between the coaxial resonator that is to say not to be the following coupling of the present invention that also will explain that circuit between the tie point 25 in each parallel oscillation loop 24 can be described by inductance 27 equally.When considering coupling of the present invention, connection between two adjacent parallel oscillation loops that intercouple according to the present invention just can not have been described by the induction coupling, describe but be coupled, as illustrated in fig. 4 by the bandreject filtering loop that exists with parallel oscillation loop form with electric capacity and inductance.Between first coaxial resonator 15.1 and the 5th coaxial resonator 15.4, as in the prior art, adopt capacitor C to realize condenser type cross-couplings (referring to Fig. 2 and Fig. 4) in addition.
According to the replacement circuit figure of Fig. 4, show and realizing coupling of the present invention between first coaxial resonator 15.1 and second coaxial resonator 15.2 and between second coaxial resonator 15.2 and the 3rd coaxial resonator 15.3.In addition, in an illustrated embodiment, be further illustrated in the routine coupling (cross-couplings) that exists between first coaxial resonator 15.1 and the 5th coaxial resonator 15.5 according to prior art, also will be described below.
From according to the end view of Fig. 3 as can be seen, for make direct neighbor, just on signal path directly before and after continuous resonator 15.1 and 15.2 produce coupling, affiliated inner wire has coreference respectively to inner wire section 21a the other side, that radially protrude on their closure.Light between two inner wires 21 is adjusted to apart from 121 and makes the capacitive couplings that produces expectation thus thus.
This capacitive couplings for example illustrates between the inner wire section 21a of two inner wires 21 of two first coaxial resonators 15.1 and 15.2 in Fig. 3, and by the corresponding E field vector 121 ' (Fig. 2) that illustrates.
In addition, in Fig. 3 also at two first resonators 15.1 and 15.2 by H field wire section 121 " induction type coupling is shown.At last, by the distance 321 between two inner wires 21 given in advance (need not to consider mentioned the inner wire section 21a that radially protrudes), correspondingly select and/or adjust the induction type coupling in advance.
But the induction type coupling also can substitute or replenish, just obtain different preconditioning or preliminary election by additional measure by other means.Complete vague generalization ground notices that be coupled needed coupling capacitance and coupling inductance of accommodation zone resistance filter circuit is provided with the variant scheme by known coupling and regulates.Thereby for example can differently regulate coupled wave door screen (just running through between two adjacent coaxial resonators opening) aspect height and/or the width, change the degree of coupling thus.Coupling pin, coupling loop or coupling contact pin can also be set between resonator equally.Coupling contact pin for example is distributed on two local height between the inner wire, that is to say same and inner wire extends (being preferably perpendicular to base plate wall) abreast, and is electrically connected with the base plate of coupled resonators at this.Coupling loop can be connected between two inner wires on the base plate with electric means and mechanical system according to inverted U-shaped.Can also with coupling loop in vertical direction (just in vertical plane) or with this vertical direction a little in the plane inclined about the rotating shaft location vertical with respect to base plate, and can on tangential direction, rotate at this.The area that is penetrated by magnetic surface is big more, and coupling is just strong more.The effect of being mentioned can also make up or part is used in combination, and regulating with the coupling of corresponding realization and conversion expectation may.
For example using the coupling pin 301 of conduction to reproduce adjusting above-mentioned by Fig. 6 a may, wherein be arranged among the upper cover plate 17b pin 301 can for change two between the inner wire 21 coupling capacitance and extend to different height and positions, just can different extend in two inner spaces between the resonator far and nearly, wherein also be arranged on the coupling pin 302 that extends or be positioned at the conduction on the base plate 17a among the base plate 17a in Fig. 6 a, the height of this coupling pin and diameter help to change coupling inductance.Show contact pin by Fig. 6 b with vertical view along the connecting line setting of two adjacent inner conductors 21 from the base plate projection, this contact pin at this with respect to the height of inner wire and on local height, extend.It is so-called coupling contact pin 307 at this.This coupling contact pin 307 is electrically connected at this base plate 17a with the shell 17 of high frequency filter.
Another embodiment that provides with vertical view and provide with vertical cross-section according to Fig. 6 d according to Fig. 6 c, for example showing, first window 303 (coupled wave door screen) between coaxial resonator 15.1 and 15.2 obviously reduces, and correspondingly another coupled wave door screen 303 between the resonator 15.2 and 15.3 obviously increases, thereby this coupled wave door screen under any circumstance all has and base plate or the parallel plane bigger width of cover plate.
In embodiment according to Fig. 6 e, show the coupling loop 305 that is used to change coupling inductance, this coupling loop 305 is positioned in the base plate to fall " U " shape.As an alternative, show the use of coupling loop by Fig. 6 f, this coupling loop can be around its vertical axis 305 ' rotation, thereby the magnetic field intensity of passing this coupling loop is changed, and has changed coupling inductance thus and can differently regulate coupling inductance.
Complete vague generalization ground notice that be used to produce the capacitive couplings of expectation and be used to produce the very different of inductance type coupling of expectation may combination in any, even all above-mentioned variant schemes can be used cumulatively.There is not restriction with regard to this point.
By there being deviation ground to form coaxial resonator 15, can outside the free transmission range of high frequency filter, produce the supression point of blanketing frequency expectation, that have definition with resonator form devious of having explained.Marginally at this be except the induction type resonator coupling of the definition mentioned, also to have the capacitive couplings of definition.The induction type of having mentioned be coupling in this can be as mentioned above by treating that the distance 321 (position of the inner wire 21 of related resonator) between the coupled resonators regulates, on the contrary, capacitive couplings is regulated by the light distance 121 of two adjacent inner conductors 21 of two adjacent resonators, and the light distance of vertically (vertically protruding) inner wire 21 that extends that the size of this light distance can be passed through to be mentioned is come given in advance.
In the embodiment shown, the coupling between first coaxial resonator 15.1 and second coaxial resonator 15.2, also between second coaxial resonator 15.2 and the 3rd coaxial resonator 15.3, realize another coupling following closely in order.
Different with first inner wire 21 of first coaxial resonator 15.1, first inner wire 21 in cross-sectional illustration to fall L shaped formation, second inner wire of present second coaxial resonator 15.2 constitutes according to T shape, just have another parallel with base plate and vertical with inner wire thus usually or with that radially protrude along inner wire, relative inner wire expansion 21a.The 3rd coaxial resonator 15.3 to can have corresponding inner wire expansion 21a equally with the 3rd inner wire 21 of this second inner wire coupling, wherein the distance between these two adjacent inner wire expansion 21a is much larger than the distance between first coaxial resonator and second coaxial resonator.In the example of second coaxial resonator and the coupling of the 3rd coaxial resonator, additional bridging component 221 is set also, this bridging component 221 is supported and location with respect to casing insulation ground for this reason.Produce two thus apart from gap 121a and 121b, these two apart from the gap in electric field vector pass through air borne.Obtained the marginal parameter of capacitive coupling by two single total distances that produce apart from 121a and 121b for the definition of expectation given in advance.
At last, from vertical view, it can also be seen that according to Fig. 2, now by another coupling between the 3rd coaxial resonator 15.3 and the 4th coaxial resonator 15.4, affiliated inner wire 21 is not the inner wire expansion (as second inner wire 21 of second coaxial resonator 15.2) with 180 ° of two relative deflections, but two mutual at an angle of 90 inner wire expansion 21a, just corresponding to the signal path of 90 ° of electromagnetic deflections.In diagram, provide two inner wires 21 with vertical view and located hermetically about second resonator 15.2 and the 3rd resonator 15.3 according to Fig. 2.
If the signal path of having explained for example is the signal path of duplexing directional filter, then can be implemented in the band pass filter that provides among Fig. 4 thus, and have one or more blanketing frequency f
s, just one or more so-called resistance utmost points.This transmission characteristic shows, quantity corresponding to the coaxial resonator that is coupled in the scope of the invention can produce a plurality of resistance utmost points (blanketing frequency), makes blanketing frequency for example be arranged in the free transmission range of band pass filter adjacent, that just be crisscross arranged (frequency range).
In the embodiment shown, can on each other optional position, just for example yet to realize another coupling of the present invention between the 4th coaxial resonator and the 5th coaxial resonator and/or between the 5th coaxial resonator and the 6th coaxial resonator.In general, under the situation of n coaxial resonator can with 5, just the size of n-1 coupling impedance is set at and makes to have the frequency f that defines respectively because the connection of capacitive couplings and inductance type coupling produces
sCoupling impedance resonance, just restrain point by producing in such transmission characteristic that is coupling in high frequency filter, locate generation at least one or a plurality of frequency f that staggers mutually at this supressions point
S1, f
S2, f
S3Deng until f
Sn, this coupling impedance resonance can be called as the coupling of bandreject filtering loop.
In the embodiment shown, can also realize conventional coupling in addition, this coupling can also be additionally provided in the high frequency filter of the present invention in addition.This conventional coupling (cross-couplings) is also according to shown in the replacement circuit figure of Fig. 4, just by having the connection line 131 of the capacitor C that is arranged among Fig. 4.
Coupling unit 31 for example shown in Figure 2 for this reason, this coupling unit works between first coaxial resonator and the 5th coaxial resonator, and usually by conductive, extend under in the cavity of resonator, in end view, become the coupling element of " bone shape " to form, this coupling element produces capacitive couplings by its increasing, the relative terminal that is connected with affiliated inner wire usually in related coaxial resonator.This is equally shown in the replacement circuit figure, just by capacitive couplings path 131.
On the contrary, realize having the bandreject filtering loop coupling 35 of inductance in parallel and electric capacity in scope of the present invention, this is equally according to shown in the replacement circuit figure of Fig. 4.
Then also will be with reference to Fig. 5, shown in it about at the band pass filter 11 of transmitting branch and about diagram at the band pass filter 13 of receiving branch.Therefrom can see a plurality of resistance utmost point f
RS, f
TS, its quantity depends on the quantity of the bandreject filtering loop coupling that is adopted.In Fig. 5, the frequency F that increases gradually is shown on X-axis, decay D is shown on Y-axis.
For band pass filter, also being illustrated in what realized in addition is not that how (imaginary curve) this decay changes under the situation of coupling of the present invention.
In band pass filter of the present invention, one or more at least resistance utmost points can be arranged so that these resistance utmost points for example are positioned at the filter range that free transmission range adjacent band pass filter and related band pass filter staggers.If under any circumstance being positioned at a centre frequency with related band pass filter outside described one or more resistances are set to actual free transmission range at this band pass filter extremely fully or at least in part differs less than ± 50%, especially less than ± 40%, ± 30%, ± 20% and especially less than in ± 10% the frequency range, then also can realize abundant advantage of the present invention.
Under the situation that two bands stagger mutually with frequency range all, this is most commonly used to the field of duplexing directional filter, if at least one or a plurality of resistance utmost point (supression point) are provided so that by suitable coupling capacitance of corresponding selection and coupling inductance centre frequency that this at least one resistance utmost point is positioned at one and related band pass filter differs the frequency range that is no more than 5 times of duplex distance (the frequency centre distance between two adjacent band pass filters just), then equally always can realize advantage of the present invention from related band pass filter abundantly.Therefore preferably, should the resistance utmost point be set outside the free transmission range of this band pass filter from band pass filter, make this resistance utmost point be positioned to be no more than 4 times, three times, twice or one times of duplex distance (the centre frequency distance between two adjacent band pass filters just) to be located.
Certainly irrespectively the single or multiple resistance utmost points are positioned at therewith in the frequency range of adjacent band pass filter.
Be noted that at last can determine respectively to hinder the utmost point when coupling of corresponding selection induction type or capacitive couplings is to form (just having than the low frequency of band pass filter or than its high frequency) under the band pass filter or on band pass filter.Then by the coupling capacitance of bandreject filtering loop coupling and coupling inductance are chosen to make the resonance frequency that produced according to different needs be positioned at band all under the band scope or on realize.
Claims (22)
1. a high frequency filter is particularly useful for duplexing directional filter, has the coaxial resonator (15) of a plurality of electromagnetic coupled, and this high frequency filter has following feature,
-this high frequency filter has the transmission characteristic that depends on coupling impedance,
It is characterized in that other following feature,
The transmission characteristic that depends on coupling impedance of-high frequency filter is included in a frequency (f
s) time at least one restrain point,
-this supression point is positioned at outside the free transmission range of high frequency filter and within the stopband range of this high frequency filter, and
-for these two before and after signal path (10) is gone up directly continuous coaxial resonator (15) have coupling capacitance and coupling inductance, make this at least one restrain point and be positioned at centre frequency with band pass filter and differ frequency (f less than ± 20%
s) locate.
2. high frequency filter according to claim 1 is characterized in that, at described frequency (f
s) time supression point regulate by coupling capacitance and coupling inductances between two coaxial resonators (15) continuous before and after described signal path (10) is gone up directly of given in advance and/or preliminary election.
3. high frequency filter according to claim 1 and 2, it is characterized in that, described at least one coupling capacitance and at least one coupling inductance be selected as making this at least one restrain point be positioned at centre frequency with band pass filter differ the frequency that is no more than this band pass filter ± 10% frequency (f
s) locate.
4. according to each described high frequency filter in the claim 1 to 3, it is characterized in that n coaxial resonator (15) intercouples on signal path (10), wherein be provided with more than one and less than n-1 bandreject filtering loop coupling.
5. according to each described high frequency filter in the claim 1 to 4, it is characterized in that, high frequency filter (1) has at least two band pass filters, and wherein at least one pair of direct continuous, adjacent coaxial resonator in front and back (15) in described signal path comprises having frequency (f concerning each band pass filter
s) bandreject filtering loop coupling, make described supression point be positioned at outside the free transmission range of related band pass filter, wherein preferably at least one restrains the free transmission range that point is positioned at another band pass filter.
6. high frequency filter according to claim 5 is characterized in that, described at least two band pass filters are parts of duplexing directional filter (3).
7. according to claim 5 or 6 described high frequency filters, it is characterized in that, described at least one supression point or preferably a plurality of supression point differ 5 times that are no more than duplex distance from the centre frequency of band pass filter, this duplex distance is the centre frequency distance of two band pass filters of duplexing directional filter just, is preferably less than 4 times, 3 times, 2 times or especially a times of duplex distance.
8. according to each described high frequency filter in the claim 1 to 7, it is characterized in that having the frequency (f of definition in generation
S1, f
S2, f
S3...) the situation of bandreject filtering loop coupling of a plurality of definition under, it is right that a plurality of coaxial resonators continuous before and after signal path (10) is gone up directly are set, wherein at least a portion blanketing frequency difference or at least a portion blanketing frequency are identical.
9. high frequency filter according to claim 8 is characterized in that, described capacitive couplings and induction type coupling can be pre, at least one frequency (f of bandreject filtering loop coupling under making
s) have frequency that is lower than band pass filter or a frequency that is higher than band pass filter.
10. according to each described high frequency filter in the claim 1 to 9, it is characterized in that, the capacitive couplings degree between two adjacent inner conductors (21) of two adjacent coaxial resonators (15) by on adjacent inner conductors (21) direction of the corresponding coupling that has radially the inner wire expansion (21a) that protrudes radially and given in advance by the light between two corresponding inner wires given in advance (21) correspondingly or the affiliated inner wire expansion (21a) thus apart from coming.
11. high frequency filter according to claim 10, it is characterized in that described inner wire expansion (21a) intersects ground, preferably forms perpendicular to this with extending axially with extending axially of affiliated inner wire (21) in the upper end region of inner wire (21).
12., it is characterized in that described have the inner wire (21) of corresponding inner wire expansion (21a) to fall formation according to claim 10 or 11 described high frequency filters.
13. high frequency filter according to claim 11, it is characterized in that, under the situation that produces two bandreject filtering loop couplings, coaxial resonator (15) coupling before being arranged on inner wire (21) and the signal line (10) and after being arranged on, Suo Shu inner wire (21) is not only on the direction at the coaxial resonator (15) of preceding coupling but also all have inner wire expansion (21a) on the direction of the coaxial resonator (15) that is coupled in the back for this reason.
14. high frequency filter according to claim 13 is characterized in that, the described inner wire (21) with affiliated inner wire expansion (21a) forms T shape.
15. according to each described high frequency filter in the claim 1 to 14, it is characterized in that, between two inner wires (21), preferably above two inner wires in the open end zone, conduction is set, be used to shorten the bridging component (221) in the open highway section between two inner wires (21), this bridging component is arranged on inner wire expansion (21a) a distance that forms on corresponding inner wire (21) of distance or the inner wire, can pre-determine thus by two light between the inner wire (21) of bridging component (221) and adjacency or the affiliated inner wire expansion (21a) apart from (121a, 121b) total distance of Zu Chenging, adjustable condenser formula coupling thus.
16. according to each described high frequency filter in the claim 1 to 15, it is characterized in that the coupling pin (301) between two adjacent coaxial resonators (15) reaches the resonator inner space to change the setting of coupling capacitance from the relative shell side (17b) of the shell (17) of coaxial resonator (15).
17. according to each described high frequency filter in the claim 1 to 16, it is characterized in that, the induction type coupling of two adjacent coaxial resonators (15) is by the position of inner wire given in advance (21) and/or from shell bottom plate or cover plate of outer casing (17a, 17b) the next given in advance and/or change of the distance between the vertically extending inner wire (21).
18. according to each described high frequency filter in the claim 1 to 17, it is characterized in that the induction type coupling of two adjacent coaxial resonators (15) comes given in advance and/or change by the different sizes of coupling window (303) between two adjacent coaxial resonators or coupled wave door screen (303).
19., it is characterized in that the induction type coupling of two adjacent coaxial resonators (15) comes given in advance and/or change by coupling pin (302), this coupling pin and shell (17 according to each described high frequency filter in the claim 1 to 18; Inner wire 17a) (21) is positioned at the same side of shell (17).
20. according to each described high frequency filter in the claim 1 to 19, it is characterized in that, the induction type coupling of two adjacent coaxial resonators (15) comes given in advance and/or change by coupling contact pin (307), this coupling contact pin is being extended on the local height with respect to inner wire between two inner wires (21), and preferably is positioned at electric means and is connected with mechanical system and fixedly on the same shell wall (17a) of inner wire (21).
21. according to each described high frequency filter in the claim 1 to 20, it is characterized in that, the induction type coupling of two adjacent coaxial resonators (15) comes given in advance and/or change by at least one coupling loop (305), this coupling loop is arranged between two inner wires (21) of two adjacent coaxial resonators (15), wherein coupling loop (305) can be crooked and/or rotation to change coupling inductance.
22., it is characterized in that described high frequency filter also has one or more condenser type cross-over connection couplings (cross-couplings) according to each described high frequency filter in the claim 1 to 21 except the coupling of one or more bandreject filterings loop.
Applications Claiming Priority (3)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| DE102006061141.1 | 2006-12-22 | ||
| DE102006061141.1A DE102006061141B4 (en) | 2006-12-22 | 2006-12-22 | High frequency filter with blocking circuit coupling |
| PCT/EP2007/010634 WO2008080503A1 (en) | 2006-12-22 | 2007-12-06 | High frequency filter with closed circuit coupling |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN101563809A true CN101563809A (en) | 2009-10-21 |
| CN101563809B CN101563809B (en) | 2014-09-17 |
Family
ID=39046815
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN200780047099.9A Active CN101563809B (en) | 2006-12-22 | 2007-12-06 | High frequency filter with closed circuit coupling |
Country Status (6)
| Country | Link |
|---|---|
| EP (1) | EP2095459A1 (en) |
| KR (1) | KR101484934B1 (en) |
| CN (1) | CN101563809B (en) |
| AU (1) | AU2007341704B2 (en) |
| DE (1) | DE102006061141B4 (en) |
| WO (1) | WO2008080503A1 (en) |
Cited By (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102790250A (en) * | 2011-05-19 | 2012-11-21 | Ace技术株式会社 | Wide-band multi-mode filter |
| CN104701592A (en) * | 2015-04-01 | 2015-06-10 | 河南理工大学 | TM mode medium cavity filter |
| CN105229847A (en) * | 2013-06-25 | 2016-01-06 | 英特尔公司 | Coupled arrangement between cavity filter resonator |
| CN106099282A (en) * | 2015-04-30 | 2016-11-09 | 凯瑟雷恩工厂两合公司 | For transmitting the high frequency filter with dielectric substrate of TM pattern in transverse direction |
| RU2806696C1 (en) * | 2023-05-22 | 2023-11-03 | Федеральное государственное бюджетное образовательное учреждение высшего образования "Саратовский государственный технический университет имени Гагарина Ю.А." (СГТУ имени Гагарина Ю.А.) | Waveguide ultranarrow microwave filter |
Families Citing this family (9)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| ATE555743T1 (en) | 2000-11-08 | 2012-05-15 | Straumann Inst Ag | (DENTAL) SURFACE CAPTURE AND CREATION |
| FI125596B (en) | 2010-11-12 | 2015-12-15 | Intel Corp | Adjustable resonator filter |
| GB201303027D0 (en) * | 2013-02-21 | 2013-04-03 | Mesaplexx Pty Ltd | Filter |
| US9509031B2 (en) * | 2013-05-23 | 2016-11-29 | Com Dev International Ltd. | Coaxial filter with elongated resonator |
| EP2814112A1 (en) * | 2013-06-13 | 2014-12-17 | Alcatel Lucent | Resonant assembly |
| EP2814111B1 (en) * | 2013-06-13 | 2020-03-18 | Alcatel Lucent | Resonant assembly |
| KR101677950B1 (en) * | 2015-04-13 | 2016-11-21 | 주식회사 에이스테크놀로지 | Cavity filter using cross-coupling |
| DE102016117415B4 (en) | 2016-09-15 | 2019-10-31 | Kathrein Mobilcom Austria Gmbh | High-frequency filter with improved signal coupling or signal extraction |
| CN113675561A (en) * | 2020-05-14 | 2021-11-19 | 大富科技(安徽)股份有限公司 | Filter and communication equipment |
Family Cites Families (12)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US3736536A (en) * | 1971-04-14 | 1973-05-29 | Bendix Corp | Microwave filter |
| JPS5390741A (en) * | 1977-01-21 | 1978-08-09 | Nec Corp | Band pass filter |
| FI88979C (en) * | 1990-12-17 | 1993-07-26 | Telenokia Oy | highfrequency bandpass filter |
| FI88830C (en) * | 1991-05-24 | 1993-07-12 | Telenokia Oy | COMB-LINE-HOEGFREKVENSFILTER |
| US5528204A (en) * | 1994-04-29 | 1996-06-18 | Motorola, Inc. | Method of tuning a ceramic duplex filter using an averaging step |
| US5812036A (en) * | 1995-04-28 | 1998-09-22 | Qualcomm Incorporated | Dielectric filter having intrinsic inter-resonator coupling |
| JP3324924B2 (en) * | 1996-01-16 | 2002-09-17 | 株式会社日立国際電気 | Tuning frequency variable bandpass filter |
| WO1999030383A2 (en) * | 1997-12-11 | 1999-06-17 | Lk-Products Oy | Resonator structure |
| SE9802871D0 (en) * | 1998-08-26 | 1998-08-26 | Fertron Oy | Cavity Resonator |
| SE0004935D0 (en) * | 2000-12-29 | 2000-12-29 | Allgon Ab | A filter including coaxial cavity resonators |
| DE10320620B3 (en) * | 2003-05-08 | 2004-11-04 | Kathrein-Werke Kg | High crossover |
| KR100656297B1 (en) * | 2005-07-28 | 2006-12-11 | (주)하이온시스템즈 | Filter that use coupling balance notch cable |
-
2006
- 2006-12-22 DE DE102006061141.1A patent/DE102006061141B4/en not_active Expired - Fee Related
-
2007
- 2007-12-06 WO PCT/EP2007/010634 patent/WO2008080503A1/en active Application Filing
- 2007-12-06 AU AU2007341704A patent/AU2007341704B2/en not_active Ceased
- 2007-12-06 KR KR1020097012217A patent/KR101484934B1/en not_active IP Right Cessation
- 2007-12-06 CN CN200780047099.9A patent/CN101563809B/en active Active
- 2007-12-06 EP EP07856439A patent/EP2095459A1/en not_active Withdrawn
Cited By (8)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102790250A (en) * | 2011-05-19 | 2012-11-21 | Ace技术株式会社 | Wide-band multi-mode filter |
| CN102790250B (en) * | 2011-05-19 | 2015-12-16 | Ace技术株式会社 | Wide-band multi-mode filter |
| CN105229847A (en) * | 2013-06-25 | 2016-01-06 | 英特尔公司 | Coupled arrangement between cavity filter resonator |
| CN105229847B (en) * | 2013-06-25 | 2018-07-17 | 英特尔公司 | Coupled arrangement between cavity filter resonator |
| CN104701592A (en) * | 2015-04-01 | 2015-06-10 | 河南理工大学 | TM mode medium cavity filter |
| CN106099282A (en) * | 2015-04-30 | 2016-11-09 | 凯瑟雷恩工厂两合公司 | For transmitting the high frequency filter with dielectric substrate of TM pattern in transverse direction |
| CN106099282B (en) * | 2015-04-30 | 2020-06-05 | 凯瑟雷恩欧洲股份公司 | High-frequency filter with dielectric matrix for transmitting TM modes in transverse direction |
| RU2806696C1 (en) * | 2023-05-22 | 2023-11-03 | Федеральное государственное бюджетное образовательное учреждение высшего образования "Саратовский государственный технический университет имени Гагарина Ю.А." (СГТУ имени Гагарина Ю.А.) | Waveguide ultranarrow microwave filter |
Also Published As
| Publication number | Publication date |
|---|---|
| WO2008080503A1 (en) | 2008-07-10 |
| DE102006061141B4 (en) | 2014-12-11 |
| AU2007341704B2 (en) | 2012-08-09 |
| EP2095459A1 (en) | 2009-09-02 |
| DE102006061141A1 (en) | 2008-06-26 |
| CN101563809B (en) | 2014-09-17 |
| AU2007341704A1 (en) | 2008-07-10 |
| KR101484934B1 (en) | 2015-01-21 |
| KR20090098822A (en) | 2009-09-17 |
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