CN101291159B - Sending terminal, receiving terminal directly realizing spread-spectrum ultra-wideband and method thereof - Google Patents

Abstract

The invention relates to a sending terminal for implementing DS-UWB. The invention comprises: an encoder for decoding data frames to send, a spread spectrum modulator capable of performing PN sequence spectrum spreading and BPSK modulating to the data outputted by the decoder, a waveshaper capable of performing wave shaping to the data outputted by the spread spectrum modulator to get digital baseband waveshape, a digital-to-analog converter capable of performing digital-to-analog conversion to the digital baseband waveshape outputted by the waveshaper to get simulative baseband waveshape, a low pass filter capable of performing low pass filtering to the simulative baseband waveshape outputted by the digital-to-analog converter; an up-converter capable of performing up conversion to the simulative baseband waveshape outputted by the low pass filter, and an RF signal emission processor capable of performing emission processing to the signal outputted by the up-converter. The sending terminal for implementing DS-UWB also comprises a corresponding transmitting method, a receiving terminal and receiving method of the receiving terminal, which can overcome the difficulties in chipping DS-UWB technology in the prior art.

Description

Realize transmitting terminal, receiving terminal and the method thereof of Direct-Spread ultra broadband

Technical field

The present invention relates to wireless communication technology field, relate in particular to a kind of transmitting terminal, receiving terminal and method thereof that realizes the low complex degree DS-UWB based on single carrier (Direct Spread Ultra Wideband, Direct-Spread ultra broadband).

Background technology

Growing along with wireless communication technology, WPAN (Wireless Personal AccessNetwork, Wireless Personal Network) technology also obtains application more and more widely because of reaching its maturity.As PHY (Physical Layer, physical layer) the standard part of high speed WPAN, the implementation of UWB (Ultra Wideband, ultra broadband) be it is generally acknowledged and comprised two kinds: the DS-UWB scheme that the first is advocated by companies such as Motorolas; Second it is OFDM-UWB (the Orthogonal Frequency Division MultiplexingUWB that is advocated by companies such as Intel, OFDM ultra-wideband) scheme, yet because the keen competition between the different interests group does not have a unified UWB standard to put into effect so far yet.

However, the various countries scholar proposes UWB scheme separately one after another respectively based on above-mentioned two schemes, and China also wishes to realize the UWB standard of oneself, and makes it chipization, industrialization.OFDM-UWB is because its higher peak-to-average force ratio has big difficulty on chipization.And, then mainly have two kinds of spread spectrum modes for the DS-UWB scheme, first kind is adopted PN (Pseudorandom Noise, pseudo noise) sequence spread spectrum; Another kind then adopts MBOK (M-ary Bi-orthogonal Keying, M unit binary orthogonal keying) to carry out spread spectrum.DS-UWB receiver based on MBOK spread spectrum mode requires height to ADC (Anolog-DigitalConverter, analog to digital converter) sample rate, and the complexity height, is difficult to chipization; And based on the DS-UWB of PN sequence spread spectrum mode for obtaining anti-multipath performance preferably, often need very high spreading ratio, thereby cause the ADC sampling rate is required still very high, still be difficult to realize chipization.

Summary of the invention

(1) technical problem that will solve

The purpose of this invention is to provide a kind of transmitting terminal, receiving terminal and method thereof that realizes based on the low complex degree DS-UWB of single carrier, to solve in the prior art that DS-UWB based on PN sequence spread spectrum mode has relatively high expectations to the ADC sample rate and the defective that causes being difficult to realizing chipization.

(2) technical scheme

In order to achieve the above object, the present invention takes following scheme:

A kind of transmitting terminal of realizing the Direct-Spread ultra broadband comprises:

Encoder carries out chnnel coding to sent Frame;

Spread spectrum modulator is carried out PN sequence spread spectrum and BPSK modulation to the data of described encoder output;

Waveshaper carries out waveform shaping to the data of described spread spectrum modulator output, obtains the digital baseband waveform;

Digital to analog converter, the digital baseband waveform that described waveshaper is exported carries out digital-to-analogue conversion, obtains the Analog Baseband waveform;

Low pass filter, the Analog Baseband waveform that described digital to analog converter is exported carries out low-pass filtering;

Upconverter, the Analog Baseband waveform that described low pass filter is exported carries out up-conversion;

The emission of radio frequency signals processor is launched processing to the signal of described upconverter output.

Wherein, also comprise between described encoder and the frequency multiplier:

Interleaver carries out block interleaving to the data of described encoder output and handles;

Described spread spectrum modulator is then carried out PN sequence spread spectrum and BPSK modulation to the data of described interleaver output.

Wherein, described encoder is LDPC encoder or Turbo encoder.

A kind of receiving terminal of realizing the Direct-Spread ultra broadband comprises:

The radiofrequency signal receiving processor, the signal that transmitting terminal is launched receives processing;

Low-converter, the bandpass signal that described radiofrequency signal receiving processor is exported carries out quadrature frequency conversion, obtains I, Q two-way base-band analog signal;

Sampler is sampled respectively to I, the Q two-way base-band analog signal of described low-converter output;

Matched filter carries out matched filter processing to I, the Q two-way sampled data of described sampler output;

The RAKE receiver, the data that described matched filter is exported wait gain or high specific to merge by the footpath, and carry out chip-level sampling, despreading, obtain the bit-level data flow;

The adaptive time domain equalization device carries out adaptive time domain equalization to the bit-level data flow of described RAKE receiver output and handles;

Decoder carries out channel-decoding to the data of described adaptive time domain equalization device output, obtains required receiving data frames.

Wherein, also comprise between described adaptive time domain equalization device and the described decoder:

Deinterleaver carries out deinterleaving to the data of described adaptive time domain equalization device output and handles;

Described decoder then carries out channel-decoding to the data of described deinterleaver output.

Wherein, described adaptive time domain equalization device is MMSE linear equalizer or DFE nonlinear equalizer.

A kind of sending method that realizes the Direct-Spread ultra broadband comprises:

A, carry out LDPC coding or Turbo coding to sent Frame;

B, the data after the described chnnel coding are carried out PN sequence spread spectrum and BPSK modulation;

C, to described spread spectrum, the modulation after data carry out waveform shaping, obtain the digital baseband waveform;

D, described digital baseband waveform is carried out digital-to-analogue conversion, obtain the Analog Baseband waveform;

E, described Analog Baseband waveform is carried out low-pass filtering;

F, the Analog Baseband waveform after the described low-pass filtering is carried out up-conversion, launch processing then.

Wherein, also comprise between described steps A and the step B:

G, the data behind the described coding are carried out block interleaving handle;

Data after then step B promptly handles described block interleaving are carried out PN sequence spread spectrum and BPSK modulation treatment.

A kind of method of reseptance of realizing the Direct-Spread ultra broadband comprises:

A, the bandpass signal that the process radiofrequency signal is handled carry out quadrature frequency conversion, obtain I, Q two-way base-band analog signal;

B, described I, Q two-way base-band analog signal are sampled respectively, obtain I, Q two-way sampled data;

C, described I, Q two-way sampled data are carried out matched filter processing;

D, to gain such as carrying out through the I of described matched filter processing, Q two paths of signals by the footpath or high specific merges, and carry out chip-level sampling, despreading, obtain the bit-level data flow;

E, the adaptive time domain equalization that described bit-level data flow is carried out MMSE or DFE are handled;

F, the data of handling through described adaptive time domain equalization are carried out channel-decoding, obtain required receiving data frames.

Wherein, also comprise between described step e and the step f:

G: the data of handling through described adaptive time domain equalization are carried out deinterleaving handle;

Data after step f then handles described deinterleaving are carried out channel-decoding.

(3) beneficial effect

The present invention has following advantage: on the one hand, the present invention realizes that the transmitting terminal of DS-UWB adopts short PN sequence Direct-Spread, greatly reduces the requirement to receiving terminal ADC sampling rate, thereby has reduced the difficulty of DS-UWB technology chipization.On the other hand, the present invention realizes that the receiving terminal of DS-UWB by quadrature frequency conversion and RAKE folding, collects simultaneously to the energy on I road and Q road, can remedy the loss of low spreading factor on energy; And by bit-level time-domain adaptive equilibrium treatment technology, can eliminate ISI (the Intersymbol Interference that causes by multipath, intersymbol interference), thereby remedies the deficiency of low spreading factor, also make system complexity be unlikely to too high simultaneously anti-multipath.

Description of drawings

Fig. 1 realizes the transmitting terminal example structure figure of DS-UWB for the present invention;

Fig. 2 realizes the sending method embodiment flow chart of DS-UWB for the present invention;

Fig. 3 is an interleaving treatment flow chart of the present invention;

Fig. 4 realizes the receiving terminal example structure figure of DS-UWB for the present invention;

Fig. 5 realizes the method for reseptance embodiment flow chart of DS-UWB for the present invention;

Fig. 6 for each footpath energy among the present invention at the distribution schematic diagram on I road and Q road;

Fig. 7 is MMSE linear adaptive equalizer device schematic diagram among the present invention;

Fig. 8 is DFE nonlinear adaptive equalizer schematic diagram among the present invention;

Fig. 9 among the present invention based on the Weight number adaptively control algolithm model of least mean square algorithm;

Figure 10 is a deinterleaving process chart of the present invention.

Embodiment

Following examples are used to illustrate the present invention, but are not used for limiting the scope of the invention.

Fig. 1 realizes the transmitting terminal example structure figure of DS-UWB for the present invention, and as shown in the figure, the transmitting terminal of present embodiment comprises: encoder 101, carry out chnnel coding to sent Frame; Interleaver 102 carries out block interleaving to the data of encoder 101 outputs and handles; Spread spectrum modulator 103 is carried out PN sequence spread spectrum and BPSK modulation to the data of interleaver 102 outputs, and wherein the order of spread spectrum and modulation treatment can be any; Waveshaper 104 carries out waveform shaping to the data of spread spectrum modulator 103 outputs, obtains the digital baseband waveform; Digital to analog converter 105, the digital baseband waveform that waveshaper 104 is exported carries out digital-to-analogue conversion, obtains the Analog Baseband waveform; Low pass filter 106, the Analog Baseband waveform of logarithmic mode transducer 105 outputs carries out low-pass filtering; Upconverter 107, the Analog Baseband waveform that low pass filter 106 is exported carries out up-conversion; Emission of radio frequency signals processor 108 is launched processing to the signal of upconverter 107 outputs.Among the figure between each device the arrow of connecting line represent the processing direction of data flow.

Fig. 2 realizes the sending method embodiment flow chart of DS-UWB for the present invention, below in conjunction with the transmitting terminal of above-mentioned Fig. 1 this method embodiment is specifically described, and may further comprise the steps:

S201, carry out LDPC coding or Turbo coding to sent Frame;

The Frame to be sent of input is the random binary bit data flow, at first data stream is carried out chnnel coding, in order to obtain performance as well as possible, can select LDPC or Turbo code, both all obtain more and more widely application because of its performance approaches shannon limit; Chnnel coding becomes n bit with the block encoding of k information bit, and code rate is k/n.

S202, the data behind the coding are carried out block interleaving handle;

Fig. 3 is the interleaving treatment schematic diagram, as shown in the figure, d[KN-1], d[KN-2] ..., d[0] and be the input traffic after the coding, every KN bit is a piece; Input traffic is filled to the matrix of K * N at first successively by row, press row serial output then; Interleave depth is K; Originally adjacent data (as d[0] and d[1]) interweaving with becoming afterwards differs K data.Through the data after the interleaving treatment, continuous wrong several bits if unexpected error is arranged can serve as to separate at interval with K data with continuous mistake after the receiving terminal deinterleaving then, thereby can reduce the influence to decoder.Simultaneously, from the above, interleaving treatment is not the necessary step of sending method that the present invention realizes DS-UWB, and accordingly, the interleaver 102 among the above-mentioned transmitting terminal embodiment also belongs to inessential technical characterictic of the present invention.

S203, the data after the interleaving treatment are carried out PN sequence spread spectrum and BPSK modulation;

If frequency expansion sequence is c[0], c[1] ..., c[N _c-1], promptly spreading ratio is N _cTo the data d[k after interweaving], export N behind the spread spectrum _cIndividual chip:

$s[n-N_{c}k]=\underset{i=1}{\overset{N_c-1}{\mathrm{\Σ}}}\left(d\right[k]\⊕c[n-N_{c}k\left]\right)\mathrm{\δ}[n-N_{c}k-i]$

δ [n-N wherein _cK-i] only work as n=N _cValue is 1 during k+i, and other situation values are 0;

Then, to the data s[k behind the spread spectrum], be modulated into m[k]=2*s[k]-1; Soon 1 is modulated into+and 1, be modulated into-1 with 0.

Be to carry out the PN sequence spread spectrum earlier to the data after the interleaving treatment in this step, then carry out the BPSK modulation, the order of spread spectrum, modulation treatment is not limit in concrete the application, can carry out the BPSK modulation earlier yet, then carries out the PN sequence spread spectrum.

S204, to spread spectrum, the modulation after data carry out waveform shaping, obtain the digital baseband waveform;

At first the data that step S203 is obtained are carried out N and are doubly risen sampling, rise sampling promptly to the data m[0 after the above-mentioned BPSK modulation], m[1], m[2] ... insert 0 operation, carry out N and doubly rise then N-1 0:m[0 of insertion between data of sampling], 0 ..., 0, m[1], 0 ... 0, m[2], 0 ..., 0,

Then the data that rise after the sampling are carried out root raised cosine filtering, obtain the digital baseband waveform;

If h[k] be the impulse response of root raised cosine filter, a[k] for rising the signal after sampling, then the signal behind the root raised cosine is b[k]=a[k] * h[k], wherein " * " represents convolution.

Above-mentionedly be filtered into the waveform shaping mode of present embodiment, but the present invention still can take other waveform shaping not as limit with root raised cosine.

S205, digital baseband waveform is carried out digital-to-analogue conversion, obtain the Analog Baseband waveform;

Directly with digital signal b[k] convert analog signal b ' to (t).

S206, the Analog Baseband waveform is carried out low-pass filtering;

Analog signal b ' (t) is carried out low-pass filtering; Owing to directly inevitably carry high fdrequency component by the converted analog signal of DAC, therefore need carry out low-pass filtering with filtering high fdrequency component wherein to it, thus smooth signal.

S207, the Analog Baseband waveform after the low-pass filtering is carried out up-conversion, launch processing then.

Promptly to signal b (t) after the low-pass filtering and carrier wave cosw _cT multiplies each other: s (t)=b (t) cosw _cT delivers to signal the emission of radio frequency signals processor then and launches processing.

Fig. 4 realizes the receiving terminal example structure figure of DS-UWB for the present invention, and as shown in the figure, the receiving terminal of present embodiment comprises: radiofrequency signal receiving processor 401 receives processing to the signal of transmitting terminal emission; Low-converter 402, the bandpass signal that radio frequency signal receiving processor 401 is exported carries out quadrature frequency conversion, obtains I, Q two-way base-band analog signal; Sampler 403 is sampled respectively to I, the Q two-way base-band analog signal of low-converter 402 outputs; Matched filter 404 carries out matched filter processing to I, the Q two-way sampled data of sampler 403 outputs; RAKE receiver 405, the data that described matched filter is exported wait gain or high specific to merge by the footpath, and carry out chip-level sampling, despreading, obtain the bit-level data flow; Adaptive time domain equalization device 406, the bit-level data flow of RAKE receiver 405 outputs is carried out adaptive time domain equalization to be handled, its realization can be selected MMSE linear equalizer or DFE nonlinear equalizer, adaptive algorithm can be selected (the LeastMean Square based on LMS, lowest mean square) some row algorithms, as LMS algorithm, time-delay LMS algorithm, sign LMS algorithm, normalization LMS algorithm etc., concrete described in follow-up method of reseptance embodiment; Deinterleaver 407 carries out deinterleaving to the data of adaptive time domain equalization device 406 outputs and handles; Decoder 408 carries out channel-decoding to the data of deinterleaver 407 outputs, obtains final required receiving data frames.

Wherein, deinterleaver 409 and aforementioned the present invention realize that the interleaver 102 among the transmitting terminal embodiment of DS-UWB is corresponding, also are not the essential features of receiving terminal of the present invention.

Fig. 5 realizes the method for reseptance embodiment flow chart of DS-UWB for the present invention, below in conjunction with the receiving terminal of above-mentioned Fig. 4 this method embodiment is specifically described, and may further comprise the steps:

S501, the bandpass signal that the process radiofrequency signal is handled carry out quadrature frequency conversion, obtain I, Q two-way base-band analog signal;

Receiving terminal receives the data by the transmitting terminal emission, at first passes through the processing of radiofrequency signal receiving processor; Again with the signal after the radio frequency processing

Multiply by local carrier cosw _cT obtains I roadbed band waveform b through low-pass filtering _I(t); Will

Multiply by local carrier sinw _cT low-pass filtering again obtains Q roadbed band waveform b _Q(t); Because the existence of multipath is arranged,

Can be expressed as:

$\tilde{s}\left(t\right)=\underset{i}{\mathrm{\Σ}}{\mathrm{\β}}_{i}s(t-{\mathrm{\τ}}_i)$

$=\underset{i}{\mathrm{\Σ}}{\mathrm{\β}}_{i}b(t-{\mathrm{\τ}}_i)\cos w_c(t-{\mathrm{\τ}}_i)$

Wherein, β _iWith τ _iBe respectively the amplitude and the time-delay in i bar footpath; Thus, can know by inference:

$b_I\left(t\right)=\underset{i}{\mathrm{\Σ}}1/2*{\mathrm{\α}}_{i}b(t-{\mathrm{\τ}}_i)\cos w_c{\mathrm{\τ}}_i=\underset{i}{\mathrm{\Σ}}{\mathrm{\β}}_{i}b(t-{\mathrm{\τ}}_i)\cos {\mathrm{\θ}}_i$

$b_Q\left(t\right)=\underset{i}{\mathrm{\Σ}}1/2*{\mathrm{\α}}_{i}b(t-{\mathrm{\τ}}_i)\sin w_c{\mathrm{\τ}}_i=\underset{i}{\mathrm{\Σ}}{\mathrm{\β}}_{i}b(t-{\mathrm{\τ}}_i)\sin {\mathrm{\θ}}_i$

Wherein, β _i=1/2* α _i, θ _i=w _cτ _i

Fig. 6 be each footpath energy at the distribution schematic diagram on I road and Q road, as shown in the figure, same footpath all can be detected on the I road He on the Q road through after the quadrature frequency conversion, energy directly equals the energy sum in this footpath on the energy in this footpath on the I road and the Q road; Because τ _iCan think at random, so θ _iAlso be at random; From average angle, the I road all the footpath energy values and should with the Q road all the footpath energy values and equate; Therefore,, I, Q two-way energy all can be collected, be handled the energy of collecting than single channel and Duo one times by orthogonal processing.

S502, I, Q two-way base-band analog signal that S501 is obtained are sampled respectively, obtain I, Q two-way sampled data;

Wherein, the speed of sampling be 4 times of spreading rate or more than, the precision of ADC be 4 bits or more than, and the data after I road and the sampling of Q road are respectively:

$b_I\left[k\right]=\underset{i}{\mathrm{\Σ}}{\mathrm{\β}}_{i}b({\mathrm{kT}}_s-{\mathrm{\τ}}_i)\cos {\mathrm{\θ}}_i=\underset{i}{\mathrm{\Σ}}{\widetilde{\mathrm{\β}}}_i\tilde{b}[k-{\mathrm{\Δ}}_i]$

$b_Q\left[k\right]=\underset{i}{\mathrm{\Σ}}{\mathrm{\β}}_{i}b({\mathrm{kT}}_s-{\mathrm{\τ}}_i)\sin {\mathrm{\θ}}_i=\underset{i}{\mathrm{\Σ}}{\widetilde{\mathrm{\α}}}_i\tilde{b}[k-{\mathrm{\Δ}}_i]$

In the following formula, Δ _i=τ _i/ T _s, T _sBe the sampling period, ${\widetilde{\mathrm{\β}}}_i={\mathrm{\β}}_i\cos {\mathrm{\θ}}_i,$ ${\widetilde{\mathrm{\α}}}_i={\mathrm{\β}}_i\sin {\mathrm{\θ}}_i.$

S503, I, Q two-way sampled data that S502 is obtained are carried out matched filter processing;

Data after the sampling are carried out matched filtering, and matched filter is root raised cosine filter, and it has the impulse response h[k identical with root raised cosine filter in the transmitting terminal], and the signal on I, the Q two-way is respectively after the matched filtering:

$a_I\left[k\right]=b_I\left[k\right]*h\left[k\right]=\underset{i}{\mathrm{\Σ}}{\widetilde{\mathrm{\β}}}_i\tilde{a}[k-{\mathrm{\Δ}}_i]$

$a_Q\left[k\right]=b_Q\left[k\right]*h\left[k\right]=\underset{i}{\mathrm{\Σ}}{\widetilde{\mathrm{\α}}}_i\tilde{a}[k-{\mathrm{\Δ}}_i]$

Wherein " * " represents convolution, $\tilde{a}\left[k\right]=\tilde{b}\left[k\right]*h\left[k\right].$

S504, to gain such as carrying out through the I of matched filter processing, Q two paths of signals by the footpath or high specific merges, and carry out chip-level sampling, despreading, obtain the bit-level data flow;

At first, equal gain combining or high specific merging are carried out in some the footpaths of getting all central energy maximums in footpath; Wherein, the signal in i bar footpath is on the I road

$a_I^i[k+{\mathrm{\Δ}}_i]={\widetilde{\mathrm{\β}}}_i\tilde{a}\left[k\right]+\underset{j}{\mathrm{\Σ}}{\widetilde{\mathrm{\β}}}_j\tilde{a}[k+{\mathrm{\Δ}}_i-{\mathrm{\Δ}}_j]$

In the following formula,

Be useful signal,

Be interference that other footpaths are brought on the I road, i.e. ISI, it finally can be eliminated by the time domain equalization of aftermentioned step, therefore can be write as $a_I^i[k+{\mathrm{\Δ}}_i]={\widetilde{\mathrm{\β}}}_i\tilde{a}\left[k\right];$ In like manner, the signal in i bar footpath is on the Q road:

$a_Q^i\left[k{+\mathrm{\Δ}}_i\right]={\widetilde{\mathrm{\α}}}_i\tilde{a}\left[k\right]+\underset{j}{\mathrm{\Σ}}{\widetilde{\mathrm{\α}}}_j\tilde{a}[k+{\mathrm{\Δ}}_i-{\mathrm{\Δ}}_j]$

Wherein, Be useful signal,

Be the interference that other footpaths are brought on the Q road, after interference is eliminated $a_Q^i\left[k{+\mathrm{\Δ}}_i\right]={\widetilde{\mathrm{\α}}}_i\tilde{a}\left[k\right];$ Selecteed each bar directly waits the signal after gain RAKE merges to be:

$r\left[k\right]=\underset{i}{\mathrm{\Σ}}\left|{\mathrm{\β}}_i\right|\left(\right|\cos {\mathrm{\θ}}_i|+|\sin {\mathrm{\θ}}_i\left|\right)\tilde{a}\left[k\right]$

And if the signal that carries out high specific RAKE merging is:

$r\left[k\right]=\underset{i}{\mathrm{\Σ}}{\mathrm{\β}}_i^2\tilde{a}\left[k\right]$

Next, the data after merging through RAKE are carried out the spreading rate sampling, obtain chip rate data stream;

Data r[k after RAKE merged] carry out the sampling output of chip-level:

$\tilde{s}\left[k\right]=r[N_{s}k+{\mathrm{\Δ}}_0]$

N wherein _sSampling rate among the expression step S502, that samples within each chip counts, Δ ₀Expression phase deviation is to aim at optimum sampling point.

At last, the above-mentioned chip rate data stream that obtains is carried out despreading handle, obtain the bit-level data flow;

Despreading is corresponding with the short PN sequence spread spectrum device of transmitting terminal; Every N _cBit of individual chip despreading output:

$\tilde{d}\left[k\right]=\underset{i=1}{\overset{N_c-1}{\mathrm{\Σ}}}\tilde{s}[N_{c}k+i]\tilde{c}\left[i\right]$

Wherein,

With the pass of the employed spreading code of the short PN sequence spread spectrum of transmitter section be $\tilde{c}\left[i\right]=2c\left[i\right]-1;$ C[i] value is 0 or 1, correspondence

Value be-1 or+1.

Among the step S506 of present embodiment, be directly to merge according to each earlier, carry out the chip-level data sampling then, carry out despreading at last and handle, obtain the bit-level data flow.RAKE in the practical application receives processing sequence to be had multiplely, can first chip-level sample, remerges, despreading then, also can first chip-level sampling, despreading again, merging at last.

S507, the bit-level data flow that S506 is obtained are carried out the time domain equalization of MMSE or DFE and are handled;

Data after the despreading are carried out the bit-level adaptive time domain equalization, realize as above-mentioned the present invention described in the receiving terminal embodiment of DS-UWB, its time-domain equalizer can be selected MMSE linear equalizer or DFE nonlinear equalizer, and adaptive algorithm all adopts the LMS algorithm; Because the dateout after RAKE merges is a real number, so the data after the despreading also are real number; All parameters, the inputoutput data of time domain equalization are real number simultaneously.

Fig. 7 is a MMSE linear equalizer structural representation, as shown in the figure, u[n] n input of expression equalizer data, n the dateout that promptly corresponding despreading module obtains

Y[n] expression equalizer n dateout; w _i(i=1,2 ..., M+L) expression tap coefficient, but self adaptation is regulated in the course of the work.Can draw by figure:

$y\left[n\right]=\underset{i=0}{\overset{M}{\mathrm{\Σ}}}{w}_{i}u[n-i]$

Fig. 8 is a DFE equaliser structure schematic diagram, as shown in the figure, u[n] n input of expression equalizer data, n the dateout that promptly corresponding despreading module obtains

Y[n] expression equalizer n dateout; w _i(i=1,2 ..., M+L) expression tap coefficient, but self adaptation is regulated in the course of the work; y _d[n] expression is to y[n] data of adjudicating.Can draw by figure:

$y\left[n\right]=\underset{i=0}{\overset{M}{\mathrm{\Σ}}}{w}_{i}u[n-i]+\underset{i=1}{\overset{L}{\mathrm{\Σ}}}{w}_{M+i}{y}_d[n-i]$

Fig. 9 is the Weight number adaptively control algolithm model based on the LMS algorithm, as shown in the figure, u[n] n input of expression equalizer data; Y[n] expression equalizer n dateout; y _d[n] expression is to y[n] data of adjudicating; D[n] n data should receiving on the representation theory; E[n] the expression error; μ represents the stepping of adaptive equalizer adjustment coefficient; Δ w _i(i=1,2 ..., M+L) expression adjustment amount.Thereby have:

$\mathrm{\&Delta;}{w}_i=\left\{\begin{array}{c}\mathrm{\&mu;}\left(d\right[n]-y[n\left]\right)u[n-i],0\&le;i\&le;M\\ \mathrm{\&mu;}\left(d\right[n]-y[n\left]\right)y_d[n-M-i],M<i\&le;M+L\end{array}\right.$

Need to prove when adopting the DFE equalizer, in the corresponding LMS algorithm y is arranged _dThe data item of decision-feedback such as [n] does not then have when adopting the MMSE linear equalizer.Here also can adopt adaptive algorithm, as time-delay LMS algorithm, sign LMS algorithm, normalization LMS algorithm etc. based on LMS.

The adaptive equalizer working method is as follows: at first transmitting terminal can send a training sequence, data d[n of every transmission], the y[n of recipient by receiving] calculate Δ w _i, adjust w then _iBe w _i+ Δ w _i, carry out the reception of next data again, finish up to the training sequence transmission; Training begins to send data after finishing, and the recipient whenever receives a data y[n], just adjudicate and obtain y _d[n] gets d[n then]=y _d[n] calculates Δ w _i, adjust w then _iBe w _i+ Δ w _i, carry out the reception of next data again.

S508, the data of handling through time domain equalization are carried out deinterleaving handle;

Deinterleaving is corresponding with the interleaving treatment of transmitting terminal, is the data after interweaving are reduced.Figure 10 handles schematic diagram for deinterleaving, as shown in the figure, y[KN-1], y[KN-2] ..., y[0] and be balanced input traffic afterwards, KN bit is a piece; Input traffic at first is filled to the matrix of N * K by row, press row serial output then.

S509, the data after handling through deinterleaving are carried out channel-decoding, obtain required receiving data frames.

The decoding of this step is corresponding to the chnnel coding of sending method.Need to prove that the decoder input is the soft information of judgement of not passing through in this step, thereby can obtain higher gain.

More than be preferred forms of the present invention, according to content disclosed by the invention, those of ordinary skill in the art can expect some identical, replacement schemes apparently, all should fall into the scope of protection of the invention.

Claims (10)

1. a transmitting terminal of realizing the Direct-Spread ultra broadband is characterized in that, comprising:

Encoder carries out chnnel coding to sent Frame;

Spread spectrum modulator is carried out PN sequence spread spectrum and BPSK modulation to the data of described encoder output;

Waveshaper carries out waveform shaping to the data of described spread spectrum modulator output, obtains the digital baseband waveform;

Digital to analog converter, the digital baseband waveform that described waveshaper is exported carries out digital-to-analogue conversion, obtains the Analog Baseband waveform;

Low pass filter, the Analog Baseband waveform that described digital to analog converter is exported carries out low-pass filtering;

Upconverter, the Analog Baseband waveform that described low pass filter is exported carries out up-conversion;

The emission of radio frequency signals processor is launched processing to the signal of described upconverter output.

2. transmitting terminal as claimed in claim 1 is characterized in that, also comprises between described encoder and the frequency multiplier:

Interleaver carries out block interleaving to the data of described encoder output and handles;

Described spread spectrum modulator is then carried out PN sequence spread spectrum and BPSK modulation to the data of described interleaver output.

3. transmitting terminal as claimed in claim 1 is characterized in that, described encoder is LDPC encoder or Turbo encoder.

4. a receiving terminal of realizing the Direct-Spread ultra broadband is characterized in that, comprising:

The radiofrequency signal receiving processor, the signal that transmitting terminal is launched receives processing;

Low-converter, the bandpass signal that described radiofrequency signal receiving processor is exported carries out quadrature frequency conversion, obtains I, Q two-way base-band analog signal;

Sampler is sampled respectively to I, the Q two-way base-band analog signal of described low-converter output;

Matched filter carries out matched filter processing to I, the Q two-way sampled data of described sampler output;

The RAKE receiver, the data that described matched filter is exported wait gain or high specific to merge by the footpath, and carry out chip-level sampling, despreading, obtain the bit-level data flow;

The adaptive time domain equalization device carries out adaptive time domain equalization to the bit-level data flow of described RAKE receiver output and handles;

Decoder carries out channel-decoding to the data of described adaptive time domain equalization device output, obtains required receiving data frames.

5. receiving terminal as claimed in claim 4 is characterized in that, also comprises between described adaptive time domain equalization device and the described decoder:

Deinterleaver carries out deinterleaving to the data of described adaptive time domain equalization device output and handles;

Described decoder then carries out channel-decoding to the data of described deinterleaver output.

6. receiving terminal as claimed in claim 4 is characterized in that, described adaptive time domain equalization device is MMSE linear equalizer or DFE nonlinear equalizer.

7. a sending method that realizes the Direct-Spread ultra broadband is characterized in that, comprising:

A, carry out LDPC coding or Turbo coding to sent Frame;

B, the data after the described chnnel coding are carried out PN sequence spread spectrum and BPSK modulation;

C, to described spread spectrum, the modulation after data carry out waveform shaping, obtain the digital baseband waveform;

D, described digital baseband waveform is carried out digital-to-analogue conversion, obtain the Analog Baseband waveform;

E, described Analog Baseband waveform is carried out low-pass filtering;

F, the Analog Baseband waveform after the described low-pass filtering is carried out up-conversion, launch processing then.

8. sending method as claimed in claim 7 is characterized in that, also comprises between described steps A and the step B:

G, the data behind the described coding are carried out block interleaving handle;

Data after then step B promptly handles described block interleaving are carried out PN sequence spread spectrum and BPSK modulation treatment.

9. a method of reseptance of realizing the Direct-Spread ultra broadband is characterized in that, comprising:

A, the bandpass signal that the process radiofrequency signal is handled carry out quadrature frequency conversion, obtain I, Q two-way base-band analog signal;

B, described I, Q two-way base-band analog signal are sampled respectively, obtain I, Q two-way sampled data;

C, described I, Q two-way sampled data are carried out matched filter processing;

D, to gain such as carrying out through the I of described matched filter processing, Q two paths of signals by the footpath or high specific merges, and carry out chip-level sampling, despreading, obtain the bit-level data flow;

E, the adaptive time domain equalization that described bit-level data flow is carried out MMSE or DFE are handled;

F, the data of handling through described adaptive time domain equalization are carried out channel-decoding, obtain required receiving data frames.

10. method of reseptance as claimed in claim 9 is characterized in that, also comprises between described step e and the step f:

G: the data of handling through described adaptive time domain equalization are carried out deinterleaving handle;

Data after step f then handles described deinterleaving are carried out channel-decoding.

Images