CN101267409A - A MIMO-OFDM dual selective channel tracking method - Google Patents

Abstract

The invention having important actual using value relates to a tracking method of MIMO-OFDM doubly selective channels, characterized in that a good channel tracking of time-frequency doubly selective channels of wireless communication by the particle filter algorithm is performed, without inserting the training sequence or the pilot symbol during the tracking process, so as to improve the system spectrum utilization and to obtain a high error rate performance.

Description

A kind of tracking of MIMO-OFDM dual-selection channel

Technical field

The present invention relates to the channel tracking method in multi-I/O OFDM (MIMO-OFDM) system, in the definite MIMO-OFDM system that says so based on the tracking of the T/F dual-selection channel of particle filter, particularly a kind of tracking of MIMO-OFDM dual-selection channel.

Background technology

As everyone knows, MIMO and OFDM technology will be the key technologies of next generation mobile communication.Both combinations have made full use of capacity and the noise robustness that space diversity, frequency diversity and time diversity are improved system.Yet the efficient performance of MIMO-OFDM depend on receiving terminal channel estimating accurately whether.The method of traditional channel estimating is the channel estimation method based on pilot tone, but in order to obtain believable channel estimating, quite a few of channel width is shared by training sequence.1996, Stuber pointed out that under rapid fading, high-doppler condition, the occupied ratio of bandwidth can be up to 50% in his works " Principles of mobile communication ".2002, Liu etc. propose to utilize Kalman filtering to carry out channel estimating and tracking in article " Space time coding and Kalmanfiltering for time-selective fading channel ", reduce the length of training signal with this.For Channel Track, in linear Gauss system, there is not a kind of algorithm can be better than Kalman filtering.But in wireless communication system, received signal is often polluted by non-Gaussian noise.On the channel tracking problem that relates to nonlinear state transfer and non-Gaussian noise, the filtering of sequential Monte Carlo is more superior than EKF.

Particle filter algorithm is a kind of basic methods of sequential Monte Carlo filtering, its main thought is to utilize the stochastic variable sample calculation of one group of relevant weights to finish estimation, to approach actual posterior probability density, when number of samples was very big, this probability Estimation can closely be intended true posterior probability.

If

The expression random particles, it contains posterior probability pdfp (x _0:n| y _1:n) characteristic, wherein { x _0:n ⁱ, i=0 ..., N _sBe and weights { w _n ⁱ, i=1 ..., N _sRelevant state set, and weights satisfy ${\mathrm{\Σ}}_i{w}_n^i=1,$ But t posterior probability density approximate representation constantly then: $p\left(x_{0:n}\right|y_{1:n})\≈{\mathrm{\Σ}}_{i=1}^{N_s}{w}_n^i\mathrm{\δ}(x_{0:n}-x_{0:n}^i).$

Summary of the invention

For under the prerequisite that improves the availability of frequency spectrum, make system obtain good bit error rate performance, the invention provides a kind of tracking of MIMO-OFDM dual-selection channel.For this tracking is provided, at first provide the channel model of the two selective channels of MIMO-OFDM.

If the impulse response of the two selective channels in the MIMO-OFDM system between transmitting antenna i and reception antenna j is made as h _{I, j}(n, τ), i=0 wherein, 1 ..., M _T, j=0,1 ..., M _R, M _TAnd M _RBe respectively the number of transmitting antenna and reception antenna.Then with reference to Proakis at " Digital Communication (Forth Edition) " described tapped delay line model:

$h_{i,j}(n,\mathrm{\τ})={\mathrm{\Σ}}_{l=0}^{L-1}{A}_l{h}_{i,j}^l(n-{\mathrm{\τ}}_{i,j}^l)+w_{i,j}\left(n\right)$ i＝0，1，…，M _T；j＝0，1，…，M _R (1)

Wherein L represents multipath number, A _lAnd τ _{I, j} ^lBe respectively the path gain in each footpath and postpone expansion, w _{I, j}(n) be multiple noise random sequence.Single footpath channel h _{I, j} ^l(n) be modeled as single order autoregression AR process, promptly

$h_{i,j}^l\left(n\right)=\mathrm{\α}{h}_{i,j}^l(n-1)$ l＝0，1，…，L-1 (2)

" Estimation and equalization of fading channels with randomcoefficients " that reference Tsatasnis in 1996 etc. deliver is defined as factor alpha:

α＝J ₀(2πf _dT _s)exp(j(2πf ₀T _s) (3)

Wherein, J ₀() is zeroth order Bessel function, f _dBe maximum doppler frequency, f ₀Be carrier wave frequency deviation, T _sBe the tracking of a kind of MIMO-OFDM dual-selection channel of symbol time, step is as follows:

Initialization particle collection h _{I, j} ^m(0), i=0,1 ..., M _TJ=0,1 ..., M _RM=1 ..., M, weight w _{I, j} ^m(0) all put 1/M, obtain a measured value after:

1) utilize the formula (1) (2) can be by h _{I, j} ^m(n-1) obtain new particle collection h _{I, j} ^m(n).

2) for each particle, use likelihood function and calculate the particle weights,

${\mathrm{lik}}_{i,j}^m\left(n\right)=p\left(y\left(n\right)\right|h_{i,j}^m\left(n\right))=\frac{1}{{\mathrm{\&sigma;}}_{\mathrm{<figure-callout\; id="2"\; label="n"\; filenames="A20081001536800072.png"\; state="\{\{state\}\}">n</figure-callout>}}\sqrt{2\mathrm{\&pi;}}}{e}^{-\frac{(y\left(n\right)-h_{i,j}^m\left(n\right)\hat{x}\left(n\right))}{2{\mathrm{\&sigma;}}_n^2}}---\left(4\right)$

3) calculate the normalization weight w _{I, j} ^m(n);

4) resample: have the sample of big weights, repeated sampling; Little weights sample is abandoned as far as possible simultaneously.So obtain M random sample, its weights are made as ${\tilde{w}}_{i,j}^m\left(n\right)=1/M.$ Sample distribution gradually distributes in posteriority,

$p\left(h_{i,j}^m\left(n\right)\right|y(1:n))\&ap;{\tilde{w}}_{i,j}^m\left(n\right){\mathrm{\&Sigma;}}_{m=1}^M{\mathrm{\&delta;}}_{h_{i,j}^m\left(n\right)}\left(\mathrm{dh}\left(n\right)\right)=\frac{1}{M}{\mathrm{\&Sigma;}}_{m=1}^M{\mathrm{\&delta;}}_{h_{i,j}^m\left(n\right)}\left(\mathrm{dh}\left(n\right)\right)---\left(5\right)$

5) obtaining channel estimation value by the posteriority distribution is:

$\hat{h}\left(n\right)=E\left(h\left(n\right)\right)=\&Integral;h\left(n\right)p\left(h\left(n\right)\right|y(1:n))\mathrm{dh}\left(n\right)\&ap;\frac{1}{M}{\mathrm{\&Sigma;}}_{m=1}^M{h}_{i,j}^m\left(n\right)---\left(6\right)$

The advantage of the inventive method: can carry out good channel tracking to the T/F dual-selection channel in the radio communication, tracing process no longer needs to insert training sequence or frequency pilot sign, can improve the availability of frequency spectrum of system, obtain high bit error rate performance.

Description of drawings

Fig. 1 adopts two two of space-time block code to receive the MIMO-OFDM system block diagram for the inventive method;

Wherein, 1.STBC coding, 2.STBC decoding, 3. particle filter channel tracking.

Fig. 2 is two two and receives MIMO-OFDM system Space Time Coding process schematic diagram;

Wherein: 4. frequency, 5. time, 6. Space Time Coding.

Fig. 3 is a particle filter tracking method parameter table;

Fig. 4 is particle filter algorithm and traditional comparing based on the least square of training sequence and the BER performance of least mean-square error method.

Embodiment

Embodiment:

With number of transmit antennas is 2, and accepting antenna number and be 2 MIMO-OFDM system is that example is introduced this method.System model is as shown in Figure 1: information sequence is through modulators modulate, then these modulation symbols are carried out Space Time Coding (STBC) by the Space Time Coding device, behind serial to parallel conversion,, at last code word is gone out by transmission antennas transmit through inverse fast fourier transform (IFFT).At receiving terminal, carry out fast Fourier transform (FFT) at first to received signal, decoding and channel tracking module during then through sky, and finally translate information sequence.

The process of Space Time Coding is as follows in the system shown in Figure 1: the sub-carrier number of establishing OFDM is N _s, the continuous information bit stream of input is after ovennodulation, with N _sFor unit divides into groups.In the beginning of per two continuous OFDM mark spaces, with two continuous groupings after serial/parallel conversion, obtain symbolic vector X (n)=[X (and 0, n), X (1, n) ..., X (N _s-1, n)] and X (n+1)=[X (0, n+1), X (1, n+1) ..., X (N _s-1, n+1)].The component of symbolic vector correspondence is carried out the Alamouti space-time block code, as shown in Figure 2, obtain 4 vector: X ₀(n), X ₁(n), X ₀(n+1), X ₁(n+1), i.e. 4 OFDM symbols, wherein n represents n OFDM mark space, and subscript representative antennas index.In n OFDM mark space, coding result X ₀(n), X ₁(n) respectively through launching simultaneously by the 1st and the 2nd antenna after the IFFT conversion, in n+1 OFDM mark space, X ₀(n+1), X ₁(n+1) respectively through launching simultaneously by the 1st and the 2nd antenna after the IFFT conversion.

Suppose that channel is constant in an OFDM mark space, then after the receiving terminal process demodulation (FFT conversion), the received signal on each subcarrier is the superposition that two distortion send signals, can be expressed as:

$Y_j(n,k)=\underset{i=0}{\overset{1}{\mathrm{\&Sigma;}}}{X}_i(n,k)H_{\mathrm{ij}}(n,k)+W_j(n,k)$ j＝0，1；k＝0，1，…N _s-1

X wherein _i(n, k), Y _j(n, k) be respectively n OFDM symbol k subcarrier on i transmitting antenna and j reception antenna transmission signal and received signal; W _j(n, k) random noise that is j reception antenna on k subcarrier during n the OFDM symbol.H _Ij(n k) is from i transmitting antenna to j reception antenna the channel frequency response coefficient on k subcarrier during n the OFDM symbol,

$H_{\mathrm{ij}}(n,k)={\mathrm{\&Sigma;}}_{l=0}^{L-1}{h}_{i,j}(n,\mathrm{\&tau;}){|}_{\mathrm{\&tau;}=l}{e}^{-\mathrm{<figure-callout\; id="2"\; label="j"\; filenames="A20081001536800072.png"\; state="\{\{state\}\}">j</figure-callout>}\frac{2\mathrm{\&pi;}}{K}\mathrm{lk}}$

H wherein _{I, j}(n, τ) i=0,1; J=0,1 is two two impulse responses of receiving two selective channels in the MIMO-OFDM system.Tracking step for this channel is as follows:

Initialization particle collection h _{I, j} ^m(0), i=0,1; J=0,1; M=1 ..., M, weight w _{I, j} ^m(0) all put 1/M, obtain a measured value after:

1) utilize the formula (1) (2) can be by h _{I, j} ^m(n-1) obtain new particle collection h _{I, j} ^m(n).

2) for each particle, use likelihood function and calculate the particle weights,

${\mathrm{lik}}_{i,j}^m\left(n\right)=p\left(y\left(n\right)\right|h_{i,j}^m\left(n\right))=\frac{1}{{\mathrm{\&sigma;}}_{\mathrm{<figure-callout\; id="2"\; label="n"\; filenames="A20081001536800072.png"\; state="\{\{state\}\}">n</figure-callout>}}\sqrt{2\mathrm{\&pi;}}}{e}^{-\frac{(y\left(n\right)-h_{i,j}^m\left(n\right)\hat{x}\left(n\right))}{2{\mathrm{\&sigma;}}_{\mathrm{<figure-callout\; id="2"\; label="n"\; filenames="A20081001536800072.png"\; state="\{\{state\}\}">n</figure-callout>}}^2}}$

3) calculate the normalization weight w _{I, j} ^m(n)

4) resample: have the sample of big weights, repeated sampling; Little weights sample is abandoned as far as possible simultaneously.So obtain M random sample, its weights are made as ${\tilde{w}}_{i,j}^m\left(n\right)=1/M.$ Sample distribution gradually distributes in posteriority,

$p\left(h_{i,j}^m\left(n\right)\right|y(1:n))\&ap;{\tilde{w}}_{i,j}^m\left(n\right){\mathrm{\&Sigma;}}_{m=1}^M{\mathrm{\&delta;}}_{h_{i,j}^m\left(n\right)}\left(\mathrm{dh}\left(n\right)\right)=\frac{1}{M}{\mathrm{\&Sigma;}}_{m=1}^M{\mathrm{\&delta;}}_{h_{i,j}^m\left(n\right)}\left(\mathrm{dh}\left(n\right)\right)$

5) obtaining channel estimation value by the posteriority distribution is:

$\hat{h}\left(n\right)=E\left(h\left(n\right)\right)=\&Integral;h\left(n\right)p\left(h\left(n\right)\right|y(1:n))\mathrm{dh}\left(n\right)\&ap;\frac{1}{M}{\mathrm{\&Sigma;}}_{m=1}^M{h}_{i,j}^m\left(n\right)$

Fig. 3 has provided the parameter list when particle filter algorithm is followed the tracks of the MIMO-OFDM dual-selection channel.When adopting particle filter algorithm to carry out channel tracking, the performance that how much can influence tracking of population adopts population N=50 that channel is followed the tracks of among the present invention.The BER performance that Fig. 4 has provided particle filter algorithm and traditional least square based on training sequence (LS) and least mean-square error (MMSE) method relatively.Under as can be seen from the figure identical signal to noise ratio (BER) situation, the BER performance of particle filter algorithm is significantly better than least square and least-mean-square error algorithm.

Claims (1)

1. 

   A kind of tracking of MIMO-OFDM dual-selection channel, step is as follows:

   Initialization particle collection h _{I, j} ^m(0), i=0,1 ..., M _tJ=0,1 ..., M _RM=1 ..., M, weight w _{I, j} ^m(0) all put 1/M, obtain a measured value after,

   1) utilizes formula $h_{i,j}(n,\mathrm{\&tau;})={\mathrm{\&Sigma;}}_{l=0}^{L-1}{A}_l{h}_{i,j}^l(n-{\mathrm{\&tau;}}_{i,j}^l)+w_{i,j}\left(n\right)$ I=0,1 ..., M _TJ=0,1 ..., M _RAnd formula $h_{i,j}^l\left(n\right)=\mathrm{\&alpha;}{h}_{i,j}^l(n-1)$ L=0,1 ..., L-1 can be by h _{I, j} ^m(n-1) obtain new particle collection h _{I, j} ^m(n);

   2) for each particle, use likelihood function and calculate the particle weights,

   ${\mathrm{lik}}_{i,j}^m\left(n\right)=p\left(y\left(n\right)\right|h_{i,j}^m\left(n\right))=\frac{1}{{\mathrm{\&sigma;}}_n\sqrt{2\mathrm{\&pi;}}}{e}^{-\frac{(y\left(n\right)-h_{i,j}^m\left(n\right)\hat{x}\left(n\right))}{2{\mathrm{\&sigma;}}_n^2}};$

   3) calculate the normalization weight w _{I, j} ^m(n);

   4) resample: have the sample of big weights, repeated sampling; Little weights sample is abandoned as far as possible simultaneously, so obtains M random sample, and its weights are made as ${\tilde{w}}_{i,j}^m\left(n\right)=1/M;$ Sample distribution gradually distributes in posteriority,

   $p\left(h_{i,j}^m\left(n\right)\right|y(1:n))\&ap;{\tilde{w}}_{i,j}^m\left(n\right){\mathrm{\&Sigma;}}_{m=1}^M{\mathrm{\&delta;}}_{h_{i,j}^m\left(n\right)}\left(\mathrm{dh}\left(n\right)\right)=\frac{1}{M}{\mathrm{\&Sigma;}}_{m=1}^M{\mathrm{\&delta;}}_{h_{i,j}^m\left(n\right)}\left(\mathrm{dh}\left(n\right)\right);$

   5) obtaining channel estimation value by the posteriority distribution is:

   $\hat{h}\left(n\right)=E\left(h\left(n\right)\right)=\&Integral;h\left(n\right)p\left(h\left(n\right)\right|y(1:n))\mathrm{dh}\left(n\right)\&ap;\frac{1}{M}{\mathrm{\&Sigma;}}_{m=1}^M{h}_{i,j}^m\left(n\right).$

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