CN101257324A - Linear combined channel estimation method in TD-SCDMA system - Google Patents

Linear combined channel estimation method in TD-SCDMA system Download PDF

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CN101257324A
CN101257324A CNA2007100377239A CN200710037723A CN101257324A CN 101257324 A CN101257324 A CN 101257324A CN A2007100377239 A CNA2007100377239 A CN A2007100377239A CN 200710037723 A CN200710037723 A CN 200710037723A CN 101257324 A CN101257324 A CN 101257324A
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陈志群
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Spreadtrum Communications Shanghai Co Ltd
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Abstract

The invention discloses a linearity combined channel estimating method in TD-SCDMA system, comprising that: signals of K districts are in real time received by a receiver, a data divide unit separates the receiving signal x of P code from the receiving signal r as the real time input of a channel estimater to perform the Fourier transform, the Fourier transform of basic intermediate code in K districts is used as the constant input value to compute the least square solution of channel impulse response of each district, finally the result of channel estimate h and the data symbol are together used in the combined detection to obtain the estimate of the sending data symbol, and reestimate after selecting a taps.

Description

Linear combined channel estimation method in the TD-SCDMA system
Technical field
The present invention relates to the channel estimation methods of receiver in a kind of wireless communication system, the linear combined channel estimation method in the particularly a kind of TD-SCDMA system.
Background technology
Next TD-SCDMA system up-link data will carry out channel estimating and joint-detection after the base station receives by antenna.Associated detection technique then refers to and makes full use of multiple access interference (MA I), a kind of signal separation techniques of within the step all users' signal all being separated.The very suitable use associated detection technique of TD-SCDMA system, because code channel number is limited and be confined on the most suitable number in this system, and all users in the same time slot are synchronous.Associated detection technique has become the focus in the 3G (Third Generation) Moblie technology.The associated detection technique that adopts in the TD-SCDMA system is on the basis of traditional detection technology, make full use of and cause all subscriber signals that multiple access disturbs and the prior information of multipath thereof, the separation of subscriber signal being used as the joint detection process that is mutually related of a unification finishes, thereby has good interference free performance, reduced the requirement of system to the power control precision, therefore can effectively utilize the uplink spectrum resource more, improve power system capacity significantly.
Channel estimating is a vital part in joint detection process, and it will influence the testing process performance in many aspects.The accuracy of the detection information of combined detector output is directly related with the quality of channel estimating, and how obtaining accurately efficiently, each user's channel impulse response is the key that follow-up base band algorithm is realized.As a rule, channel estimating is accurate more, just can obtain good more systematic function.
In the TD-SCDMA system under the identical networking situation, the receiver channel method of estimation generally has two big classes, promptly single cell channel estimation method and multiple cell combined channel estimation method.
Single cell channel estimation method is exactly to continue to use Steiner estimator in the past, will be used as to disturb from the signal of other sub-district and handle, and obviously its performance seriously is subject to interference, usually can't operate as normal in the TD-SCDMA of identical networking system.
Summary of the invention
The purpose of this invention is to provide the linear combined channel estimation method in a kind of TD-SCDMA system,, make it to be applicable to the TD-SCDMA system of identical networking to improve performance for estimating channel.
For solving the problems of the technologies described above, this multiple cell combined channel estimation method is applied to channel estimating with multiuser detection, to be used as different users from the signal of different districts, and adopt suitable multiuser detection partly to eliminate the phase mutual interference between the different districts.Technical scheme of the present invention is:
Linear combined channel estimation method in a kind of TD-SCDMA system is characterized in that this method may further comprise the steps:
(1) the real-time signal that receives K sub-district from receiver;
(2) data splitting block is isolated the received signal x of P chip of corresponding intermediate code part from the received signal r of a time slot, as the real-time input of channel estimator;
(3) basic midamble code according to K the sub-district that participates in the combined channel estimation constructs a P * KP rank complex matrix
Figure A20071003772300052
The cyclic shift of classifying k sub-district basic midamble code as;
(4) the Fourier transform FFT{M of the basic midamble code of K sub-district of calculating participation combined channel estimation k(:, 1) }, M wherein k(:, 1) representing matrix M kFirst row, i.e. basic midamble code itself, being expressed as matrix form is Λ k=[λ K, 1λ K, P] T=FFT{M k(:, 1), p=1 ..., P, storage computation is Λ as a result kFixedly input value as channel estimator;
(5) make S=MM H, characteristic value Λ=[λ of calculating S 1λ P] T, wherein HThe expression complex-conjugate transpose, TThe expression transposition, computational methods are λ p = Σ k | λ k , p | 2 , λ K, pBe M kCharacteristic value, storage vector Λ is as the fixedly input value of channel estimator;
(6) the Fourier transform FFT{x} of calculating received signal x;
(7) calculate the least square solution of estimation of the channel impulse response of each sub-district h ^ k = K * IFFT { conj { Λ k } . * FFT { x } . / Λ } , Wherein * represents multiplication, and IFFT{} represents contrary fast fourier transform, and conj{} represents complex conjugate, and .* represents that corresponding element multiplies each other, and FFT{} represents fast fourier transform ./expression corresponding element is divided by;
(8) based on the result of above-mentioned channel estimating, selected tap is used for estimating once more;
(9) selected tap forms a new channel impulse response vector h ', new matrix M of row formation of extraction correspondence from matrix M ' and, the least square solution of channel impulse response estimation is
Figure A20071003772300063
Wherein
Figure A20071003772300064
Expression Moore-Penrose pseudoinverse;
(10) h as a result of channel estimating is applied to joint-detection with the data symbol part of received signal r, to obtain to sending the estimation of data symbol.
The criterion of the selected tap when estimating once more in the described step 9 is based on the hypothesis to the multidiameter delay expansion.
The condition that the described M ' that is used for estimating once more is a row non-singular matrix is that the columns of M ' is less than or equal to P.
Described P=128, set basis is referring to 3GPP TS 25.221 physical channels and transmission channel mapping (TDD) the 5A.2.3 joint to physical channel.
Described received signal x can be expressed as
x＝Mh+n
Wherein
Figure A20071003772300065
Figure A20071003772300066
Be the channel impulse response of k sub-district,
Figure A20071003772300067
Be noise;
Minimize the Euclidean norm of evaluated error
Figure A20071003772300068
The least square solution that can obtain the estimation of channel impulse response is
h ^ = KM H ( M M H ) - 1 x
Wherein -1Expression is inverted.
The described new matrix M that is used for estimating once more ' be a row non-singular matrix, the least square solution of channel impulse response estimation is h ^ ′ = K ( M ′ H M ′ ) - 1 M ′ H x .
Adopt shortcut calculation in the described estimation once more: calculate M ' HIn M ' time, calculate M by the method for fast fourier transform HM therefrom extracts desired element then; Calculate (M ' HM ') -1The time, earlier with the partitioning of matrix, carry out Cholesky then and decompose; Calculate M ' HDuring x, calculate M by the method for fast fourier transform equally HX therefrom extracts desired element then.
Compared with prior art, beneficial effect of the present invention is as follows:
In the channel estimation results of technical solution of the present invention, arbitrary sub-district accesses supression preferably to the Recombinant Interferon of other sub-district, and the channel estimation window of the user's correspondence in the sub-district can reflect the multi-path environment that this user experiences more exactly.Therefore, compare with single cell channel estimated result, performance for estimating channel of the present invention has greatly improved.
Description of drawings
Fig. 1 is a typical TD-SCDMA structure of time slot schematic diagram.
Fig. 2 is channel estimating and joint-detection schematic diagram.
Fig. 3 is the simulation result figure of single cell channel estimation method and multiple cell combined channel estimation method.
Embodiment
The present invention will be further described below in conjunction with drawings and Examples, but should not limit protection scope of the present invention with this.
As shown in Figure 1, provide a typical TD-SCDMA structure of time slot schematic diagram.A time slot is made of at interval the intermediate code of the data symbol of two sections 352 chips, 144 chips and the protection of 16 chips, altogether 864 chips.
In general different basic midamble codes is used in different sub-district, and basic midamble code generates intermediate code and saves referring to 3GPP TS 25.221 physical channels and transmission channel mapping (TDD) 5A.2.3 to physical channel.
Consider one and can receive the situation that K sub-district transmits simultaneously.From receiver, receive the signal of K sub-district in real time.
Fig. 2 provides a channel estimating and joint-detection schematic diagram, as shown in Figure 2, the received signal r of a time slot comprises 864 chips, pass through data splitting block, intercept the received signal x of wherein corresponding intermediate code part, promptly 496 chips of the 369th chip to the have the real-time input of P chip as channel estimator altogether, get P=128 here.
The received signal x of corresponding intermediate code part can be expressed as
x＝Mh+n
Wherein
Figure A20071003772300081
Be that M is a P * KP rank complex matrix,
Figure A20071003772300082
The cyclic shift of classifying k sub-district basic midamble code (Basic Midamble Code) as.
Figure A20071003772300083
Figure A20071003772300084
Be the channel impulse response of k sub-district, wherein TThe expression transposition.
Figure A20071003772300085
Be noise.
The least square of the estimation of channel impulse response (LS, Least Square) separate into
h ^ = KM H ( MM H ) - 1 x
Wherein HThe expression complex-conjugate transpose, -1Expression is inverted.
Make S=MM H, M so kWith S all be circular matrix (Circulant Matrices).According to the character of circular matrix, M kCharacteristic value be λ K, p, p=1 ..., P is expressed as matrix form, i.e. Λ k=[λ K, 1λ K, P] T=FFT{M k(:, 1) }, M wherein k(:, 1) representing matrix M kFirst row, i.e. basic midamble code itself.Similarly, the characteristic value of S can be expressed as Λ=[λ 1λ P] T, wherein λ p = Σ k | λ k , p | 2 , p = 1 , · · · , P .
Store described result of calculation Λ k, Λ is as the fixedly input value of channel estimator.Calculate the Fourier transform FFT{x} of received signal x.
Therefore the least square solution of the estimation of channel impulse response also can basis
h ^ k = K * IFFT { conj { Λ k } . * FFT { x } . / Λ } Calculate channel estimation results.
Wherein * represents multiplication, and IFFT{} represents contrary fast fourier transform, and conj{} represents complex conjugate, and * represents that corresponding element multiplies each other, and FFT{} represents fast fourier transform ./expression corresponding element is divided by.
Based on above-mentioned channel estimation results,, for example, select some may exist the tap of multipath signal to estimate once more based on hypothesis to the multidiameter delay expansion according to certain criterion.Selected tap can form a new channel impulse response vector h ', new matrix M of row formation of extraction correspondence from matrix M ' and, the least square solution of channel impulse response estimation can be write as so
Figure A20071003772300092
Wherein
Figure A20071003772300093
Expression Moore-Penrose pseudoinverse.
When above-mentioned new matrix M ' columns when being less than or equal to P, M ' is a row non-singular matrix, following formula can be write as so
h ^ ′ = K ( M ′ H M ′ ) - 1 M ′ H x
In the above-mentioned process of estimating once more, can use some shortcut calculations.For example, calculating M ' HIn M ' time, can calculate M by the method for fast fourier transform HM therefrom extracts desired element then; Calculate (M ' HM ') -1The time, can carry out Cholesky then and decompose earlier with the partitioning of matrix; Calculating M ' HIn the time of x, can calculate M by the method for fast fourier transform equally HX therefrom extracts desired element then.
As shown in Figure 2, the result of channel estimating will be applied to joint-detection, obtain sending the estimation of data symbol with the data symbol of received signal part.
By an emulation good effect of the technical program is described, simulated conditions as shown in Table 1 and Table 2, set basis is referring to 3GPP TS 25.102 subscriber equipment wireless transmission and reception (TDD).
Table 1 simulated conditions
Figure A20071003772300095
Figure A20071003772300101
Table 2 multipath fading environments propagation conditions
Figure A20071003772300102
Based on above-mentioned simulated conditions, Fig. 3 has provided the Matlab simulation result figure of single cell channel estimation method and multiple cell combined channel estimation method, and abscissa is tap among the figure, and ordinate is an intensity.Two figure in the left side are single cell channel results estimated, and last figure is single cell channel estimated result of sub-district 1, and figure below is single cell channel estimated result of sub-district 2; Two results that figure is a technical solution of the present invention in the right, last figure is the linear combined channel estimation results in many sub-districts of sub-district 1, figure below is the multi-plot joint linear channel estimated result of sub-district 2.
Obviously, in the channel estimation results of single sub-district, sub-district 2 has been subjected to the interference from sub-district the last 1, and in the channel estimation results of technical solution of the present invention, interference from sub-district 1 is restrained preferably, can see the channel estimation window of user's correspondence in the sub-district 2 more clearlyly, reflect the multi-path environment of this user's experience more exactly.Therefore, compare with single cell channel estimated result, the present invention has bigger performance improvement.
The above is preferred embodiment of the present invention only, is not to be used for limiting practical range of the present invention.Be that all equivalences of doing according to the content of the present patent application claim change and modification, all should be technology category of the present invention.

Claims (7)

1. the linear combined channel estimation method in the TD-SCDMA system is characterized in that this method may further comprise the steps:
(1) the real-time signal that receives K sub-district from receiver;
(2) data splitting block is isolated the received signal x of P chip of corresponding intermediate code part from the received signal r of a time slot, as the real-time input of channel estimator;
(3) basic midamble code according to K the sub-district that participates in the combined channel estimation constructs a P * KP rank complex matrix
Figure A2007100377230002C1
Figure A2007100377230002C2
The cyclic shift of classifying k sub-district basic midamble code as;
(4) the Fourier transform FFT{M of the basic midamble code of K sub-district of calculating participation combined channel estimation k(:, 1) }, M wherein k(:, 1) representing matrix M kFirst row, i.e. basic midamble code itself, being expressed as matrix form is Λ k=[λ K, 1λ K, P] T=FFT{M k(:, 1), p=1 ..., P, storage computation is Λ as a result kFixedly input value as channel estimator;
(5) make S=MM H, characteristic value Λ=[λ of calculating S 1λ P] T, wherein HThe expression complex-conjugate transpose, TThe expression transposition, computational methods are λ p = Σ k | λ k , p | 2 , λ K, pBe M kCharacteristic value, storage vector Λ is as the fixedly input value of channel estimator;
(6) the Fourier transform FFT{x} of calculating received signal x;
(7) calculate the least square solution of estimation of the channel impulse response of each sub-district h ^ k = K * IFFT { conj { Λ k } . * FFT { x } . / Λ } , Wherein * represents multiplication, and IFFT{} represents contrary fast fourier transform, and conj{} represents complex conjugate, and * represents that corresponding element multiplies each other, and FFT{} represents fast fourier transform ./expression corresponding element is divided by;
(8) based on the result of above-mentioned channel estimating, selected tap is used for estimating once more;
(9) selected tap forms a new channel impulse response vector h ', new matrix M of row formation of extraction correspondence from matrix M ' and, the least square solution of channel impulse response estimation is
Figure A2007100377230002C6
Wherein
Figure A2007100377230002C7
Expression Moore-Penrose pseudoinverse;
(10) h as a result of channel estimating is applied to joint-detection with the data symbol part of received signal r, to obtain to sending the estimation of data symbol.
2. the linear combined channel estimation method in the TD-SCDMA according to claim 1 system, the criterion that it is characterized in that described selected tap when estimating once more is based on the hypothesis to the multidiameter delay expansion.
3. the linear combined channel estimation method in the TD-SCDMA according to claim 1 system is characterized in that condition that the described M ' that is used for estimating once more is a row non-singular matrix is that the columns of M ' is less than or equal to P.
4. according to the linear combined channel estimation method in claim 1 or the 3 described TD-SCDMA systems, it is characterized in that described P=128.
5. the linear combined channel estimation method in the TD-SCDMA according to claim 1 system is characterized in that described received signal x is expressed as
x＝Mh+n
Wherein
Figure A2007100377230003C1
Figure A2007100377230003C2
Be the channel impulse response of k sub-district,
Figure A2007100377230003C3
Be noise;
The least square solution of the estimation of channel impulse response is
h ^ = KM H ( MM H ) - 1 x
Wherein -1Expression is inverted.
6. according to the linear combined channel estimation method in claim 1 or the 3 described TD-SCDMA systems, it is characterized in that the described new matrix M that is used for estimating once more ' be a row non-singular matrix, the least square solution of channel impulse response estimation is h ^ ′ = K ( M ′ H M ′ ) - 1 M ′ H x .
7. the linear combined channel estimation method in the TD-SCDMA according to claim 6 system is characterized in that describedly adopting shortcut calculation in estimating once more: calculate M ' HIn M ' time, calculate M by the method for fast fourier transform HM therefrom extracts desired element then; Calculate (M ' HM ') -1The time, earlier with the partitioning of matrix, carry out Cholesky then and decompose; Calculate M ' HDuring x, calculate M by the method for fast fourier transform equally HX therefrom extracts desired element then.
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Cited By (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN101931450B (en) * 2009-06-19 2012-09-05 联芯科技有限公司 Method for selecting codebooks and device thereof
CN102739282A (en) * 2011-04-02 2012-10-17 联芯科技有限公司 Multi-antenna combined detection system of TD-SCDMA system and multi-antenna combined detection method thereof
CN111953380A (en) * 2020-07-02 2020-11-17 中国人民解放军战略支援部队信息工程大学 Non-periodic long code direct sequence spread spectrum signal time delay estimation method and system based on norm fitting

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CN1533191A (en) * 2003-03-21 2004-09-29 乐金电子(中国)研究开发中心有限公司 Adaptive channel evaluating method and device based on expected medium code of construction
EP1487165A1 (en) * 2003-06-14 2004-12-15 Lg Electronics Inc. TD-SCDMA channel estimation method and apparatus
CN1770650A (en) * 2004-10-15 2006-05-10 展讯通信（上海）有限公司 Maximum ratio combining of channel estimation for joint detection in TD-SCDMA systems

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Publication number Priority date Publication date Assignee Title
CN1533191A (en) * 2003-03-21 2004-09-29 乐金电子(中国)研究开发中心有限公司 Adaptive channel evaluating method and device based on expected medium code of construction
EP1487165A1 (en) * 2003-06-14 2004-12-15 Lg Electronics Inc. TD-SCDMA channel estimation method and apparatus
CN1770650A (en) * 2004-10-15 2006-05-10 展讯通信（上海）有限公司 Maximum ratio combining of channel estimation for joint detection in TD-SCDMA systems

Cited By (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN101931450B (en) * 2009-06-19 2012-09-05 联芯科技有限公司 Method for selecting codebooks and device thereof
CN102739282A (en) * 2011-04-02 2012-10-17 联芯科技有限公司 Multi-antenna combined detection system of TD-SCDMA system and multi-antenna combined detection method thereof
CN102739282B (en) * 2011-04-02 2015-02-04 联芯科技有限公司 Multi-antenna combined detection system of TD-SCDMA system and multi-antenna combined detection method thereof
CN111953380A (en) * 2020-07-02 2020-11-17 中国人民解放军战略支援部队信息工程大学 Non-periodic long code direct sequence spread spectrum signal time delay estimation method and system based on norm fitting

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