CN101184979B - Systems, methods, and apparatus for highband excitation generation - Google Patents

Systems, methods, and apparatus for highband excitation generation Download PDF

Info

Publication number
CN101184979B
CN101184979B CN2006800183519A CN200680018351A CN101184979B CN 101184979 B CN101184979 B CN 101184979B CN 2006800183519 A CN2006800183519 A CN 2006800183519A CN 200680018351 A CN200680018351 A CN 200680018351A CN 101184979 B CN101184979 B CN 101184979B
Authority
CN
China
Prior art keywords
signal
band
harmonic wave
band excitation
narrow
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Active
Application number
CN2006800183519A
Other languages
Chinese (zh)
Other versions
CN101184979A (en
Inventor
科恩·贝尔纳德·福斯
阿南塔帕德马纳卜汉·A·坎达达伊
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Qualcomm Inc
Original Assignee
Qualcomm Inc
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Qualcomm Inc filed Critical Qualcomm Inc
Priority claimed from PCT/US2006/012234 external-priority patent/WO2006130221A1/en
Publication of CN101184979A publication Critical patent/CN101184979A/en
Application granted granted Critical
Publication of CN101184979B publication Critical patent/CN101184979B/en
Active legal-status Critical Current
Anticipated expiration legal-status Critical

Links

Images

Landscapes

  • Compression, Expansion, Code Conversion, And Decoders (AREA)
  • Digital Transmission Methods That Use Modulated Carrier Waves (AREA)
  • Measurement And Recording Of Electrical Phenomena And Electrical Characteristics Of The Living Body (AREA)
  • Transmitters (AREA)
  • Analogue/Digital Conversion (AREA)

Abstract

In one embodiment, a method of generating a highband excitation signal includes harmonically extending the spectrum of a signal that is based on a lowband excitation signal; calculating a time-domain envelope of a signal that is based on the lowband excitation signal; and modulating a noise signal according to the time-domain envelope. The method also includes combining (A) a harmonically extended signal based on a result of the harmonically extending and (B) a modulated noise signal based on a result of the modulating. In this method, the highband excitation signal is based on a result of the combining.

Description

Be used for system, method and apparatus that high band excitation produces
The application's case is advocated the rights and interests of the 60/667th, No. 901 U.S. Provisional Patent Application case that is entitled as " CODING THE HIGH-FREQUENCYBAND OF WIDEBAND SPEECH " of application on April 1st, 2005.The application's case is also advocated the rights and interests of the 60/673rd, No. 965 U.S. Provisional Patent Application case that is entitled as " PARAMETER CODING IN A HIGH-BANDSPEECH CODER " of application on April 22nd, 2005.
Technical field
The present invention relates to signal Processing.
Background technology
The bandwidth Conventional cap of the voice communication on the PSTN (PSTN) is in the frequency range of 300-3400kHz.(for example the new network of cellular phone and ip voice (Internet Protocol, VoIP)) possibly not have identical bandwidth constraints, and possibly on this type of network, transmit and receive the voice communication that comprises the broadband frequency range to be used for voice communication.For instance, possibly need support to extend downwardly into 50Hz and/or until 7 or the audio frequency range of 8kHz.Also possibly need to support to have other application of the audio speech content in the scope beyond the traditional PSTN restriction, for example high quality audio or audio/video conference.
The scope that speech coder is supported can be improved sharpness to the extension of upper frequency.For instance, for example distinguishing, the fricative information spinner of " s " and " f " will be in high-frequency.High frequency band extends other quality that also can improve voice, for example has rate.For instance, in addition turbid vowel also can have the spectrum energy that is higher than PSTN restriction far away.
A kind of method of wideband speech coding relates to the convergent-divergent narrow-band speech coding technology technology of the scope of the 0-4kHz that is configured to encode (for example, through) with the covering wide band spectrum.For instance, voice signal can the higher rate sampling be in high-frequency component to comprise, and the narrow-band coding techniques is reconfigurable to use more filter factors to represent this broadband signal.Yet for example the narrow-band coding techniques calculated amount of CELP (code book Excited Linear Prediction) is bigger, and the broadband celp coder possibly consume too much cycle of treatment, to such an extent as to for many move with other Embedded Application for unrealistic.Using this technology that the entire spectrum of broadband signal is encoded to required quality also possibly cause bandwidth to increase greatly and make us and can't accept.Can be transferred in the system that only supports the narrow-band coding and/or before by said system decodes, need carry out code conversion through coded signal through narrow-band of coded signal part in addition, even at this said.
The another kind of method of wideband speech coding relates to from the high frequency band spectrum envelope of extrapolating through coding narrow-band spectrum envelope.Though this method can be implemented the rough spectrum envelope or the resonance peak structure of the highband part of the voice signal that can't from the spectrum envelope of narrow-band part, calculate to a nicety out usually not increasing bandwidth and do not need under the situation of code conversion.
Possibly need to implement wideband speech coding, make that can pass through narrow-band channel (for example, the PSTN channel) through the narrow-band part of coded signal at least sends, and do not carry out code conversion or other remarkable modification.Also possibly need the broadband code extension efficient, so that the user's that (for example) avoided possibly accepting to serve in the application of the broadcasting on for example wireless cellular telephony and wired and wireless channel number significantly reduces.
Summary of the invention
In one embodiment, a kind of method that produces high band excitation signal comprises: harmonic wave extends the frequency spectrum based on the signal of low band excitation signal; Calculating is based on the temporal envelope of the signal of said low band excitation signal; And come the zoop signal according to said temporal envelope.Said method also comprise result that combination (A) extends based on said harmonic wave through harmonic wave extend signal with (B) based on the result of said modulation through the zoop signal.In the method, said high band excitation signal is based on the result of said combination.
In another embodiment, a kind of equipment comprises: the frequency spectrum stretcher, and it extends through the harmonic wave that is configured to carry out based on the frequency spectrum of the signal of low band excitation signal; The envelope counter, it is through being configured to calculate the temporal envelope based on the signal of said low band excitation signal; First combiner, it is through being configured to carry out according to said temporal envelope the modulation of noise signal; And second combiner, its through the result that is configured to calculate (A) and extends based on said harmonic wave through harmonic wave extend signal with (B) based on the result's of said modulation summation through the zoop signal.Said high band excitation signal is based on the result of said summation.
In another embodiment, a kind of equipment comprises: be used for the device of harmonic wave extension based on the frequency spectrum of the signal of low band excitation signal; Be used to calculate device based on the temporal envelope of the signal of said low band excitation signal; Be used for coming the device of zoop signal according to said temporal envelope; And be used for result that combination (A) extends based on said harmonic wave through harmonic wave extend signal with (B) based on the result's of said modulation device through the zoop signal.In this equipment, said high band excitation signal is based on the result of said combination.
In another embodiment, a kind of method that produces high band excitation signal comprises: extend signal through nonlinear function being applied to calculate through harmonic wave from the low band excitation signal that the low frequency of voice signal partly derives; And extend signal and mix through the zoop signal through harmonic wave with the generation high band excitation signal with said.
Description of drawings
Fig. 1 a shows the calcspar according to the wideband speech coding device A100 of an embodiment.
Fig. 1 b shows the calcspar of the embodiment A102 of wideband speech coding device A100.
Fig. 2 a shows the calcspar according to the broadband Voice decoder B100 of an embodiment.
Fig. 2 b shows the calcspar of the embodiment B102 of wideband speech coding device B100.
Fig. 3 a shows the calcspar of the embodiment A112 of bank of filters A110.
Fig. 3 b shows the calcspar of the embodiment B122 of bank of filters B120.
The bandwidth of the low and high frequency band of the instance of Fig. 4 a displaying bank of filters A110 covers.
The bandwidth of the low and high frequency band of another instance of Fig. 4 b displaying bank of filters A110 covers.
Fig. 4 c shows the calcspar of the embodiment A114 of bank of filters A112.
Fig. 4 d shows the calcspar of the embodiment B124 of bank of filters B122.
The instance of the frequency of Fig. 5 a displaying voice signal and the curve of Logarithmic magnitude.
Fig. 5 b shows the calcspar of basic linear predictive coding system.
Fig. 6 shows the calcspar of the embodiment A122 of narrowband encoder A120.
Fig. 7 shows the calcspar of the embodiment B112 of narrow-band demoder B110.
Fig. 8 a shows the instance of curve of frequency and Logarithmic magnitude of the residual signal of turbid voice.
Fig. 8 b shows the instance of curve of time and Logarithmic magnitude of the residual signal of turbid voice.
Fig. 9 shows the calcspar also carry out long-term base of prediction linear predictive coding system.
Figure 10 shows the calcspar of the embodiment A202 of high band encoder A200.
Figure 11 shows the calcspar of the embodiment A302 of high band excitation generator A300.
Figure 12 shows the calcspar of the embodiment A402 of frequency spectrum stretcher A400.
Figure 12 a shows that frequency spectrum extends the curve of the signal spectrum at each point place in the instance of operating.
Figure 12 b shows that frequency spectrum extends the curve of the signal spectrum at each point place in another instance of operating.
Figure 13 shows the calcspar of the embodiment A304 of high band excitation generator A302.
Figure 14 shows the calcspar of the embodiment A306 of high band excitation generator A302.
Figure 15 shows the process flow diagram of envelope calculation task T100.
Figure 16 shows the calcspar of the embodiment 492 of combiner 490.
Figure 17 explains the method for the periodic index of calculating high-frequency band signals S30.
Figure 18 shows the calcspar of the embodiment A312 of high band excitation generator A302.
Figure 19 shows the calcspar of the embodiment A314 of high band excitation generator A302.
Figure 20 shows the calcspar of the embodiment A316 of high band excitation generator A302.
Figure 21 shows the process flow diagram of gain calculating task T200.
Figure 22 shows the process flow diagram of the embodiment T210 of gain calculating task T200.
Figure 23 a impression window graph of function.
Figure 23 b shows the subframe that will the window function shown in Figure 23 a be applied to voice signal.
Figure 24 shows the calcspar of the embodiment B202 of high band decoder B200.
Figure 25 shows the calcspar of the embodiment AD10 of wideband speech coding device A100.
Figure 26 a shows the synoptic diagram of the embodiment D122 of lag line D120.
Figure 26 b shows the synoptic diagram of the embodiment D124 of lag line D120.
Figure 27 shows the synoptic diagram of the embodiment D130 of lag line D120.
Figure 28 shows the calcspar of the embodiment AD12 of wideband speech coding device AD10.
Figure 29 shows the process flow diagram according to the signal processing method MD100 of an embodiment.
Figure 30 shows the process flow diagram according to the method M100 of an embodiment.
Figure 31 a shows the process flow diagram according to the method M200 of an embodiment.
The process flow diagram of the embodiment M210 of Figure 31 b methods of exhibiting M200.
Figure 32 shows the process flow diagram according to the method M300 of an embodiment.
In each figure and the description of enclosing, same reference numerals is represented identical or similar elements or signal.
Embodiment
Embodiment described herein comprises can bandwidth only increases by about 800 to 1000bps (bps) system, method and apparatus to support transmission and/or storage broadband voice signal through being configured to the narrow-band speech coder extension to be provided.The potential advantage of this type of embodiment comprise support with the compatibility of narrow band system embedded encoded, between narrow-band and high frequency band encoding channel, relatively easily distribute and reallocate, avoid the bigger broadband synthetic operation of calculated amount, and keep the low sampling rate of treating through the signal of the bigger waveform coding routine processing of calculated amount.
Only if receive context limited especially, otherwise this paper uses a technical term " calculating " represent any one of its its ordinary meaning, for example calculate, produce and from the tabulation of value, select.This is described in content and claims when using a technical term " comprising ", does not get rid of other element or operation.Use a technical term " A is based on B " represent any one of its its ordinary meaning to comprise following situation: (i) " A equals B " and (ii) " A is at least based on B ".Term " Internet Protocol " comprises edition 4 and the subsequent version of describing as among IETF (the Internet engineering work group) RFC (Request for Comment) 791 (for example, version 6).
Fig. 1 a shows the calcspar according to the wideband speech coding device A100 of an embodiment.Bank of filters A110 is through being configured to that broadband voice signal S10 is carried out filtering to produce narrow-band signal S20 and high-frequency band signals S30.Narrowband encoder A120 is through being configured to encode narrow-band signal S20 to produce narrow-band (NB) filter parameter S40 and narrow-band residual signal S50.Describe in further detail like this paper, narrowband encoder A120 is usually through being configured to as codebook index or taking another quantized versions and produce narrow band filter parameter S 40 and through coding narrow-band pumping signal S50.High band encoder A200 is through being configured to according to the information coding high-frequency band signals S30 in coding narrow-band pumping signal S50 to produce high frequency band coding parameter S60.Describe in further detail like this paper, high band encoder A200 is usually through being configured to as codebook index or taking another quantized versions and produce high frequency band coding parameter S60.The particular instance of wideband speech coding device A100 is through being configured to coding broadband voice signal S10 under the speed of about 8.55kbps (kbps); Wherein about 7.55kbps is used for narrow band filter parameter S 40 and warp coding narrow-band pumping signal S50, and about 1kbps is used for high frequency band coding parameter S60.
Possibly need and to be combined as single bit stream through coding narrow-band and high-frequency band signals.For instance, possibly need will be multiplexed together with as being used for transmission (for example, on wired, optics or wireless transmission channel) through coding broadband voice signal or being used for storage through coded signal.Fig. 1 b shows the calcspar of the embodiment A102 of wideband speech coding device A100; Wideband speech coding device A100 comprises multiplexer A130, and it is through being configured to narrow band filter parameter S 40, being combined as multiplex signal S70 through coding narrow-band pumping signal S50 and high band filter parameter S 60.
That a kind of equipment that comprises scrambler A102 also can comprise is for example wired through being configured to multiplex signal S70 is transferred to, the circuit in the transmission channel of optics or wireless channel.This equipment also can be through being configured to that signal is carried out one or more chnnel coding operations; For example error correction code (for example; The rate-compatible convolutional encoding) and/or error detection code (for example; And/or one or more layers procotol coding (for example, Ethernet, TCP/IP, cdma2000) cyclic redundancy code).
Possibly need multiplexer A130 through being configured to embed as separable multiplex signal S70 tributary through coding narrow-band signal (comprising narrow band filter parameter S 40 and warp coding narrow-band pumping signal S50); The another part (for example, high frequency band and/or low band signal) that makes warp coding narrow-band signal can be independent of multiplex signal S70 is resumed and decodes.For instance, multiplex signal S70 can make warp coding narrow-band signal to recover through divesting high band filter parameter S 60 through disposing.A potential advantage of this characteristic is to avoid need carrying out code conversion through the coding broadband signal to said before the system of decoding of highband part will being delivered to the decoding of supporting narrow-band signal but not supporting through the coding broadband signal.
Fig. 2 a shows the calcspar according to the broadband Voice decoder B100 of an embodiment.Narrow-band demoder B110 through be configured to decode narrow band filter parameter S 40 and through coding narrow-band pumping signal S50 to produce narrow-band signal S90.High band decoder B200 through be configured to based on through coding narrow-band pumping signal S50 according to the narrow-band pumping signal S80 high frequency band coding parameter S60 that decodes, to produce high-frequency band signals S100.In this example, narrow-band demoder B110 is through being configured to that narrow-band pumping signal S80 is provided to high band decoder B200.Bank of filters B120 is through being configured to narrow-band signal S90 and high-frequency band signals S100 combination to produce broadband voice signal S110.
Fig. 2 b is the calcspar of the embodiment B102 of broadband Voice decoder B100, and broadband Voice decoder B100 comprises demultiplexer B130, and it produces through coded signal S40, S50 and S60 through being configured to from multiplex signal S70.A kind of equipment that comprises demoder B102 can comprise through being configured to receive from the transmission channel of for example wired, optics or wireless channel the circuit of multiplex signal S70.This equipment also can be through being configured to that signal is carried out one or more channel-decoding operations; For example the error correction decoding (for example; The rate-compatible convolution decoder) and/or error-detecting decoding (for example; Cyclic redundancy is decoded), and/or one or more layers procotol decoding (for example, Ethernet, TCP/IP, cdma2000).
Bank of filters A110 is through being configured to according to division frequency band scheme input signal to be carried out filtering to produce low frequency sub-band and high-frequency sub-band.Look the design standards of application-specific and decide, the output sub-band can have the bandwidth that equates or does not wait and possible overlapping or not overlapping.The bank of filters A110 configuration that produces two above sub-bands also is possible.For instance, this bank of filters can be through being configured to produce one or more low band signal, and said low band signal comprises the component in the frequency range (the for example scope of 50-300Hz) below the frequency range that is in narrow-band signal S20.This bank of filters also maybe be through being configured to produce one or more extra high-frequency band signals, and said extra high-frequency band signals comprises the above interior component of frequency range (the for example scope of 14-20,16-20 or 16-32kHz) of frequency range that is in high-frequency band signals S30.In the case; Can implement wideband speech coding device A100 with this signal of independent coding (one or more); And multiplexer A130 can be through being configured to be included in (for example, as removable part) among the multiplex signal S70 with extra through coded signal (one or more).
Fig. 3 a shows the calcspar of the embodiment A112 of bank of filters A110, and bank of filters A110 is through being configured to produce two sub-band signal with the sampling rate that reduces.Bank of filters A110 is through being configured to receive the broadband voice signal S10 with high-frequency (or high frequency band) part and low frequency (or low-frequency band) part.Bank of filters A112 comprises low-frequency band processing path and the high frequency band processing path through being configured to receive broadband voice signal S10 and producing high frequency band voice signal S30 through being configured to receive broadband voice signal S10 and producing narrow-band voice signal S20.110 pairs of broadband voice signals of low-pass filter S10 carries out filtering with the low frequency sub-band through selecting, and 130 pairs of broadband voice signals of Hi-pass filter S10 carries out filtering with the high-frequency sub-band through selecting.Because the bandwidth ratio broadband voice signal S10 of two sub-band signal is narrow,, its sampling rate do not have information loss so can reducing to a certain extent.ST 120 (is for example selected factor according to required downwards; Sample through removing signal and/or replace sample with mean value) reduce the sampling rate of low-pass signal, and ST 140 likewise required is selected the sampling rate that factor reduces high communication number according to another downwards.
Fig. 3 b shows the calcspar of the corresponding embodiment B122 of bank of filters B120.Upwards ST 150 (for example, fill in and/or pass through reproduction copies through zero) increases the sampling rate of narrow-band signal S90, and 160 pairs of low-pass filters upwards sampled signal carry out filtering with only through low-frequency band part (for example, to prevent aliasing).Equally, upwards ST 170 increases the sampling rate of high-frequency band signals S100, and 180 pairs of Hi-pass filters upwards sampled signal carry out filtering only to pass through highband part.Then, two passband signals are sued for peace to form broadband voice signal S110.In some embodiments of demoder B100, bank of filters B120 is through being configured to produce according to one or more flexible strategy that received and/or calculated by high band decoder B200 the weighted sum of two passband signals.Also expect the bank of filters B120 of two above passband signal combination configuration.
Each be embodied as finite impulse response (FIR) (FIR) wave filter of wave filter 110,130,160,180 or be embodied as IIR (IIR) wave filter.Encoder filters 110 and 130 frequency response can have symmetry or the limited proportionality of dissimilar shape between stopband and the passband.Equally, demoder wave filter 160 and 180 frequency response can have symmetry or the limited proportionality of dissimilar shape between stopband and the passband.Possibly need (but not being that strictness is necessary) low-pass filter 110 and low-pass filter 160 to have same response, and Hi-pass filter 130 have same response with Hi-pass filter 180.In an example, two wave filters are to the 110,130 and 160, the 180th, quadrature mirror filter (QMF) group, its median filter to 110,130 and wave filter have same factor to 160,180.
In representative instance, low-pass filter 110 has the passband (for example, 0 to 4kHz frequency band) of the limited PSTN scope that comprises 300-3400Hz.The relative bandwidth of broadband voice signal S10, narrow-band signal S20 and high-frequency band signals S30 in two different embodiments of Fig. 4 a and 4b displaying.In these two particular instances, broadband voice signal S10 has the sampling rate (expression 0 is to the interior frequency component of 8kHz scope) of 16kHz, and narrow-band signal S20 has the sampling rate (frequency component that expression 0 is arrived in the 4kHz scope) of 8kHz.
In the instance of Fig. 4 a, do not exist obviously overlapping between two sub-frequency bands.High-frequency band signals S30 shown in this instance can obtain through the Hi-pass filter 130 that use has the passband of 4-8kHz.In the case, maybe be through being that factor sampling downwards is reduced to 8kHz through filtering signal with sampling rate with 2.Can expect that this operation can significantly reduce the computational complexity to the further processing operation of signal, this operation will move down into the passband energy does not have information loss in 0 to the 4kHz scope.
In the alternate example of Fig. 4 b, the upper and lower sub-band has obviously overlapping, makes two sub-band signal all describe 3.5 to 4kHz zone.High-frequency band signals S30 in this instance can obtain through the Hi-pass filter 130 that use has the passband of 3.5-7kHz.In the case, maybe be through being that factor sampling downwards is reduced to 7kHz through filtering signal with sampling rate with 16/7.Can expect that this operation can significantly reduce the computational complexity to the further processing operation of signal, this operation will move down into the passband energy does not have information loss in 0 to the 3.5kHz scope.
In the call type code communication handset, the obvious response on the frequency range of one or more transducers (that is, microphone and earphone or loudspeaker) shortage 7-8kHz.In the instance of Fig. 4 b, broadband voice signal S10 be in 7 and 8kHz between part be not included in coded signal.Other particular instance of Hi-pass filter 130 has the passband of 3.5-7.5kHz and 3.5-8kHz.
In some embodiments, as in the instance of Fig. 4 b, providing overlapping permission to use low pass and/or the Hi-pass filter that on the overlay region, has level and smooth decay between the sub-band.This type of wave filter with have sharply or the wave filter of " brickwall (brick-wall) " response is compared, be prone to design usually, not too complicated in the calculating, and/or the delay that causes is less.Wave filter with drastic shift district often has higher secondary lobe (this possibly cause aliasing) than the wave filter of the similar grade with level and smooth decay.Wave filter with drastic shift district also possibly have long impulse response, and this possibly cause the ring illusion.For bank of filters embodiment with one or more iir filters; Allow the level and smooth decay on the overlay region can make it possible to use limit away from the wave filter (one or more) of unit circle, this is for guaranteeing that stable fixed point embodiment maybe be more important.
The overlapping permission low-frequency band of sub-band is mixed with the level and smooth of high frequency band, and this can cause the less illusion of hearing, reduces aliasing, and/or make a frequency band not too obvious to the transformation of another frequency band.In addition, the code efficiency of narrowband encoder A120 (for example, wave coder) can increase along with frequency is continuous and descend.For instance, possibly under low bitrate, especially there is the coding quality that reduces narrowband encoder under the situation of ground unrest.Under this type of situation, provide sub-band the overlapping quality that improves the frequency component of duplicating in the overlay region.
In addition, the overlapping permission low-frequency band of sub-band is mixed with the level and smooth of high frequency band, and it possibly cause the less illusion of hearing, reduces aliasing, and/or make a frequency band not too obvious to the transformation of another frequency band.This characteristic possibly especially cater to the need according to the embodiment of different coding method operation for narrowband encoder A120 and high band encoder A200.For instance, the different coding technology can produce and sound very various signals.Scrambler with codebook index form coding spectrum envelope can produce the signal that has with the scrambler different audio that changes the coding amplitude spectrum into.Time domain coding device (for example, pulse-code modulated or PCM encoder) can produce the signal that has with Frequency Domain Coding device different audio.With the scrambler of the representation coded signal of spectrum envelope and corresponding residual signal can produce have with only with the signal of the scrambler different audio of spectrum envelope representation coded signal.Signal encoding for can producing, the scrambler of the representation of its waveform is had and output from the output different audio of sinusoidal coder.Under this type of situation, use wave filter to define in the broadband signal that non-overlapped sub-band possibly cause synthesizing the transformation between the sub-band more suddenly and sensuously more obvious with drastic shift district.
Have the QMF bank of filters of complementary overlapping frequency response although use usually in the sub-band technology, this type of wave filter is inappropriate at least some embodiments in the broadband coding embodiment described herein.The QMF bank of filters at scrambler place is through being configured to produce aliasing largely, in the said corresponding QMF bank of filters that is aliasing in the demoder place by cancellation.This configuration possibly be inappropriate for the application that signal causes a large amount of distortions between the bank of filters, because distortion can reduce the effectiveness of aliasing cancellation property.For instance, application described herein comprises the coding embodiment through being configured under low-down bit rate, operate.Because bit rate is very low, be rendered as obvious distortion so compare with original signal probably through decoded signal, make the use of QMF bank of filters can cause the aliasing of not cancellation.
In addition, scrambler can be through the composite signal that is configured to be similar to original signal on the sensigenous but in fact significantly is different from original signal.For instance, such as this paper the description scrambler of from narrow-band is residual, deriving high band excitation can produce this signal because in decoded signal, possibly not exist actual high frequency band residual fully.The distortion largely of in this type of is used, using the QMF bank of filters can cause the aliasing by not cancellation to cause.Use the application of QMF bank of filters to have high bit speed (for example, surpass 12kbps, and for G.722 surpassing 64kbps) usually for AMR.
If the affected children frequency band is narrower, can reduce the amount distortion that the QMF aliasing causes so, because the influence of aliasing is limited to the bandwidth that equates with the sub-band width.Yet, comprising the half the instance of pact of broadband bandwidth for wherein each sub-band described herein, the distortion that is caused by the aliasing of not cancellation possibly influence the major part of signal.The position influence of frequency band of the aliasing of not cancellation above also possibly receiving, quality of signals takes place.For instance, near the distortion that (for example, between 3 and 4 kHz) produce the broadband voice signal center maybe be much more harmful than near the distortion that (for example, more than the 6kHz) signal edge takes place.
Though the response of the wave filter of QMF bank of filters is strict relevant each other, the low-frequency band of bank of filters A110 and B120 and high frequency band path can be through being configured to have complete incoherent frequency spectrum except that two sub-frequency bands overlapping.We with the overlay defining of two sub-frequency bands be the frequency response of high band filter drop to-frequency response of the some tremendously low frequency band filter of 20dB drops to-distance of the point of 20dB.In the various instances of bank of filters A110 and/or B120, this overlapping scope arrives about 1kHz for about 200Hz.But about 400 to about 600Hz scope presentation code efficient and the desired trade-off between the perception smoothness.In the particular instance that preceding text are mentioned, overlap near the 500Hz.
Possibly need to implement bank of filters A112 and/or the next operation of in some stage execution graph 4a and 4b, explaining of B122.For instance, Fig. 4 c shows the calcspar of the embodiment A114 of bank of filters A112, inserts in embodiment A114 use is a series of, takes a sample, selects with other and operate high-pass filtering and the downward sampling operation of carrying out function equivalent.This type of embodiment can be prone to design and/maybe can allow to re-use the functional block of logic and/or code.For instance, can use the identical function piece carry out shown in Fig. 4 c to 14kHz select and to the operation of selecting of 7kHz.Can pass through signal and function e Jn πOr sequence (1) n multiplies each other and implements reversing spectrum operation, and the value of said sequence (1) n replaces between+1 and-1.The spectrum shaping operation can be embodied as through configuration so that thereby signal shaping obtains the low-pass filter of required overall filter response.
Notice, since the cause of reversing spectrum operation, the reversing spectrum of high-frequency band signals S30.The correspondingly subsequent operation in configuration codes device and the respective decoder.For instance, high band excitation generator A300 described herein can be through being configured to produce the high band excitation signal S120 that has the reversing spectrum form equally.
Fig. 4 d shows the calcspar of the embodiment B124 of bank of filters B122, insert in the bank of filters B122 uses-series, again sample circuit other operate the sample circuit high-pass filtering that makes progress of carrying out function equivalent and operate.Bank of filters B124 comprises the reversing spectrum operation in the high frequency band, and it makes and the middle similar operation counter-rotating of carrying out of the bank of filters (for example, bank of filters A114) of for example scrambler.In this particular instance, bank of filters B124 also comprises the notch filter in low-frequency band and the high frequency band, and it weakens the component of signal at 7100Hz place, but this type of wave filter be choose wantonly and need not comprise this type of wave filter.Together the attorney docket of application is that 050551 patent application case " SYSTEMS; METHODS; AND APPARATUS FOR SPEECH SIGNAL FILTERING " comprises about the additional description of the response of the element of the particular of bank of filters A110 and B120 and graphic therewith, and this material is incorporated at this by reference.
Narrowband encoder A120 implements according to source-filter model, and it is encoded to input speech signal (A) a group and describes the parameter of wave filter and (B) drive the pumping signal that described wave filter produces the synthetic duplicate of input speech signal.Fig. 5 a shows the instance of the spectrum envelope of voice signal.The peak value that shows the characteristic of this spectrum envelope is represented the resonance of voice range and is called resonance peak.Most of speech coders to this rough spectrum structured coding of major general is one group of parameter (for example a, filter coefficient).
Fig. 5 b shows the instance like the elementary sources-filter configuration of the coding of the spectrum envelope that is applied to narrow-band signal S20.Analysis module calculates one group of parameter describing corresponding to the wave filter of the speech sound in a period of time (common 20 milliseconds).Prewhitening filter (be also referred to as and analyze or prediction error filter) according to those filter parameter configurations is removed spectrum envelope signal is carried out the frequency spectrum leveling.The whitened signal of gained (being also referred to as residual) is compared with primary speech signal, has less energy and therefore change less and be easy to encode.Because the error that the residual signal coding is caused also possibly be dispersed on the frequency spectrum more equably.Filter parameter and residual common through quantizing to be used for effectively transmission on channel.At the demoder place, according to the composite filter of filter parameter configuration by based on residual signal excitation to produce the synthetic version of raw tone sound.Usually through being configured to have transfer function, said transfer function is the inverted versions of the transfer function of prewhitening filter to composite filter.
Fig. 6 shows the calcspar of the basic embodiment A122 of narrowband encoder A120.In this example, linear predictive coding (LPC) analysis module 210 spectrum envelopes with narrow-band signal S20 are encoded to one group of linear prediction (LP) coefficient (for example, the coefficient 1/A (z) of full utmost point wave filter).Analysis module is treated to a series of non-overlapped frames with input signal usually, wherein calculates one group of new coefficient for each frame.Frame period normally can expect the cycle that signal is static in this locality; A common instance is 20 milliseconds (being equivalent to following 160 samples of sampling rate of 8kHz).In an example, lpc analysis module 210 is through being configured to calculate one group of 10 LP filter coefficient to describe the resonance peak structure of each 20 milliseconds of frame.Also possibly implement analysis module input signal is treated to a series of overlapping frame.
Analysis module can perhaps can at first carry out weighting according to window function (for example, Hamming window) to sample through being configured to directly analyze the sample of each frame.Also can go up execution analysis at window (for example, 30 milliseconds of windows) greater than frame.This window can symmetry (5-20-5 for example makes it comprise and then before 20 milliseconds of frames and afterwards 5 milliseconds) or asymmetric (10-20 for example makes it comprise last 10 milliseconds of previous frame).The lpc analysis module is usually through being configured to use Levinson-Durbin recursion or Leroux-Gueguen algorithm computation LP filter coefficient.In another embodiment, analysis module can be through being configured to calculate one group of cepstrum coefficient rather than one group of LP filter coefficient of each frame.
The output speed of scrambler A120 can significantly reduce through quantification filtering device coefficient, and less relatively to the influence of reproduction quality.Coefficient of linear prediction wave filter is difficult to effective quantification, and is mapped as another representation usually, and for example line spectrum pair (LSP) or line spectral frequencies (LSF) quantize and/or entropy coding being used for.In the instance of Fig. 6, LP filter coefficient-LSF conversion 220 is transformed to one group of corresponding LSF with said group of LP filter coefficient.Other of LP filter coefficient representation one to one comprises partial autocorrelation coefficient, log area ratio value, adpedance and composes (ISP) and adpedance spectral frequency (ISF), and it is used for GSM (global system for mobile communications) AMR-WB (the how fast broadband of self-adaptation) coder.Usually, the conversion between one group of LP filter coefficient and the one group of corresponding LSF is reversible, but embodiment also comprises can not be under the error free situation reversible scrambler A120 embodiment of conversion.
Quantizer 230 is through being configured to quantize said group of narrow-band LSF (or other coefficient representation), and narrowband encoder A122 through the result that is configured to export this quantification as narrow band filter parameter S 40.This quantizer comprises vector quantizer usually, and it is encoded to the index for the corresponding vectorial clauses and subclauses in table or the code book with input vector.
As shown in Figure 6, narrowband encoder A122 is also through making narrow-band signal S20 produce residual signal through the prewhitening filter 260 (be also referred to as and analyze or prediction error filter) according to said group of filter coefficient configuration.In this particular instance, prewhitening filter 260 is embodied as the FIR wave filter, but also can use the IIR embodiment.This residual signal will contain the sensuously more important speech frame information of not representing in the narrow band filter parameter S 40, for example relevant with tone long-term structure usually.Quantizer 270 is through being configured to calculate the narrow-band pumping signal S50 output of quantization means form to encode as warp of this residual signal.This quantizer comprises vector quantizer usually, and it is encoded to the index for the corresponding vectorial clauses and subclauses in table or the code book with input vector.Perhaps, this quantizer can dynamically produce vector at the demoder place, rather than as in the sparse code book method, from memory storage, retrieve vector through being configured to send one or more parameters from said parameter.The method is used for the encoding scheme of algebraically CELP (code book Excited Linear Prediction) for example and the coder of for example 3GPP2 (third generation partnership relation 2) EVRC (strengthening the variable bit rate coder).
Need narrowband encoder A120 to produce through coding narrow-band pumping signal according to the same filter parameter value that will can be used for corresponding narrow-band demoder.In this way, the warp coding narrow-band pumping signal of gained possibly considered the undesirable property of those parameter values, for example quantization error to a certain extent.Therefore, need to use and to dispose prewhitening filter by available same tie numerical value at the demoder place.In the basic instance of scrambler A122 as shown in Figure 6; 240 pairs of narrow-band coding parameters of quantizer S40 de-quantization; The conversion 250 of LSF-LP filter coefficient is shone upon back one group of corresponding LP filter coefficient with income value, and this group coefficient is used to dispose prewhitening filter 260 to produce the residual signal that is quantized by quantizer 270.
Some embodiments of narrowband encoder A120 are calculated through coding narrow-band pumping signal S50 through a vector that from one group of code book vector, identifies with the residual signal optimum matching through being configured to.Yet, notice that narrowband encoder A120 also can be through implementing in fact not produce residual signal with the quantization means form of calculating residual signal.For instance; Narrowband encoder A120 can be through being configured to use many code book vectors (for example to produce corresponding composite signal; According to one group of current filter parameter), and vectorial in selection and the perceptual weighting territory with the code book of the institute's signal correction that produces couplet of original narrow-band signal S20 optimum matching.
Fig. 7 shows the calcspar of the embodiment B112 of narrow-band demoder B110.310 pairs of narrow band filter parameter S 40 de-quantizations of quantizer (in the case; De-quantization is one group of LSF); And the conversion 320 of LSF-LP filter coefficient is transformed to one group of filter coefficient (for example, like the quantizer 240 and conversion 250 descriptions of preceding text with reference to narrowband encoder A122) with LSF.340 pairs of narrow-band residual signals of quantizer S40 de-quantization is to produce narrow-band pumping signal S80.Based on filter coefficient and narrow-band pumping signal S80, narrow-band composite filter 330 synthesis of narrow band signal S90.In other words, narrow-band composite filter 330 is through being configured to according to the de-quantization filter coefficient narrow-band pumping signal S80 to be carried out spectrum shaping, to produce narrow-band signal S90.Narrow-band demoder B112 also is provided to high band encoder A200 with narrow-band pumping signal S80, and high band encoder A200 uses narrow-band pumping signal S80 to derive high band excitation signal S120, such as this paper description.In some embodiments of describing hereinafter, narrow-band demoder B110 can be through being configured to that the extraneous information relevant with narrow-band signal (for example, spectral tilt, pitch gain and hysteresis, and speech pattern) is provided to high band decoder B200.
The system of narrowband encoder A122 and narrow-band demoder B112 is the basic instance of synthesis analysis speech coder and decoder device.Code book Excited Linear Prediction (CELP) coding is the general series of of synthesis analysis coding; And the embodiment of this type of scrambler can be carried out residual waveform coding, wherein comprises for example selector bar purpose operation from fixing and self-adaptation code book, error minimize operation and/or perceptual weighting operation.Other embodiment of synthesis analysis coding comprises MELP (MELP), algebraically CELP (ACELP), lax CELP (RCELP), Regular-Pulse Excitation (RPE), multiple-pulse CELP (MPE) and vector sum Excited Linear Prediction (VSELP) coding.The correlative coding method comprises multi-band excitation (MBE) and prototype waveform interpolation (PWI) coding.The instance of standard synthesis analysis speech coder and decoder device comprises ETSI (ETSI) the GSM full rate coder (GSM06.10) that uses residual excited linear predictive (RELP), GSM EFR coder (ETSI-GSM 06.60), ITU (International Telecommunications Union (ITU)) standard the 11.8kb/s G.729 IS of Annex E scrambler, IS-136 (interim standard) 641 coders (time division multiple access (TDMA) scheme), GSM AMR (GSM-AMR) coder, and 4GV TM(the 4th generation Vocoder TM) coder (Qualcomm of California diego, california (QUALCOMM Incorporated, San Diego, CA)).Narrowband encoder A120 and corresponding demoder B110 can implement according to any one or any other speech coding technology in these technology (known or leaved for development), and said speech coding technology is expressed as voice signal (A) a group and describes the parameter of wave filter and the pumping signal that (B) is used to drive described wave filter reproduction speech signal.
Even prewhitening filter is removed rough spectrum envelope from narrow-band signal S20 after, also possibly keep quite a large amount of meticulous harmonic structure (especially for turbid voice).The spectrum curve of an instance of the residual signal (as producing) of Fig. 8 a displaying voiced sound signal (for example, vowel) by prewhitening filter.Periodic structure visible in this instance is relevant with tone, and the different voiced sounds that send of same speaker possibly have different resonance peak structure but have similar tone structure.Fig. 8 b shows the time-domain curve of the instance of this residual signal, and it shows the time series of tone pulses.
Can increase code efficiency and/or voice quality through the characteristic of using one or more parameter value coding tone structures.The frequency (being also referred to as fundamental frequency) that a key property of tone structure is a first harmonic, it arrives in the 400Hz scope 60 usually.This characteristic is encoded to the inverted versions of fundamental frequency usually, is also referred to as pitch lag (pitch lag).The number of sample in pitch period of pitch lag indication, and may be encoded as one or more codebook index.Voice signal from male speaker often recently has bigger pitch lag from women speaker's voice signal.
Another characteristics of signals relevant with the tone structure is periodically, the intensity of its indication harmonic structure, or in other words, signal is harmonic wave or non-harmonic degree.Periodic two typical designators are zero crossing and normalized autocorrelation function (NACF).Periodically also can be indicated by pitch gain, said pitch gain is encoded to code book gain (for example, quantizing the gain of self-adaptation code book) usually.
Narrowband encoder A120 can comprise one or more modules through the long-term harmonic structure of the narrow-band signal S20 that is configured to encode.As shown in Figure 9, a spendable typical CELP example comprises open loop lpc analysis module, and its coding short-term characteristic or rough spectrum envelope are the closed type loop long-term forecasting analysis phase afterwards, said stage coding fine pitch or harmonic structure.Short-term characteristic is encoded to filter coefficient, and long-time quality is encoded to the for example value of the parameter of pitch lag and pitch gain.For instance, narrowband encoder A120 can be through configuration so that to comprise the form output warp coding narrow-band pumping signal S50 of one or more codebook index (for example, this index of fixed password and self-adaptation codebook index) and corresponding yield value.The calculating of this quantization means form of narrow-band residual signal (for example, through quantizer 270) can comprise to be selected these index and calculates these values.Epenthesis was transferred the prototype waveform in the coding of tone structure also can comprise, and said operation can comprise calculates poor between the continuous tone pulse.Can be to the modeling of forbidding long-term structure corresponding to the frame of clear voice (it is similar to noise and not systematization usually).
Embodiment according to the narrow-band demoder B110 of example shown in Figure 9 can be through being configured to after long-term structure (tone or harmonic structure) has been recovered, narrow-band pumping signal S80 to be outputed to high band decoder B200.For instance, this demoder can be through being configured to export narrow-band pumping signal S80 as the de-quantization version through coding narrow-band pumping signal S50.Certainly, also possibly implement narrow-band demoder B110, make high band decoder B200 carry out de-quantization through coding narrow-band pumping signal S50 to obtain narrow-band pumping signal S80.
In the embodiment according to the wideband speech coding device A100 of example shown in Figure 9, high band encoder A200 can be through being configured to receive the narrow-band pumping signal that is produced by short run analysis or prewhitening filter.In other words, narrowband encoder A120 can be through being configured to before the long-term structure of coding, the narrow-band pumping signal to be outputed to high band encoder A200.Yet high band encoder A200 need receive from narrow-band channel will be by the same-code information of high band decoder B200 reception, and the coding parameter that makes high band encoder A200 produce possibly considered the undesirable property of said information to a certain extent.Therefore, maybe be preferably, high band encoder A200 is from treating through coding narrow-band pumping signal S50, to rebuild narrow-band pumping signal S80 by the identical parametersization and/or the quantification of wideband speech coding device A100 output.A potential advantage of the method is to calculate the high frequency band gain factor S60b that hereinafter is described more exactly.
Except the parameter of the short-term of describing narrow-band signal S20 and/or long-term structure, narrowband encoder A120 also can produce the parameter value relevant with other characteristic of narrow-band signal S20.These values (it possibly quantize to be exported by wideband speech coding device A100 through suitable) can be included in the narrow band filter parameter S 40 or output separately.High band encoder A200 also can be through being configured to calculate high frequency band coding parameter S60 according to one or more (for example, after the de-quantization) in these additional parameter.At broadband Voice decoder B100 place, high band decoder B200 can be through being configured to receive parameter value via narrow-band demoder B110 (for example, after the de-quantization).Perhaps, high band decoder B200 can be through being configured to direct reception (and possibly be used for de-quantization) parameter value.
In an instance of additional narrow frequencyband coding parameter, narrowband encoder A120 produces the spectral tilt of each frame and the value of speech pattern parameter.The shape of spectrum envelope is relevant on spectral tilt and the passband, and representes by quantizing first reflection coefficient usually.For most of voiced sounds, spectrum energy reduces along with the continuous increase of frequency, makes the reflection coefficient of winning for negative and can approaching-1.Most of voicelesss sound have smooth frequency spectrum, thereby make the reflection coefficient of winning near zero, perhaps under high-frequency, have more energy, thereby make the reflection coefficient of winning for just and can approaching+1.
Speech pattern (being also referred to as the sounding pattern) indication present frame representes that turbid voice still are clear voice.This parameter can have binary value, and it is based on the voice activity (for example, the relation between this index and the threshold value) of periodic one or more indexs (for example, zero crossing, NACF, pitch gain) and/or frame.In other embodiments, the speech pattern parameter has one or more other states to indicate the pattern of the transformation between for example noiseless or ground unrest or the noiseless and turbid voice.
High band encoder A200 is through being configured to according to source-filter model high-frequency band signals S30 that encodes, and wherein the excitation of this wave filter is based on through coding narrow-band pumping signal.Figure 10 shows the calcspar of the embodiment A202 of high band encoder A200, and high band encoder A200 is through being configured to produce the high frequency band coding parameter S60 stream that comprises high band filter parameter S 60a and high frequency band gain factor S60b.High band excitation generator A300 is from deriving high band excitation signal S120 through coding narrow-band pumping signal S50.Analysis module A210 produces one group of parameter value of the spectrum envelope of describing high-frequency band signals S30.In this particular instance, analysis module A210 produces one group of LP filter coefficient through being configured to carry out lpc analysis so that for each frame of high-frequency band signals S30.Coefficient of linear prediction wave filter-LSF conversion 410 is transformed to one group of corresponding LSF with said group of LP filter coefficient.Said with reference to analysis module 210 and conversion 220 like preceding text, analysis module A210 and/or conversion 410 can be through being configured to use other coefficient sets (for example, cepstrum coefficient) and/or the coefficient representation (for example, ISP).
Quantizer 420 is through being configured to quantize said group of high frequency band LSF (or other coefficient representation, for example ISP), and high band encoder A202 through the result that is configured to export this quantification as high band filter parameter S 60a.This quantizer comprises vector quantizer usually, and it is encoded to the index for the corresponding vectorial clauses and subclauses in table or the code book with input vector.
High band encoder A202 also comprises composite filter A220, and it is through being configured to produce synthetic high-frequency band signals S130 according to the high band excitation signal S120 of analysis module A210 generation with through code frequency spectrum envelope (for example, said group of LP filter coefficient).Composite filter A220 is embodied as iir filter usually, but also can use the FIR embodiment.In particular instance, composite filter A220 is embodied as sextic property autoregressive filter.
It is poor that high frequency band gain factor counter A230 calculates between the level of original high-frequency band signals S30 and synthetic high-frequency band signals S130 one or more, with the gain envelope of designated frame.Quantizer 430 can be embodied as input vector is encoded to the vector quantizer for the index of the corresponding vectorial clauses and subclauses in table or the code book; It quantize to specify the value (one or more) of gain envelope, and high band encoder A202 through the result that is configured to export this quantification as high frequency band gain factor S60b.
In embodiment shown in figure 10, composite filter A220 is through being configured to from analysis module A210 receiving filter coefficient.The alternate embodiment of high band encoder A202 comprises quantizer and inverse transform; It is through being configured to decoding filter coefficient from high band filter parameter S 60a, and in the case composite filter A220 through being configured to change reception into through the decoding filter coefficient.This alternative arrangements can be supported the calculated gains envelope more exactly by high frequency band gain calculator A230.
In a particular instance, the respectively every frame output hexad LSF of analysis module A210 and high frequency band gain calculator A230 and one group of five yield value, the feasible broadband extension that can only realize narrow-band signal S20 with 11 bonus values of every frame.Ear is often more insensitive for the frequency error under the high-frequency, thereby the high frequency band of low LPC level coding can produce the signal with the perceived quality that can compare with the narrow-band coding of higher LPC level.The typical embodiments of high band encoder A200 can be rebuild through being configured to 8 to 12 high-quality that are used for spectrum envelope of every frame output, and every frame is exported other 8 to 12 high-quality reconstructions that are used for temporal envelope.In another particular instance, the every frame of analysis module A210 is exported one group of eight LSF.
Some embodiments of high band encoder A200 are through being configured to produce high band excitation signal S120 in the following manner: produce the random noise signal with high-band frequency component, and according to the temporal envelope of narrow-band signal S20, narrow-band pumping signal S80 or high-frequency band signals S30 noise signal is carried out which amplitude modulation.Though this method based on noise can produce suitable result for voiceless sound, yet it maybe be undesirable for voiced sound, and the residual of voiced sound is generally harmonic wave and therefore has certain periodic structure.
High band excitation generator A300 produces high band excitation signal S120 through being configured to extend to through the frequency spectrum with narrow-band pumping signal S80 in the high-band frequency range.Figure 11 shows the calcspar of the embodiment A302 of high band excitation generator A300.Quantizer 450 through be configured to de-quantization through coding narrow-band pumping signal S50 to produce narrow-band pumping signal S80.Frequency spectrum stretcher A400 extends signal S160 through being configured to produce harmonic wave based on narrow-band pumping signal S80.The temporal envelope combination that combiner 470 calculates through the random noise signal that is configured to noise generator 480 is produced and envelope counter 460 with generation through zoop signal S170.Combiner 490 extends harmonic wave signal S60 and mixes through zoop signal S170 to produce high band excitation signal S120 through being configured to.
In an example, frequency spectrum stretcher A400 extends signal S160 through being configured to that narrow-band pumping signal S80 is carried out spectrum folding operation (being also referred to as mirror) to produce harmonic wave.Spectrum folding can be filled in pumping signal S80 execution and then use Hi-pass filter and keep false signal by zero.In another example, frequency spectrum stretcher A400 is through being configured to produce harmonic wave extension signal S160 through narrow-band pumping signal S80 frequency spectrum being translated to (for example, via upwards sampling, multiply each other with the constant frequency cosine signal afterwards) in the high frequency band.
Spectrum folding and translation method can produce harmonic structure and on phase place and/or frequency, extend signal with the discontinuous frequency spectrum of the original harmonic structure of narrow-band pumping signal S80.For instance, these class methods can produce the signal of the peak value with the multiple place that is not positioned at fundamental frequency usually, and this possibly cause the illusion of microphonia in the voice signal of rebuilding.These methods produce toward contact has the unnatural high-frequency harmonic wave of transferring characteristic than forte.Yet; Bandwidth is restricted to and is not more than 3400Hz because the PSTN signal can be taken a sample under 8kHz; So the top frequency spectrum of narrow-band pumping signal S80 possibly contain seldom or not contain energy, make that translating the extension signal that operation produces according to spectrum folding or frequency spectrum can have the spectral hole more than the 3400Hz.
Produce other method that harmonic wave extends signal S160 and comprise one or more fundamental frequencies of identification narrow-band pumping signal S80 and homophonic according to said information generating.For instance, the harmonic structure of pumping signal can be described with amplitude and phase information by fundamental frequency.Another embodiment of high band excitation generator A300 produces harmonic wave extension signal S160 based on fundamental frequency and amplitude (for example, as being indicated by pitch lag and pitch gain).Yet it is relevant on phase place to remove anharmonic wave extension signal and narrow-band pumping signal S80, otherwise the quality through decoded speech of gained maybe be unacceptable.
Can use nonlinear function produce with the narrow-band excitation phase on mutually dry doubling keep harmonic structure and do not have the high band excitation signal of phase discontinuity.Nonlinear function also can provide the noise level of the increase between the high-frequency harmonic wave, and it often sounds more natural than the tone high-frequency harmonic wave that the method for translating through for example spectrum folding and frequency spectrum produces.Can comprise ABS function (being also referred to as full-wave rectification), half-wave rectification, square, cube and slicing by the typical memoryless nonlinear function that the various embodiments of frequency spectrum stretcher A400 are used.Other embodiment of frequency spectrum stretcher A400 can be through being configured to use the nonlinear function with memory.
Figure 12 is the calcspar of the embodiment A402 of frequency spectrum stretcher A400, and frequency spectrum stretcher A400 is through being configured to use the frequency spectrum that nonlinear function extends narrow-band pumping signal S80.Upwards ST 510 is through being configured to the sampling that makes progress to narrow-band pumping signal S80.Possibly carry out fully upwards sampling so that the aliasing when using nonlinear function minimizes to signal.In a particular instance, upwards ST 510 is a factor to the signal sampling that makes progress with 8.Upwards ST 510 can be filled in and the result is carried out LPF carry out upwards sampling operation through input signal being carried out zero through being configured to.Nonlinear function counter 520 is applied to nonlinear function through sampled signal upwards through being configured to.Extend (for example, square) for frequency spectrum, ABS function is not need energy scaleization with respect to a potential advantage of other nonlinear function.In some embodiments, can come to use effectively ABS function through the sign bit of peeling off or remove each sample.Nonlinear function counter 520 also can be through being configured to carry out the amplitude deviation of extending signal through make progress sampling or frequency spectrum.
ST 530 is taken a sample downwards through being configured to that the frequency spectrum of using nonlinear function is extended the result downwards.Downwards ST 530 possibly need to carry out the bandpass filtering operation to select frequency spectrum to extend the required frequency band of signal before reducing sampling rate (for example, so that reduce or avoid because aliasing or the error that unnecessary image causes).ST 530 possibly also need reduce sampling rate an above stage downwards.
Figure 12 a shows that frequency spectrum extends the figure of the signal spectrum at each point place in the instance of operating, and wherein frequency scaling is identical on each curve.Curve (a) is showed the frequency spectrum of the instance of narrow-band pumping signal S80.Curve (b) shows that signal S80 is a upwards sampling frequency spectrum afterwards of factor with 8.Curve (c) is showed the instance of using nonlinear function extension frequency spectrum afterwards.Curve (d) is showed the frequency spectrum after the LPF.In this example, passband extends to the upper frequency limit (for example, 7kHz or 8kHz) of high-frequency band signals S30.
Curve (e) is showed the phase one frequency spectrum afterwards of sampling downwards, and wherein making sampling rate is that factor reduces to obtain broadband signal with 4.Curve (f) displaying carrying out high-pass filtering operation is with the frequency spectrum after the highband part of selecting the extension signal, and the subordinate phase frequency spectrum afterwards of curve (g) displaying sampling downwards, and wherein making sampling rate is that factor reduces with 2.In a particular instance; ST 530 passes through the Hi-pass filter 130 of bank of filters A112 (or other structure or routine with same response) and the subordinate phase that downward ST 140 is carried out high-pass filtering and downward sampling, the frequency spectrum extension signal that has frequency range and the sampling rate of high-frequency band signals S30 with generation through making broadband signal downwards.
As visible in the curve (g), the downward sampling of the high communication number shown in the curve (f) impels its reversing spectrum.In this example, ST 530 is also operated through being configured to that signal is carried out spectrum inversion downwards.Curve (h) is showed the result who uses the spectrum inversion operation, and said spectrum inversion operation can be passed through signal and function e Jn πOr sequence (1) nMultiply each other and carry out, said sequence (1) nValue between+1 and-1 alternately.This operation is equivalent in frequency domain the digital spectrum translocation distance π with signal.Notice, also can operate and obtain identical result through use downward sample circuit spectrum inversion with different order.Upwards the operation of sampling and/or sampling downwards also can (for example, 7kHz) frequency spectrum extends signal through being configured to comprise the sampling rate that sampling again obtains to have high-frequency band signals S30.
Notice like preceding text; Bank of filters A110 and B120 can be through implementing to make one among narrow-band and high-frequency band signals S20, the S30 or both to have the reversing spectrum form in output place of bank of filters A110; Be encoded and decode with the reversing spectrum form, and in broadband voice signal S110 before the output at bank of filters B120 place reversing spectrum once more.Certainly, in the case, with need the spectrum inversion shown in Figure 12 a not operating, because high band excitation signal S120 will also need have the reversing spectrum form.
Each task of the upwards sample circuit sampling downwards that the frequency spectrum extension that frequency spectrum stretcher A402 carries out is operated can dispose and arrangement by many different modes.For instance, Figure 12 b shows that frequency spectrum extends the figure of the signal spectrum at each point place in another instance of operating, and wherein frequency scaling is identical on each curve.Curve (a) is showed the frequency spectrum of the instance of narrow-band pumping signal S80.Curve (b) shows that signal S80 is a upwards sampling frequency spectrum afterwards of factor with 2.Curve (c) is showed the instance of using nonlinear function extension frequency spectrum afterwards.In the case, accept contingent aliasing in the upper frequency.
Curve (d) is showed the frequency spectrum after the reversing spectrum operation.Curve (e) is showed the frequency spectrum afterwards of single stage of sampling downwards, and wherein making sampling rate is that factor reduces to extend signal to obtain required frequency spectrum with 2.In this example, said signal is taked the reversing spectrum form, and can be used for handling in the embodiment of high band encoder A200 of the high-frequency band signals S30 that takes this form.
The frequency spectrum that nonlinear function counter 520 produces extends signal, and amplitude obviously reduces along with the frequency increase probably.Frequency spectrum stretcher A402 comprises frequency spectrum tenderizer 540, and it is through being configured to operating through the albefaction of sampled signal execution downwards.Frequency spectrum tenderizer 540 can be through being configured to carry out fixedly albefaction operation or carrying out the adaptive whitening operation.In the particular instance of adaptive whitening, frequency spectrum tenderizer 540 comprises: the lpc analysis module, and it is through being configured to according to calculating one group of four filter coefficient through downward sampled signal; And four analysis filters, it is through being configured to according to those coefficients signal to be carried out albefaction.Other embodiment of frequency spectrum stretcher A400 comprises frequency spectrum tenderizer 540 configuration to frequency spectrum extension signal operation before downward ST 530.
Can implement high band excitation generator A300 and extend signal S160 as high band excitation signal S120 with output harmonic wave.Yet, in some cases, only use harmonic wave extension signal possibly cause the illusion that can hear as high band excitation.The harmonic structure of voice is not so good as in the low-frequency band obvious in high frequency band usually, and in high band excitation signal, uses too much harmonic structure possibly cause buzz.This illusion maybe be especially obvious in from women speaker's voice signal.
Embodiment comprises through being configured to harmonic wave is extended the embodiment of the high band excitation generator A300 that signal S160 mixes with noise signal.Shown in figure 11, high band excitation generator A302 comprises noise generator 480, and it is through being configured to produce random noise signal.In an example, noise generator 480 is through being configured to produce unit variance white pseudo-random noise signal, but in other embodiments, noise signal not need for white and can have power density along with change of frequency.Noise generator 480 maybe through be configured to the output noise signal as the determinacy function so that can duplicate its state at the demoder place.For instance, noise generator 480 can be through being configured to the output noise signal conduct determinacy function of information encoded (for example, narrow band filter parameter S 40 and/or warp coding narrow-band pumping signal S50) in same number of frames previously.
Extending before signal S160 mixes with harmonic wave, the random noise signal that noise generator 480 produces can be through the temporal envelope of which amplitude modulation with energy distribution in time with approximate narrow-band signal S20, high-frequency band signals S30, narrow-band pumping signal S80 or harmonic wave extension signal S160.Shown in figure 11, high band excitation generator A302 comprises combiner 470, and it carries out which amplitude modulation through the temporal envelope that is configured to calculate according to envelope counter 460 to the noise signal that noise generator 480 produces.For instance, combiner 470 can be embodied as multiplier, its through be provided with come convergent-divergent noise generator 480 with the temporal envelope that calculates according to envelope counter 460 output to produce through zoop signal S170.
Shown in the calcspar of Figure 13, in the embodiment A304 of high band excitation generator A302, envelope counter 460 is through being provided with to calculate the envelope that harmonic wave extends signal S160.Shown in the calcspar of Figure 14, in the embodiment A306 of high band excitation generator A302, envelope counter 460 is through being provided with to calculate the envelope of narrow-band pumping signal S80.The other embodiment of high band excitation generator A302 can otherwise be configured in time to extend signal S160 to harmonic wave according to the position of narrow-band tone pulses and add noise.
Envelope counter 460 can comprise the task of a series of subtasks and carry out envelope and calculate as one through being configured to.Figure 15 shows the process flow diagram of the instance T100 of this task.Subtask T110 calculate envelope treat the signal of modeling (for example, narrow-band pumping signal S80 or harmonic wave extend signal S160) frame each sample square to produce the square value sequence.Subtask T120 carries out smooth operation to the square value sequence.In an example, subtask T120 uses an IIR low-pass filter according to following expression formula to sequence:
y(n)＝ax(n)+(1-a)y(n-1)， (1)
Wherein x is the wave filter input, and y is wave filter output, Domain Index when n is, and a is the smoothing factor with the value between 0.5 and 1.The value of smoothing factor a can be fixing, perhaps in alternate embodiment, can be according to the indication of noise in the input signal and self-adaptation, and make under muting situation a near 1, and exist under the situation of noise near 0.5.Subtask T130 is applied to through each sample of level and smooth sequence square root function to produce temporal envelope.
This embodiment of envelope counter 460 can be through being configured to according to execute the task each subtasks of T100 of serial and/or parallel mode.In the other embodiment of task T100, can the logical operation of band before the T110 of subtask, it is through the required frequency part of the signal that is configured to select envelope to treat modeling, for example 3-4kHz scope.
Combiner 490 extends harmonic wave signal S160 and mixes through zoop signal S170 to produce high band excitation signal S120 through being configured to.The embodiment of combiner 490 can through configuration (for example) with high band excitation signal S120 is calculated as harmonic wave extend signal S160 with through zoop signal S170 with.This embodiment of combiner 490 can be through being configured to through before summation, extending signal S160 and/or to using weighting factor through zoop signal S170 to harmonic wave, and high band excitation signal S120 is calculated as weighted sum.Can calculate each this type of weighting factor according to one or more standards, and said weighting factor can be fixed value, perhaps by frame or by the adaptation value that calculates on the sub-frame basis.
Figure 16 shows the calcspar of the embodiment 492 of combiner 490, and said embodiment 492 is extended signal S160 and weighted sum through zoop signal S170 through being configured to that high band excitation signal S120 is calculated as harmonic wave.Combiner 492 is through being configured to extend signal S160 according to harmonic wave weighting factor S180 weighting harmonic wave, and through zoop signal S170, and output high band excitation signal S120 is as by the summation of weighted signal according to noise weighting factor S190 weighting.In this example, combiner 492 comprises weighting factor counter 550, and it is through being configured to calculate harmonic wave weighting factor S180 and noise weighting factor S190.
Weighting factor counter 550 can be in being configured to according to high band excitation signal S120 the required ratio of harmonic content and noise content calculate weighting factor S180 and S190.For instance, combiner 492 possibly need produce high band excitation signal S120 with have with the harmonic energy of high-frequency band signals S30 and noise energy than similar harmonic energy and noise energy ratio.In some embodiments of weighting factor counter 550, calculate weighting factor S180, S190 according to one or more parameters relevant (for example, pitch gain and/or speech pattern) with the periodicity of narrow-band signal S20 or narrow-band residual signal.This embodiment of weighting factor counter 550 can be through the value that is configured to assign (for example) to be directly proportional with pitch gain to harmonic wave weighting factor S180, and/or is compared to turbid voice signal to the higher value of noise weighting factor S190 appointment for clear voice signal.
In other embodiments, weighting factor counter 550 is through being configured to calculate according to the periodic index of high-frequency band signals S30 the value of harmonic wave weighting factor S180 and/or noise weighting factor S190.In this type of instance; Weighting factor counter 550 is calculated as harmonic wave weighting factor S180 the maximal value of coefficient of autocorrelation of present frame or the subframe of high-frequency band signals S30, wherein in the delay that comprises a pitch lag and do not comprise in the hunting zone of delay of zero sample and carry out auto-correlation.Figure 17 shows that the delay with a pitch lag is that center and the length with the width that is not more than a pitch lag are the instance of this hunting zone of n sample.
Figure 17 also shows the instance of weighting factor counter 550 in another method of the periodic index of some stages calculating high-frequency band signals S30.In the phase one, present frame is divided into many subframes, and discerns the delay of coefficient of autocorrelation when maximum separately to each subframe.Mentioned like preceding text, in the delay that comprises a pitch lag and do not comprise in the hunting zone of delay of zero sample and carry out auto-correlation.
In subordinate phase, through the delay with corresponding identification be applied to each subframe, the subframe that connects gained to be to set up the optimal delay frame and the related coefficient that harmonic wave weighting factor S180 is calculated as between primitive frame and the optimal delay frame is set up deferred frame.In another alternate embodiment, weighting factor counter 550 is calculated as harmonic wave weighting factor S180 the mean value of the maximum coefficient of autocorrelation that obtains to each subframe in the phase one.The embodiment of weighting factor counter 550 also can be through being configured to the convergent-divergent related coefficient, and/or with itself and another value combination, to calculate the value of harmonic wave weighting factor S180.
Weighting factor counter 550 possibly need only otherwise indicating frame to have the periodic index of calculating high-frequency band signals S30 under the periodic situation.For instance, weighting factor counter 550 can be through the periodic index that is configured to calculate high-frequency band signals S30 according to periodic another designator (for example, pitch gain) and the relation between the threshold value of present frame.In an example, weighting factor counter 550 is just carried out auto-correlation computation to high-frequency band signals S30 through the value that only is configured to the pitch gain (for example, the residual self-adaptation code book gain of narrow-band) when frame during greater than 0.5 (perhaps, at least 0.5).In another example, weighting factor counter 550 is through being configured to only to the frame with special sound mode state (for example, only to the voiced sound signal) high-frequency band signals S30 to be carried out auto-correlation computation.Under this type of situation, weighting factor counter 550 can be through being configured to assign the default weighting factor to the frame with other speech pattern state and/or less pitch gain value.
Embodiment comprises through being configured to calculate the other embodiment of the weighting factor counter 550 of weighting factor according to being different from periodicity or the characteristic except that periodically.For instance, this embodiment can be through being configured to the voice signal with big pitch lag than assigning bigger value to the voice signal with little pitch lag to noise gain factor S190.This type of embodiment of another of weighting factor counter 550 is confirmed the index of the humorous degree of broadband voice signal S10 or high-frequency band signals S30 through being configured to signal energy according to the multiple place that is in fundamental frequency with respect to the index of the signal energy that is in other frequency component place.
Some embodiments of wideband speech coding device A100 are exported periodically or the indication of humorous degree (for example, the indication frame is that harmonic wave still is non-harmonic 1 flag) through being configured to another index based on pitch gain described herein and/or periodicity or humorous degree.In an example, corresponding broadband Voice decoder B100 uses this to indicate and disposes the for example operation of weighting factor calculating.In another example, this indication is used for the value that scrambler and/or demoder place come the computing voice mode parameter.
Possibly need high band excitation generator A302 to produce high band excitation signal S120, make the energy of pumping signal roughly not receive the influence of the particular value of weighting factor S180 and S190.In the case; Weighting factor counter 550 can be through the value that is configured to calculate harmonic wave weighting factor S180 or noise weighting factor S190 (or receive this value from another element of memory storage or high band encoder A200), and derive the value of another weighting factor according to for example following expression formula:
(W Harmonic wave) 2+ (W Noise) 2=1, (2)
W wherein Harmonic waveExpression harmonic wave weighting factor S180, and W NoiseExpression noise weighting factor S190.Perhaps, weighting factor counter 550 can through be configured to according to the value of the periodic measurement of present frame or subframe from many select to weighting factor S180, S190 corresponding one, wherein said to through calculating to satisfy the for example constant energy ratio of expression formula (2) in advance.For the embodiment of the weighting factor counter 550 of following expression formula (2), the representative value of harmonic wave weighting factor S180 arrives in about 1.0 scopes about 0.7, and the representative value of noise weighting factor S190 arrives in about 0.7 scope about 0.1.Other embodiment of weighting factor counter 550 can be operated according to extend expression formula (2) pattern that signal S160 and the required baseline between zoop signal S170 add weight update according to harmonic wave through being configured to.
When using sparse code book (the most of code book of clauses and subclauses) when calculating residual quantization means form, in the synthetic speech signal illusion possibly take place as null value.Especially when with low bitrate coding narrow-band signal, it is sparse code book to take place.The sparse illusion that causes of code book is quasi periodic usually in time, and mainly more than 3kHz, takes place.Because people's ear has time resolution preferably under upper frequency, so these illusions maybe be more obvious in high frequency band.
Embodiment comprises the embodiment through the high band excitation generator A300 that is configured to carry out anti-sparseness filtering.Figure 18 shows the calcspar of the embodiment A312 of high band excitation generator A302, and said embodiment A312 comprises anti-sparseness filtering device 600, and it is through being configured to carry out filtering to what quantizer 450 produced through de-quantization narrow-band pumping signal.Figure 19 shows the calcspar of the embodiment A314 of high band excitation generator A302, and said embodiment A314 comprises anti-sparseness filtering device 600, and it extends signal through the frequency spectrum that is configured to frequency spectrum stretcher A400 is produced and carries out filtering.Figure 20 shows the calcspar of the embodiment A316 of high band excitation generator A302, and said embodiment A316 comprises anti-sparseness filtering device 600, and it is through being configured to that the output of combiner 490 is carried out filtering to produce high band excitation signal S120.Certainly, expection and disclose any one the embodiment of high band excitation generator A300 of characteristics combination of characteristic and embodiment A312, A314 and A316 clearly with any one of embodiment A304 and A306 at this.Anti-sparseness filtering device 600 is also configurable in frequency spectrum stretcher A400: for example the element in frequency spectrum stretcher A402 510,520,530 and 540 any one after.Pay particular attention to, anti-sparseness filtering device 600 also can be used for the embodiment that execution spectrum folding, frequency spectrum are translated or harmonic wave extends of frequency spectrum stretcher A400.
Anti-sparseness filtering device 600 can be through being configured to change its phase of input signals.For instance, anti-sparseness filtering device 600 possibly and arranged through configuration, makes the phase place of high band excitation signal S120 along with time randomization or alternate manner distribute more equably.The response that possibly also need anti-sparseness filtering device 600 is the frequency spectrum leveling, and feasible amplitude frequency spectrum through filtering signal does not have sizable change.In an example, anti-sparseness filtering device 600 is embodied as the all-pass filter with transfer function according to following expression formula:
H ( z ) = - 0.7 + z - 4 1 - 0.7 z - 4 · 0.6 + z - 6 1 + 0.6 z - 6 . - - - ( 3 )
An effect of this wave filter can be the energy dissipation of input signal to be opened make it no longer only concentrate in several samples.
The sparse illusion that causes of code book is more obvious for the signal of the residual similar noise that comprises less tone information wherein usually, and also more obvious for the voice in the ground unrest.Usually cause less illusion under the sparse situation that has long-term structure in excitation, and in fact phase modification can cause the noise in the voiced sound signal.Therefore, possibly need configuration anti-sparseness filtering device 600 the voiceless sound signal is carried out filtering and at least some voiced sound signals are passed through.The voiceless sound signal (for example is characterised in that the low pitch gain; Quantize the gain of narrow-band self-adaptation code book) and near zero or be positive spectral tilt (for example; Quantize first reflection coefficient), thus indication leveling or acclivitous spectrum envelope along with the continuous increase of frequency.The typical embodiments of anti-sparseness filtering device 600 is through to voiceless sound (for example being configured to; Value like spectral tilt is indicated) carry out filtering; When pitch gain is lower than threshold value (perhaps, being not more than threshold value), voiced sound is carried out filtering, and otherwise under the situation of not making change, signal is passed through.
The other embodiment of anti-sparseness filtering device 600 comprises two or more wave filters, and it revises angle (for example, up to 180 degree) through being configured to have different maximum phases.In the case; Anti-sparseness filtering device 600 can be through according to pitch gain (for example being configured to; Quantize self-adaptation code book or LTP gain) value form in wave filters at these and select be used to have frame so that maximum phase that will be bigger is revised the angle than the low pitch yield value.The embodiment of anti-sparseness filtering device 600 also can comprise different composition wave filters; It is through being configured to revise phase place on the part more or less at frequency spectrum, so that will be used to have the frame than the low pitch yield value through the wave filter that is configured to modification phase place on the wider frequency range at input signal.
In order to duplicate exactly, possibly make the high frequency band of synthetic broadband voice signal S100 and the ratio between the narrow-band level partly be similar to the said ratio among the original broadband voice signal S10 through encoding speech signal.Except the spectrum envelope that high frequency band coding parameter S60a representes, high band encoder A200 also can be through being configured to represent through fixed time or gain envelope the characteristic of high-frequency band signals S30.Shown in figure 10; High band encoder A202 comprises high frequency band gain factor counter A230; It is through disposing and arranging to calculate one or more gain factors according to the relation between high-frequency band signals S30 and the synthetic high-frequency band signals S130 (for example, the difference or the ratio of said two signals between the energy on frame or its certain part).In other embodiment of high band encoder A202, high frequency band gain calculator A230 can likewise dispose but change into through arranging to come the calculated gains envelope according to this time-varying relationship between high-frequency band signals S30 and narrow-band pumping signal S80 or the high band excitation signal S120.
The temporal envelope of narrow-band pumping signal S80 and high-frequency band signals S30 is similar probably.Therefore; Coding usually will be only more effective based on the gain envelope of high-frequency band signals S30 than coding based on the gain envelope of the relation between high-frequency band signals S30 and the narrow-band pumping signal S80 (or the signal of therefrom deriving, for example high band excitation signal S120 or synthetic high-frequency band signals S130).In typical embodiments, high band encoder A202 is through being configured to be output as 8 to 12 the quantization index that each frame is specified 5 gain factors.
High frequency band gain factor counter A230 can comprise the task of one or more serial subtasks and carry out gain factor and calculate as one through being configured to.Figure 21 shows that the relative energy according to high-frequency band signals S30 and synthetic high-frequency band signals S130 calculates the process flow diagram of instance T200 of task of the yield value of corresponding subframe.Task 220a and 220b calculate the energy of the corresponding subframe of each signal.For instance, task 220a and 220b can through be configured to energy be calculated as each sub-frame sample square with.Task T230 is calculated as the gain factor of subframe the square root of the ratio of those energy.In this example, task T230 is calculated as gain factor the square root of ratio of energy of energy and the synthetic high-frequency band signals S130 of high-frequency band signals S30 on the subframe.
High frequency band gain factor counter A230 maybe be through being configured to calculate subframe energy according to window function.Figure 22 shows the process flow diagram of this embodiment T210 of gain factor calculation task T200.Task T215a is applied to high-frequency band signals S30 with window function, and task T215b is applied to synthetic high-frequency band signals S130 with the uniform window function.The embodiment 222a of task 220a and 220b and 222b calculate the energy of window separately, and task T230 is calculated as the gain factor of subframe the square root of the ratio of energy.
Possibly need to use and the overlapping window function of adjacent sub-frames.For instance, can be overlapping-window function of the generation gain factor that the phase add mode is used can help to reduce or avoid the uncontinuity between the subframe.In an example, high frequency band gain factor counter A230 is through being configured to use the trapezoidal window function shown in Figure 23 a, wherein each overlapping one millisecond of window and two adjacent sub-frames.Figure 23 b shows each of five sub-frame that this window function is applied to 20 milliseconds of frames.Other embodiment of high frequency band gain factor counter A230 can have negative lap cycle not and/or different windows shape (for example, rectangle, Hamming) through being configured to the use window function of (its can symmetry or asymmetric).The embodiment of high frequency band gain factor counter A230 also possibly be applied to the different windows function different subframes in the frame and/or comprise the frame of the subframe with different length through being configured to.
The instance of following value (not having restriction) as particular is provided.To the frame of one 20 milliseconds of these situation supposition, but can use any other duration.For the high-frequency band signals with the 7kHz sampling, each frame has 140 samples.If this frame is divided into five sub-frame with equal length, each subframe will have 28 samples so, and the window shown in Figure 23 a will be wide for 42 samples.For the high-frequency band signals with the 8kHz sampling, each frame has 160 samples.If this frame is divided into five sub-frame with equal length, each subframe will have 32 samples so, and the window shown in Figure 23 a will be wide for 48 samples.In other embodiments, can use subframe with any width, and even the embodiment that possibly make high frequency band gain calculator A230 through being configured to produce different gain factors to each sample of frame.
Figure 24 shows the calcspar of the embodiment B202 of high band decoder B200.High band decoder B202 comprises high band excitation generator B300, and it is through being configured to produce high band excitation signal S120 based on narrow-band pumping signal S80.Look particular system design and select and decide, can implement high band excitation generator B300 according to any one of the embodiment of high band excitation generator A300 described herein.Usually, need high band excitation generator B300 be embodied as the identical response of high band excitation generator that has with the high band encoder of specific coding system.Yet; Because narrow-band demoder B110 will carry out the de-quantization through coding narrow-band pumping signal S50 usually; So in most of the cases; High band excitation generator B300 can be embodied as from narrow-band demoder B110 and receive narrow-band pumping signal S80, and need not comprise through being configured to the quantizer through coding narrow-band pumping signal S50 de-quantization.Narrow-band demoder B110 also can be embodied as the instance that comprises anti-sparseness filtering device 600, and it is through be provided with so that the narrow-band composite filter of wave filter 330 carries out filtering to said signal for example being input to through the narrow-band pumping signal of de-quantization before.
Quantizer 560 is through being configured to the de-quantization to high band filter parameter S 60a (being one group of LSF in this example); And LSF-LP filter coefficient conversion 570 is through being configured to that LSF is transformed to one group of filter coefficient (for example, like the quantizer 240 and conversion 250 descriptions of preceding text with reference to narrowband encoder A122).In other embodiments, mentioned like preceding text, can use different coefficient sets (for example, cepstrum coefficient) and/or the coefficient representation is (for example, ISP).High frequency band composite filter B200 is through being configured to produce synthetic high-frequency band signals according to high band excitation signal S120 and said group of filter coefficient.The system that comprises composite filter for high band encoder wherein (for example; As in the instance of above-mentioned scrambler A202); Maybe high frequency band composite filter B200 be embodied as and have the response identical (for example, identical transfer function) with said composite filter.
High band decoder B202 also comprises through being configured to the quantizer 580 to high frequency band gain factor S60b de-quantization; With through configuration with arrange will be applied to synthetic high-frequency band signals through the gain factor of de-quantization to produce the gain control element 590 (for example, multiplier or amplifier) of high-frequency band signals S100.For the gain envelope of frame wherein situation by an above gain factor appointment; Gain control element 590 can comprise through being configured to gain factor to be applied to according to window function the logic of each sub-frame; Said window function can be identical or different with the window function of being used by the gain calculator (for example, high frequency band gain calculator A230) of corresponding high band encoder.In other embodiment of high band decoder B202, gain control element 590 warps dispose similarly but the gain factor through de-quantization are applied to narrow-band pumping signal S80 or are applied to high band excitation signal S120 to change into through arrangement.
Mentioned like preceding text, possibly in high band encoder and high band decoder, obtain equal state (for example, through using through the de-quantization value during encoding).Therefore, possibly guarantee in coded system that the corresponding noise generator among high band excitation generator A300 and the B300 has equal state according to this embodiment.For instance; The high band excitation generator A300 of this embodiment and B300 can make that the state of noise generator is that information encoded has been (for example in the same number of frames through configuration; Narrow band filter parameter S 40 or its part, and/or through coding narrow-band pumping signal S50 or its part) the determinacy function.
One or more (for example, quantizer 230,420 or 430) in the quantizer of element described herein can quantize through being configured to carry out class vector.For instance, this quantizer can be in being configured to and/or in the same number of frames in the high frequency band channel based on narrow-band channel information encoded from one group of code book, select a code book.This technology is the code efficiency that cost provides increase to store extra code book usually.
Referring to for example Fig. 8 and 9 argumentations, after from narrow-band voice signal S20, removing rough spectrum envelope, quite a large amount of periodic structures possibly be retained in the residual signal like preceding text.For instance, residual signal can contain rough recurrent pulses or spiking sequence in time.This structure (relevant with tone usually) especially might occur in the voiced speech signal.The calculating of the quantization means form of narrow-band residual signal can comprise according to the model of the long term periodicities of being represented by (for example) one or more code books this tone structure of encoding.
The tone structure of actual residual signals possibly not mated with periodic model fully.For instance, residual signal possibly comprise the less shake of the location rule property of tone pulses, makes in the frame distance between the continuous tone pulse not exclusively equate and said structure is not suitable rule.These scramblings tend to reduce code efficiency.
Some embodiments of narrowband encoder A120 through be configured to through before quantizing or during be applied to the auto-adaptive time deviation residual; Or through otherwise in code-excited signal, comprising the auto-adaptive time deviation, carry out the regularization of tone structure.For instance; This scrambler can through be configured to select or otherwise computing time deviation degree (for example; According to one or more perceptual weightings and/or error minimize standard), make the pumping signal of gained and model the best of long term periodicities fit.The regularization of tone structure is carried out by the celp coder group that is called lax code exciting lnear predict (RCELP) scrambler.
The RCELP scrambler is usually through being configured to the execution time deviation as the self-adaptation time shift.This time shift can be negative several milliseconds and arrives the just delay of several milliseconds of scopes, and it changes the uncontinuity that can hear to avoid usually smoothly.In some embodiments, this scrambler is through being configured to the segmented mode application ruleization wherein each frame or subframe deviation fixedly time shift accordingly.In other embodiments, scrambler turns into and is continuous departure function through being configured to application rule, makes frame or subframe according to tone contour (being also referred to as the tone track) and deviation.In some cases (for example; Described in the open case of No. 2004/0098255 U.S. Patent application), scrambler is through being configured to through offset applications is being comprised time deviation in being used for calculating through the perceptual weighting input signal of code-excited signal through code-excited signal.
Scrambler computation ruleization and quantification through code-excited signal, and demoder to through code-excited signal de-quantization to obtain to be used for synthetic pumping signal through decodeing speech signal.Therefore show the delay of the variation identical be included in delay in code-excited signal through regularization through decoded output signal.Usually, not with the information transmission of any specified rule amount to demoder.
Regularization often makes residual signal be prone to coding, and this has improved from the coding gain of long-term predictor and has therefore advanced overall code efficiency, and can not produce illusion usually.Possibly need only to the unvoiced frame executing ruleization.For instance, narrowband encoder A124 can those have the frame or the subframe of long-term structure (for example, voiced sound signal) through being configured to only to squint.Even possibly need only to comprising the subframe executing ruleization of tone pulses energy.The various embodiments of RCELP coding have been described in the 5th, 704, No. 003 United States Patent (USP) people such as () Kleijn and the 6th, 879, No. 955 United States Patent (USP)s (Rao) and No. 2004/0098255 open case of U.S. Patent application people such as () Kovesi.The existing embodiment of RCELP scrambler comprises like enhancing variable bit rate coder (EVRC) and third generation partnership relation plan 2 (3GPP2) alternative mode vocoder (SMV) described in the IS-127 of telecommunications industry association (TIA).
Unfortunately, regularization is for wherein causing some problems from the wideband speech coding device (system that for example, comprises wideband speech coding device A100 and broadband Voice decoder B100) of deriving high band excitation through coding narrow-band pumping signal.Because high band excitation signal derives from the time deviation signal, so high band excitation signal will have the time response different time characteristic with original high frequency band voice signal usually.In other words, high band excitation signal will be no longer synchronous with original high frequency band voice signal.
Temporal misalignment between deviation high band excitation signal and the original high frequency band voice signal possibly cause some problems.For instance, the deviation high band excitation signal possibly no longer provide suitable source forcing for the composite filter according to the filter parameter configuration of from original high frequency band voice signal, extracting.Therefore, synthetic high-frequency band signals can contain the illusion of hearing that reduces through the perceived quality of decoding broadband voice signal.
Temporal misalignment also possibly cause the poor efficiency of gain envelope coding.Mentioned like preceding text, exist relevant between the temporal envelope of narrow-band pumping signal S80 and high-frequency band signals S30 probably.Through gain envelope, compare the raising that can realize code efficiency with direct coding gain envelope according to the coding of the relation between these two temporal envelope high-frequency band signals.Yet, when through the regularization of coding narrow-band pumping signal, this relevant possibly weakening.Temporal misalignment between narrow-band pumping signal S80 and the high-frequency band signals S30 can cause occurring fluctuation among the high frequency band gain factor S60b, and code efficiency possibly reduce.
Embodiment comprises according to the wideband speech coding method of the corresponding time deviation that in coding narrow-band pumping signal, comprises to high frequency band voice signal execution time deviation.The potential advantage of these class methods comprises to be improved through the quality of decoding broadband voice signal and/or the efficient of improvement coding high frequency band gain envelope.
Figure 25 shows the calcspar of the embodiment AD10 of wideband speech coding device A100.Scrambler AD10 comprises the embodiment A124 of narrowband encoder A120, and said embodiment A124 is through being configured to calculating executing ruleization during coding narrow-band pumping signal S50.For instance, narrowband encoder A124 can be according to the one or more configurations in the RCELP embodiment of preceding text argumentation.
Narrowband encoder A124 is also through being configured to export the regularization data-signal SD10 of the degree of specifying applied time deviation.For narrowband encoder A124 through being configured to fixing time shift is applied to the various situation of each frame or subframe; Regularization data-signal SD10 can comprise a series of values, and it is that unit is designated as integer or non integer value with each time shift amount with sample, millisecond or a certain increment At All Other Times.For narrowband encoder A124 (for example through the time scale that is configured to otherwise to revise frame or other sample sequence; Through compressing a part and expanding another part) situation; Regularization information signal SD10 can comprise the corresponding description of revising, for example one group of function parameter.In a particular instance, the fixedly time shift of narrowband encoder A124 through being configured to frame is divided into three sub-frame and calculates each subframe makes regularization data-signal SD10 indicate three time shift amounts through each regularization frame of coding narrow-band signal.
Wideband speech coding device AD10 comprises lag line D120, and it is through being configured to advance or block according to the retardation by input signal indication the several portions of high frequency band voice signal S30, thus generation time deviation high frequency band voice signal S30a.In instance shown in Figure 25, lag line D120 is through being configured to according to coming the execution time deviation to high frequency band voice signal S30 by the deviation of regularization data-signal SD10 indication.In this way,, the identical time deviation amount that comprises among the coding narrow-band pumping signal S50 is applied to the appropriate section of high frequency band voice signal S30 before also analyzing.Although this instance is shown as the individual component of high band encoder A200 with lag line D120, in other embodiments, lag line D120 is configured to the part of high band encoder.
The other embodiment of high band encoder A200 can be through being configured to carry out the not spectrum analysis of deviation high frequency band voice signal S30 (for example, lpc analysis), and before calculating high frequency band gain parameter S60b, carry out the time deviation of high frequency band voice signal S30.This scrambler can comprise (for example) embodiment through the lag line D120 that is configured to the execution time deviation.Yet, under this type of situation, the spectrum envelope with high band excitation signal S120 misalignment in time can be described based on high band filter parameter S 60a to the not analysis of deviation signal S30.
Lag line D120 can be applied to the logic element of high frequency band voice signal S30 and any combination of memory element is disposed with the required time biased operation according to being suitable for.For instance, lag line D120 can be through being configured to from impact damper, to read high frequency band voice signal S30 according to required time shift.Figure 26 a shows the synoptic diagram of this embodiment D122 of lag line D120, and said lag line D120 comprises shift register SR1.Shift register SR1 is the impact damper with about length m through m the most recent sample that is configured to receive and store high frequency band voice signal S30.Value m equals just (or " propelling ") and the summation of bearing (or " retardance ") time shift of the maximum of supporting at least.Value m equals the length of frame or the subframe of high-frequency band signals S30 may be more convenient.
Lag line D122 is through being configured to the deviation post OL output time deviation high-frequency band signals S30a from shift register SR1.The location of deviation post OL is according to being changed near reference position (zero time shift) by the current time shift of for example regularization data-signal SD10 indication.Lag line D122 can be through being configured to support the propelling and the retardance that equate to limit, and perhaps a restriction limits greater than another, and making can be in one direction than on other direction, carrying out bigger skew.Figure 26 a shows that the positive time shift of supporting is greater than the particular instance of bearing time shift.Lag line D122 can be through being configured to once to export one or more samples (for example look the output bus width and decide).
The regularization time shift that has greater than several milliseconds value can cause the illusion of hearing in decoded signal.Usually, the value of the regularization time shift of being carried out by narrowband encoder A124 will be no more than several milliseconds, make time shift by regularization data-signal SD10 indication with limited.Yet, possibly need under this type of situation lag line D122 through be configured to align and/or negative direction on time shift force maximum constraints (for example, to follow more strict restriction of the restriction of forcing) than narrowband encoder.
Figure 26 b shows the synoptic diagram of the embodiment D124 of lag line D122, and lag line D122 comprises displacement window SW.In this example, the location of the deviation post OL window SW that is shifted limits.Although Figure 26 b shows the situation of buffer length m greater than the width of displacement window SW, lag line D124 also can be through implementing to make the width of displacement window SW equal m.
In other embodiments, lag line D120 is through being configured to according to required time shift high frequency band voice signal S30 to be written to impact damper.Figure 27 shows the synoptic diagram of the embodiment D130 of lag line D120, and said embodiment D130 comprises through two shift register SR2 that are configured to receive and store high frequency band voice signal S30 and SR3.Lag line D130 is through being configured to according to for example being written to shift register SR3 from frame or the subframe of shift register SR2 by the time shift of regularization data-signal SD10 indication.Shift register SR3 is configured to fifo buffer, and it is through being configured to output time deviation high-frequency band signals S30.
In particular instance shown in Figure 27, shift register SR2 comprises frame buffer part FB1 and delay buffer part DB, and shift register SR3 comprises frame buffer part FB2, advances bumper portion AB and retardance bumper portion RB.Advance impact damper AB and the length of retardance impact damper RB to equate, perhaps wherein one can be greater than another person, make skew on the direction of being supported greater than the skew on the other direction of being supported.Delay buffer DB and retardance bumper portion RB can be through being configured to have equal length.Perhaps; The comparable retardance impact damper of delay buffer DB RB is short to transfer to the shift register SR3 required time interval with sample from frame buffer FB1 to consider, said transfer can comprise other processing operation that for example before storing shift register SR3 into, makes sample bias earlier.
In the instance of Figure 27, frame buffer FB1 is through being configured to have the length with the equal in length of the frame of high-frequency band signals S30.In another example, frame buffer FB1 is through being configured to have the length with the equal in length of the sub-frame of high-frequency band signals S30.In the case, lag line D130 can be used for identical (for example, average) delay is applied to the logic of all subframes of frame to be squinted through being configured to comprise.Lag line D130 also can comprise the value and the logic that blocks impact damper RB or advance impact damper AB value to be rewritten to average that is used for from frame buffer FB1.In another example; Shift register SR3 can be through being configured to only receive via frame buffer FB1 the value of high-frequency band signals S30; And in the case, lag line D130 can comprise the logic of inserting in carrying out on the gap that is used between successive frame that is written to shift register SR3 or subframe.In other embodiments, lag line D130 can carry out biased operation (for example, according to the function of being described by regularization data-signal SD10) to said sample before being configured to be written to shift register SR3 from the sample of frame buffer FB1.
Lag line D120 possibly need use based on but be not equal to time deviation by the deviation of regularization data-signal SD10 appointment.Figure 28 shows the calcspar of the embodiment AD12 of wideband speech coding device AD10, and wideband speech coding device AD10 comprises length of delay mapper D110.Length of delay mapper D110 is through mapping length of delay SD10a through being configured to the Deviation Mapping by regularization data-signal SD10 indication.Lag line D120 is through being configured to according to coming generation time deviation high frequency band voice signal S30a by the deviation of indicating through mapping length of delay SD10a.
Can expect that the time shift that narrowband encoder is used makes progress in time smoothly.Therefore, usually computing voice is applied to the average narrow-band time shift of subframe and enough according to the squint respective frame of high frequency band voice signal S30 of this mean value image duration.In this type of instance, length of delay mapper D110 is through the mean value of the subframe delay value that is configured to calculate each frame, and lag line D120 is through being configured to the mean value that calculates is applied to the respective frame of high-frequency band signals S30.In other instance, can calculate and use than the mean value in short period (for example, two sub-frame, or half frame) or the longer cycle (for example, two frames).Be under the situation of non integer value of sample at mean value, length of delay mapper D110 can be before being configured to said value to be outputed to lag line D120 be rounded to said value the integer number of sample.
Narrowband encoder A124 can be through being configured in the regularization time shift that in coding narrow-band pumping signal, comprises the sample of non-integer number.In the case, length of delay mapper D110 maybe be through being configured to the narrow-band time shift is rounded to the integer number of sample, and lag line D120 possibly need to be applied to high frequency band voice signal S30 through the time shift that rounds up.
In some embodiments of wideband speech coding device AD10, narrow-band voice signal S20 is different with the sampling rate possibility of high frequency band voice signal S30.Under this type of situation; Length of delay mapper D110 can be through being configured to regulate the time shift amount of indicating among the regularization data-signal SD10, with the difference between the sampling rate of considering narrow-band voice signal S20 (or narrow-band pumping signal S80) and high frequency band voice signal S30.For instance, length of delay mapper D110 can be through being configured to the ratio convergent-divergent time shift amount according to sampling rate.In the particular instance that preceding text are mentioned, with 8kHz narrow-band voice signal S20 is taken a sample, and high frequency band voice signal S30 is taken a sample with 7kHz.In the case, length of delay mapper D110 is through being configured to that each side-play amount multiply by 7/8.The embodiment of length of delay mapper D110 also can be through being configured to carry out this convergent-divergent computing and integer described herein rounds up and/or the time shift average calculating operation.
In other embodiment, the time scale (for example, through compress a part and expand another part) of lag line D120 through being configured to otherwise revise frame or other sample sequence.For instance, narrowband encoder A124 can be through being configured to come executing ruleization according to the function of for example tone contour or track.In the case, regularization data-signal SD10 can comprise the corresponding description (for example one group of parameter) to said function, and lag line D120 can comprise the logic of according to said function frame or the subframe of high frequency band voice signal S30 being carried out deviation through being configured to.In other embodiments, length of delay mapper D110 through be configured to said function through lag line D120 be applied to before the high frequency band voice signal S30 to said function average, convergent-divergent and/or round up.For instance; Length of delay mapper D110 can be through being configured to according to one or more length of delays of said function calculation; Each length of delay indication number of samples, it is then used with one or more respective frame or subframe execution time deviation to high frequency band voice signal S30 by lag line D120.
Figure 29 shows according to the process flow diagram of the corresponding time deviation that in coding narrow-band pumping signal, comprises to the method MD100 of high frequency band voice signal execution time deviation.Task TD100 handles the broadband voice signal to obtain narrow-band voice signal and high frequency band voice signal.For instance, task TD100 can carry out filtering to the broadband voice signal through being configured to use the bank of filters (the for example embodiment of bank of filters A110) with low-pass filter and Hi-pass filter.Task TD200 is encoded to narrow-band pumping signal and a plurality of narrow band filter parameter through coding at least with the narrow-band voice signal.Said narrow-band pumping signal and/or filter parameter through coding can quantize, and also can comprise for example other parameter of speech pattern parameter through the narrow-band pumping signal of coding.Task TD200 also comprises the time deviation in the narrow-band pumping signal of coding.
Task TD300 produces high band excitation signal based on the narrow-band pumping signal.In the case, the narrow-band pumping signal is based on the narrow-band pumping signal through coding.Task TD400 is encoded to a plurality of high band filter parameters according to said at least high band excitation signal with the high frequency band voice signal at least.For instance, task TD400 can be a plurality of quantification LSF through being configured to the high frequency band speech signal coding.Task TD500 is applied to the high frequency band voice signal with time shift, said time shift based on the relevant information of time deviation that in coding narrow-band pumping signal, comprises.
Task TD400 can be through being configured to that the high frequency band voice signal is carried out spectrum analysis (for example, lpc analysis), and/or calculate the gain envelope of high frequency band voice signal.Under this type of situation, task TD500 can be through being configured to before said analysis and/or the calculating of gain envelope, time shift to be applied to the high frequency band voice signal.
Other embodiment of wideband speech coding device A100 is through being configured to the time deviation counter-rotating with the high band excitation signal S120 that is caused by the time deviation that in coding narrow-band pumping signal, comprises.For instance; High band excitation generator A300 can be through implementing to comprise the embodiment of lag line D120; The said embodiment of lag line D120 is through being configured to receive regularization data-signal SD10 or warp mapping length of delay SD10a; And the time shift of will reversing accordingly is applied to narrow-band pumping signal S80, and/or be applied to the signal subsequently (for example, harmonic wave extends signal S160 or high band excitation signal S120) based on said narrow-band pumping signal S80.
Other wideband speech coding device embodiment can be encoded to narrow-band voice signal S20 and high frequency band voice signal S30 through being configured to independently of one another, makes high frequency band voice signal S30 be encoded as the representation of high frequency band spectrum envelope and high band excitation signal.This embodiment can be through being configured to the basis information relevant with the time deviation that in coding narrow-band pumping signal, comprises to high frequency band residual signal execution time deviation, or otherwise time deviation is included in the coding high band excitation signal.For instance, high band encoder can comprise described herein through being configured to time deviation is applied to the embodiment of the lag line D120 and/or the length of delay mapper D110 of high frequency band residual signal.The potential advantage of this operation comprise to the high frequency band residual signal than efficient coding, and the better coupling between synthesis of narrow frequency band and the high frequency band voice signal.
Mentioned like preceding text, embodiment described herein comprises and can be used for carrying out the compatible of embedded encoded embodiment, support and narrow band system and needing to avoid code conversion.Support to the high frequency band coding also can be used on cost distinguishing chip, chipset, device and/or the network with broadband support and back compatible property and only has chip, chipset, device and/or the network that narrow-band is supported.As the support to high frequency band coding described herein also can be used to support the technology of low-frequency band coding be used in combination, and according to system, method or the equipment of this embodiment can support to for example about 50 or 100Hz until about 7 or the coding of the frequency component of 8kHz.
Mentioned like preceding text, add the high frequency band support to speech coder and can improve sharpness, especially aspect fricative differentiation.Although this differentiation possibly derived out according to specific context usually by human listener, the high frequency band support can be used (system that for example is used for automated voice menu navigation and/or automatic call treatment) and served as and launch characteristic in speech recognition and other machine decipher.
Equipment according to an embodiment can be embedded in the portable radio communication device (for example, cellular phone or PDA(Personal Digital Assistant)).Perhaps, this equipment can be included in another communicator, for example the VoIP mobile phone, through the personal computer that is configured to support VoIP communication or through being configured to the network equipment of routing telephone or VoIP communication.For instance, the equipment according to an embodiment may be implemented in the chip or chipset of communicator.Look application-specific and decide; This device also can comprise for example following characteristic: analog to digital and/or digital-to-analog to voice signal are changed, are used for voice signal is carried out the circuit of amplification and/or other signal processing operations, and/or are used to launch and/or receive the radio circuit through encoding speech signal.
Clearly expection and announcement embodiment can comprise the 60/667th; No. 901 and the 60/673rd; In the further feature that discloses in No. 965 U.S. Provisional Patent Application cases any one or one above and/or therewith use advocated the rights and interests of said temporary patent application case in the application's case.This category feature comprises removal and betides in the high frequency band and the non-existent substantially high-energy burst with short duration in narrow-band.This category feature comprises the for example fixing or adaptive smooth of the coefficient representation of high frequency band LSF.Fixing or the self-adaptation that this category feature comprises the noise that is associated with the quantification of the coefficient representation of for example LSF is shaped.This category feature also comprises the fixing or adaptive smooth of gain envelope, and the adaptive attenuation of gain envelope.
Provide above introduction to description embodiment so that make the those skilled in the art can make or use the present invention.Possibly make various modifications to these embodiment, and the General Principle that this paper provides also can be applicable to other embodiment.For instance; But be embodied as to embodiment a part or whole part hard-wired circuit; Be embodied as the circuit arrangement that is fabricated onto in the special IC; Perhaps be embodied as as machine readable code and be loaded into the firmware program in the Nonvolatile memory devices or load or be loaded into the software program the data storage medium from data storage medium, said code be can be by the instruction of the array of logic elements execution of for example microprocessor or other digital signal processing unit.Data storage medium can be memory element array; For example semiconductor memory (its can comprise (being not limited to) dynamically or static RAM (SRAM) (RAS), ROM (ROM (read-only memory)) and/or quickflashing RAM), or ferroelectric, magnetic resistance, two-way switch semiconductor, polymkeric substance or phase transition storage; The perhaps disc type medium of disk or CD for example.Any one or instruction group or sequence more than one that term " software " is interpreted as comprising source code, assembly language code, machine code, binary code, firmware, macrocode, microcode, can be carried out by array of logic elements, and any combination of this type of instance.
The various elements of the embodiment of high band excitation generator A300 and B300, high band encoder A100, high band decoder B200, wideband speech coding device A100 and broadband Voice decoder B100 can be embodied as (for example) and stay and to exist on the same chip in the chipset or electronics and/or optical devices between two or more chips, but also there is other configuration that does not have this restriction in expection.One or more elements of this equipment can be embodied as one or more instruction groups in whole or in part; Said instruction group through be configured to one or more fix or programmable logic element (for example; Transistor, door) to carry out on the array, said element for example is microprocessor, embedded processor, the IP kernel heart, digital signal processor, FPGA (field programmable gate array), ASSP (Application Specific Standard Product) and ASIC (special IC).One or more these class components also (for example possibly have common structure; Be used for carrying out processor corresponding to the code section of different elements at different time, through carrying out to carry out instruction group corresponding to the task of different elements at different time, perhaps at different time to the electronics of different elements executable operations and/or the configuration of optical devices).In addition, one or more these class components possibly be used to carry out task or other the instruction group not directly related with operation of equipment, for example relevant with another operation of device that is embedded with said equipment or system task.
Figure 30 shows the process flow diagram that the said highband part of voice signal with narrow-band part and highband part is carried out Methods for Coding M100 according to an embodiment.Task X100 calculates one group of filter parameter of the spectrum envelope that characterizes highband part.Task X200 extends signal through nonlinear function being applied to calculate frequency spectrum from the signal that narrow-band partly derives.Task X300 produces synthetic high-frequency band signals according to (A) said group of filter parameter and the high band excitation signal of (B) extending signal based on said frequency spectrum.Task X400 comes the calculated gains envelope based on the relation between the energy of the energy of (C) highband part and the signal of (D) partly deriving from narrow-band.
Figure 31 a shows the process flow diagram that produces the method M200 of high band excitation signal according to an embodiment.Task Y100 extends signal through nonlinear function being applied to calculate through harmonic wave from the narrow-band pumping signal that the narrow-band of voice signal partly derives.Task Y200 will extend signal and mix through the zoop signal to produce high band excitation signal through harmonic wave.Figure 31 b shows the process flow diagram that produces the method M210 of high band excitation signal according to another embodiment that comprises task Y300 and Y400.Task Y300 calculates temporal envelope according to the narrow-band pumping signal with through the energy in time that harmonic wave extends one in the signal.Task Y400 according to temporal envelope zoop signal to produce through the zoop signal.
Figure 32 shows the process flow diagram of the method M300 that the said highband part of voice signal with narrow-band part and highband part is decoded according to an embodiment.Task Z100 receives one group of filter parameter of the spectrum envelope that characterizes said highband part and characterizes one group of gain factor of the temporal envelope of said highband part.Task Z200 extends signal through nonlinear function being applied to calculate frequency spectrum from the signal that narrow-band partly derives.Task Z300 produces synthetic high-frequency band signals according to (A) said group of filter parameter and the high band excitation signal of (B) extending signal based on said frequency spectrum.Task Z400 modulates the gain envelope of said synthetic high-frequency band signals based on said group of gain factor.For instance; Task Z400 can through be configured to through said group of gain factor being applied to partly derive from narrow-band pumping signal, be applied to frequency spectrum and extend signal, be applied to high band excitation signal; Or be applied to synthetic high-frequency band signals, modulate the gain envelope of said synthetic high-frequency band signals.
Embodiment also comprises like (for example) among this paper through said additional voice decoding, Code And Decode method to clearly disclosing through the description of the structure embodiment that is configured to carry out additional voice decoding, Code And Decode method.Each of these methods also (for example can positively be implemented; In one or more data storage mediums of enumerating like preceding text) one or more instruction groups for reading and/or carry out by the machine that comprises logic element (for example, processor, microprocessor, microcontroller or other finite state machine) array.Therefore, the embodiment that the present invention shows without wishing to be held to preceding text, but should meet with this paper in the consistent broad range of (comprising in the appended claims of a part of the original disclosure of being submitted to of formation) principle of disclosing by any way and novel feature.

Claims (32)

1. method that produces high band excitation signal, said method comprises:
Harmonic wave extends the frequency spectrum based on the signal of low band excitation signal;
Calculating is based on the temporal envelope of the signal of said low band excitation signal;
Determinacy function according to the information in encoding speech signal produces noise signal;
Modulate said noise signal according to said temporal envelope; And
The result that combination (A) is extended based on said harmonic wave through harmonic wave extend signal with (B) based on the result of said modulation through the zoop signal,
Wherein said high band excitation signal is based on the result of said combination.
2. method according to claim 1, wherein said harmonic wave are extended and are comprised nonlinear function is applied to the signal based on said low band excitation signal.
3. method according to claim 2, wherein said application nonlinear function are included in and use said nonlinear function in the time domain.
4. method according to claim 2, wherein said nonlinear function are memoryless nonlinear functions.
5. method according to claim 2, wherein said nonlinear function is time-independent.
6. method according to claim 2, wherein said nonlinear function comprise at least one in ABS function, chi square function and the slicing function.
7. method according to claim 2, wherein said nonlinear function is an ABS function.
8. method according to claim 1, wherein said calculating based on the temporal envelope of the signal of said low band excitation signal comprise calculate said low band excitation signal, based on the low-frequency band voice signal of said low band excitation signal with saidly extend the temporal envelope of one in the signal through harmonic wave.
9. method according to claim 1, wherein said harmonic wave extension comprise harmonic wave and extend the upwards frequency spectrum of sampled signal based on said low band excitation signal.
10. method according to claim 1, said method comprise that (A) extends signal through harmonic wave and carry out the frequency spectrum leveling and (B) said high band excitation signal is carried out in the frequency spectrum leveling at least one said before the said combination.
11. method according to claim 10, wherein said frequency spectrum leveling comprises:
Based on a plurality of filter coefficients of calculated signals of treating the frequency spectrum leveling; And
Use prewhitening filter that the said signal of frequency spectrum leveling of treating is carried out filtering according to said a plurality of filter coefficient configurations.
12. method according to claim 1, wherein said combination comprise, and calculating is said extends signal and said weighted sum through the zoop signal through harmonic wave, wherein said high band excitation signal is based on said weighted sum.
13. method according to claim 12 is wherein calculated weighted sum and is comprised according to the first weighting factor weighting is said and extend signal through harmonic wave, and said through the zoop signal according to the second weighting factor weighting,
Wherein said method comprises according to the time change condition calculates one in said first and second weighting factors; And calculate another person in said first and second weighting factors, make the energy summation of said first and second weighting factors along with the time is constant substantially.
14. method according to claim 12 is wherein calculated weighted sum and is comprised according to the first weighting factor weighting is said and extend signal through harmonic wave, and said through the zoop signal according to the second weighting factor weighting,
Wherein said method comprises according in the sounding degree of the periodic index of (A) voice signal and (B) voice signal at least one calculates in said first and second weighting factors at least one.
15. method according to claim 12; Wherein calculating weighted sum comprises according to the first weighting factor weighting said through harmonic wave extension signal; And it is said through the zoop signal according to the second weighting factor weighting; Wherein said method comprises from the residual quantization means form of low-frequency band and obtains said low band excitation signal and pitch gain value, and
Wherein said method comprises according to said at least pitch gain value calculates one in said first and second weighting factors.
16. method according to claim 1, said method comprise (i) according to said high band excitation signal coding high frequency band voice signal with (ii) according to decode in the high frequency band voice signal at least one of said high band excitation signal.
17. an equipment that is used to produce high band excitation signal, it comprises:
The frequency spectrum stretcher, it extends through the harmonic wave that is configured to carry out based on the frequency spectrum of the signal of low band excitation signal;
The envelope counter, it is through being configured to calculate the temporal envelope based on the signal of said low band excitation signal;
Noise generator, its determinacy function according to the information in encoding speech signal produces noise signal;
First combiner, it is through being configured to carry out according to said temporal envelope the modulation of said noise signal; And
Second combiner, its through the result that is configured to calculate (A) and extends based on said harmonic wave through harmonic wave extend signal with (B) based on the result's of said modulation summation through the zoop signal,
Wherein said high band excitation signal is based on the result of said summation.
18. equipment according to claim 17, wherein said frequency spectrum stretcher extends through the said harmonic wave that is configured to use nonlinear function and carries out based on the frequency spectrum of the signal of said low band excitation signal.
19. equipment according to claim 18, wherein said nonlinear function comprise in ABS function, chi square function and the slicing function at least one.
20. equipment according to claim 18, wherein said nonlinear function is an ABS function.
21. equipment according to claim 17, wherein said envelope counter is through being configured to based on said low band excitation signal, based on the low-frequency band voice signal of said low band excitation signal with saidly extend one in the signal through harmonic wave and calculate said temporal envelope.
22. equipment according to claim 17, wherein said frequency spectrum stretcher is through being configured to carry out the harmonic wave extension based on the upwards frequency spectrum of sampled signal of said low band excitation signal.
23. equipment according to claim 17, said equipment comprises the frequency spectrum tenderizer, and said frequency spectrum tenderizer extends in signal and the said high band excitation signal at least one through harmonic wave and carries out the frequency spectrum leveling said through being configured to.
24. equipment according to claim 23; Wherein said frequency spectrum tenderizer is through being configured to based on a plurality of filter coefficients of calculated signals of treating frequency spectrum leveling, and uses the prewhitening filter according to said a plurality of filter coefficients configurations that the said signal of frequency spectrum leveling of treating is carried out filtering.
25. equipment according to claim 17, wherein said second combiner saidly extends signal and said weighted sum through the zoop signal through harmonic wave through being configured to calculate, and wherein said high band excitation signal is based on said weighted sum.
26. equipment according to claim 25, wherein said second combiner is said through harmonic wave extension signal through being configured to according to the first weighting factor weighting, and said through the zoop signal according to the second weighting factor weighting, and
Wherein said second combiner is through being configured to calculate one in said first and second weighting factors according to the time change condition, and
Wherein said second combiner is through being configured to calculate another person in said first and second weighting factors, makes the energy summation of said first and second weighting factors along with the time is constant substantially.
27. equipment according to claim 17; Wherein said second combiner is through being configured to extend signal according to the first weighting factor weighting is said through harmonic wave; Said according to the second weighting factor weighting through the zoop signal; And calculate said through harmonic wave extension signal and said weighted sum through the zoop signal
Wherein said second combiner is through being configured to calculate in said first and second weighting factors at least one according in the sounding degree of the periodic index of (A) voice signal and (B) voice signal at least one.
28. equipment according to claim 17; Wherein said second combiner is through being configured to extend signal according to the first weighting factor weighting is said through harmonic wave; Said according to the second weighting factor weighting through the zoop signal, and calculate and saidly extend signal and said weighted sum through the zoop signal through harmonic wave, wherein said equipment comprises de-quantizer; Said de-quantizer is through being configured to obtain said low band excitation signal and pitch gain value from the residual quantization means form of low-frequency band, and
Wherein said second combiner is through being configured to calculate in said first and second weighting factors at least one according to said at least pitch gain value.
29. equipment according to claim 17; Said equipment comprises at least one in following: (i) high frequency band speech coder; It is through being configured to according to said high band excitation signal coding high frequency band voice signal and (ii) high frequency band Voice decoder, and it is through being configured to according to the said high band excitation signal high frequency band voice signal of decoding.
30. equipment according to claim 17, said equipment comprises cellular phone.
31. equipment according to claim 17, said equipment comprise that wherein said a plurality of bags are described said low band excitation signal through being configured to launch the device of a plurality of bags consistent with the version of Internet Protocol.
32. equipment according to claim 17, said equipment comprise that wherein said a plurality of bags are described said low band excitation signal through being configured to receive the device of a plurality of bags consistent with the version of Internet Protocol.
CN2006800183519A 2005-04-01 2006-04-03 Systems, methods, and apparatus for highband excitation generation Active CN101184979B (en)

Applications Claiming Priority (5)

Application Number Priority Date Filing Date Title
US66790105P 2005-04-01 2005-04-01
US60/667,901 2005-04-01
US67396505P 2005-04-22 2005-04-22
US60/673,965 2005-04-22
PCT/US2006/012234 WO2006130221A1 (en) 2005-04-01 2006-04-03 Systems, methods, and apparatus for highband excitation generation

Publications (2)

Publication Number Publication Date
CN101184979A CN101184979A (en) 2008-05-21
CN101184979B true CN101184979B (en) 2012-04-25

Family

ID=39406063

Family Applications (8)

Application Number Title Priority Date Filing Date
CN2006800182696A Active CN101185120B (en) 2005-04-01 2006-04-03 Systems, methods, and apparatus for highband burst suppression
CN2006800182709A Active CN101185124B (en) 2005-04-01 2006-04-03 Method and apparatus for dividing frequency band coding of voice signal
CN2006800181496A Active CN101180677B (en) 2005-04-01 2006-04-03 Systems, methods, and apparatus for wideband speech coding
CN200680018213.0A Active CN101185127B (en) 2005-04-01 2006-04-03 Methods and apparatus for coding and decoding highband part of voice signal
CN2006800183538A Active CN101185125B (en) 2005-04-01 2006-04-03 Methods and apparatus for anti-sparseness filtering of spectrally extended voice prediction excitation signal
CN2006800181405A Active CN101180676B (en) 2005-04-01 2006-04-03 Methods and apparatus for quantization of spectral envelope representation
CN200680018212.6A Active CN101185126B (en) 2005-04-01 2006-04-03 Systems, methods, and apparatus for highband time warping
CN2006800183519A Active CN101184979B (en) 2005-04-01 2006-04-03 Systems, methods, and apparatus for highband excitation generation

Family Applications Before (7)

Application Number Title Priority Date Filing Date
CN2006800182696A Active CN101185120B (en) 2005-04-01 2006-04-03 Systems, methods, and apparatus for highband burst suppression
CN2006800182709A Active CN101185124B (en) 2005-04-01 2006-04-03 Method and apparatus for dividing frequency band coding of voice signal
CN2006800181496A Active CN101180677B (en) 2005-04-01 2006-04-03 Systems, methods, and apparatus for wideband speech coding
CN200680018213.0A Active CN101185127B (en) 2005-04-01 2006-04-03 Methods and apparatus for coding and decoding highband part of voice signal
CN2006800183538A Active CN101185125B (en) 2005-04-01 2006-04-03 Methods and apparatus for anti-sparseness filtering of spectrally extended voice prediction excitation signal
CN2006800181405A Active CN101180676B (en) 2005-04-01 2006-04-03 Methods and apparatus for quantization of spectral envelope representation
CN200680018212.6A Active CN101185126B (en) 2005-04-01 2006-04-03 Systems, methods, and apparatus for highband time warping

Country Status (3)

Country Link
CN (8) CN101185120B (en)
ES (3) ES2351935T3 (en)
UA (6) UA94041C2 (en)

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN111179963A (en) * 2013-07-22 2020-05-19 弗劳恩霍夫应用研究促进协会 Audio signal decoding and encoding apparatus and method with adaptive spectral tile selection

Families Citing this family (39)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
SG161223A1 (en) 2005-04-01 2010-05-27 Qualcomm Inc Method and apparatus for vector quantizing of a spectral envelope representation
CN101620854B (en) * 2008-06-30 2012-04-04 华为技术有限公司 Method, system and device for band extension
CN101964690B (en) * 2009-07-22 2012-07-04 联芯科技有限公司 HARQ merged decoding method, device and system
CN102044250B (en) * 2009-10-23 2012-06-27 华为技术有限公司 Band spreading method and apparatus
EP2551848A4 (en) * 2010-03-23 2016-07-27 Lg Electronics Inc Method and apparatus for processing an audio signal
CN102610231B (en) 2011-01-24 2013-10-09 华为技术有限公司 Method and device for expanding bandwidth
ES2916257T3 (en) * 2011-02-18 2022-06-29 Ntt Docomo Inc Voice decoder, voice scrambler, voice decoding method, voice coding method, voice decoding program, and voice coding program
US9070361B2 (en) * 2011-06-10 2015-06-30 Google Technology Holdings LLC Method and apparatus for encoding a wideband speech signal utilizing downmixing of a highband component
EP2774145B1 (en) * 2011-11-03 2020-06-17 VoiceAge EVS LLC Improving non-speech content for low rate celp decoder
CN102543091B (en) * 2011-12-29 2014-12-24 深圳万兴信息科技股份有限公司 System and method for generating simulation sound effect
ES2568640T3 (en) * 2012-02-23 2016-05-03 Dolby International Ab Procedures and systems to efficiently recover high frequency audio content
ES2689072T3 (en) * 2012-05-23 2018-11-08 Nippon Telegraph And Telephone Corporation Encoding an audio signal
CN105551497B (en) 2013-01-15 2019-03-19 华为技术有限公司 Coding method, coding/decoding method, encoding apparatus and decoding apparatus
US9728200B2 (en) * 2013-01-29 2017-08-08 Qualcomm Incorporated Systems, methods, apparatus, and computer-readable media for adaptive formant sharpening in linear prediction coding
CN106847297B (en) * 2013-01-29 2020-07-07 华为技术有限公司 Prediction method of high-frequency band signal, encoding/decoding device
US9601125B2 (en) * 2013-02-08 2017-03-21 Qualcomm Incorporated Systems and methods of performing noise modulation and gain adjustment
US9711156B2 (en) * 2013-02-08 2017-07-18 Qualcomm Incorporated Systems and methods of performing filtering for gain determination
EP2830055A1 (en) 2013-07-22 2015-01-28 Fraunhofer-Gesellschaft zur Förderung der angewandten Forschung e.V. Context-based entropy coding of sample values of a spectral envelope
US9620134B2 (en) * 2013-10-10 2017-04-11 Qualcomm Incorporated Gain shape estimation for improved tracking of high-band temporal characteristics
US10083708B2 (en) * 2013-10-11 2018-09-25 Qualcomm Incorporated Estimation of mixing factors to generate high-band excitation signal
US9384746B2 (en) * 2013-10-14 2016-07-05 Qualcomm Incorporated Systems and methods of energy-scaled signal processing
US9293143B2 (en) * 2013-12-11 2016-03-22 Qualcomm Incorporated Bandwidth extension mode selection
US20150170655A1 (en) * 2013-12-15 2015-06-18 Qualcomm Incorporated Systems and methods of blind bandwidth extension
US10163447B2 (en) * 2013-12-16 2018-12-25 Qualcomm Incorporated High-band signal modeling
CN103714822B (en) * 2013-12-27 2017-01-11 广州华多网络科技有限公司 Sub-band coding and decoding method and device based on SILK coder decoder
US9984699B2 (en) * 2014-06-26 2018-05-29 Qualcomm Incorporated High-band signal coding using mismatched frequency ranges
CN106448688B (en) * 2014-07-28 2019-11-05 华为技术有限公司 Audio coding method and relevant apparatus
EP2980798A1 (en) * 2014-07-28 2016-02-03 Fraunhofer-Gesellschaft zur Förderung der angewandten Forschung e.V. Harmonicity-dependent controlling of a harmonic filter tool
US9595269B2 (en) * 2015-01-19 2017-03-14 Qualcomm Incorporated Scaling for gain shape circuitry
WO2016142002A1 (en) 2015-03-09 2016-09-15 Fraunhofer-Gesellschaft Zur Foerderung Der Angewandten Forschung E.V. Audio encoder, audio decoder, method for encoding an audio signal and method for decoding an encoded audio signal
US10847170B2 (en) * 2015-06-18 2020-11-24 Qualcomm Incorporated Device and method for generating a high-band signal from non-linearly processed sub-ranges
FI3696813T3 (en) 2016-04-12 2023-01-31 Audio encoder for encoding an audio signal, method for encoding an audio signal and computer program under consideration of a detected peak spectral region in an upper frequency band
CN110050304B (en) * 2016-12-16 2022-11-29 瑞典爱立信有限公司 Method, encoder and decoder for processing envelope representation coefficients
US10825467B2 (en) * 2017-04-21 2020-11-03 Qualcomm Incorporated Non-harmonic speech detection and bandwidth extension in a multi-source environment
US10431231B2 (en) * 2017-06-29 2019-10-01 Qualcomm Incorporated High-band residual prediction with time-domain inter-channel bandwidth extension
TWI723545B (en) * 2019-09-17 2021-04-01 宏碁股份有限公司 Speech processing method and device thereof
WO2020118321A2 (en) * 2020-02-14 2020-06-11 Futurewei Technologies, Inc. Multi-rate crest factor reduction
CN111402907B (en) * 2020-03-13 2023-04-18 大连理工大学 G.722.1-based multi-description speech coding method
US11935546B2 (en) * 2021-08-19 2024-03-19 Semiconductor Components Industries, Llc Transmission error robust ADPCM compressor with enhanced response

Citations (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP1300833A2 (en) * 2001-10-04 2003-04-09 AT&T Corp. A method of bandwidth extension for narrow-band speech
CN1455390A (en) * 2002-04-30 2003-11-12 Lg电子株式会社 Apparatus and method for estimating harmonic wave of sound coder

Family Cites Families (23)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4805193A (en) * 1987-06-04 1989-02-14 Motorola, Inc. Protection of energy information in sub-band coding
US5455888A (en) * 1992-12-04 1995-10-03 Northern Telecom Limited Speech bandwidth extension method and apparatus
EP0732687B2 (en) * 1995-03-13 2005-10-12 Matsushita Electric Industrial Co., Ltd. Apparatus for expanding speech bandwidth
US6097824A (en) * 1997-06-06 2000-08-01 Audiologic, Incorporated Continuous frequency dynamic range audio compressor
FI113571B (en) * 1998-03-09 2004-05-14 Nokia Corp speech Coding
US6829360B1 (en) * 1999-05-14 2004-12-07 Matsushita Electric Industrial Co., Ltd. Method and apparatus for expanding band of audio signal
US6393394B1 (en) * 1999-07-19 2002-05-21 Qualcomm Incorporated Method and apparatus for interleaving line spectral information quantization methods in a speech coder
JP4792613B2 (en) * 1999-09-29 2011-10-12 ソニー株式会社 Information processing apparatus and method, and recording medium
WO2001037263A1 (en) * 1999-11-16 2001-05-25 Koninklijke Philips Electronics N.V. Wideband audio transmission system
AU2547201A (en) * 2000-01-11 2001-07-24 Matsushita Electric Industrial Co., Ltd. Multi-mode voice encoding device and decoding device
US6704711B2 (en) * 2000-01-28 2004-03-09 Telefonaktiebolaget Lm Ericsson (Publ) System and method for modifying speech signals
US6732070B1 (en) * 2000-02-16 2004-05-04 Nokia Mobile Phones, Ltd. Wideband speech codec using a higher sampling rate in analysis and synthesis filtering than in excitation searching
US6947888B1 (en) * 2000-10-17 2005-09-20 Qualcomm Incorporated Method and apparatus for high performance low bit-rate coding of unvoiced speech
US6615169B1 (en) * 2000-10-18 2003-09-02 Nokia Corporation High frequency enhancement layer coding in wideband speech codec
MXPA03002115A (en) * 2001-07-13 2003-08-26 Matsushita Electric Ind Co Ltd Audio signal decoding device and audio signal encoding device.
DE60208426T2 (en) * 2001-11-02 2006-08-24 Matsushita Electric Industrial Co., Ltd., Kadoma DEVICE FOR SIGNAL CODING, SIGNAL DECODING AND SYSTEM FOR DISTRIBUTING AUDIO DATA
ES2268112T3 (en) * 2001-11-14 2007-03-16 Matsushita Electric Industrial Co., Ltd. AUDIO CODING AND DECODING.
EP1444688B1 (en) * 2001-11-14 2006-08-16 Matsushita Electric Industrial Co., Ltd. Encoding device and decoding device
WO2003065353A1 (en) * 2002-01-30 2003-08-07 Matsushita Electric Industrial Co., Ltd. Audio encoding and decoding device and methods thereof
BRPI0305710B1 (en) * 2002-08-01 2017-11-07 Panasonic Corporation "APPARATUS AND METHOD OF DECODING OF AUDIO"
CN1186765C (en) * 2002-12-19 2005-01-26 北京工业大学 Method for encoding 2.3kb/s harmonic wave excidted linear prediction speech
FI118550B (en) * 2003-07-14 2007-12-14 Nokia Corp Enhanced excitation for higher frequency band coding in a codec utilizing band splitting based coding methods
CN1598926A (en) * 2003-09-16 2005-03-23 株式会社东芝 Audio coding method and equipment with noise restaining

Patent Citations (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP1300833A2 (en) * 2001-10-04 2003-04-09 AT&T Corp. A method of bandwidth extension for narrow-band speech
CN1455390A (en) * 2002-04-30 2003-11-12 Lg电子株式会社 Apparatus and method for estimating harmonic wave of sound coder

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
同上.

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN111179963A (en) * 2013-07-22 2020-05-19 弗劳恩霍夫应用研究促进协会 Audio signal decoding and encoding apparatus and method with adaptive spectral tile selection

Also Published As

Publication number Publication date
UA95776C2 (en) 2011-09-12
CN101185126A (en) 2008-05-21
UA94041C2 (en) 2011-04-11
CN101185127B (en) 2014-04-23
CN101185120A (en) 2008-05-21
ES2350494T3 (en) 2011-01-24
CN101185125B (en) 2012-01-11
UA92341C2 (en) 2010-10-25
UA91853C2 (en) 2010-09-10
CN101180677A (en) 2008-05-14
CN101184979A (en) 2008-05-21
ES2358125T3 (en) 2011-05-05
CN101185124B (en) 2012-01-11
CN101185120B (en) 2012-05-30
ES2351935T3 (en) 2011-02-14
CN101180676B (en) 2011-12-14
CN101180676A (en) 2008-05-14
CN101185127A (en) 2008-05-21
CN101185124A (en) 2008-05-21
UA93677C2 (en) 2011-03-10
CN101185125A (en) 2008-05-21
CN101180677B (en) 2011-02-09
UA92742C2 (en) 2010-12-10
CN101185126B (en) 2014-08-06

Similar Documents

Publication Publication Date Title
CN101184979B (en) Systems, methods, and apparatus for highband excitation generation
CN102110440B (en) System, method, and apparatus for gain factor attenuation
CN102411935B (en) Method and apparatus of anti-sparseness filtering for wideband extension speech predication excitation signal
CN104123946A (en) Systemand method for including identifier with packet associated with speech signal
CN101496097A (en) Systems and methods for including an identifier with a packet associated with a speech signal

Legal Events

Date Code Title Description
C06 Publication
PB01 Publication
C10 Entry into substantive examination
SE01 Entry into force of request for substantive examination
REG Reference to a national code

Ref country code: HK

Ref legal event code: DE

Ref document number: 1114901

Country of ref document: HK

C14 Grant of patent or utility model
GR01 Patent grant
REG Reference to a national code

Ref country code: HK

Ref legal event code: GR

Ref document number: 1114901

Country of ref document: HK