CN101090386B - Device and method for frequency domain demodulation of block transmission system based on filter bank - Google Patents
Device and method for frequency domain demodulation of block transmission system based on filter bank Download PDFInfo
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Abstract
本发明涉及一种基于滤波器组的分块传输系统频域解调装置及其方法，先对接收的数据块做Q＝DxN点的DFT变换，将时域数据变换到频域；然后根据各子带占用频谱对应的均衡子载波位置和估计的各均衡子载波信道频率响应，对每个均衡子载波做单点ZF或MMMSE均衡；接着针对各占用的子带频域子载波位置，分别进行匹配滤波，能量收集和频偏补偿操作；然后采用多个D点IFFT，分别将各个子带的频域数据变换到时域，最后K点逆正交变换装置，对输入的K个并串转换装置输出的符号序列进行K点逆正交变换，完成滤波器组传输信号的解调。本发明与现有技术相比，基于频域均衡和频域滤波器组解调的接收方法在保持相同性能的条件下，具有更低的实现复杂度。
The present invention relates to a frequency domain demodulation device and method for a block transmission system based on a filter bank. Firstly, DFT transformation of Q=DxN points is performed on the received data block, and the time domain data is transformed into the frequency domain; then according to each Perform single-point ZF or MMMSE equalization on each equalized subcarrier for the equalized subcarrier position corresponding to the subband occupied spectrum and the estimated channel frequency response of each equalized subcarrier; Matched filtering, energy collection and frequency offset compensation operations; then multiple D-point IFFTs are used to transform the frequency domain data of each sub-band into the time domain, and finally the K-point inverse orthogonal transformation device converts the input K parallel-to-serial The symbol sequence output by the device is subjected to K-point inverse orthogonal transformation to complete the demodulation of the filter bank transmission signal. Compared with the prior art, the receiving method based on frequency domain equalization and frequency domain filter bank demodulation has lower implementation complexity under the condition of maintaining the same performance.
Description
Technical field
The present invention relates to a kind of wide-band mobile communication, the fdma system of the bank of filters in mobile communication and the digital communication (FDMA).
Background technology
In recent years, wireless communication system develops rapidly towards the broadband direction; Be accompanied by this development trend, the bandwidth that wireless communication system occupies is more and more higher, and transmission rate is more and more higher, and spectrum efficiency also requires more and more higher.In wideband wireless mobile communication system and broadband radio access network, require a plurality of users to insert simultaneously, need to adopt multiple access technology.Usually the multiple access technology that adopts mainly contains three kinds: frequency division multiple access, time division multiple access and code division multiple access.The frequency division multiple access technology is that user's information distribution is transmitted to the carrier channel of different frequency.Tdma is that different information distribution is transmitted to different time slots, and a carrier wave can transmit a plurality of users' information by time slot, and the number of users of transmission depends on the number of time slot.CDMA (Code Division Multiple Access) adopts spread spectrum communication mode, a plurality of users' of the pseudo noise code modulation that it can be different with transmission on the same carrier wave at one time signal.According to discovering in recent years, for the throughput of effective elevator system, the combination multiple access technology of frequency division multiple access technology (FDMA) and tdma (TDMA) will become the main multiple access technology of future mobile.Existing fdma system mainly contains two kinds of implementations, and a kind of fdma system that is based on the OFDM technology is as OFDM (OFDMA) [1] with based on OFDM (DFT-S-OFDMA) system of DFT spread-spectrum; Another kind is based on the fdma system of bank of filters technology, as filtering multitone (FMT) [3], and generalized multi-carrier (GMC) and based on generalized multi-carrier (GMC) the frequency division multiple access scheme DFT-S-GMC of discrete Fourier transform (DFT) (DFT).Based on the fdma system of OFDM technology, have the multiple access that synchronous error is caused and disturb responsive defective.Bandwidth based on each subband of fdma system of bank of filters technology is bigger with respect to carrier wave frequency deviation and Doppler frequency shift; has certain frequency domain protection simultaneously between each subband at interval; the frequency spectrum of each subband has precipitous attenuation outside a channel in addition, disturbs between the multi-user that these features make this system cause carrier wave frequency deviation and timing error to have stronger robustness.
The reception programme of existing fdma system based on bank of filters (DFT-S-GMC) adopts single carrier frequency domain equalization and bank of filters time domain implementation structure (as Li Mingqi, Zhang Xiaodong, Li Yuanjie, Zhou Bin, " based on the generalized multiple carrier frequency division multiple access ul transmissions scheme-DFT-S-GMC of DFT spread spectrum ", telecommunications science (B3G monograph), the 6th phase, 2006; XiaodongZhang, Mingqi Li, Honglin Hu Haifeng Wang Bin Zhou, Xiaohu You, " DFT SpreadGeneralized Multi-Carrier Scheme For Broadband Mobile Communications ", PIMRC2006.).Adopt single carrier frequency domain equalization to need earlier the data block that receives to be done the DFT conversion of Q (Q=DxN) point, time domain data is transformed to frequency domain.Take the balanced sub-carrier positions of frequency spectrum correspondence and each balanced sub-carrier channels frequency response of estimation according to each subband then, each balanced subcarrier is done single-point ZF or MMMSE equilibrium.Then again balanced data is done the IDFT conversion that Q is ordered, frequency domain data is transformed to time domain.Therefore, adopt single carrier frequency domain equalization need carry out the Fourier transform of counting more greatly for twice, its computational complexity is higher.In addition, when many Methods of Subband Filter Banks adopt non-critical sampling (the up-sampling rate N of bank of filters prototype filter is greater than the number of sub-bands of bank of filters), adopt time domain filtering group implementation structure also higher complexity will be arranged.
Summary of the invention
The present invention is in the time of will solving the reception programme of existing fdma system based on bank of filters (DFT-S-GMC) employing single carrier frequency domain equalization and bank of filters time domain implementation structure, single carrier frequency domain equalization need carry out the Fourier transform of counting more greatly for twice, and its computational complexity is higher; And when many Methods of Subband Filter Banks adopt non-critical sampling (the up-sampling rate N of bank of filters prototype filter is greater than the number of sub-bands of bank of filters), the time domain filtering group implementation structure complexity technical problems of high that it adopts, and a kind of block transmission system frequency field demodulation device and method thereof based on bank of filters is provided.
Technical solution of the present invention is a kind of block transmission system frequency field demodulation device based on bank of filters, comprise the Cyclic Prefix removal device in the receiver, string and conversion equipment, Q point FFT converting means, the balanced subcarrier of subband is separated mapping device, inverse orthogonal transformation device that subband balancer, K are ordered and parallel/serial conversion equipment are characterized in: also comprise the subband matched filter, energy collecting device, the compensate of frequency deviation device, D point IFFT converting means, wherein:
The subband matched filter is used for the signal phasor of the balanced output of each subband is carried out the frequency domain matched filtering;
Energy collecting device is used for the signal energy at each subband spectrum edge is collected;
The compensate of frequency deviation device is used to compensate the frequency shift (FS) of each subband;
D point IFFT converting means is used for each the subband frequency-region signal behind the compensate of frequency deviation is transformed to time-domain signal.
String and conversion equipment are used for the serial data sequence of input is converted to the parallel data sequence.
And the string conversion equipment, be used for the parallel data block sequence of input is carried out and gone here and there conversion operations or be used for each the subband time-domain signal sequence after the IFFT conversion is carried out and gone here and there conversion operations.
Q point FFT converting means is used for the parallel data sequence of input is carried out Q point FFT conversion.
The balanced subcarrier of subband is separated mapping device, is used for extracting the signal phasor that receives on each subband frequency domain equalization subcarrier by the number of sub carrier wave and the sequence number of each subband spectrum correspondence of CU.
The subband balancer is used for each subband signal of separating the mapping extraction through the balanced subcarrier of subband is carried out equilibrium respectively.
K point inverse orthogonal transformation device is used for the K of input and the symbol sebolic addressing of conversion equipment output of going here and there are carried out K point inverse orthogonal transformation.
Technical method of the present invention is: a kind of frequency domain of block transmission system demodulation method based on bank of filters: earlier the data block that receives is done the DFT conversion that Q=DxN is ordered, time domain data is transformed to frequency domain; Take the balanced sub-carrier positions of frequency spectrum correspondence and each balanced sub-carrier channels frequency response of estimation according to each subband then, each balanced subcarrier is done single-point ZF or MMMSE equilibrium; Then, carry out matched filtering respectively, collection of energy and compensate of frequency deviation operation at the subband subcarrier in frequency domain position that respectively takies; Adopt a plurality of D point IFFT then, frequency domain data with each subband transforms to time domain respectively, last K point inverse orthogonal transformation device, according to transmitting terminal orthogonal transform rule, the K of input and the symbol sebolic addressing of conversion equipment output of going here and there are carried out K point inverse orthogonal transformation, finish the demodulation of bank of filters transmission signals.
The present invention with compare with time domain filtering demodulated received method based on single carrier frequency domain equalization, under the condition that keeps identical performance, have lower implementation complexity based on the method for reseptance of frequency domain equalization and frequency domain filter group demodulation.And the receiver complexity that adopts frequency-domain demodulation is less than the receiver complexity that adopts the time domain demodulation, especially at receiving terminal to each user's independence demodulation, the less situation of each CU number of sub-bands simultaneously.As taking 28 subbands when (expiring subband), the real multiplier of frequency-domain demodulation is about 1/2nd of time domain demodulation; And when taking 1 subband, the real multiplier of frequency-domain demodulation has only 1/3rd of time domain demodulation.
Description of drawings
Fig. 1 is based on the block diagram of transmitter of the fdma system of the many Methods of Subband Filter Banks of time domain loop structure;
The block diagram of the receiver of the fdma system that many Methods of Subband Filter Banks that are based on Fig. 2 realize;
Fig. 3 is that loop-around data becomes the block operations schematic diagram;
Fig. 4 is a data block collection of energy operation chart;
DFT-S-GMC systematic bits bit error rate performance figure when Fig. 5 is 1 subband;
DFT-S-GMC systematic bits bit error rate performance figure when Fig. 6 is 6 subbands.
Embodiment
Below in conjunction with specific embodiment, further set forth the present invention.Should be understood that these embodiment only to be used to the present invention is described and be not used in and limit the scope of the invention.Should be understood that in addition those skilled in the art can make various changes or modifications the present invention after the content of having read the present invention's instruction, these equivalent form of values fall within the application's appended claims institute restricted portion equally.
A kind of block transmission system frequency field demodulation device based on bank of filters of the present invention is used for the receiver of the fdma system realized based on the transmitter of the fdma system of the many Methods of Subband Filter Banks of time domain loop structure with based on many Methods of Subband Filter Banks.
Fig. 1 illustrates a kind of block diagram of transmitter of the fdma system based on the many Methods of Subband Filter Banks of time domain loop structure.Comprising a data block segmenting device 10, string and conversion equipment 11, the orthogonal converter that K is ordered 12, subband mapping device 13,15, one loop-around datas of the inverse filterbank conversion (IFBT) that M is ordered device 14, displacements adding up device become block assembly 16 and a Cyclic Prefix adding set 17.
Suppose { a
n, n=0,1,2....} is the serial modulated symbols sequence that is input to the data block segmenting device 10 of transmitter; Data block segmenting device 10 is used for symbol modulated string character data sequence { a
n, n=0,1,2....} is divided into string character sequence of blocks of data { b
k, k=0,1,2..., D-1}, here, b
kRepresent that a number of elements equals the row vector of K, wherein D be the IFBT number of symbols of stack in its backward shift adding up device 15, and K is the counting of FFT conversion in the FFT converting means 12 thereafter.Because emitter is identical and is independently the operation of each serial data block of input, therefore only describes the operation to a serial data block of emission and receiving system in scheme is thereafter described.
String and conversion equipment 11 are used for string character sequence of blocks of data { b
k, k=0,1,2..., each data block is gone here and there and conversion operations among the D-1}, to form D parallel symbol data block { c
k, k=0,1 ..., D-1}, here, { c
k(n ') } number of elements of expression and the same column vector of FFT transform size K;
Displacement adding up device 15, be used for and the sequence of blocks of data of string conversion output by the N stack that is shifted at interval of the shift-orthogonal of the prototype filter of multiphase filter correspondence.Particularly, at k constantly, with k-1 constantly the length that generates of waveform synthesizer be that the preceding N point data of the data sequence of L sends, get remaining L-N point data again, after afterbody adds N zero, with k constantly and the L point data piece { g of string conversion output
k(n), n=0,1,2..., the L-1} addition constitutes new L point data sequence; And k+1 constantly will this newly-generated L point sequence preceding N point data send, get remaining L-N point data again, after afterbody adds N zero, with k+1 constantly and the L point data piece { g that exports of string conversion
K+1(n), n=0,1,2..., the L-1} addition constitutes the data updated sequence.So go round and begin again.Through the displacement adding up device, the sequence of blocks of data of input serial is transformed into corresponding data block sequence { s (n), n=0,1,2..., E-1}.And relation is each other obeyed
Obviously, the length of sequence s (n) is E=(D-1) * N+L, and wherein L is a prototype filter length, and N is prototype filter shift-orthogonal interval; Loop-around data becomes block assembly 16, is used for the data sequence after synthetic through waveform is carried out buffer memory, blocks piecemeal and the waveform overlap-add operation that circulates from beginning to end, and it is operated as shown in Figure 3.At first, buffer storage length is the synthetic back of the waveform output sequence of E.Be that the data sequence of E is divided into length and is respectively F1 then with the length of buffer memory, the three segment data pieces of Q and F2 make E=F1+Q+F2.Preferably, Q=D * N.Select D and N, make Q 〉=F1+F2.The three segment data pieces that will be divided into the at last stack that circulates from beginning to end, the last F1 point data stack of the Q point data piece of the preceding F1 point data of intercepting and intercepting soon, simultaneously, with the preceding F2 point data stack of the Q point data piece of back F2 point data and the intercepting of intercepting, formation length is the cycling wave form sequence of Q
Because Q is the integral multiple of IFBT number of symbols D multiplexing in each data block, sequence
Be the continuous cyclic sequences of head and the tail.In fact, output sequence can be expressed as
N=0,1 ..., Q-1, (())
QExpression delivery Q computing.
Cyclic Prefix adding set 17, the protection that is used for adding a length-specific in the head or tail portion of cycling wave form sequence are used to reduce interchannel interference (preferably, this protection length at interval should greater than channel maximum delay extension length) at interval.Preferably, protection adding set at interval can be adopted Cyclic Prefix (CP) adding set, and a part that also is about to described data block afterbody copies to its front end, forms the data block symbols of final band CP.Through Cyclic Prefix adding set, input data sequence
Be transformed into complete data block symbols sequence t (n), n=0,1 ..., P-1}, wherein, P=Q+C, C are circulating prefix-length.
Fig. 2 illustrates a kind of block diagram of receiver of the fdma system of realizing based on many Methods of Subband Filter Banks.Comprising 30, one strings of a Cyclic Prefix removal device and 31, one Q points of conversion equipment FFT converting means 32, the balanced subcarrier of subband is separated mapping device 33, and K subband balancer (only illustrates three 340 for simplicity's sake, among Fig. 1,341,342), K subband matched filter (for simplicity's sake, only illustrate three 350,351 among Fig. 1,352), K energy collecting device (only illustrates three 360,361 for simplicity's sake, among Fig. 1,362), K compensate of frequency deviation device (only illustrates three 370,371 for simplicity's sake, among Fig. 1,372), K D point IFFT converting means (only illustrates three 380,381 for simplicity's sake, among Fig. 1,382), the K and the conversion equipment of going here and there (only illustrate three 390,391 for simplicity's sake, among Fig. 1,392), an inverse orthogonal transformation device 40 and parallel/serial conversion equipment 41 that K is ordered.
Especially, for the communication system up link, the receiving system of Fig. 2 example is only at a user's received signal.Receive for the multi-user, both can adopt the receiving system of a cover respectively at each user as Fig. 2, also can separate mapping device 33 all devices before, and adopt a cover belt carrier wave to separate mapping device 33 all devices afterwards respectively at each user to the shared subband subcarrier of all users.
Suppose the receiver ideal synchronisation, and supposition r (n), and n=0,1 ..., P-1} is the string character sequence that is input to the Cyclic Prefix removal device 30 of receiver;
Cyclic Prefix removal device 30 is used for adding rule according to the transmitting terminal Cyclic Prefix, C sampled value before in the data block cast out, formation length be Q serial data sequence o (n), n=0,1,2 ..., Q-1};
The string and conversion equipment 31, be used for will the input serial data sequence o (n), n=0,1,2 ..., Q-1} be converted to the parallel data sequence p (n), n=0,1,2 ..., Q-1};
Q point FFT converting means 32, be used for to the input the parallel data sequence p (n), n=0,1,2 ..., Q-1} carries out Q point FFT conversion.Through the FFT conversion, the parallel data sequence of input be transformed into corresponding parallel data sequence q (k), k=0,1,2 ..., Q-1}, relation is each other obeyed
The balanced subcarrier of subband is separated mapping device 33, is used for extracting the signal phasor that receives on each subband frequency domain equalization subcarrier by the number of sub carrier wave and the sequence number of each subband spectrum correspondence of CU.The balanced number of sub carrier wave that each subband takies is W
l(l=0, L, K-1), and
Q is that frequency domain equalization FFT conversion is counted, and M is a bank of filters sub-band sum order.Because the balanced number of sub carrier wave of each subband is necessary for integer, therefore, when Q is not the integral multiple of M, that is W is when being non-integer, and the balanced number of sub carrier wave that each subband takies can round off between adjacent sub-bands accordingly.The balanced number of sub carrier wave of each subband this moment can be inequality, but the balanced number of sub carrier wave sum of all subbands should equal Q.Be without loss of generality, suppose that the balanced number of sub carrier wave of l subband taking is W
l(K-1), and corresponding balanced subcarrier sequence number is k for l=0, L
l+ (0:W
l-1), k
lIt is the balanced sub-carrier offset amount of l subband.Separate mapping through the balanced subcarrier of subband, for l subband, the signal phasor that is used for frequency domain equalization of output is t
lAnd t (k)=q (k (k),
l+ k), k=0, L, W
l-1.Because Q=N * D, and N 〉=M, so W
l〉=D.
Subband balancer 340,341,342 is used for each subband signal of separating the mapping extraction through the balanced subcarrier of subband is carried out equilibrium respectively.Through the subband equilibrium, (l=0, L, K-1) individual subband, the signal phasor behind the frequency domain equalization of output are u (k), and u for l
l(k)=t
l(k) h (k
l+ k), k=0, L, W
l-1.Wherein, h (k
l+ k) be k
lThe frequency domain equalization coefficient of+k subcarrier.For ZF (ZF) equilibrium,
For least mean-square error (MMSE) equilibrium,
H (k
l+ k) be k
lThe channel frequency response of+k frequency domain equalization subcarrier.σ
2Be the noise variance on the frequency domain equalization subcarrier.
Subband matched filter 350,351,352 is used for the signal phasor of the balanced output of each subband is carried out the frequency domain matched filtering, promptly is that the signal phasor that each subband frequency domain equalization is exported be multiply by the conjugation of respective sub-bands frequency response.For l (l=0, L, K-1) individual subband, sub-bands of frequencies response is
K=0, L, W
l-1, f wherein "
P, l(n)=f '
P, l((n+F1))
Q, n=0, L, Q-1, f '
P, l(n)=f
p(n) exp (j2 π ln/M), n=0, L, L-1, and { f
p(n), n=0,1,2..., L-1} are bank of filters prototype filter coefficient (that is impulse response), F1 becomes the length of the first segment data piece of intercepting in the block assembly 16 for the transmitting terminal loop-around data.In fact, for given system parameters, each sub-bands of frequencies response is constant, can produce by off-line.Through the subband matched filter, for l subband, the signal phasor of output is
K=0, L, W
l-1, and
K=0, L, W
l-1.
Energy collecting device 360,361,362 is used for the signal energy at each subband spectrum edge is collected.(K-1) individual subband promptly is to be W with length for l=0, L for l
l, frequency-region signal vector with raised cosine Energy distribution
K=0, L, W
lIt is D (D＜W that the energy at-1 two ends (that is the energy at l subband spectrum edge) is collected length
l), the signal phasor v with smooth Energy distribution
l(k) in.Preferably a kind of implementation method is, earlier with signal phasor
Be divided into length and be respectively D and W
lTwo sections sequences of the stem of-D and afterbody are then with preceding W in afterbody sequence and the stem sequence
lThe addition of-D point sequence constitutes the sequence v that length is D at last
l(k), k=0, L, D-1.Its operating process as shown in Figure 4.
Compensate of frequency deviation device 370,371,372 is used to compensate the frequency shift (FS) of each subband.Compensate of frequency deviation both can be realized in time domain, also can realize at frequency domain.Realize in time domain, need multiply by the phase compensation sequence to time domain sequences, so complexity is higher.And realize at frequency domain, only need carry out cyclic shift and get final product frequency domain sequence.Particularly, (K-1) individual subband is with the signal phasor v that obtains after the collection of energy for l=0, L for l
l(k), k=0, L, D-1, cyclic shift ξ to the right
lIndividual numerical point.ξ wherein
l=((k
l))
D, k
lBe the 1st frequency domain equalization sub-carrier offset amount of l subband.Through compensate of frequency deviation, for l subband, the signal phasor of output is
And
K=0, L, D-1.D point IFFT converting means 380,381,382 is used for each the subband frequency-region signal behind the compensate of frequency deviation
K=0, L, D-1 is transformed to time-domain signal.Through the IFFT conversion, (K-1) individual subband, the signal phasor of output are w for l=0, L for l
l(k '), k '=0, L, D-1, and
K ' 0, L, and D-1, here, { w
l(k ') } column vector that number of elements is D of expression;
And string conversion equipment 390,391 and 392, be used for each the subband time-domain signal sequence w after the IFFT conversion
l(k '), k '=0, L, D-1 carry out and go here and there conversion operations.Through and the string conversion equipment, for l (l=0, L, K-1) individual subband, the serial signal vector of output is x
l(k '), k '=0, L, D-1, here, { x
l(k ') } represent that a number of elements is the row vector of D;
K point inverse orthogonal transformation device 40 is used for the K of input and the symbol sebolic addressing x of conversion equipment output of going here and there
l(k '), k '=0, L, D-1 according to the rule of transmitting terminal orthogonal transform, carries out K point inverse orthogonal transformation.Adopt K point DFT conversion for transmitting terminal, receiving terminal adopts K point IDFT conversion, and then Shu Ru a K serial data sequence is transformed into D parallel data block sequence { y
K '(n '), k '=0,1 ..., D-1}, and
N ' 0, L, and K-1, k '=0,1 ..., D-1, here, { y
K '(n ') } column vector that number of elements is K of expression;
And string conversion equipment 41, be used for parallel data block sequence { y to input
K '(n '), n '=0, L, K-1, k '=0,1 ..., each parallel data block carries out respectively and goes here and there conversion operations among the D-1}.Process and string conversion equipment are output as serial data symbol sebolic addressing { z
k(n), n=0, L, K-1, k=0,1 ..., D-1} is used for the symbol demodulation and the decoding of receiving terminal, to recover the information bit of emission.Here, { z
k(n) } number of elements of expression is the row vector of K;
Embodiment:
System emulation and result
(1) system emulation parameter
Systematic sampling frequency 7.68MHz
Sub-band sum order (M): 28
Take number of sub-bands (K): 1 subband/6 subband
Prototype filter: root raised cosine
Prototype filter length (L): 392
Filter up-sampling rate (N): 32
Subband mapping mode: concentrate mapping (only at 6 subband situations)
Coded system/code check: Turbo (1/2)
Modulation system: QPSK
Antenna configurations: receive for 11
Channel model: PB (3km/h)
Equalization algorithm: MMSE frequency domain equalization
The frequency domain equalization Q:512 that counts
The multiplexing tilde of each data block is counted D:16
Contrast simulation system: frequency-domain demodulation method and time domain demodulation method
(2) simulation result
By Fig. 5 and Fig. 6 as seen, when adopting 1 and 6 subbands, based on the DFT-S-GMC systematic bits error rate of frequency-domain demodulation much at one, promptly adopt frequency-domain demodulation not cause systemic loss of energy.
(3) complexity relatively
Separate during table 1 and be in harmonious proportion the frequency-domain demodulation complexity relatively
Wherein Round (.) represents to round up computing.Once multiple removing is equivalent to 6 realities and takes advantage of with 2 realities and remove, and 28 FFT is equivalent to FFT and 7 FFT of 4 of 74 times, and 512 and 4 FFT adopt 2-base algorithms, 7 FFT employing WFTA algorithm (taking advantage of again for totally 9 times).
By table as seen, the receiver complexity that adopts frequency-domain demodulation is less than the receiver complexity that adopts the time domain demodulation, especially at receiving terminal (base station) to each user's independence demodulation, the less situation of each CU number of sub-bands of while.As taking 28 subbands when (expiring subband), the real multiplier of frequency-domain demodulation is about 1/2nd of time domain demodulation.And when taking 1 subband, the real multiplier of frequency-domain demodulation has only 1/3rd of time domain demodulation.
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| CN102611650B (en) * | 2011-11-22 | 2015-01-07 | 河南科技大学 | Frequency-domain channel estimation method and device of generalized multi-carrier system |
| CN102624468B (en) * | 2011-12-30 | 2014-09-10 | 成都中安频谱科技有限公司 | Automatic broadband detection method based on dual fast Fourier transformation (FFT) |
| CN103428128B (en) * | 2012-05-14 | 2016-09-14 | 南京中兴软件有限责任公司 | Interference elimination method and device |
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