CN101079577A - Voltage regulator having current canceling compensation - Google Patents
Voltage regulator having current canceling compensation Download PDFInfo
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- CN101079577A CN101079577A CN 200610136583 CN200610136583A CN101079577A CN 101079577 A CN101079577 A CN 101079577A CN 200610136583 CN200610136583 CN 200610136583 CN 200610136583 A CN200610136583 A CN 200610136583A CN 101079577 A CN101079577 A CN 101079577A
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- error amplifier
- network
- amplifier
- pwm
- gain
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Abstract
A voltage regulator which includes a network for improved compensation for reference voltage changes includes an IC including an error amplifier and a pulse width modulator (PWM), wherein an input of the PWM is coupled to an output of the error amplifier. A low pass filter comprising an inductor is in series with a grounded capacitor coupled to an output of the PWM, wherein an output of the regulator (Vout) is at a node between the inductor and the capacitor. A first feedback network is disposed between Vout and an inverting input of the error amplifier and a second feedback network is disposed between an output of the error amplifier and the inverting input of the error amplifier. A current cancellation network is coupled to the inverting input of the error amplifier. The current cancellation network injects a canceling current into the inverting input that is substantially equal in magnitude and opposite in polarity to current flowing through the second feedback network triggered by a change in reference voltage when applied to the error amplifier.
Description
The cross reference of related application
The application requires the priority of the 60/802nd, No. 949 provisional application of submission on May 24th, 2006, and its content integral body by reference is incorporated among the application.
Technical field
The present invention relates to the closed loop voltage regulator, relate in particular to the conversion regulator that is used to improve transient response with compensating network
Background technology
When selecting the compensate component value, usually in the value of the good response that allows load current step is changed with allow to exist between the value of good response that reference voltage is changed compromise for the closed loop voltage regulator.That is, when reference voltage and thus output voltage became a new value, variation provided fast that the component value of stable response may cause unacceptable overshoot level to load current step.
Fig. 1 illustrates the schematic diagram of typical closed-loop pulse-width modulation DC-DC transducer 100.In operation, with reference voltage V
REFBe applied to the noninvert input of error amplifier A1.The output of A1, promptly node COMP drives pulse width modulator PWM 125, and it exports PWM
OUTBy LF and CF filtering and become the output voltage V of the transducer of crossing over load RL
OUT
V
OUTWith the voltage at node COMP place one relation is arranged, be generally the gain that is arbitrarily designated as K1 and add a certain variation greater than 1.V
OUTFeed back to the node that is shown FB by the feedback network 110 that is shown resistor R FB among Fig. 1, the paraphase input of this node and A1 is shared.Be applied to another feedback network 120 shown in the square frame of dotted line limit between the node FB and node COMB of amplifier A1.Feedback network 120 shown in Fig. 1 comprises R1, C1, C
HFFeedback network 110 and 120 is provided with stability and other operating characteristic of transducer 100.Generally speaking, C
HFBe than the big a lot of impedance of C1, and can when the typical operation of analysis circuit 100, be left in the basket.
Under stable state, amplifier A1 is driven into V with the COMP node
COMPThereby, be driven into V
OUT, make the voltage (V at node FB place
FB) equal V
REFExcept that temporal effect, V
OUTEqual V
REFAnd V
FBWith V
REFEquate.Available have the R1 of quite long RC time constant and load current that the C1 value compensates specific pwm circuit best changes.
Yet, when in response to V
REFVariation the time, long RC time constant generally produces V
OUTIn unacceptable overshoot.With reference to Fig. 1 and 2, if V
REFVariable quantity is Δ V
REF, then A1 will make V
COMPChange Δ V
COMP, Δ V
COMPAnd then drive PWM, so that the V of expectation
OUTXWith the voltage V in the stable state
FBAlso change Δ V
REFNote, because have by PWM 125 and the gain K1 that comprises the low pass filter of LF and CF, so Δ V
COMPEqual Δ V
REF/ K1.This change in voltage that causes crossing over the tandem compound of R1 and C1 is Δ V
REFWith Δ V
REF/ K1's is poor.If V
REFChange Δ V
REF, the voltage of then crossing over R1-C1 becomes Δ V
REF-Δ V
REF/ K1, or Δ V
REF* (1-1/K1).If the impedance of R1 and C1 is designated as Z1, then generation equals Δ V
REF* the electric current I of (1-1/K1)/Z1 (R1-C1).
With reference to Fig. 1 and 2, if V
REFVariable quantity is Δ V
REF, then A1 is driven into V with node
COMP, V
COMPAnd then drive PWM, so that the V of expectation
OUTWith the voltage V in the stable state
FBAlso change Δ V
REFYet, because have by PWM 125 and the gain K1 that comprises the low pass filter of LF and CF, so V
COMPOnly change Δ V
REF/ K1.This voltage that causes crossing over the tandem compound of R1 and C1 is V
REFAnd V
COMPPoor.If V
REFChange Δ V
REF, the voltage of then crossing over R1-C1 becomes Δ V
REF-Δ V
REF/ K1, or Δ V
REF* (1-1/K1).If the impedance of R1 and C1 is designated as Z1, then generation equals Δ V
REF* the electric current I of (1-1/K1)/Z1 (R1-C1).
I (R1-C1) occurs in FB node place.Remove from V
OUTFlow through outside the feedback resistor RFB other path that is used for this electric current that is not associated with the FB node.Therefore will cause crossing over the voltage drop of RFB, thereby make actual V
OUTThe VFB that do not match has caused V
OUTWith V
REFMismatch.
Fig. 2 illustrates as R1, C1 considerable time V during the constant network is provided
REF=Δ V
REFThe analog response of each node of the transducer 100 that causes of variation.As noted above, because by PWM 125 and the gain K1 that comprises the low pass filter of LF and CF, V
COMP＜V
REFAs a result, seen I (R1-C1).This electric current causes the V of the reality seen
OUTClosely do not follow the trail of V
REF(the V that it equals to expect
OUT).This causes for V
REFVariation, V
OUTShown in the overshoot of not expecting, it generally forces the compromise of component value, such as reducing etc. of R1C1 time constant.Yet as noted above, the response that reduces 100 pairs of load current steps of circuit are changed of R1C1 time constant reduces.What need is the pulse width modulated converter design of the compensate component value of the trade-off of performance between a kind of response that allows to select to remove response that load current step is changed and reference voltage is changed.
Summary of the invention
A kind of voltage regulator comprises the IC that contains error amplifier and pulse width modulator (PWM), and wherein the output of error amplifier is coupled in the input of PWM.Comprise that the low pass filter of the inductor of connecting with ground capacitor is coupled to the output of modulator, wherein output (the V of adjuster
Out) node place between inductor and capacitor.First feedback network places V
OutAnd between the paraphase of the error amplifier input, and second feedback network places between the paraphase input of the output of error amplifier and error amplifier.The current canceling network coupled is to the paraphase input of error amplifier.This current canceling network injects to the paraphase input and equates substantially and opposite polarity counteracting electric current with the size of current that is flow through second feedback network by the change triggers of reference voltage when being applied to error amplifier.
The current canceling network preferably places between the paraphase and noninvert input of error amplifier.The current canceling network and comprises first amplifier (for example, operational amplifier) in one embodiment and constitutes the RC of the network that is driven by first amplifier preferably on IC.First amplifier generally provides the gain greater than 1.
In one embodiment, the time constant of the RC of formation network equals the time constant of second feedback network substantially.This arrangement allows to use identical R and C in each network.In one embodiment, first amplifier is on IC, and the output of first amplifier is connected on the IC bonding welding pad and connects with the external terminal as IC.
This voltage regulator can comprise the structure that supports at least one IC pin, and this IC pin provides fixed gain greater than 1 for first amplifier.In an embodiment of this arrangement, fixed gain can equal 2-1/ (by the gain of PWM and low pass filter).
Comprise among first amplifier and the embodiment of formation that at the current canceling network transducer also can comprise and be used to detect the gain of PWM and adjust the structure of first Amplifier Gain with the gain of tracking PWM by the RC of the network of first amplifier driving.
Voltage regulator is carried out current canceling comprise the step that a kind of voltage regulator is provided with the method for improving the compensation that reference voltage is changed, this voltage regulator comprises error amplifier and pulse width modulator (PWM), and wherein the output of error amplifier is coupled in the input of PWM; Be coupled to the low pass filter that comprises the inductor of connecting of the output of PWM, wherein output (the V of adjuster with ground capacitor
Out) node place between inductor and capacitor; Place V
OutAnd first feedback network between the paraphase of the error amplifier input and place the output of error amplifier and the paraphase input of error amplifier between second feedback network.The size of current that flows through second feedback network with being triggered by the change of the reference voltage that is applied to error amplifier equates substantially and opposite polarity counteracting electric current is injected in the paraphase input.
Cancellation network can comprise first amplifier and the RC that constitutes the network that is driven by first amplifier, is used to provide the counteracting electric current.In this is arranged, this method also can comprise the gain that detects PWM and adjust the step of first Amplifier Gain with the gain of following the trail of PWM, and the current canceling that wherein flows through by the electric current of second feedback network of the change triggers of the reference voltage that is applied to error amplifier automatically provides by the adjustment to first amplifier gain.
Being included as first amplifier at adjuster provides among at least one embodiment greater than the IC pin of 1 fixed gain, and this method can comprise that also the RC with the formation network of IC outside is connected this IC pin and is connected to step between the pin of error amplifier paraphase input.In this embodiment, this method can comprise also fixed gain is set as the step that equals 2-1/ (by the gain of PWM and low pass filter) that the impedance that wherein constitutes the RC of network equals the impedance of second feedback network.
Description of drawings
By can realizing understanding more comprehensively to reading over of the following detailed description and accompanying drawing, in the accompanying drawing to the present invention and feature and advantage thereof:
Fig. 1 shows the schematic diagram of the DC-DC transducer of known closed loop pulsewidth accent.
Fig. 2 shows the variation for reference voltage, the analog response at several nodes place of transducer 100 shown in Figure 1.
Fig. 3 illustrates and comprises the schematic diagram of the closed loop pulse-width modulation DC-DC transducer of exemplary current cancellation network according to an embodiment of the invention.
Fig. 4 illustrates for reference voltage (V
REF) variation, the response at several nodes place of converter circuit shown in Figure 3.
Embodiment
A kind of voltage regulator comprises the error amplifier that is coupled to pulse width modulator (PWM), and wherein the input of PWM is connected to the output of error amplifier.Comprise that the low pass filter of the inductor of connecting with ground capacitor is coupled to the output of modulator, wherein output (the V of adjuster
Out) node place between inductor and capacitor.First feedback network places V
OutAnd between the paraphase of the error amplifier input, and second feedback network places between the paraphase input of the output of error amplifier and error amplifier.Current canceling network according to the present invention places between the noninvert input of the paraphase input of error amplifier and error amplifier.
The current canceling network injects automatically to node FB and equates and opposite polarity electric current substantially that with I (R1-C1) size I (R1-C1) is as above described at V with respect to circuit shown in Figure 1 100
REFFlow through R during the variation
FBAs a result, the current canceling that enters node FB leaves the electric current of this node, because they are opposite polarities." equal substantially " used herein generally refers to the enough injection currents of coupling equally of I (R1-C1) and makes at V
REFV during the variation
OUTOvershoot is reduced to predetermined maximum acceptable level, such as＜10mV etc.If between electric current that provides by the current canceling network and I (R1-C1) electric current, mismatch is arranged, then also can there be the overshoot that reduces of several mV, the size of overshoot is that current mismatch multiply by R
FBResistance value.For example, if the 3mV overshoot is a maximum receivable level, then require this current mismatch less than 3mV/R
FB
Therefore, offset and to eliminate or at least significantly reduced V substantially
REFWhat take place during variation flows through R
FBElectric current.Because V
FBKeep equaling substantially V
OUTSo, can eliminate substantially because V
REFChange the overshoot that causes.Therefore, have according to the closed loop voltage regulator of current canceling network of the present invention and removed compromise when selecting the compensate component value, and allow the good response to the variation of load current step and reference voltage thus.
With reference to figure 3, show closed loop pulse-width modulation DC-DC transducer 300, it comprises according to of the present invention by the exemplary current cancellation network 320 shown in the square frame of dotted line limit.Other assembly of transducer 300 is generally identical with the assembly of describing with respect to the transducer shown in Fig. 1 100.Only for simplicity, suppose that transducer 300 has and transducer 100 identical construction, and also correspondingly quote for similar assembly.
Exemplary current cancellation network 320 shown in Fig. 3 comprises amplifier 315, and it drives the RC network that comprises the resistor R 2 of connecting with capacitor C2.Amplifier 315 provides the gain that illustrates K2.In one embodiment, amplifier 315 comprises having provides from the operational amplifier of its Voltage Feedback that outputs to its paraphase input with the resitstance voltage divider of gain K2 that expectation is provided.Operational amplifier and include the input resistor R1 of the other end of ground connection and the situation of the resitstance voltage divider of feedback resistor R2 under, when operating in known noninvert structure, gain K2 is 1+R2/R1.Amplifier 315 is generally on chip.Other assembly shown in Fig. 3 can be placed on the chip or not on chip, though because common LF of size restrictions and CF can not be on chips.
The voltage V at the output node RCOMP place of amplifier 315
RCOMPBe the V of amplifier 315
REFGain be duplicating of amplifying of K2, it is greater than 1.R2 and C2 are connected between node R COMP and the node FB.As already pointed out, the RCOMP node can be that external terminal is to provide the user adjustability by the outside RC of use or other suitable reactance network between RCOMP and FB pin.
About the operation of closed loop pulse-width modulation DC-DC transducer 300, for V
REF=Δ V
REFChange, V
RCOMPChange K2* Δ V
REFBecause the voltage at node FB place is driven with coupling V by A1
REF, then the voltage (R2-C2 among Fig. 3) of the spanning network that is driven by amplifier 315 changes K2* Δ V
REF-Δ V
REF, or (K2-1) * Δ V
REFTherefore, current canceling network 320 will inject FB with respect to the opposite polarity electric current I of I (R1-C1) (R2-C2).As a result, V
REFThe electric current that flows through RFB 110 during the variation is eliminated basically, as a result V
FBAnd V
OUTClosely follow the trail of.This elimination or basic at least the elimination because V
REFChange the overshoot that causes.
Be used for offsetting the R2 of entire I (R1-C1) basically and the suitable value of C2 can followingly be calculated.In a preferred embodiment, R
2C
2Time constant equal R
1C
1Time constant.If R
2C
2Have and R
1C
1Identical time constant, and R
2C
2Impedance be called Z2, then, obtain by I (R1-C1)=I (R2-C2) is set:
(K2-1)*ΔV
REF/Z2＝(1-1/K1)*ΔV
REF/Z1。
Above equation is reduced to Z2=Z1* (K2-1)/(1-1/K1).For example, if K2=2, and the gain K1=8 by PWM and low pass filter, the Z2=Z1*8/7 that then is used for I (R2-C2) is to offset I (R1-C1).
As noted above, the invention provides the selection that the RCOMP node is set to the exterior I C pin of transducer 300.The electric current that this arrangement permission is provided by current canceling can be adjusted in the IC outside.
Fig. 4 illustrates the instantaneous performance of simulation of the closed loop pulse-width modulation DC-DC transducer 300 with current canceling network 320 that schematically shows among Fig. 3.Because the electric current I (R2-C2) that is generated by current canceling network 320 equals I (R1-C1), see actual V
OUTThe V that closely mates expectation
OUT
An alternative embodiment of the invention comprises at least one and V
REFCompare the IC pin that has greater than 1 fixed gain K2.Therefore the user can apply an outside R-C network between the paraphase input FB of this pin and error amplifier.The subclass of above embodiment can make gain accurately equal 2-1/K1, so that Z2=Z1, and the component of identical value can be used for R1, C1 and R2, C2.
Another embodiment comprises that detecting actual modulator gains, i.e. the variation of K1 so that K2 follows the trail of K1, makes that the value of Z2 does not need to change so that whole basically current cancelings to be provided when the modulator gain changes.That is it is constant that value, (K2-1)/(1-1/K1) keeps.Notice that unless modulator has been equipped with feedforward compensation, otherwise modulator gain K1 is directly proportional with the voltage of the input of PWM filter.By known amplifying technique, this voltage can be used for modified gain K2.
The present invention can be used for providing the improved conversion regulator circuit that has benefited from accurate Vout tracking, and it comprises DC-DC transducer, motor controller circuit etc.
Should be appreciated that although described the present invention in conjunction with preferable specific embodiment of the present invention, the description of front and any example that is provided all are in order to illustrate rather than to limit the scope of the invention.In addition, advantage in the scope of the invention and improvement are conspicuous for those skilled in the art in the invention.
Claims (15)
1. voltage regulator comprises:
The IC that comprises error amplifier and pulse width modulator (PWM), the output of described error amplifier is coupled in the input of wherein said PWM;
Be coupled to low pass filter output, that comprise the inductor of connecting of described PWM, the output (V of wherein said adjuster with ground capacitor
Out) node place between described inductor and described capacitor;
Place described V
OutAnd first feedback network between the paraphase of the described error amplifier input and place the output of described error amplifier and the described paraphase input of described error amplifier between second feedback network, and
Be coupled to the current canceling network of the described paraphase input of described error amplifier, described current canceling network injects with the size of current that is flow through described second feedback network by the change triggering of the reference voltage that is applied to described error amplifier to described paraphase input and equates and opposite polarity counteracting electric current substantially.
2. voltage regulator as claimed in claim 1 is characterized in that, described current canceling network places between the noninvert input of the described paraphase input of described error amplifier and described error amplifier.
3. voltage regulator as claimed in claim 1 is characterized in that, described current canceling network is on described IC.
4. voltage regulator as claimed in claim 1 is characterized in that, described cancellation network comprises first amplifier and constitutes the RC of the network that is driven by described first amplifier.
5. voltage regulator as claimed in claim 4 is characterized in that, described first amplifier provides the gain greater than 1.
6. voltage regulator as claimed in claim 4 is characterized in that the time constant of the RC of described formation network equals the time constant of described second feedback network substantially.
7. voltage regulator as claimed in claim 4 is characterized in that, described first amplifier is on described IC, and the bonding welding pad that the output of wherein said first amplifier is connected to described IC connects with the external terminal as described IC.
8. voltage regulator as claimed in claim 4 is characterized in that, described adjuster comprises the structure that supports at least one IC pin, and described IC pin provides fixed gain greater than 1 for described first amplifier.
9. transducer as claimed in claim 8 is characterized in that, described fixed gain equals 2-1/ (by the gain of described PWM and described low pass filter).
10. transducer as claimed in claim 4 is characterized in that, also comprises being used to detect the gain of described PWM and adjusting the structure of described first Amplifier Gain with the described gain of following the trail of described PWM.
11. one kind is used for voltage regulator is carried out current canceling to improve the method for the compensation that reference voltage is changed, may further comprise the steps:
One voltage regulator is provided, and described voltage regulator comprises the voltage regulator of error amplifier and pulse width modulator (PWM), and the output of described error amplifier is coupled in the input of wherein said PWM; Be coupled to low pass filter output, that comprise the inductor of connecting of described PWM, the output (V of wherein said adjuster with ground capacitor
Out) node place between described inductor and described capacitor; Place described V
OutAnd first feedback network between the paraphase of the described error amplifier input; And place second feedback network between the described paraphase input of the output of described error amplifier and described error amplifier, and
Substantially equate and opposite polarity counteracting electric current with the size of current that flows through described second feedback network by the change triggering of the reference voltage that is applied to described error amplifier to described paraphase input injection.
12. method as claimed in claim 11 is characterized in that, comprises that first amplifier and formation provide described counteracting electric current by the cancellation network of the RC of the network of described first amplifier driving.
13. method as claimed in claim 11, it is characterized in that, described adjuster is included as described first amplifier at least one IC pin greater than 1 fixed gain is provided, and described method comprises that also the RC with the described formation network of described IC outside is connected described IC pin and is connected to step between the IC pin of described paraphase input of described error amplifier.
14. method as claimed in claim 13, it is characterized in that, also comprise described fixed gain is made as the step that equals 2-1/ (by the gain of described PWM and described low pass filter), the impedance of the RC of wherein said formation network equals the impedance of described second feedback network.
15. method as claimed in claim 12, it is characterized in that, also comprise the gain that detects described PWM and adjust the step of described first Amplifier Gain, wherein the change by the reference voltage that is applied to described error amplifier is triggered and the current canceling that flows through the described electric current of described second feedback network provides automatically by described adjustment with the described gain of following the trail of described PWM.
Applications Claiming Priority (2)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| US80294906P | 2006-05-24 | 2006-05-24 | |
| US60/802,949 | 2006-05-24 |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN101079577A true CN101079577A (en) | 2007-11-28 |
| CN101079577B CN101079577B (en) | 2012-05-16 |
Family
ID=38906860
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN2006101365836A Expired - Fee Related CN101079577B (en) | 2006-05-24 | 2006-10-23 | Voltage regulator having current canceling compensation |
Country Status (2)
| Country | Link |
|---|---|
| CN (1) | CN101079577B (en) |
| TW (1) | TWI325679B (en) |
Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102299628A (en) * | 2010-06-25 | 2011-12-28 | 立锜科技股份有限公司 | Voltage regulator and control circuit and method therefor |
| CN103812337A (en) * | 2012-11-01 | 2014-05-21 | 恒耀电子股份有限公司 | Current control circuit applied to power converter and control method thereof |
| CN106300917A (en) * | 2016-10-09 | 2017-01-04 | 深圳市钜能科技有限公司 | Negative-feedback circuit |
Family Cites Families (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US5264782A (en) * | 1992-08-10 | 1993-11-23 | International Business Machines Corporation | Dropout recovery circuit |
| US6181120B1 (en) * | 1999-09-01 | 2001-01-30 | Intersil Corporation | Current mode dc/dc converter with controlled output impedance |
| US6388451B1 (en) * | 2000-08-16 | 2002-05-14 | Ford Global Technologies, Inc. | Leakage current cancellation device |
| US6437999B1 (en) * | 2001-05-12 | 2002-08-20 | Technical Witts, Inc. | Power electronic circuits with ripple current cancellation |
-
2006
- 2006-10-11 TW TW95137301A patent/TWI325679B/en not_active IP Right Cessation
- 2006-10-23 CN CN2006101365836A patent/CN101079577B/en not_active Expired - Fee Related
Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102299628A (en) * | 2010-06-25 | 2011-12-28 | 立锜科技股份有限公司 | Voltage regulator and control circuit and method therefor |
| CN103812337A (en) * | 2012-11-01 | 2014-05-21 | 恒耀电子股份有限公司 | Current control circuit applied to power converter and control method thereof |
| CN106300917A (en) * | 2016-10-09 | 2017-01-04 | 深圳市钜能科技有限公司 | Negative-feedback circuit |
Also Published As
| Publication number | Publication date |
|---|---|
| CN101079577B (en) | 2012-05-16 |
| TW200744295A (en) | 2007-12-01 |
| TWI325679B (en) | 2010-06-01 |
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