CN101076947A - Method and device for evaluating and mending base band frequency error of receiver - Google Patents
Method and device for evaluating and mending base band frequency error of receiver Download PDFInfo
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Abstract
A method and apparatus for estimating and correcting baseband frequency error in a receiver. In one embodiment, an equalizer performs equalization on a sample data stream and generates filter tap values based on the equalization. An estimated frequency error signal is generated based on at least one of the filter tap values. A rotating phasor is generated based on the estimated frequency error signal. The rotating phasor signal is multiplied with the sample data stream to correct the frequency of the sample data stream. In another embodiment, a channel estimator performs channel estimation and generates Rake receiver finger weights based on at least one of the finger weights. An estimated frequency error signal is generated based on at least one of the finger weights.
Description
Technical field
The present invention is about wireless receiver.More particular words it, the present invention is about a kind of assessment and correct the method and the device of baseband frequency error in the receiver.
Background technology
Adaptive type receiver such as normalization lowest mean square (NLMS) eqalizing cricuit that is used for wireless transmission/receive unit (WTRUs) and base station sees through its correlation filter values of tap of an iterative program optimization, and this iterative program requires repeatedly iteration to approach convergence.Described values of tap in time through and converge to a least mean-square error (MMSE) that is used to carry out channel estimating and separate.
One NLMS receiver comprises an eqalizing cricuit with an equalizer filter, and this filter is continuous in convergence process, becomes channel a period of time because it tries to follow the trail of.Its complexity of following the trail of this channel is high more, and the values of tap of describedization device can be farther from convergence.Generally speaking, channel (that is fast-developing channel status) is difficult to follow the trail of for eqalizing cricuit faster.Remaining automatic frequency control (AFC) error in the base band in the input eqalizing cricuit causes it seems on the channel surface also faster than reality.The increase of the apparent speed of channel only can be by strengthening the used NLMS algorithm of NLMS receiver the mode of step-size give part and relax.The step-size of this increasing allows equalizer filter to follow the trail of " soon " channel more accurately, but also can strengthen the error that MMSE separates, and this causes the performance deterioration of receiver.
The receiver of employ channel estimation also can be because of remaining AFC error deterioration.Because the bandwidth that is used for the suitable equalizer filter of channel estimating is a function of the apparent speed of channel, big AFC error forces use can't effectively suppress the wide-band filter of news of making an uproar, thereby causes channel estimating more accurately.Want to have a simple solution to suppress remaining AFC error.
Summary of the invention
The present invention is about the method and the device of baseband frequency error in a kind of assessment and the correction receiver.In one embodiment, an eqalizing cricuit serves as that the basis produces filter tap values to equalization such as a sample data crossfire carry out and with these equalization.One estimated frequency error signal by based on described filter tap values at least one and produce.One rotating phasor is produced based on this estimated frequency error signal.This rotating phasor multiply by the frequency that corrects this sample data stream mutually with this sample data stream.In another embodiment, a channel estimator with refer to weight (finger weights) at least one be that the basis carries out channel estimating and produce Rake receiver referring to weight.One estimated frequency error signal by based on described finger weight at least one and produce.
Description of drawings
Of the present inventionly further understand and can from following detailed description, obtain, below describe system in detail and propose with way of example and should read together with alterations, graphic in:
The 1st figure is a calcspar according to the example BFC system of one embodiment of the invention, and this system comprises a frequency error estimator that is used to remove remaining AFC error;
The 2nd figure is the calcspar of the frequency error estimator of one the 1st drawing system 100;
The 3rd figure is a calcspar according to the example BFC system of another embodiment of the present invention;
The 4th figure is a high-level flowchart according to the method for one embodiment of the invention, and this method is used for correcting one and has the sample data stream frequency of wireless communication receiver of the eqalizing cricuit of equalization such as execution;
The 5th figure is the flow chart of a method, and it serves as that the basis produces estimated frequency error signal that this method is used for the filter tap values that the filter tap values that produces from the used eqalizing cricuit of the 4th drawing method is extracted;
The 6th figure is a flow chart according to the method for one embodiment of the invention, and it serves as that the basis produces estimated frequency error signal that this method is used for extracting values of tap with several that are averaged;
The 7th figure is a flow chart according to the method for one embodiment of the invention, and this method is used for the value of the intensity of comparison phase difference signal and threshold signal to judge whether stoping estimated frequency error signal to be updated;
The 8th figure is a flow chart according to the method for one embodiment of the invention, and this method is used for the value of the instantaneous power of comparison phase difference signal and threshold signal to judge whether stoping estimated frequency error signal to be updated;
The 9th figure is a high-level flowchart according to the method for one embodiment of the invention, and this method is used for correcting one and has the sample data stream frequency of the wireless communication receiver of the channel estimator of carrying out channel estimating; And
The 10th figure is the flow chart of a method, and this method is used for referring to that with the Rake receiver that produces from the used channel estimator of the 9th drawing method the finger weight that weight is extracted serves as that the basis produces estimated frequency error signal.
Embodiment
The graphic explanation preferred embodiment of following reference is wherein represented similar elements with same numbers.
Hereinafter, the non-limitation of term " WTRU " comprises a subscriber equipment (UE), a mobile radio station, a kneetop computer, a personal digital assistant (PDA), affixed or moving user unit, a calling set or any other type of device that can operate in wireless environment.Hereinafter, the non-limitation of term " base station " comprises that any other tipping that is situated between in an access point (AP), a B node (Node-B), a site controller or the wireless environment puts type.
Feature of the present invention can be merged in the integrated circuit (IC) or be configured in one and comprise in the circuit of multiple interconnect assembly.
Below with regard to NLMS eqalizing cricuit explanation the present invention.But it will be appreciated that NLMS eqalizing cricuit type receiver just is used as an example and provides, the present invention can be applicable to carry out any other adaptive type etc. and changes the receiver of algorithm and receiver such as the piece type eqalizing cricuit and the Rake receiver of employ channel estimation.
The 1st figure one is used to remove the calcspar of the example BFC system 100 of remaining AFC error according to one embodiment of the invention.BFC system 100 can be merged in a WTRU or the base station.BFC system 100 comprises a multiplier 102, an eqalizing cricuit 104, a frequency error estimator 106, a controller 108 and a numerically-controlled oscillator (NCO) 110.Eqalizing cricuit 104 is provided by the sample data stream 112 that is provided via multiplier 102 by a receiver front end (not shown).Describedization device can operate according to a NLMS algorithm.The right adaptive type eqalizing cricuit algorithm that also can use any other type.
The filter tap values 114 that eqalizing cricuit 104 produces is provided as an input of delivering frequency error estimator 106.Frequency error estimator 106 produces an estimated frequency error signal 116.Residual frequency error behind the AFC can be by BFC being observed the basis or estimating that from local channel for example a rake finger restore one's right reevaluating significantly reduces with at least one values of tap in the eqalizing cricuit 104 only.BFC system is by being observed basis assessment frequency error, producing by one multiple sinusoidal (or rotating phasor), will importing sample data stream and be multiplied by this phasor to correct this input sample data stream and the sample 118 of frequency correction to be closed the input that the loop mode is used for eqalizing cricuit 104 with reach with one or more values of tap in the eqalizing cricuit 104.
Residual frequency error system assesses by one or many persons' of the values of tap of periodic measurement eqalizing cricuit 104 phase change (or local channel estimation).The major part of the phase change between the different samples that eqalizing cricuit filter tap values 114 is recorded is because make an uproar news and decline.But, because of the phase change that declines and the news of making an uproar cause is zero average (for example mean value is zero).Therefore, the expectation mean value of any sample can be zero, that is the mean value of signal is zero.So can utilize the filtering operation to remove make an uproar news and the decline component that causes phase change, and restore because of the slow change phase change due to the frequency error from whole phase change (for example because of remaining AFC error due to).
In case assessed frequency error by frequency error estimator 106, controller 108 is handled estimated frequency error signal 116 to produce a frequency adjusted signal 120.Controller 108 can merely be adjusted the gain of estimated frequency error signal 116, and perhaps available one more complicated algorithm (for example ratio-integration-difference quotient (PID)) is handled estimated frequency error signal 116.Frequency adjusted signal 120 is sent to NCO110, and it produces a rotating phasor 122 corresponding to frequency adjusted signal 120.Multiplier 102 is multiplied by sample data stream 112 with rotating phasor 122 and is input to eqalizing cricuit 104 with the sample 118 that produces frequency correction.
Remaining AFC error appears for the multiplication error in the baseband signal in base band and has a multiple sinusoidal form, such as g (t) * exp (j*2pi*f*t), wherein g (t) is that not deterioration baseband signal and the exp (j*2pi*f*t) that wants is the multiple sine of representing error.By being multiplied by exp (j*2pi*f*t), multiple sinusoidal counteracting the and only stay the signal g (t) that wants.Estimated frequency error signal 116 is input to controller 108, and it exports a signal 120 subsequently, and this signal can be a proportional version of input for instance, for example four (4) times of estimated frequency error signal 116 values.The output signal 120 of controller 108 also can comprise other, for example one with proportional of the integration of estimated frequency error signal 116 and/or difference quotient.More common, output signal 120 also can through delete make its in certain scope with interior or have other these type of nonlinear functions to be used for this signal.NCO (110) gets a frequency values as an input, and exports a constant complex signal of intensity that possesses the instantaneous frequency of the value that equals this input, exp (j*2pi*f*t) for example, and wherein f is this incoming frequency.
The 2nd figure is the calcspar of frequency error estimator 106 of the BFC system 100 of one the 1st figure.
In frequency error estimator 106, values of tap extraction unit 202 outputs on the output signal 203 to be used for carrying out frequency estimation from filter tap values 114 (or from a channel estimator) extraction one suitable values of tap or values of tap mean deviation.For instance, the suitable values of tap of at least one correspondence FSP in a particular channel can be extracted from equalizer filter values of tap 114.Values of tap extraction unit 202 is the frequency drift of the values of tap of traceable extraction also.
The values of tap of extracting 203 is transferred to a delay cell 204 and a conjugation value cell 206.Delay cell 204 makes the values of tap 203 of extraction postpone one period scheduled time by exporting a delayed tap value 205.Conjugate generator system is used for producing a conjugate 207 of the values of tap 203 of extraction.Multiplier 208 is multiplied by conjugation values of tap 207 with delayed tap value 205.The output 209 of multiplier 208 has a phase value that equals the phase difference of 207 of delayed tap value 205 and conjugation values of tap.The average frequency of this phase value and signal 203 is proportional, and is therefore also proportional with the average frequency of sample data stream 112.
An angle value 213 of the output 209 of multiplier 208 is measured in arc tangent unit 212.Angle value 213 equals the phase difference of 207 of signal 205 and signals.Therefore ask angle value 213 average just be equal to the phase difference of asking 207 of signal 205 and signals on average.Angle value 213 filters average in the hope of angle value 213 through phase change filter 218.Actual measurement average phase-difference and known delay amount are used to produce estimated frequency error signal 116.
For instance, at a retardation D (second) and be that the gain of frequency error estimator 106 is 1/ (2*PI*D) under the condition of the phase place measured of unit with the radian." gain " means that a signal (shown in signal 114) that possesses a clean frequency error becomes the conversion of a measured value of estimated frequency error signal 116.If signal 114 has the average frequency of 1Hz, then the output valve on the estimated frequency error signal 116 can be 1/ (2*PI*D).
The intensity of multiplier 208 output 209 can be measured and be compared with the mean amplitude of tide of multiplier 208 outputs 209, just suspends phase change filter 218 when following as long as the intensity of multiplier 208 outputs 209 drops to a threshold value thus.When filter 218 is suspended, estimated frequency error signal 116 can not change (that is signal 116 is not updated), and input 213 is not used, and the internal state of filter 218 can not change.Signal 209 is that less relatively time stick signal 221 is very.This angle value that has on signal 213 gives the effect that abandons and improve estimated frequency error signal 116 when channel suffers the deep fading when being the most noisy.
Another is selected, and an available power detecting device (not shown) replaces the average power (that is square intensity) of intensity detector 214 with the output 209 of calculating multiplier 208, compares to export 209 the instantaneous power and the part of average power thus.
Other anomalies also belong to possibility.
The 3rd figure one is used to remove the calcspar of the example BFC system 300 of remaining AFC error according to another embodiment of the present invention.BFC system 300 can be merged in a WTRU or the base station.BFC system 300 comprises a multiplier 302, a rake combiner (or a type eqalizing cricuit) 304, one channel estimator 306, a frequency error estimator 308, a controller 310 and a NCO 312.
In a Rake receiver, be that the basis determines one to refer to weight with channel estimating at a specific multi-path component that is assigned to a rake finger.Channel estimator 306 produces Rake receiver and refers to weight 316, and it is taken as an input and offers frequency error estimator 308.Frequency error estimator 308 operates in a mode similar to the 1st figure and frequency error estimator shown in 2 106.
In case estimate frequency error by frequency error estimator 308, controller 310 is handled estimated frequency error signal 318 to produce a frequency adjusted signal 322.Frequency adjusted signal 322 is sent to NCO 312, and it produces a rotating phasor 324 corresponding to frequency adjusted signal 322.Multiplier 302 is multiplied by sample data stream 314 with rotating phasor 324 and is input to channel estimator 306 and rake combiner 304 with the sample 320 that produces frequency correction.Another selection, an available type eqalizing cricuit replaces rake combiner 304.
Estimated frequency error signal 318 controlled devices 310 that frequency error estimator 308 produces and NCO 312 handle, and this NCO adds a rotating phasor 324 all in sample data stream 314.
The 4th figure is a high-level flowchart according to the method 400 of one embodiment of the invention, and it comprises and is used for correcting a method step of sample data stream frequency of wireless communication receiver with eqalizing cricuit of equalization such as execution.In step 405, to equalization such as a sample data crossfire carry out.In step 410, serve as that the basis produces filter tap values with described equalization.In step 415, serve as that the basis produces an estimated frequency error signal with at least one of described filter tap values.In step 420, serve as that the basis produces a rotating phasor signal with this estimated frequency error signal.In step 425, with this sample data stream on this rotating phasor signal times to correct the frequency of this sample data stream
The 5th figure is the flow chart of a method 500, and it comprises a filter tap values that is used for extracting with the filter tap values that produces from the 4th drawing method 400 used eqalizing cricuits is the method step that the basis produces estimated frequency error signal.In step 505, extract a suitable values of tap from (producing the step 410 of the 4th figure) filter tap values.In step 510, postpone this extraction values of tap.In step 515, produce a conjugate of this extraction values of tap.In step 520, the conjugate of this extraction values of tap is multiplied by this delayed extracted tap value to produce a phase difference signal, it represents the phase difference between this conjugate extracted tap value and this delayed extracted tap value.In step 525, measure the phase difference between this conjugate extracted tap value and this delayed extracted tap value.In step 530, by asking average this estimated frequency error signal that produces of described measured phase difference.In step 535, be that basic selectivity stops this estimated frequency error signal to be updated with a value of a threshold signal.
The 6th figure is a flow chart according to the method 600 of one embodiment of the invention, and it comprises and is used for extracting values of tap with several that are averaged is the method step that the basis produces estimated frequency error signal.In step 605, extract several values of tap from (producing the step 410 of the 4th figure) filter tap values.In step 610, ask the average of described extraction values of tap to produce a mean value of described extraction values of tap.In step 615, postpone this average tap value.In step 620, produce a conjugate of this average tap value.In step 625, the conjugate of this average tap value is multiplied by this delayed average tap value to produce a phase difference signal, it represents the phase difference between this conjugate average tap value and this delayed average tap value.In step 630, measure the phase difference between this conjugate average tap value and this delayed average tap value.In step 635, by asking average this estimated frequency error signal that produces of this measured phase difference.In step 640, be that basic selectivity stops this estimated frequency error signal to be updated with a value of a threshold signal.
The 7th figure is a flow chart according to the method 700 of one embodiment of the invention, and it comprises the intensity that is used for the comparison phase difference signal and the method step of value to judge whether to stop estimated frequency error signal to be updated of threshold signal.In step 705, calculate an intensity of phase difference signal.In step 710, ask intensity average of this phase difference signal.In step 715, produce threshold signal by a conversion coefficient being multiplied by this phase difference signal mean intensity.In step 720, the value of the intensity of this phase difference signal and this threshold signal relatively.In step 725, if this phase difference signal intensity is lower than this threshold signal value and then stops this estimated frequency error signal to be updated.
The 8th figure is a flow chart according to the method 800 of one embodiment of the invention, and it comprises the instantaneous power that is used for the comparison phase difference signal and the method step of value to judge whether to stop estimated frequency error signal to be updated of threshold signal.In step 805, calculate the instantaneous power of phase difference signal.In step 810, ask the average of this instantaneous power that differs power signal.In step 815, produce threshold signal by a conversion coefficient being multiplied by the average instantaneous power of this phase difference signal.In step 820, the value of the instantaneous of this phase difference signal and this threshold signal relatively.In step 825, if this phase difference signal instantaneous power is lower than this threshold signal value and then stops this estimated frequency error signal to be updated.
The 9th figure is a high-level flowchart according to the method 900 of one embodiment of the invention, and it comprises and is used for correcting a method step with wireless communication receiver one sample data crossfire frequency of the channel estimator of carrying out channel estimating.In step 905, a sample data crossfire is carried out the channel estimating operation.In step 910, serve as that basis generation Rake receiver refers to weight with this channel estimating operation.In step 915, serve as that the basis produces an estimated frequency error signal with at least one of described finger weight.In step 920, serve as that the basis produces a rotating phasor signal with this estimated frequency error signal.In step 925, with this sample data stream on this rotating phasor signal times to correct the frequency of this sample data stream.
The 10th figure is the flow chart of a method 1000, and it comprises and is used for referring to that with the Rake receiver that produces from the 9th drawing method 900 used channel estimator the finger weight that weight is extracted is the method step that the basis produces estimated frequency error signal.In step 1005, refer to that from (producing the step 910 of the 9th figure) Rake receiver weight extraction one suitably refers to weight.In step 1010, postpone this extraction and refer to weight.In step 1015, produce the conjugate that this extraction refers to weight.In step 1020, this extraction is referred to that the conjugate of weight is multiplied by this delayed extracted and refers to weight to produce a phase difference signal, on behalf of this conjugate extracted, it refer to that weight and this delayed extracted refer to the phase difference between the weight.In step 1025, measure this conjugate extracted and refer to that weight and this delayed extracted refer to the phase difference between the weight.In step 1030, by asking average this estimated frequency error signal that produces of this measured phase difference.In step 1035, be that basic selectivity stops this estimated frequency error signal to be updated with a value of a threshold signal.
Though below with regard to the preferred embodiment particular combinations feature of the present invention and element are described, each feature or element can be used alone and not be used in combination together with other features of preferred embodiment and element or to be with or without other features of the present invention and the multiple of element.
Claims (120)
1. the base band frequency in the wireless communication receiver corrects the BFC system, and it comprises:
One eqalizing cricuit, it is used for equalization such as a sample data crossfire carry out and serves as that the basis produces filter tap values with described equalization;
One frequency error estimator, its one at least that is used for described filter tap values serves as that the basis produces an estimated frequency error signal;
One oscillator, it is used for this estimated frequency error signal serves as that the basis produces a rotating phasor signal; And
One multiplier, it is used for this sample data stream on this rotating phasor signal times to correct the frequency of this sample data stream.
2. the system as claimed in claim 1, wherein this frequency error estimator comprises:
One values of tap extraction unit, it is used for extracting a suitable values of tap and exporting this extraction values of tap from the filter tap values that describedization device is produced;
One delay cell, it is coupled to this values of tap extraction unit, is used for postponing this extraction values of tap;
One conjugate generator, it is coupled to this values of tap extraction unit and this delay cell, is used for producing a conjugate of this extraction values of tap; And
One first multiplier, it is coupled to this delay cell and this conjugate generator, the conjugate that is used for extracting values of tap is multiplied by this delayed extracted tap value to produce a phase difference signal, and it represents the phase difference between this conjugate extracted tap value and this delayed extracted tap value.
3. system as claimed in claim 2, wherein this frequency error estimator more comprises:
One arc tangent unit, the output that it is coupled to this first multiplier is used for measuring the phase difference between this conjugate extracted tap value and this delayed extracted tap value; And
One first filter, it is used to ask the average of this measure phase difference, makes this average phase-difference be used as this estimated frequency error signal from this frequency error estimator output thus.
4. system as claimed in claim 3, wherein this frequency error estimator more comprises a comparator circuit, it is coupled to this multiplier and this first filter, be used for that selectivity sends a stick signal to this first filter based on a value of a threshold signal, wherein this stick signal causes this first filter to suspend.
5. system as claimed in claim 4, wherein this comparator circuit comprises:
One intensity detector, it is coupled to this first multiplier and this arc tangent unit, is used for calculating an intensity of this phase difference signal; And
One comparator, it is used for the relatively intensity of this phase difference signal and the value of this threshold signal, and produces this stick signal when this phase difference signal intensity is lower than this threshold signal value.
6. system as claimed in claim 5, wherein this comparator circuit more comprises:
One second filter, it is used to ask intensity average of this phase difference signal; And
One second multiplier, it is used for a conversion coefficient is multiplied by the mean intensity of this phase difference signal to produce this threshold signal.
7. system as claimed in claim 4, wherein this comparator circuit comprises:
One power detecting device, it is used to calculate the instantaneous power of this phase difference signal; And
One comparator, it is used for the relatively instantaneous power of this phase difference signal and a value of a threshold signal, and this comparator produces this stick signal when this phase difference signal instantaneous power is lower than this threshold signal value thus.
8. system as claimed in claim 7, wherein this comparator circuit more comprises:
One second filter, it is used to ask instantaneous power average of this phase difference signal; And
One second multiplier, it is used for a conversion coefficient is multiplied by the average instantaneous power of this phase difference signal to produce this threshold signal.
9. the system as claimed in claim 1, wherein this frequency error estimator comprises:
One values of tap extraction unit, it is used for extracting several values of tap from the filter tap values that describedization device is produced, and asks the average to produce a mean value of described extraction values of tap of described extraction values of tap;
One delay cell, it is coupled to this values of tap extraction unit, is used for postponing this average tap value;
One conjugate generator, it is coupled to this values of tap extraction unit and this delay cell, is used for producing a conjugate of this average tap value; And
One first multiplier, it is coupled to this delay cell and this conjugate generator, be used for the conjugate of this average tap value is multiplied by this delayed average tap value to produce a phase difference signal, it represents the phase difference between this conjugate average tap value and this delayed average tap value.
10. system as claimed in claim 9, wherein this frequency error estimator more comprises:
One arc tangent unit, the output that it is coupled to this first multiplier is used for measuring the phase difference between this conjugate average tap value and this delayed average tap value; And
One first filter, it is used to ask the average of this measure phase difference, and this average phase-difference is exported to be used as this estimated frequency error signal from this frequency error estimator.
11. system as claimed in claim 10, wherein this frequency error estimator more comprises a comparator circuit, it is coupled to this multiplier and this first filter, be used for that selectivity sends a stick signal to this first filter based on a value of a threshold signal, wherein this stick signal causes this first filter to suspend.
12. system as claimed in claim 11, wherein this comparator circuit comprises:
One intensity detector, it is coupled to this first multiplier and this arc tangent unit, is used for calculating an intensity of this phase difference signal; And
One comparator, it is used for the relatively intensity of this phase difference signal and the value of this threshold signal, and produces this stick signal when this phase difference signal intensity is lower than this threshold signal value.
13. system as claimed in claim 12, wherein this comparator circuit more comprises:
One second filter, it is used to ask intensity average of this phase difference signal; And
One second multiplier, it is used for a conversion coefficient is multiplied by the mean intensity of this phase difference signal to produce this threshold signal.
14. system as claimed in claim 11, wherein this comparator circuit comprises:
One power detecting device, it is used to calculate the instantaneous power of this phase difference signal; And
One comparator, it is used for the relatively instantaneous power of this phase difference signal and the value of this threshold signal, and this comparator produces this stick signal when this phase difference signal instantaneous power is lower than this threshold signal value thus.
15. system as claimed in claim 14, wherein this comparator circuit more comprises:
One second filter, it is used to ask instantaneous power average of this phase difference signal; And
One second multiplier, it is used for a conversion coefficient is multiplied by the average instantaneous power of this phase difference signal to produce this threshold signal.
16. the system as claimed in claim 1, it more comprises a controller, and it is coupled between this frequency error estimator and this oscillator, is used for adjusting the gain of this estimated frequency error signal.
17. system as claimed in claim 16, wherein this oscillator is a numerically-controlled oscillator NCO who is controlled by this controller.
18. the system as claimed in claim 1, it more comprises a controller, it is coupled between this frequency error estimator and this oscillator, this controller is used for handling from this estimated frequency error signal that this frequency error estimator was received with one ratio-integration-difference quotient PID algorithm, and the estimated frequency error signal after will handling is input to this oscillator.
19. system as claimed in claim 18, wherein this oscillator is a numerically-controlled oscillator NCO who is controlled by this controller.
20. the system as claimed in claim 1, wherein saidization device are used a normalization lowest mean square NLMS algorithm.
21. the base band frequency in the wireless communication receiver corrects the BFC system, it comprises:
One channel estimator, it is used for a sample data crossfire is carried out a channel estimating operation and serves as that the basis produces Rake receiver and refers to weight with this channel estimating operation;
One frequency error estimator, its one at least that is used for described finger weight serves as that the basis produces an estimated frequency error signal;
One oscillator, it is used for this estimated frequency error signal serves as that the basis produces a rotating phasor signal; And
One multiplier, it is used for this sample data stream on this rotating phasor signal times to correct the frequency of this sample data stream.
22. system as claimed in claim 21, wherein this frequency error estimator comprises:
One values of tap extraction unit, its Rake receiver that is used for producing from this channel estimator refer to that weight extraction one suitable Rake receiver refers to weight;
One delay cell, it is coupled to this values of tap extraction unit, is used for postponing this extraction and refers to weight;
One conjugate generator, it is coupled to this values of tap extraction unit and this delay cell, is used for producing the conjugate that this extraction refers to weight; And
One first multiplier, it is coupled to this delay cell and this conjugate generator, be used for this extraction is referred to that the conjugate of weight is multiplied by this delayed extracted and refers to weight to produce a phase difference signal, its representative refers to that in this conjugate extracted weight and this delayed extracted refer to the phase difference between the weight.
23. the system as claimed in claim 22, wherein this frequency error estimator more comprises:
One arc tangent unit, the output that it is coupled to this first multiplier is used for measuring this conjugate extracted and refers to that weight and this delayed extracted refer to the phase difference between the weight; And
One first filter, it is used to ask the average of this measure phase difference, and this average phase-difference is exported to be used as this estimated frequency error signal from this frequency error estimator.
24. system as claimed in claim 23, wherein this frequency error estimator more comprises a comparator circuit, it is coupled to this multiplier and this first filter, be used for that selectivity sends a stick signal to this first filter based on a value of a threshold signal, wherein this stick signal causes this first filter to suspend.
25. system as claimed in claim 24, wherein this comparator circuit comprises:
One intensity detector, it is coupled to this first multiplier and this arc tangent unit, is used for calculating an intensity of this phase difference signal; And
One comparator, it is used for the relatively intensity of this phase difference signal and the value of this threshold signal, and produces this stick signal when this phase difference signal intensity is lower than this threshold signal value.
26. system as claimed in claim 25, wherein this comparator circuit more comprises:
One second filter, it is used to ask intensity average of this phase difference signal; And
One second multiplier, it is used for a conversion coefficient is multiplied by the mean intensity of this phase difference signal to produce this threshold signal.
27. system as claimed in claim 24, wherein this comparator circuit comprises:
One power detecting device, it is used to calculate the instantaneous power of this phase difference signal; And
One comparator, it is used for the relatively instantaneous power of this phase difference signal and the value of this threshold signal, and this comparator produces this stick signal when this phase difference signal instantaneous power is lower than this threshold signal value thus.
28. system as claimed in claim 27, wherein this comparator circuit more comprises:
One second filter, it is used to ask instantaneous power average of this phase difference signal; And
One second multiplier, it is used for a conversion coefficient is multiplied by the average instantaneous power of this phase difference signal to produce this threshold signal.
29. system as claimed in claim 21, wherein this frequency error estimator comprises:
One values of tap extraction unit, it is used for from being referred to that by the Rake receiver that this channel estimator produced weight extracts several Rake receivers and refer to weight, and ask described extraction refer to weight on average to produce the average finger weight that described extraction refers to weight;
One delay cell, it is coupled to this values of tap extraction unit, is used for postponing on average referring to weight;
One conjugate generator, it is coupled to this values of tap extraction unit and this delay cell, is used for producing the conjugate that this on average refers to weight; And
One first multiplier, it is coupled to this delay cell and this conjugate generator, be used for being somebody's turn to do on average the conjugate that refers to weight and be multiplied by this hysteresis and on average refer to weight to produce a phase difference signal, on behalf of this conjugation, it refer to that on average weight and this hysteresis on average refer to the phase difference between the weight.
30. system as claimed in claim 29, wherein this frequency error estimator more comprises:
One arc tangent unit, the output that it is coupled to this first multiplier is used for measuring this conjugation and refers to that on average weight and this hysteresis on average refer to the phase difference between the weight; And
One first filter, it is used to ask the average of this measure phase difference, and this average phase-difference is exported to be used as this estimated frequency error signal from this frequency error estimator.
31. system as claimed in claim 30, wherein this frequency error estimator more comprises a comparator circuit, it is coupled to this multiplier and this first filter, be used for that selectivity sends a stick signal to this first filter based on a value of a threshold signal, wherein this stick signal causes this first filter to suspend.
32. system as claimed in claim 31, wherein this comparator circuit comprises:
One intensity detector, it is coupled to this first multiplier and this arc tangent unit, is used for calculating an intensity of this phase difference signal; And
One comparator, it is used for the relatively intensity of this phase difference signal and the value of this threshold signal, and produces this stick signal when this phase difference signal intensity is lower than this threshold signal value.
33. system as claimed in claim 32, wherein this comparator circuit more comprises:
One second filter, it is used to ask intensity average of this phase difference signal; And
One second multiplier, it is used for a conversion coefficient is multiplied by the mean intensity of this phase difference signal to produce this threshold signal.
34. system as claimed in claim 31, wherein this comparator circuit comprises:
One power detecting device, it is used to calculate the instantaneous power of this phase difference signal; And
One comparator, it is used for the relatively instantaneous power of this phase difference signal and the value of this threshold signal, and this comparator produces this stick signal when this phase difference signal instantaneous power is lower than this threshold signal value thus.
35. system as claimed in claim 34, wherein this comparator circuit more comprises:
One second filter, it is used to ask instantaneous power average of this phase difference signal; And
One second multiplier, it is used for a conversion coefficient is multiplied by the instantaneous power of this phase difference signal to produce this threshold signal.
36. system as claimed in claim 31 more comprises a controller, it is coupled between this frequency error estimator and this oscillator, is used for adjusting the gain of this estimated frequency error signal.
37. system as claimed in claim 36, wherein this oscillator is the numerically-controlled oscillator NCO by this controller control.
38. system as claimed in claim 31, more comprise a controller, it is coupled between this frequency error estimator and this oscillator, this controller be used for one ratio-integration-difference quotient PID algorithm handle this estimated frequency error signal of receiving from this frequency error estimator and will handle after estimated frequency error signal be input to this oscillator.
39. system as claimed in claim 38, wherein this oscillator is a numerically-controlled oscillator NCO who is controlled by this controller.
40. system as claimed in claim 31, wherein saidization device uses a normalization lowest mean square NLMS algorithm.
41. one kind is carried out the method that base band frequency corrects BFC in wireless communication receiver, it comprises:
(a) to equalization such as a sample data crossfire carry out;
(b) serve as that the basis produces filter tap values with described equalization;
(c) one at least with described filter tap values serves as that the basis produces an estimated frequency error signal;
(d) serve as that the basis produces a rotating phasor signal with this estimated frequency error signal; And
(e) with this sample data stream on this rotating phasor signal times, to correct the frequency of this sample data stream.
42. method as claimed in claim 41, wherein step (c) more comprises:
(c1) from the filter tap values of described generation, extract a suitable values of tap;
(c2) postpone this extraction values of tap;
(c3) produce a conjugate of this extraction values of tap; And
(c4) conjugate that will extract values of tap is multiplied by this delayed extracted tap value to produce a phase difference signal, and it represents the phase difference between this conjugate extracted tap value and this delayed extracted tap value.
43. method as claimed in claim 42, wherein step (c) more comprises:
(c5) measure phase difference between this conjugate extracted tap value and this delayed extracted tap value; And
(c6) by asking average this estimated frequency error signal that produces of this measure phase difference.
44. method as claimed in claim 43, wherein step (c) more comprises:
(c7) selectivity stops this estimated frequency error signal to be updated based on a value of a threshold signal.
45. method as claimed in claim 44, wherein step (c) more comprises:
(c8) calculate an intensity of this phase difference signal;
(c9) value of the intensity of this phase difference signal and this threshold signal relatively; And
(c10) when being lower than this threshold signal value, this phase difference signal intensity stop this estimated frequency error signal to be updated.
46. method as claimed in claim 45, wherein step (c) more comprises:
(c11) ask intensity average of this phase difference signal; And
(c12) produce this threshold signal by the mean intensity that a conversion coefficient is multiplied by this phase difference signal.
47. method as claimed in claim 44, wherein step (c) more comprises:
(c8) calculate the instantaneous power of this phase difference signal;
(c9) value of the instantaneous power of this phase difference signal and this threshold signal relatively; And
(c10) when being lower than this threshold signal value, this phase difference signal instantaneous power stop this estimated frequency error signal to be updated.
48. method as claimed in claim 47, wherein step (c) more comprises:
(c10) ask instantaneous power average of this phase difference signal; And
(c11) produce this threshold signal by the average instantaneous power that a conversion coefficient is multiplied by this phase difference signal.
49. method as claimed in claim 41, wherein step (c) more comprises:
(c1) from the filter tap values that produces, extract several values of tap;
(c2) ask the average of described extraction values of tap to produce a mean value of described extraction values of tap;
(c3) postpone this average tap value;
(c4) produce a conjugate of this average tap value; And
(c5) conjugate with this average tap value is multiplied by this delayed average tap value to produce a phase difference signal, and it represents the phase difference between this conjugate average tap value and this delayed average tap value.
50. method as claimed in claim 49, wherein step (c) more comprises:
(c6) measure phase difference between this conjugate average tap value and this delayed average tap value; And
(c7) by asking average this estimated frequency error signal that produces of this measure phase difference.
51. method as claimed in claim 50, wherein step (c) more comprises:
(c8) selectivity stops this estimated frequency error signal to be updated based on a value of a threshold signal.
52. method as claimed in claim 51, wherein step (c) more comprises:
(c9) calculate an intensity of this phase difference signal;
(c10) value of the intensity of this phase difference signal and this threshold signal relatively; And
(c11) when being lower than this threshold signal value, this phase difference signal intensity stop this estimated frequency error signal to be updated.
53. method as claimed in claim 52, wherein step (c) more comprises:
(c12) ask intensity average of this phase difference signal; And
(c13) produce this threshold signal by the mean intensity that a conversion coefficient is multiplied by this phase difference signal.
54. method as claimed in claim 51, wherein step (c) more comprises:
(c9) calculate the instantaneous power of this phase difference signal;
(c10) value of the instantaneous power of this phase difference signal and this threshold signal relatively; And
(c11) when being lower than this threshold signal value, this phase difference signal instantaneous power stop this estimated frequency error signal to be updated.
55. method as claimed in claim 54, wherein step (c) more comprises:
(c12) ask instantaneous power average of this phase difference signal; And
(c13) conversion coefficient is multiplied by the average instantaneous power of this phase difference signal and produces this threshold signal.
56. method as claimed in claim 41 more comprises:
(f) adjust the gain of this estimated frequency error signal.
57. method as claimed in claim 41 more comprises:
(f) handle this estimated frequency error signal with one ratio-integration-difference quotient PID algorithm.
58. method as claimed in claim 41 is wherein utilized a normalization lowest mean square NLMS algorithm execution in step (a).
59. one kind is carried out the method that base band frequency corrects BFC in wireless communication receiver, it comprises:
(a) a sample data crossfire is carried out a channel estimating operation;
(b) serve as that basis generation Rake receiver refers to weight with this channel estimating operation;
(c) one at least with described finger weight serves as that the basis produces an estimated frequency error signal;
(d) serve as that the basis produces a rotating phasor signal with this estimated frequency error signal; And
(e) with this sample data stream on this rotating phasor signal times to correct the frequency of this sample data stream.
60. method as claimed in claim 59, wherein step (c) more comprises:
(c1) Rake receiver from described generation refers to that extraction one suitably refers to weight the weight;
(c2) postpone this extraction and refer to weight;
(c3) produce the conjugate that this extraction refers to weight; And
(c4) this extraction is referred to the conjugate of weight is multiplied by this delayed extracted and refers to weight to produce a phase difference signal, on behalf of this conjugate extracted, it refer to that weight and this delayed extracted refer to the phase difference between the weight.
61. method as claimed in claim 60, wherein step (c) more comprises:
(c5) measure this conjugate extracted and refer to that weight and this delayed extracted refer to the phase difference between the weight; And
(c6) by asking average this estimated frequency error signal that produces of this measure phase difference.
62. method as claimed in claim 61, wherein step (c) more comprises:
(c7) selectivity stops this estimated frequency error signal to be updated based on a value of a threshold signal.
63. method as claimed in claim 62, wherein step (c) more comprises:
(c8) calculate an intensity of this phase difference signal;
(c9) value of the intensity of this phase difference signal and this threshold signal relatively; And
(c10) when being lower than this threshold signal value, this phase difference signal intensity stop this estimated frequency error signal to be updated.
64. as the described method of claim 63, wherein step (c) more comprises:
(c11) ask intensity average of this phase difference signal; And
(c12) produce this threshold signal by the mean intensity that a conversion coefficient is multiplied by this phase difference signal.
65. method as claimed in claim 62, wherein step (c) more comprises:
(c8) calculate the instantaneous power of this phase difference signal;
(c9) value of the instantaneous power of this phase difference signal and this threshold signal relatively; And
(c10) when being lower than this threshold signal value, this phase difference signal instantaneous power stop this estimated frequency error signal to be updated.
66. as the described method of claim 65, wherein step (c) more comprises:
(c11) ask instantaneous power average of this phase difference signal; And
(c12) produce this threshold signal by the average instantaneous power that a conversion coefficient is multiplied by this phase difference signal.
67. method as claimed in claim 59, wherein step (c) more comprises:
(c1) refer to extract the weight several from the Rake receiver that produces and refer to weight;
(c2) ask described extraction to refer to the average of weight to produce the mean value that described extraction refers to weight;
(c3) postpone on average to refer to weight;
(c4) produce a conjugate of this average tap value; And
(c5) will be somebody's turn to do on average the conjugate that refers to weight and be multiplied by this hysteresis and on average refer to weight to produce a phase difference signal, on behalf of this conjugation, it refer to that on average weight and this hysteresis on average refer to the phase difference between the weight.
68. as the described method of claim 67, wherein step (c) more comprises:
(c6) measure this conjugation and refer to that on average weight and this hysteresis on average refer to the phase difference between the weight; And
(c7) by asking average this estimated frequency error signal that produces of this measure phase difference.
69. as the described method of claim 68, wherein step (c) more comprises:
(c8) selectivity stops this estimated frequency error signal to be updated based on a value of a threshold signal.
70. as the described method of claim 69, wherein step (c) more comprises:
(c9) calculate an intensity of this phase difference signal;
(c10) value of the intensity of this phase difference signal and this threshold signal relatively; And
(c11) when being lower than this threshold signal value, this phase difference signal intensity stop this estimated frequency error signal to be updated.
71. as the described method of claim 70, wherein step (c) more comprises:
(c12) ask intensity average of this phase difference signal; And
(c13) produce this threshold signal by the mean intensity that a conversion coefficient is multiplied by this phase difference signal.
72. as the described method of claim 69, wherein step (c) more comprises:
(c9) calculate the instantaneous power of this phase difference signal;
(c10) value of the instantaneous power of this phase difference signal and this threshold signal relatively; And
(c11) when being lower than this threshold signal value, this phase difference signal instantaneous power stop this estimated frequency error signal to be updated.
73. as the described method of claim 72, wherein step (c) more comprises:
(c12) ask instantaneous power average of this phase difference signal; And
(c13) conversion coefficient is multiplied by the average instantaneous power of this phase difference signal and produces this threshold signal.
74. method as claimed in claim 59 more comprises:
(f) adjust the gain of this estimated frequency error signal.
75. method as claimed in claim 59 more comprises:
(f) handle this estimated frequency error signal with one ratio-integration-difference quotient PID algorithm.
76. method as claimed in claim 59 is wherein utilized a normalization lowest mean square NLMS algorithm execution in step (a).
77. an integrated circuit (IC), it comprises:
One eqalizing cricuit, it is used for equalization such as a sample data crossfire carry out and serves as that the basis produces filter tap values with described equalization;
One frequency error estimator, its one at least that is used for described filter tap values serves as that the basis produces an estimated frequency error signal;
One oscillator, it is used for this estimated frequency error signal serves as that the basis produces a rotating phasor signal; And
One multiplier, it is used for this sample data stream on this rotating phasor signal times to correct the frequency of this sample data stream.
78. as the described IC of claim 77, wherein this frequency error estimator comprises:
One values of tap extraction unit, it is used for extracting a suitable values of tap and exporting this extraction values of tap from the filter tap values that is produced by describedization device;
One delay cell, it is coupled to this values of tap extraction unit, is used for postponing this extraction values of tap;
One conjugate generator, it is coupled to this values of tap extraction unit and this delay cell, is used for producing a conjugate of this extraction values of tap; And
One first multiplier, it is coupled to this delay cell and this conjugate generator, the conjugate that is used for extracting values of tap is multiplied by this delayed extracted tap value to produce a phase difference signal, and it represents the phase difference between this conjugate extracted tap value and this delayed extracted tap value.
79. as the described IC of claim 78, wherein this frequency error estimator more comprises:
One arc tangent unit, the output that it is coupled to this first multiplier is used for measuring the phase difference between this conjugate extracted tap value and this delayed extracted tap value; And
One first filter, it is used to ask the average of this measure phase difference, and this average phase-difference is exported to be used as this estimated frequency error signal from this frequency error estimator.
80. as the described IC of claim 79, wherein this frequency error estimator more comprises a comparator circuit, it is coupled to this multiplier and this first filter, be used for that selectivity sends a stick signal to this first filter based on a value of a threshold signal, wherein this stick signal causes this first filter to suspend.
81. as the described IC of claim 80, wherein this comparator circuit comprises:
One intensity detector, it is coupled to this first multiplier and this arc tangent unit, is used for calculating an intensity of this phase difference signal; And
One comparator, it is used for the relatively intensity of this phase difference signal and the value of this threshold signal, and produces this stick signal when this phase difference signal intensity is lower than this threshold signal value.
82. as the described IC of claim 81, wherein this comparator circuit more comprises:
One second filter, it is used to ask intensity average of this phase difference signal; And
One second multiplier, it is used for a conversion coefficient is multiplied by the mean intensity of this phase difference signal to produce this threshold signal.
83. as the described IC of claim 80, wherein this comparator circuit comprises:
One power detecting device, it is used to calculate the instantaneous power of this phase difference signal; And
One comparator, it is used for the relatively instantaneous power of this phase difference signal and a value of a threshold signal, and this comparator produces this stick signal when this phase difference signal instantaneous power is lower than this threshold signal value thus.
84. as the described IC of claim 83, wherein this comparator circuit more comprises:
One second filter, it is used to ask instantaneous power average of this phase difference signal; And
One second multiplier, it is used for a conversion coefficient is multiplied by the average instantaneous power of this phase difference signal to produce this threshold signal.
85. as the described IC of claim 77, wherein this frequency error estimator comprises:
One values of tap extraction unit, it is used for extracting several values of tap from the filter tap values that describedization device is produced, and asks the average to produce a mean value of described extraction values of tap of described extraction values of tap;
One delay cell, it is coupled to this values of tap extraction unit, is used for postponing this average tap value;
One conjugate generator, it is coupled to this values of tap extraction unit and this delay cell, is used for producing a conjugate of this average tap value; And
One first multiplier, it is coupled to this delay cell and this conjugate generator, be used for the conjugate of this average tap value is multiplied by this delayed average tap value to produce a phase difference signal, it represents the phase difference between this conjugate average tap value and this delayed average tap value.
86. as the described IC of claim 85, wherein this frequency error estimator more comprises:
One arc tangent unit, the output that it is coupled to this first multiplier is used for measuring the phase difference between this conjugate average tap value and this delayed average tap value; And
One first filter, it is used to ask the average of this measure phase difference, and this average phase-difference is exported to be used as this estimated frequency error signal from this frequency error estimator.
87. as the described IC of claim 86, wherein this frequency error estimator more comprises a comparator circuit, it is coupled to this multiplier and this first filter, be used for that selectivity sends a stick signal to this first filter based on a value of a threshold signal, wherein this stick signal causes this first filter to suspend.
88. as the described IC of claim 87, wherein this comparator circuit comprises:
One intensity detector, it is coupled to this first multiplier and this arc tangent unit, is used for calculating an intensity of this phase difference signal; And
One comparator, it is used for the relatively intensity of this phase difference signal and the value of this threshold signal, and produces this stick signal when this phase difference signal intensity is lower than this threshold signal value.
89. as the described IC of claim 88, wherein this comparator circuit more comprises:
One second filter, it is used to ask intensity average of this phase difference signal; And
One second multiplier, it is used for a conversion coefficient is multiplied by the mean intensity of this phase difference signal to produce this threshold signal.
90. as the described IC of claim 87, wherein this comparator circuit comprises:
One power detecting device, it is used to calculate the instantaneous power of this phase difference signal; And
One comparator, it is used for the relatively instantaneous power of this phase difference signal and the value of this threshold signal, and this comparator produces this stick signal when this phase difference signal instantaneous power is lower than this threshold signal value thus.
91. as the described IC of claim 90, wherein this comparator circuit more comprises:
One second filter, it is used to ask instantaneous power average of this phase difference signal; And
One second multiplier, it is used for a conversion coefficient is multiplied by the average instantaneous power of this phase difference signal to produce this threshold signal.
92. as the described IC of claim 77, it more comprises a controller, it is coupled between this frequency error estimator and this oscillator, is used for adjusting the gain of this estimated frequency error signal.
93. as the described IC of claim 92, wherein this oscillator is a numerically-controlled oscillator NCO who is controlled by this controller.
94. as the described IC of claim 77, more comprise a controller, it is coupled between this frequency error estimator and this oscillator, this controller be used for one ratio-integration-difference quotient PID algorithm handle from by this estimated frequency error signal that this frequency error estimator received and the estimated frequency error signal after will handling be input to this oscillator.
95. as the described IC of claim 94, wherein this oscillator is a numerically-controlled oscillator NCO who is controlled by this controller.
96. as the described IC of claim 77, wherein saidization device uses a normalization lowest mean square NLMS algorithm.
97. as the described IC of claim 77, wherein this IC is embedded in the wireless transmission/receive unit WTRU.
98. as the described IC of claim 77, wherein this IC is embedded in the base station.
99. an integrated circuit (IC), it comprises:
One channel estimator, it is used for a sample data crossfire is carried out a channel estimating operation and serves as that the basis produces Rake receiver and refers to weight with this channel estimating operation;
One frequency error estimator, its one at least that is used for described finger weight serves as that the basis produces an estimated frequency error signal;
One oscillator, it is used for this estimated frequency error signal serves as that the basis produces a rotating phasor signal; And
One multiplier, it is used for this sample data stream on this rotating phasor signal times to correct the frequency of this sample data stream.
100. as the described IC of claim 99, wherein this frequency error estimator comprises:
One values of tap extraction unit, it is used for from being referred to that by the Rake receiver that this channel estimator produced weight extraction one suitable Rake receiver refers to weight;
One delay cell, it is coupled to this values of tap extraction unit, is used for postponing this extraction and refers to weight;
One conjugate generator, it is coupled to this values of tap extraction unit and this delay cell, is used for producing the conjugate that this extraction refers to weight; And
One first multiplier, it is coupled to this delay cell and this conjugate generator, be used for this extraction is referred to that the conjugate of weight is multiplied by this delayed extracted and refers to weight to produce a phase difference signal, on behalf of this conjugate extracted, it refer to that weight and this delayed extracted refer to the phase difference between the weight.
101. as the described IC of claim 100, wherein this frequency error estimator more comprises:
One arc tangent unit, the output that it is coupled to this first multiplier is used for measuring this conjugate extracted and refers to that weight and this delayed extracted refer to the phase difference between the weight; And
One first filter, it is used to ask the average of this measure phase difference, and this average phase-difference is exported to be used as this estimated frequency error signal from this frequency error estimator.
102. as the described IC of claim 101, wherein this frequency error estimator more comprises a comparator circuit, it is coupled to this multiplier and this first filter, be used for that selectivity sends a stick signal to this first filter based on a value of a threshold signal, wherein this stick signal causes this first filter to suspend.
103. as the described IC of claim 102, wherein this comparator circuit comprises:
One intensity detector, it is coupled to this first multiplier and this arc tangent unit, is used for calculating an intensity of this phase difference signal; And
One comparator, it is used for the relatively intensity of this phase difference signal and the value of this threshold signal, and produces this stick signal when this phase difference signal intensity is lower than this threshold signal value.
104. as the described IC of claim 103, wherein this comparator circuit more comprises:
One second filter, it is used to ask intensity average of this phase difference signal; And
One second multiplier, it is used for a conversion coefficient is multiplied by the mean intensity of this phase difference signal to produce this threshold signal.
105. as the described IC of claim 102, wherein this comparator circuit comprises:
One power detecting device, it is used to calculate the instantaneous power of this phase difference signal; And
One comparator, it is used for the relatively instantaneous power of this phase difference signal and the value of this threshold signal, and this comparator produces this stick signal when this phase difference signal instantaneous power is lower than this threshold signal value thus.
106. as the described IC of claim 105, wherein this comparator circuit more comprises:
One second filter, it is used to ask instantaneous power average of this phase difference signal; And
One second multiplier, it is used for a conversion coefficient is multiplied by the average instantaneous power of this phase difference signal to produce this threshold signal.
107. as the described IC of claim 99, wherein this frequency error estimator comprises:
One values of tap extraction unit, it is used for from being referred to that by the Rake receiver that this channel estimator produced weight extracts several Rake receivers and refer to weight, and ask described extraction refer to weight on average to produce the average finger weight that described extraction refers to weight;
One delay cell, it is coupled to this values of tap extraction unit, is used for postponing on average referring to weight;
One conjugate generator, it is coupled to this values of tap extraction unit and this delay cell, is used for producing the conjugate that this on average refers to weight; And
One first multiplier, it is coupled to this delay cell and this conjugate generator, be used for being somebody's turn to do on average the conjugate that refers to weight and be multiplied by this hysteresis and on average refer to weight to produce a phase difference signal, on behalf of this conjugation, it refer to that on average weight and this hysteresis on average refer to the phase difference between the weight.
108. as the described IC of claim 107, wherein this frequency error estimator more comprises:
One arc tangent unit, the output that it is coupled to this first multiplier is used for measuring this conjugation and refers to that on average weight and this hysteresis on average refer to the phase difference between the weight; And
One first filter, it is used to ask the average of this measure phase difference, and this average phase-difference is exported to be used as this estimated frequency error signal from this frequency error estimator.
109. as the described IC of claim 108, wherein this frequency error estimator comprises a comparator circuit, it is coupled to this multiplier and this first filter, a value that is used for a threshold signal is that basic selectivity sends a stick signal to this first filter, and wherein this stick signal causes this first filter to suspend.
110. as the described IC of claim 109, wherein this comparator circuit comprises:
One intensity detector, it is coupled to this first multiplier and this arc tangent unit, is used for calculating an intensity of this phase difference signal; And
One comparator, it is used for the relatively intensity of this phase difference signal and the value of this threshold signal, and produces this stick signal when this phase difference signal intensity is lower than this threshold signal value.
111. as the described IC of claim 110, wherein this comparator circuit more comprises:
One second filter, it is used to ask intensity average of this phase difference signal; And
One second multiplier, it is used for a conversion coefficient is multiplied by the mean intensity of this phase difference signal to produce this threshold signal.
112. as the described IC of claim 109, wherein this comparator circuit comprises:
One power detecting device, it is used to calculate the instantaneous power of this phase difference signal; And
One comparator, it is used for the relatively instantaneous power of this phase difference signal and the value of this threshold signal, and this comparator produces this stick signal when this phase difference signal instantaneous power is lower than this threshold signal value thus.
113. as the described IC of claim 112, wherein this comparator circuit more comprises:
One second filter, it is used to ask instantaneous power average of this phase difference signal; And
One second multiplier, it is used for a conversion coefficient is multiplied by the instantaneous power of this phase difference signal to produce this threshold signal.
114. as the described IC of claim 109, more comprise a controller, it is coupled between this frequency error estimator and this oscillator, is used for adjusting the gain of this estimated frequency error signal.
115. as the described IC of claim 114, wherein this oscillator is a numerically-controlled oscillator NCO who is controlled by this controller.
116. as the described IC of claim 109, it more comprises a controller, it is coupled between this frequency error estimator and this oscillator, this controller be used for one ratio-integration-difference quotient PID algorithm handle from by this estimated frequency error signal that this frequency error estimator was received and the estimated frequency error signal after will handling be input to this oscillator.
117. as the described IC of claim 116, wherein this oscillator is-the numerically-controlled oscillator NCO that controlled by this controller.
118. as the described IC of claim 109, wherein saidization device uses a normalization lowest mean square NLMS algorithm.
119. as the described IC of claim 99, wherein this IC is embedded in the wireless transmission/receive unit WTRU.
120. as the described IC of claim 99, wherein this IC is embedded in the base station.
Applications Claiming Priority (3)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| US62587404P | 2004-11-08 | 2004-11-08 | |
| US60/625,874 | 2004-11-08 | ||
| US11/209,097 | 2005-08-22 |
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|---|---|---|---|
| CN201010157861A Division CN101867388A (en) | 2004-11-08 | 2005-10-19 | The method and the device of baseband frequency error in assessment and the correction receiver |
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| CN101076947A true CN101076947A (en) | 2007-11-21 |
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| CN 200580037813 Pending CN101076947A (en) | 2004-11-08 | 2005-10-19 | Method and device for evaluating and mending base band frequency error of receiver |
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Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
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| CN107241285A (en) * | 2016-03-28 | 2017-10-10 | 三星显示有限公司 | The initial method of receiver, display and serial link |
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| Publication number | Priority date | Publication date | Assignee | Title |
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| CN107241285A (en) * | 2016-03-28 | 2017-10-10 | 三星显示有限公司 | The initial method of receiver, display and serial link |
| CN107241285B (en) * | 2016-03-28 | 2021-05-14 | 三星显示有限公司 | Receiver, display and serial link initialization method |
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