CN100490294C  Series resonant highfrequency chain sinusoidal wave inverse power supply circuit  Google Patents
Series resonant highfrequency chain sinusoidal wave inverse power supply circuit Download PDFInfo
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 CN100490294C CN100490294C CNB200410048604XA CN200410048604A CN100490294C CN 100490294 C CN100490294 C CN 100490294C CN B200410048604X A CNB200410048604X A CN B200410048604XA CN 200410048604 A CN200410048604 A CN 200410048604A CN 100490294 C CN100490294 C CN 100490294C
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 power tube
 end
 prime
 back grade
 high frequency
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 239000003990 capacitor Substances 0.000 claims description 25
 238000006243 chemical reaction Methods 0.000 claims description 10
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 Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSSSECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSSREFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
 Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
 Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED ENDUSER APPLICATIONS
 Y02B70/00—Technologies for an efficient enduser side electric power management and consumption
 Y02B70/10—Technologies improving the efficiency by using switchedmode power supplies [SMPS], i.e. efficient power electronics conversion
 Y02B70/14—Reduction of losses in power supplies
 Y02B70/1416—Converters benefiting from a resonance, e.g. resonant or quasiresonant converters
 Y02B70/1441—Converters benefiting from a resonance, e.g. resonant or quasiresonant converters in DC/AC or AC/DC converters

 Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSSSECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSSREFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
 Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
 Y02P—CLIMATE CHANGE MITIGATION TECHNOLOGIES IN THE PRODUCTION OR PROCESSING OF GOODS
 Y02P80/00—Climate change mitigation technologies for sectorwide applications
 Y02P80/10—Efficient use of energy
 Y02P80/11—Efficient use of energy of electric energy
 Y02P80/112—Power supplies with power electronics for efficient use of energy, e.g. power factor correction [PFC] or resonant converters
Abstract
Description
Technical field
The present invention relates to a kind of sinewave inverter circuit, adopt series resonance to realize the sinewave inverter circuit of the current source type high frequency chain isolation transmission of power.
Background technology
At present, sinewave inverter is widely used in ups system, alternating current machine power supply, induction heating and renewable energy system, and high frequency chain inversion transformation technique substitutes traditional inversion transformation technique just gradually with advantages such as its highperformance, high reliability, smallsized light weights.According to different circuit structures, highfrequency chain inverter mainly is divided into voltagesource type, current source type and difference frequency pattern etc.
Unidirectional electrical potential source sinewave inverter is owing to contain the diode rectification part in the main circuit, and energy can only oneway transmission; Owing to contain the twostage low frequency filtering, the volume of inverter is relatively large, system responses is slow again; And the transmission of its two stage power, power component is many in the circuit, loss is big, efficient is low; The quasisinglestage sinewave inverter of development is realized transmitted in both directions, minimizing filtering progression, the quickening system responses of energy on its basis.
Twoway cycle voltage of transformation source type sinewave inverter adopts bidirectional switch, and during the change of current, transformer secondary leakage inductance, filter inductance and inductive load electric current do not have continuous current circuit, produces voltage overshoot and causes circuit reliability poor, and electromagnetic interference is serious; Adopt back level active clamp and soft switch technique to realize the overvoltage supression, but inevitably increased the complexity of circuit and control, also reduced the reliability of circuit working simultaneously.
Twoway flyback current source inverter relative voltage source inventer, its circuit structure is simple relatively, and is less also fairly simple owing to switching device in control; Also solved the intrinsic voltageovershoot problem of voltage source inverter simultaneously.But because inverter is a theoretical foundation with the Power Conversion operation principle of inverseexcitation type DC/DC, all switches are operated in the discontinuous current state, and main switching device bears bigger current stress; The utilization ratio of flyback transformer is also lower, and the duty ratio of switch generally is no more than 0.45, and the utilance of power supply is not high yet, generally only is suitable for the lowpower applications scope.
Twoway difference frequency type inverter according to the difference frequency principle, utilizes two groups of high frequency transformers to isolate and waveform combination, and the difference frequency voltage waveform that obtains having the bidirectional voltage mode characteristic through the synchronous modulation and the LC filtering of bidirectional switch, is output as the sine wave of fundamental frequency.The former avris of inverter needs two groups of highfrequency inversion bridges, and circuit structure complexity, number of switches efficiencies of transmission numerous, inverter are not high; In order to realize difference frequency work, also need two transformers with two groups of secondary, this has strengthened the design difficulty of transformer and the task complexity of circuit simultaneously.
Summary of the invention
In order to overcome the abovementioned problems in the prior art, the invention provides a kind of series resonance high frequency chain sinewave inverter circuit, the present invention has realized the bidirectional power transmission of inverter, all power switch pipes work in omnidistance zero current condition, overcome the intrinsic voltage overshoot of voltage source highfrequency chain inverter, realize current source inverter in, the high power capacity transmission, and improve the power supply reliability of operation.
The technical scheme that the present invention solves its technical problem employing is:
The full bridge structure that the prime full bridge inverter adopts first to fourth prime power tube to constitute, the series resonance of resonant inductance and resonant capacitance realizes the conversion of directcurrent input power supplying to the resonance current source, and realizes that at the zero crossing in resonance current source the switch of all power tubes switches.
Adopt the high frequency transformer of a former limit winding, two secondary windings to realize the coupled transfer in resonance current source, two secondary winding N2, N3 are the reversed polarity coiling of equal turn numbers.
Two secondary windings of high frequency transformer and first to fourth a back grade power tube are combined into common emitter, halfbridge mode and 3 kinds of structures of common collector, realize all wave conversions of back level; Described first to fourth prime power tube and described first to fourth back grade power tube are to have the power tube of inverse parallel diode in the body or formed by diodeless power tube and diode combinations in the body.
When omitting output inductor, solved because the voltage overshoot that filter inductance causes when not having continuous current circuit; And, when realizing the power capacity of multimode expanding system in parallel, be exactly the parallel connection that equivalence becomes filter capacitor owing to adopt capacitor filtering.
The invention has the beneficial effects as follows: the full bridge structure of four switches, resonant inductance and resonant capacitance convert the input dc power potential source to the highfrequency resonant current source, and the zero crossing that utilizes resonance current realizes the omnidistance Zero Current Switch of all power transistors, need not when circuit design to consider that the switch of power transistor absorbs circuit.Two secondary windings of former limit winding high frequency transformer is realized power transmission and electrical isolation; The original edge voltage of high frequency transformer is an output load voltage reduced value, rather than direct current voltage, thereby effectively reduces umber of turn in the design of transformer, also with regard to the corresponding influence that has reduced the stray parameter of transformer to the circuit operation.The reasonable connection of two secondary windings of high frequency transformer and four power transistor S1, S2, S3, S4 realizes all wave conversion of resonance current source to the powerfrequency voltage source, not only simplified circuit structure, and in control, need not to detect the twoway flow that the output current direction just can realize power, control logic is simple.The cycle conversion fraction is realized the change of current of nature high frequency by diode in the body of power transistor when realizing the power forward transmitted, need not the driven of power transistor, thereby reduces the switching loss of power transistor.No matter during in the forward transmitted of power or reverse transfer, diode is all realized the change of current at the zero crossing of resonance current in power transistor or its body, so transformer leakage inductance stored energy has not fundamentally been eliminated because the voltageovershoot problem that transformer leakage inductance causes.Output adopts capacitor filtering, does not therefore exist because the overpressure problems that filter inductance does not have continuous current circuit to cause; Being connected in parallel on of multimode is exactly in fact the parallel connection of output capacitance, thereby adopts the power capacity expansion of the hot plug realization in parallel system of multimode easily.
Description of drawings
The present invention is further described below in conjunction with drawings and Examples.
Fig. 1 is the electrical connection diagram of first embodiment of the present invention;
Fig. 2 is the electrical connection diagram of second embodiment of the present invention;
Fig. 3 is the electrical connection diagram of the 3rd embodiment of the present invention.
In abovementioned accompanying drawing, V _{DC}Be directcurrent input power supplying, M1, M2, M3, M4 are the prime power tube that has inverse parallel diode in the body, L _{r}Be series resonance inductance, C _{r}Be series resonance electric capacity, N1 is the former limit of a high frequency transformer winding, and N2 is the high frequency transformer first secondary winding, and N3 is the high frequency transformer second secondary winding, and S1, S2, S3, S4 are the back level power tube that has inverse parallel diode in the body, C _{o}Be output filter capacitor, R _{L}Be load, i _{Lr}Be resonance current; I _{o}Be output current, V _{o}Be sine wave output voltage.
Embodiment
Embodiment 1
In Fig. 1, the prime full bridge inverter adopts the full bridge structure that is made of first to fourth prime power tube, directcurrent input power supplying V _{DC}Positive pole link to each other with the drain electrode of the first prime power tube M1 and the 3rd prime power tube M3, negative pole links to each other with the source electrode of the second prime power tube M2 and the 4th prime power tube M4; The series resonance inductance L _{r}An end link to each other the other end and series resonance capacitor C with the source electrode of the first prime power tube M1 and the drain electrode of the second prime power tube M2 _{r}An end link to each other; End of the same name and the series resonance capacitor C of the former limit winding N1 of high frequency transformer _{r}The other end link to each other, the different name end links to each other with the source electrode of the 3rd prime power tube M3 and the drain electrode of the 4th prime power tube M4; The series resonance inductance L _{r}With the series resonance capacitor C _{r}Series resonance realize the conversion of directcurrent input power supplying to the resonance current source, and realize the switch switching of first to fourth prime power tube (M1, M2, M3, M4) and first to fourth back grade power tube (S1, S2, S3, S4) at the zero crossing in resonance current source.
Adopt the described high frequency transformer of a former limit winding N1, two secondary windings (N2, N3) to realize the coupled transfer in resonance current source, two secondary windings (N2, N3) are the reversed polarity coiling.
Two secondary windings (N2, N3) by described high frequency transformer are realized back all wave conversions of level and filter circuit with described first to fourth back grade power tube (S1, S2, S3, S4): the end of the same name of a secondary winding N2 of described high frequency transformer links to each other with the collector electrode of the first back grade power tube S1, and the different name end links to each other with the collector electrode of the 3rd back grade power tube S3; The different name end of another secondary winding N3 of described high frequency transformer links to each other with the collector electrode of the second back grade power tube S2, and end of the same name links to each other with the collector electrode of the 4th back grade power tube S4; Output filter capacitor C _{o}An end and first the back grade power tube S1 and second the back grade power tube S2 emitter and load R _{L}An end link to each other output filter capacitor C _{o}The other end and the 3rd the back grade power tube S3 and the 4th the back grade power tube S4 emitter and load R _{L}The other end link to each other.
Described first to fourth prime power tube (M1, M2, M3, M4) and described first to fourth back grade power tube (S1, S2, S3, S4) are for having the power tube of inverse parallel diode in the body or being formed by diodeless power tube and diode combinations in the body.
Embodiment 2
In Fig. 2, the prime full bridge inverter adopts the full bridge structure that is made of first to fourth prime power tube, directcurrent input power supplying V _{DC}Positive pole link to each other with the drain electrode of the first prime power tube M1 and the 3rd prime power tube M3, negative pole links to each other with the source electrode of the second prime power tube M2 and the 4th prime power tube M4; The series resonance inductance L _{r}An end link to each other the other end and series resonance capacitor C with the source electrode of the first prime power tube M1 and the drain electrode of the second prime power tube M2 _{r}An end link to each other; End of the same name and the series resonance capacitor C of the former limit winding N1 of high frequency transformer _{r}The other end link to each other, the different name end links to each other with the source electrode of the 3rd prime power tube M3 and the drain electrode of the 4th prime power tube M4; The series resonance inductance L _{r}With the series resonance capacitor C _{r}Series resonance realize the conversion of directcurrent input power supplying to the resonance current source, and realize the switch switching of first to fourth prime power tube (M1, M2, M3, M4) and first to fourth back grade power tube (S1, S2, S3, S4) at the zero crossing in resonance current source.
Adopt the described high frequency transformer of a former limit winding N1, two secondary windings (N2, N3) to realize the coupled transfer in resonance current source, two secondary windings (N2, N3) are the reversed polarity coiling.
Two secondary windings (N2, N3) by described high frequency transformer are realized back all wave conversions of level and filter circuit with described first to fourth back grade power tube (S1, S2, S3, S4): the end of the same name of a secondary winding N2 of described high frequency transformer links to each other with the collector electrode of the first back grade power tube S1, and the different name end links to each other with the collector electrode of the 3rd back grade power tube S3; The end of the same name of another secondary winding N3 of described high frequency transformer links to each other with the emitter of the second back grade power tube S2, and the different name end links to each other with the emitter of the 4th back grade power tube S4; Output filter capacitor C _{o}An end and first the back grade power tube S1 emitter, the 4th the back grade power tube S4 collector electrode and load R _{L}An end link to each other output filter capacitor C _{o}The other end and the 3rd the back grade power tube S3 emitter, second the back grade power tube S2 collector electrode and load R _{L}The other end link to each other.
Described first to fourth prime power tube (M1, M2, M3, M4) and described first to fourth back grade power tube (S1, S2, S3, S4) are for having the power tube of inverse parallel diode in the body or being formed by diodeless power tube and diode combinations in the body.
Embodiment 3
In Fig. 3, the prime full bridge inverter adopts the full bridge structure that is made of first to fourth prime power tube, directcurrent input power supplying V _{DC}Positive pole link to each other with the drain electrode of the first prime power tube M1 and the 3rd prime power tube M3, negative pole links to each other with the source electrode of the second prime power tube M2 and the 4th prime power tube M4; The series resonance inductance L _{r}An end link to each other the other end and series resonance capacitor C with the source electrode of the first prime power tube M1 and the drain electrode of the second prime power tube M2 _{r}An end link to each other; End of the same name and the series resonance capacitor C of the former limit winding N1 of high frequency transformer _{r}The other end link to each other, the different name end links to each other with the source electrode of the 3rd prime power tube M3 and the drain electrode of the 4th prime power tube M4; The series resonance inductance L _{r}With the series resonance capacitor C _{r}Series resonance realize the conversion of directcurrent input power supplying to the resonance current source, and realize the switch switching of first to fourth prime power tube (M1, M2, M3, M4) and first to fourth back grade power tube (S1, S2, S3, S4) at the zero crossing in resonance current source.
Adopt the described high frequency transformer of a former limit winding N1, two secondary windings (N2, N3) to realize the coupled transfer in resonance current source, two secondary windings (N2, N3) are the reversed polarity coiling;
Two secondary windings (N2, N3) by described high frequency transformer are realized back all wave conversions of level and filter circuit with described first to fourth back grade power tube (S1, S2, S3, S4): the end of the same name of a secondary winding N2 of described high frequency transformer links to each other with the emitter of the 3rd back grade power tube S3, and the different name end links to each other with the emitter of the first back grade power tube S1; The end of the same name of another secondary winding N3 of described high frequency transformer links to each other with the emitter of the second back grade power tube S2, and the different name end links to each other with the emitter of the 4th back grade power tube S4; Output filter capacitor C _{o}An end and the 3rd the back grade power tube S3 and the 4th the back grade power tube S4 collector electrode and load R _{L}An end link to each other output filter capacitor C _{o}The other end and first the back grade power tube S1 and second the back grade power tube S2 collector electrode and load R _{L}The other end link to each other.
Described first to fourth prime power tube (M1, M2, M3, M4) and described first to fourth back grade power tube (S1, S2, S3, S4) are for having the power tube of inverse parallel diode in the body or being formed by diodeless power tube and diode combinations in the body.
In the abovedescribed embodiments, the drive signal of the power transistor that all labels are identical is consistent.
Claims (3)
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DE102006025975B4 (en) *  20060602  20080828  Siemens Ag Österreich  Inverter circuit and method for operating the inverter circuit 
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CN102594317B (en) *  20110110  20140723  曹先国  Power switch with voltage polarity inversion function 
WO2013005405A1 (en) *  20110704  20130110  パナソニック株式会社  Switching power supply 
CN102437750B (en) *  20111031  20140730  上海大学  Digital control device and method of LLC (Logic Link Control) synchronous rectification resonant converter 
CN102624275A (en) *  20120416  20120801  唐山电动车研发与检测有限公司  Inverter based on digital signal processor (DSP) phaseshifted full bridge 
CN102723873B (en) *  20120601  20150107  燕山大学  Dualinput fullisolation integrated current transformer 
CN103795251A (en)  20121029  20140514  台达电子工业股份有限公司  Power converter and control method thereof 
CN103956930B (en) *  20140519  20160817  电子科技大学  A kind of frequency modulating method for full bridge inverter 
CN105915095A (en) *  20160506  20160831  燕山大学  LC series resonance high frequency chain matrixtype inverter topology and resonance modulation method thereof 
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