CN100481757C - Super-complementary-code generating method, and communication system using the same - Google Patents

Abstract

This invention discloses a super complementary code producing method, the system and the communication system using the super complementary code. At first produce N complete complementary codes, and every complementary code has N basic codes, and every basic code has N to the power 2 elements, interacting compute the basic codes to get several complementary codes, every super complementary code has several sub-code, and every sub-code has at least one element. The system producing super complementary is mainly composed of orthogonal matrix assembly, the sequence producer, the complete complementary code producer and the super complementary producer. The super complementary code produced by this invention has the characteristics of 'non-connection interference' and 'non-multi-way interference'. In addition, because the length of the sub-code of the super complementary code can be lowered to 1, so it can lower the ratio of the gain value and the number of users to 1 at least, and the super complementary code of this invention can increase the number of supporting communication users.

Description

Produce the system of super-complementary-code and utilize the communication system of super-complementary-code

Technical field

The present invention relates to a kind of production method and generation system of mutual-complementing code, and code division multiple address communication system, especially, relate to the generation system of super-complementary-code and utilize the code division multiple address communication system of super-complementary-code.

Background technology

When third generation wireless communication system was about to enter global deployment, the realization framework of fourth-generation system had become one of modal research topic of present communication circle.Yet its performance of air interface (air-interface) technology that is used for third generation system at present should be done further improvement, to satisfy the needs of fourth-generation system.In a mobile communication system, ' up ' refers to by the transmission of mobile phone end to the base station direction, and ' descending ' refers to by the transmission of base station to mobile phone.Now based on traditional code division multiple access (CDMA) technology second and third in generation system (as IS-95, WCDMA and cdma2000) up link (up-link) be generally asynchronous and be easy to generate a lot of problems, thereby become a weakness in the whole wireless transmission loop.Because with complete obiteration, (Multiple Access Interference MAI), so that influences performance to the orthogonality between the user identification code and cause inserting interference than multiple access more serious in down link (down-link) in up link.This data transmission bauds that has also caused up link in the non-synchronous transmissions characteristic of up link is far below down link, thereby limited the total amount of data of whole system.Because the change that not stopping mobile and different user and different base station between relative distance of each cellphone subscriber in a sub-district, caused the up link of a mobile communication system must be operated on the pattern of non-synchronous transmissions, this asynchronous characteristic in up link make we can not when uplink, use desirable orthogonal code (as Walsh-Hadamard codes and OVSF codes ... etc.).Therefore, in the up link of existing second and third system, all used imperfect orthogonal code (as Gold codes and Kasami codes), because imperfect orthogonal code will be more more effective than desirable orthogonal code under asynchronous channel in generation.Yet, only in up link, use imperfect orthogonal code not tackle the problem at its root, because it is very difficult will removing to control the their cross correlation of Gold codes or Kasami codes sign indicating number and intersymbol in an asynchronous up link, sometimes because produced high cross correlation value, and the radio transmission performance in this zone is greatly descended to unacceptable strange or even cycle.

Up to the present, in the mobile communication system (as IS-95, WCDMA and cdma2000) based on traditional C DMA technology, still can't guarantee has the similar radio transmission performance of up-downgoing in synchronous down link and asynchronous up link.At first, mainly determine because transmit the size of signal power in the ascender by the mobile phone lithium battery.Be sent to outdoor signal energy because the user usually at the indoor mobile phone of beating, will be lowered again greatly again, and there only have a fraction of energy to spread out of by window to be outdoor to the base station.The second, between mobile phone and the base station difference of antenna height also determined in up link to be covered easilier, the influence of local scattering (local scattering) or transmission/penetration loss etc.The 3rd, up link is because the data that are transmitted into the base station from each mobile phone end in same sub-district are asynchronous, so the part aperiodicity cross-correlation function of User Recognition intersymbol, rather than correlation function periodically, has determined the radio transmission performance of up link; Unfortunately, the former more is difficult to control than the latter usually, has also caused inserting interference problem than multiple access even more serious in down link.

Therefore, be necessary to provide the code division multiple access system of a kind of innovation and tool progressive, to address the above problem.

With the user identification code of mutual-complementing code, be a solution as code division multiple address communication system.About mutual-complementing code and expansion thereof, more existing paper publishings, for example, (N moves the mutual orthogonal sequence of preface to " the N-ShiftCross-Orthogonal Sequences.IEEE Trans.On Information Theory; vol.34; no.1; pp.143-146; Jan.1988 " of Suehiro N and Hatori N, IEEE information theory transactions, in January, 1988, the 34th volume, the 1st phase, the 143-146 page or leaf), " the ComplementarySets of Sequences.IEEE Trans.On Information Theory; vol.IT-18; pp.644-652, Sept.1972 " of C-C TSENG and C.L.Liu (the complementation set of sequence, IEEE information theory transactions, in September, 1972, the 18th volume, the 5th phase, 644-652 page or leaf), " the Complete complementary codecomposed of N-multiple-shift orthogonal sequences Trans.IECE of Japan; vol.J65-A, pp.1247-1253, Dec.1982 " of Suehiro N (moves the complete complementary code that the orthogonal sequence of preface is formed by the multiple of N, Japan IECE transactions, December nineteen eighty-two, J65-A volume, 1247-1253 page or leaf).These papers have provided definition, character and the extended mode of complete complementary code, but very strong mutual constraint is arranged between code length and basic code number, the supported number of users, the number of combinations of code length and basic code number is limited, and the number of combinations of code length and number of users is limited.For example, the complete complementary code that proposes in the paper of Suehiro just needs N ³N address (user) supported in the position, processing gain (PG, a processing gain) timing, and number of users is less, uses inconvenience.

Also there are some patents on the basis of complete complementary code, to expand new sign indicating number.A kind of spread spectrum multiple access coding method of patent PCT/CN00/00028 (CN 1156094C) with zero correlation window; be with two basic codes of mutual-complementing code sequence arrangement (not overlapping on the time) in time; central insertion guardtime interval, thus make its correlation properties have zero correlative window characteristic.As long as channel maximum time diffusing capacity with maximum timing error sum less than length of window, then cdma system does not have that multiple access insert to disturb, no multipath interference (multipath interference).Another patent PCT.JP00/00373 (CN 1145281C) uses the adaptive interference-free spread-spectrum system of the binary code sequence sets with zero correlation zone properties, provide a binary system frequency expansion sequence with zero correlation block (ZCZ) characteristic, a sequence (sign indicating number) is distributed to a user, the width of ZCZ is adjusted according to channel condition, and then spread spectrum system (particularly DS-CDMA system) works in noiseless mode.What above-mentioned two patents produced all is the sign indicating number with zero correlation window, and multiple access access interference and multipath disturb and can't eliminate outside the zero correlation window.Its zero correlation window limited length because bigger zero correlation window means bigger protection (overhead) at interval, and makes the number of codes (supported number of users) that produces reduce.

Summary of the invention

The objective of the invention is at the deficiencies in the prior art, a kind of system that produces super-complementary-code is provided.Make the super-complementary-code that is produced have the characteristic of " the no multiple access of the two-way same sex (isotropic) inserts and disturbs " and " the two-way same sex does not have multipath and disturbs "." the two-way same sex does not have multiple access and inserts interference " no matter refer in the synchronous or asynchronous channel of upstream or downstream, any relative time skew cross correlation value between any two user identification code down is zero." the two-way same sex does not have multipath and disturbs " no matter refer in the synchronous or asynchronous channel of upstream or downstream, any relative time skew auto-correlation submaximum value of any one user identification code down is zero.Therefore, two-way same sex code division multiple address communication system of the present invention can successfully be eliminated all harmful multiple access and insert interference and multipath interference, improves signal receiving performance greatly.In addition, the super-complementary-code that the present invention produces is because the length of its subcode can be reduced to 1, so the I of the ratio of its processing gain (PG, processing gain) value and number of users is reduced to 1, and the super-complementary-code that utilizes the present invention to produce can improve support user's number.

The present invention seeks to be achieved through the following technical solutions: a kind of system that produces super-complementary-code is characterized in that this system comprises:

One orthogonal matrix library module, have one first orthogonal matrix, one second orthogonal matrix and one the 3rd orthogonal matrix, the dimension of described first orthogonal matrix, second orthogonal matrix and the 3rd orthogonal matrix is N * N, and the absolute value of its each element is 1, and N is a positive integer.

One sequence generator, with described first orthogonal matrix of cause and the second orthogonal matrix computing and produce N sequence, each sequence has N ²Individual element.

One complete complementary code generator, with the described sequence of cause and the 3rd orthogonal matrix computing and produce N complete complementary code, each complete complementary code has N basic code, and each basic code has N ²Individual element.And a super-complementary-code generator, producing a plurality of super-complementary-codes with the described basic code interacting operation of cause, each super-complementary-code has a plurality of subcodes, and each subcode has at least one element.

The present invention also aims to provide a kind of code division multiple address communication system that utilizes super-complementary-code.

The present invention seeks to be achieved through the following technical solutions: a kind of code division multiple address communication system that utilizes super-complementary-code comprises emitter and receiving system.

Emitter comprises:

A plurality of spread spectrum modulator form a plurality of spread-spectrum signals with a plurality of subcodes of super-complementary-code to the data spread spectrum; A plurality of carrier frequency modulators are modulated described spread-spectrum signal with a plurality of carrier frequencies; And the synthesizer that transmits, be used for synthetic spread-spectrum signal through the carrier frequency modulation to form a composite signal.

Receiving system comprises:

A plurality of carrier frequency demodulators are a plurality of spread-spectrum signals with a plurality of these composite signals of carrier frequency demodulation; A plurality of demodulators, a plurality of subcodes of using super-complementary-code are to the spread-spectrum signal demodulation; And a received signal synthesizer, be used for synthetic spread-spectrum signal through demodulation, with receive this user's data.

The present invention has following technique effect: the super-complementary-code that the present invention proposes can be as the user identification code of cdma system, and super-complementary-code of a user can be supported 2N ²Individual user.A super-complementary-code comprises 2N ²Individual subcode.Subcode length can be chosen independently, the shortlyest can be 1.In the existing document, the subcode length of complete complementary code is relevant with the complete complementary code number, if will support N user, then subcode length is N ²The super-complementary-code that the present invention proposes has desirable correlation properties.In subcode length, the periodic cross-correlation of super-complementary-code, aperiodic, cross-correlation was zero everywhere, and cycle auto-correlation, aperiodic, auto-correlation was zero except that the zero shift part everywhere.User identification code as cdma system, has orthogonality completely, under synchronous or asynchronous transmission, single footpath or multipath channel condition, all do not have multiple access to insert and disturb and the multipath interference, this system that makes becomes (noise-limited) of noise limited, than present interference-limited cdma system, capacity is largely increased.Sign indicating number in aforementioned two patents only has desirable correlation properties in zero correlation window; but zero correlation window limited length; because bigger zero correlation window means bigger protection (overhead) at interval; and the number of codes (supported number of users) that make to produce reduces, so multiple access inserts and disturbs and the multipath interference can't be eliminated outside the zero correlation window.

The present invention produces 2N ²Individual super-complementary-code is obtained N by the computing of first orthogonal matrix and second orthogonal matrix earlier ²Individual length is N ²Basic code; Use insertion again, and with the 3rd orthogonal matrix computing, the N N doubly that obtained extended length ²Individual basic code; Repeat previous step, up to obtaining N ²Individual basic code, the length of each basic code equal required subcode length and N ²Product; Obtain 2N by interacting operation at last ²Individual super-complementary-code, each super-complementary-code comprises 2N ²Individual subcode.

The cdma system of the super-complementary-code that proposes with the present invention is a multicarrier system.After user's data is distinguished spread spectrum by each subcode, via the carrier channel transmission of different frequency.That is to say that a plurality of subcodes walk abreast in time.And patent PCT/CN00/00028 (CN 1156094C) and PCT.JP00/00373 (CN1145281C) are single-carrier system.This patent system is because of a plurality of subcodes parallel transmission in time; do not need protection the time interval; avoided time overhead; and the frequency configuration of multiple carrier channel can adopt OFDM (OFDM) mode; the carrier wave mutually orthogonal of each subchannel; frequency spectrum is overlapped, has not only reduced the phase mutual interference between subcarrier, has further improved the availability of frequency spectrum simultaneously.In addition, the quadrature modulation of subchannel and demodulation can realize by the mode that adopts IDFT and DFT, greatly reduce system complexity.

Description of drawings

Fig. 1 produces the system configuration schematic diagram of super-complementary-code for the present invention;

Fig. 2 utilizes the structural representation of emitter of the code division multiple address communication system of super-complementary-code for the present invention;

Fig. 3 utilizes the structural representation of receiving system of the code division multiple address communication system of super-complementary-code for the present invention;

Fig. 4 utilizes the structural representation of emitter of employing OFDM mode of the code division multiple address communication system of super-complementary-code for the present invention;

Fig. 5 utilizes the structural representation of receiving system of employing OFDM mode of the code division multiple address communication system of super-complementary-code for the present invention;

Fig. 6 separates the spread spectrum schematic flow sheet for the present invention in single footpath and synchronously;

Fig. 7 for the present invention single footpath and asynchronous under separate the spread spectrum schematic flow sheet;

Fig. 8 separates the spread spectrum schematic flow sheet for the present invention in two footpaths and synchronously;

Fig. 9 for the present invention two footpaths and asynchronous under separate the spread spectrum schematic flow sheet.

The element shown symbol description:

10: the present invention produces the system of super-complementary-code, 11: the orthogonal matrix library module, 111: the first orthogonal matrixes, 112: the second orthogonal matrixes, 113: the three orthogonal matrixes, 12: sequence generator, 13: the complete complementary code generator, 14: the super-complementary-code generator, 15: the extended length device, 20: emitter, 21: the first emitters, 211,212,213: spread spectrum modulator, 214,215,216: the carrier frequency modulator, 217: synthesizer transmits, 22: the second emitters, 221,222,223: spread spectrum modulator, 224,225,226: the carrier frequency modulator, 227: synthesizer transmits, 23: the R emitters, 24: multipath channel, 30: receiving system, 31,32,33: the carrier frequency demodulator, 34,35,36: demodulator, 37: received signal synthesizer, 38: judgment device, 40: emitter, 41: the first emitters, 411: Fourier inversion device, 412: parallel/serial converter, 42: the second emitters, 421: Fourier inversion device, 422: parallel/serial converter, 43: the R emitters, 44: multipath channel, 50: receiving system, 51: serial/parallel converter, 52: Fourier transformer, 53: signal synthetic apparatus, 54: judgment device

Embodiment

Specify the present invention below with reference to the accompanying drawings.

See also Fig. 1, it shows that the present invention produces the integrated stand composition of the system 10 of super-complementary-code.The system 10 of this generation super-complementary-code comprises: an orthogonal matrix library module 11, a sequence generator 12, a complete complementary code generator 13, a super-complementary-code generator 14 and an extended length device 15.

This orthogonal matrix library module 11 has one first orthogonal matrix 111, one second orthogonal matrix 112 and one the 3rd orthogonal matrix 113.The dimension of this first orthogonal matrix 111, this second orthogonal matrix 112 and the 3rd orthogonal matrix 113 is N * N, and the absolute value of each element is 1, and N is a positive integer.

Make at first that A is first orthogonal matrix 111, and A _iBe i of A row vector (i=1,2 ..., N), represent with following formula (1):

$\begin{array}{ccc}A=\left[a_{\mathrm{ij}}\right]=\left[\begin{array}{c}{A}_1\\ {\mathrm{<figure-callout\; id="2"\; label="A"\; filenames="C200410089169E00221.png,C200410089169E00241.png"\; state="\{\{state\}\}">A</figure-callout>}}_2\\ \&CenterDot;\\ \&CenterDot;\\ \&CenterDot;\\ A_N\end{array}\right];& \left|a_{\mathrm{ij}}\right|=1,& \mathrm{for\; i},j=\mathrm{1,2},\&CenterDot;\&CenterDot;\&CenterDot;,N\end{array}---\left(1\right)$

Make that B is second orthogonal matrix 112, D is the 3rd orthogonal matrix 113 again, and B and D use (2) and (3) expression respectively:

B＝[b _ij]；|b _ij|＝1，for?i，j＝1，2，…，N (2)

D＝[d _ij]；|d _ij|＝1，for?i，j＝1，2，…，N (3)

This sequence generator 12 is to get N sequence C with these second orthogonal matrix, 112 computings by this first orthogonal matrix 111 ₁, C ₂..., C _N, each sequence has N ²Individual element, represent with following formula:

$\begin{array}{c}{\mathrm{<figure-callout\; id="1"\; label="C"\; filenames="C200410089169E00181.png,C200410089169E00221.png"\; state="\{\{state\}\}">C</figure-callout>}}_1=(b_{11}{\mathrm{<figure-callout\; id="1"\; label="A"\; filenames="C200410089169E00181.png,C200410089169E00221.png"\; state="\{\{state\}\}">A</figure-callout>}}_1,b_{12}{\mathrm{<figure-callout\; id="2"\; label="A"\; filenames="C200410089169E00221.png,C200410089169E00241.png"\; state="\{\{state\}\}">A</figure-callout>}}_2,\&CenterDot;\&CenterDot;\&CenterDot;,b_{1N}{A}_N)=({\mathrm{<figure-callout\; id="11"\; label="c"\; filenames="C200410089169E00171.png,C200410089169E00172.png"\; state="\{\{state\}\}">c</figure-callout>}}_{11},{\mathrm{<figure-callout\; id="12"\; label="c"\; filenames="C200410089169E00171.png,C200410089169E00172.png"\; state="\{\{state\}\}">c</figure-callout>}}_{12},\&CenterDot;\&CenterDot;\&CenterDot;,c_{{1N}^2})\\ {\mathrm{<figure-callout\; id="2"\; label="C"\; filenames="C200410089169E00221.png,C200410089169E00241.png"\; state="\{\{state\}\}">C</figure-callout>}}_2=(b_{21}{A}_1,b_{22}{A}_2,\&CenterDot;\&CenterDot;\&CenterDot;,b_{2N}{A}_N)=({\mathrm{<figure-callout\; id="21"\; label="c"\; filenames="C200410089169E00181.png"\; state="\{\{state\}\}">c</figure-callout>}}_{21},{\mathrm{<figure-callout\; id="22"\; label="c"\; filenames="C200410089169E00181.png"\; state="\{\{state\}\}">c</figure-callout>}}_{22},\&CenterDot;\&CenterDot;\&CenterDot;,c_{{2N}^2})\\ \&CenterDot;\\ \&CenterDot;\\ \&CenterDot;\\ C_N=(b_{N1}{A}_1,b_{N2}{A}_2,\&CenterDot;\&CenterDot;\&CenterDot;,b_{\mathrm{NN}}{A}_N)=({\mathrm{<figure-callout\; id="1"\; label="c\; N"\; filenames="C200410089169E00181.png,C200410089169E00221.png"\; state="\{\{state\}\}">c</figure-callout>}}_N,{\mathrm{<figure-callout\; id="2"\; label="c\; N"\; filenames="C200410089169E00221.png,C200410089169E00241.png"\; state="\{\{state\}\}">c</figure-callout>}}_N,\&CenterDot;\&CenterDot;\&CenterDot;,c_{{\mathrm{NN}}^2})\end{array}---\left(4\right)$

This complete complementary code generator 13 is by these sequence C ₁, C ₂..., C _NGet N complete complementary code E with 113 computings of the 3rd orthogonal matrix ₁, E ₂..., E _N, E wherein ₁={ E ₁₁, E ₁₂..., E _1N, E ₂={ E ₂₁, E ₂₂..., E _2N..., E _N={ E _N1, E _N2..., E _NNRespectively be a complete complementary code, each complete complementary code has N basic code, for example: E ₁₁, E ₁₂..., E _1N, each basic code has N ²Individual element, represent with following formula:

$E_{\mathrm{ij}}=(c_{i1}{\mathrm{<figure-callout\; id="1"\; label="d\; j"\; filenames="C200410089169E00181.png,C200410089169E00221.png"\; state="\{\{state\}\}">d</figure-callout>}}_j,\&CenterDot;\&CenterDot;\&CenterDot;,c_{\mathrm{iN}}{d}_{\mathrm{jN}},c_{i(N+1)}{\mathrm{<figure-callout\; id="1"\; label="d\; j"\; filenames="C200410089169E00181.png,C200410089169E00221.png"\; state="\{\{state\}\}">d</figure-callout>}}_j,\&CenterDot;\&CenterDot;\&CenterDot;,c_{i\left(2N\right)}{d}_{\mathrm{jN}},\&CenterDot;\&CenterDot;\&CenterDot;,c_{i(N^2-N+1)}{\mathrm{<figure-callout\; id="1"\; label="d\; j"\; filenames="C200410089169E00181.png,C200410089169E00221.png"\; state="\{\{state\}\}">d</figure-callout>}}_j,\&CenterDot;\&CenterDot;\&CenterDot;,c_{{\mathrm{iN}}^2}{d}_{\mathrm{jN}})$

(5)

$\begin{array}{cc}=({\mathrm{<figure-callout\; id="1"\; label="e\; ij"\; filenames="C200410089169E00181.png,C200410089169E00221.png"\; state="\{\{state\}\}">e</figure-callout>}}_{\mathrm{ij}},{\mathrm{<figure-callout\; id="2"\; label="e\; ij"\; filenames="C200410089169E00221.png,C200410089169E00241.png"\; state="\{\{state\}\}">e</figure-callout>}}_{\mathrm{ij}},\&CenterDot;\&CenterDot;\&CenterDot;,e_{{\mathrm{ijN}}^2}),& \mathrm{for\; i},j=\mathrm{1,2},\&CenterDot;\&CenterDot;\&CenterDot;,N\end{array}$

N basic code arranged in each complete complementary code that utilizes said method to produce, and the length of each basic code is N ²So the length of each complete complementary code is N * N ²=N ³If under the situation that does not change the basic code number that is comprised in each complete complementary code, wish to change the length of this complete complementary code, then can be in addition with an extended length device 15, with N complete complementary code with 113 computings of the 3rd orthogonal matrix and must an extended length N times complete complementary code.

This extended length device 15 is applicable on any complete complementary code, at first the basic code in the complete complementary code is become a sequence F with inserting the mode of arranging mutually, the length of this sequence then is the length of original complete complementary code, and the subcode length of establishing original complete complementary code is N ^R-1, N subcode arranged in the complete complementary code, this sequence F represents with following formula:

$F_i=(e_{i11},e_{i21},\&CenterDot;\&CenterDot;\&CenterDot;,e_{\mathrm{iN}1},e_{i12},e_{i22},\&CenterDot;\&CenterDot;\&CenterDot;,e_{\mathrm{iN}2},\&CenterDot;\&CenterDot;\&CenterDot;,e_{i1N^{r-1}}{e}_{i2N^{r-1}},\&CenterDot;\&CenterDot;\&CenterDot;,e_{\mathrm{iN}{N}^{r-1}})$

(6)

$\begin{array}{cc}=(f_{i1},f_{i2},\&CenterDot;\&CenterDot;\&CenterDot;,f_{{\mathrm{iN}}^r}),& \mathrm{for\; i}=\mathrm{1,2},\&CenterDot;\&CenterDot;\&CenterDot;N;r\&GreaterEqual;3\end{array}$

With above-mentioned N sequence F ₁, F ₂..., F _NReplace producing the sequence C of complete complementary code originally ₁, C ₂..., C _N, use sequence F again ₁, F ₂..., F _NThe computing of doing once in (5) formula with the 3rd orthogonal matrix 113 just can produce extended length N complete complementary code doubly.

Therefore, just can become original N to the subcode extended length in original complete complementary code as long as repeat the expansion of n aforesaid way ⁿDoubly (n is a positive integer), and the length of complete complementary code also and then expands to original N because subcode length changes ⁿDoubly (n is a positive integer), if but when complete complementary code used code division multiple access system, will find to compare with other traditional spreading codes, support under the identical situation of number of users that in maximum the PG value of this kind complete complementary code (length of subcode number * each subcode that each user uses) can be more a lot of greatly than other conventional code.Therefore, the present invention utilizes this super-complementary-code generator 14 again, gets 2N with these basic code interacting operations ²Individual super-complementary-code, each super-complementary-code has 2N ²Individual subcode, each subcode has at least one element.Recycling super-complementary-code generator 14 is described 2N ²Individual super-complementary-code is done expansion in the same way again, up to the number that produces required super-complementary-code and the number of elements of each subcode.

For convenience of description, shilling first, second and third above-mentioned orthogonal matrix 111,112 and A, B and these three orthogonal matrixes of D of 113 all are that a dimension is 2 Hadamard matrix, to (5) formula, then can produce E according to (1) ₁₁, E ₁₂, E ₂₁, E ₂₂Four basic codes, represent with following formula:

E ₁₁＝T ₁＝[T ₁₁，T ₁₂，T ₁₃，T ₁₄]

E ₁₂＝T ₂＝[T ₂₁，T ₂₂，T ₂₃，T ₂₄]

(7)

E ₂₁＝T ₃＝[T ₃₁，T ₃₂，T ₃₃，T ₃₄]

E ₂₂＝T ₄＝[T ₄₁，T ₄₂，T ₄₃，T ₄₄]

Four basic codes are done interacting operation, then can produce super-complementary-code, as shown in the formula expression:

S ₁＝{T ₁₁，T ₂₁，T ₁₂，T ₂₂，…，T ₁₄，T ₂₄}＝{S ₁₁，S ₁₂，…，S ₁₈}

S ₂＝{T ₁₁，T ₂₁，T ₁₂，T ₂₂，…，T ₁₄，T ₂₄}＝{S ₂₁，S ₂₂，…，S ₂₈}

S ₃＝{T ₂₁，T ₁₁，T ₂₂，T ₁₂，…，T ₂₄，T ₁₄}＝{S ₃₁，S ₃₂，…，S ₃₈}

S ₄＝{T ₂₁，T ₁₁，T ₂₂，T ₁₂，…，T ₂₄，T ₁₄}＝{S ₄₁，S ₄₂，…，S ₄₈}

(8)

S ₅＝{T ₃₁，T ₄₁，T ₃₂，T ₄₂，…，T ₃₄，T ₄₄}＝{S ₅₁，S ₅₂，…，S ₅₈}

S ₆＝{T ₃₁，T ₄₁，T ₃₂，T ₄₂，…，T ₃₄，T ₄₄}＝{S ₆₁，S ₆₂，…，S ₆₈}

S ₇＝{T ₄₁，T ₃₁，T ₄₂，T ₃₂，…，T ₄₄，T ₃₄}＝{S ₇₁，S ₇₂，…，S ₇₈}

S ₈＝{T ₄₁，T ₃₁，T ₄₂，T ₃₂，…，T ₄₄，T ₃₄}＝{S ₈₁，S ₈₂，…，S ₈₈}

Result according to (8) formula shows that through the super-complementary-code that super-complementary-code generator 14 is produced, the number of its code length and sign indicating number all becomes original twice.Therefore, can do expansion to the sign indicating number after the expansion more in the same way again, the number of code length of wanting up to obtaining and sign indicating number.Following (9) formula is the general general formula of extended mode of the present invention.

S ₁＝{T ₁₁，T ₂₁，T ₁₂，T ₂₂，…，T _1N，T _2N}＝{S ₁₁，S ₁₂，…，S _1(2N)}

S ₂＝{T ₁₁，T ₂₁，T ₁₂，T ₂₂，…，T _1N，T _2N}＝{S ₂₁，S ₂₂，…，S _2(2N)}

S ₃＝{T ₂₁，T ₁₁，T ₂₂，T ₁₂，…，T _2N，T _1N}＝{S ₃₁，S ₃₂，…，S _3(2N)}

S ₄＝{T ₂₁，T ₁₁，T ₂₂，T ₁₂，…，T _2N，T _1N}＝{S ₄₁，S ₄₂，…，S _4(2N)}

S _4j+1＝{T _(2j+1)1，T _(2j+2)1，T _(2j+1)2，T _(2j+2)2，…，T _(2j+1)N，T _(2j+2)N}

＝{S _(4j+1)1，S _(4j+1)2，…，S _(4j+1)2N}

S _4j+2＝{T _(2j+1)1，T _(2j+2)1，T _(2j+1)2，T _(2j+2)2，…，T _(2j+1)N，T _(2j+2)N}

＝{S _(4j+2)1，S _(4j+2)2，…，S _(4j+2)2N}

S _4j+3＝{T _(2j+2)1，T _(2j+1)1，T _(2j+2)2，T _(2j+1)2，…，T _(2j+2)N，T _(2j+1)N} (9)

＝{S _(4j+3)1，S _(4j+3)2，…，S _(4j+3)2N}

S _4j+4＝{T _(2j+2)1，T _(2j+1)1，T _(2j+2)2，T _(2j+1)2，…，T _(2j+2)N，T _(2j+1)N}

＝{S _(4j+4)1，S _(4j+4)2，…，S _(4j+4)2N}

.

.

.

S _2N-3＝{T _(N-1)1，T _N1，T _(N-1)2，T _N2，…，T _(N-1)N，T _NN}＝{S _(2N-3)1，S _(2N-3)2，…，S _(2N-3)2N}

S _2N-2＝{T _(N-1)1，T _N1，T _(N-1)2，T _N2，…，T _(N-1)N，T _NN}＝{S _(2N-2)1，S _(2N-2)2，…，S _(2N-2)2N}

S _2N-1＝{T _N1，T _(N-1)1，T _N2，T _(N-1)2，…，T _NN，T _(N-1)N}＝{S _(2N-1)1，S _(2N-1)2，…，S _(2N-1)2N}

S _2N＝{T _N1，T _(N-1)1，T _N2，T _(N-1)2，…，T _NN，T _(N-1)N}＝{S _(2N)1，S _(2N)2，…，S _(2N)2N}

for?j＝0，1，…，(N/2)-1

" T " expression " complementation of T " briefly is exactly the meaning of (-1) * T in the following formula.

Produce the embodiment of super-complementary-code

Now how to produce super-complementary-code with the following example explanation, at first, if wish that producing a sub-code length is 1, each mutual-complementing code has the super-complementary-code (2N of 8 subcodes ²=8, N=2), then at first make A, B, the D matrix of first, second and third orthogonal matrix in (1), (2), (3) all equal 2 * 2 Hadamard matrix, wherein+and expression+1 ,-expression-1:

$A=\left[\begin{array}{cc}+& +\\ +& -\end{array}\right],$ $B=\left[\begin{array}{cc}+& +\\ +& -\end{array}\right],$ $D=\left[\begin{array}{cc}+& +\\ +& -\end{array}\right]$

Then with first and second orthogonal matrix A and B computing to produce the C sequence in (4) formula:

C ₁＝(+?+?+?-)

C ₂＝(+?+?-?+)

Again with sequence C and the 3rd orthogonal matrix D computing producing the E in (5) formula,

E ₁₁＝T ₁＝(+?+?+?-)

E ₁₂＝T ₂＝(+?-?+?+)

E ₂₁＝T ₃＝(+?+?-?+)

E ₂₂＝T ₄＝(+?-?-?-)

This just obtains the basic code in (7) formula, and the length of these basic codes is 4.Utilize the method in (9) formula that basic code is extended to super-complementary-code again, super-complementary-code has 8 subcodes, can support 8 users, and the length of each subcode is 1, and distinguishes each subcode with comma.

S ₁＝(+，+，+，-，+，+，-，+)

S ₂＝(+，-，+，+，+，-，-，-)

S ₃＝(+，+，-，+，+，+，+，-)

S ₄＝(+，-，-，-，+，-，+，+)

S ₅＝(+，+，+，-，-，-，+，-)

S ₆＝(+，-，+，+，-，+，+，+)

S ₇＝(+，+，-，+，-，-，-，+)

S ₈＝(+，-，-，-，-，+，-，-)

Therefore, according to above embodiment, the processing gain of the super-complementary-code that the present invention produced (PG) is 8 * 1=8 (length of subcode number * each subcode that each user uses).And because the length of its subcode can be reduced to 1, so the I of the ratio of its processing gain (PG) value and number of users is reduced to 1, therefore, the super-complementary-code that utilizes the present invention to produce can improve support user's number.

If wish that producing a sub-code length is 4, each mutual-complementing code has the super-complementary-code of 8 subcodes, then similarly makes A, B, the D matrix of first, second and third orthogonal matrix in (1), (2), (3) all equal 2 * 2 Hardamard matrix.

$A=\left[\begin{array}{cc}+& +\\ +& -\end{array}\right],$ $B=\left[\begin{array}{cc}+& +\\ +& -\end{array}\right],$ $D=\left[\begin{array}{cc}+& +\\ +& -\end{array}\right]$

Then with first and second orthogonal matrix A and B computing to produce the C sequence in (3) formula:

C ₁＝(+?+?+?-)

C ₂＝(+?+?-?+)

Again with sequence C and the 3rd orthogonal matrix D computing producing the E in (5) formula,

E ₁₁＝T ₁＝(+?+?+?-)

E ₁₂＝T ₂＝(+?-?+?+)

E ₂₁＝T ₃＝(+?+?-?+)

E ₂₂＝T ₄＝(+?-?-?-)

Utilize the extended mode in (6) formula again, uses twice afterwards just can be 4 times of the extended length of each basic code,

E ₁₁＝T ₁＝(+?+?+?-?+?+?-?+?+?+?+?-?-?-?+?-)

E ₁₂＝T ₂＝(+?-?+?+?+?-?-?-?+?-?+?+?-?+?+?+)

E ₂₁＝T ₃＝(+?+?+?-?+?+?-?+?-?-?-?+?+?+?-?+)

E ₂₂＝T ₄＝(+?-?+?+?+?-?-?-?-?+?-?-?+?-?-?-)

This just obtains the basic code in (7) formula, and the length of these basic codes is 16.Utilize once the method in (9) formula that complete complementary code is extended to super-complementary-code again, this super-complementary-code has 8 subcodes, can support 8 users, and each subcode length is 4, and distinguishes each subcode with comma.

S ₁＝(+++-，+-++，++-+，+---，+++-，+-++，--+-，-+++)

S ₂＝(+++-，-+--，++-+，-+++，+++-，-+--，--+-，+---)

S ₃＝(+-++，+++-，+---，++-+，+-++，+++-，-+++，--+-)

S ₄＝(+-++，---+，+---，--+-，+-++，---+，-+++，++-+)

S ₅＝(+++-，+-++，++-+，+---，---+，-+--，++-+，+---)

S ₆＝(+++-，-+--，++-+，-+++，---+，+-++，++-+，-+++)

S ₇＝(+-++，+++-，+---，++-+，-+--，---+，+---，++-+)

S ₈＝(+-++，---+，+---，--+-，-+--，+++-，+---，--+-)

Therefore, utilize extended length device 15 of the present invention (just utilizing the extended method of (6) formula), can determine the length of each subcode of super-complementary-code.Utilize super-complementary-code generator 14 of the present invention (just utilizing the method for (9) formula) again, can determine the subcode number of each super-complementary-code, the number of users that can support.So utilize system 10 of the present invention can produce any needed super-complementary-code.

Utilize the code division multiple access system of super-complementary-code

With reference to shown in Figure 2, it shows that the present invention utilizes the emitter 20 of the code division multiple access system of super-complementary-code, and emitter 20 comprises: launch first subscriber signal first emitter 21, emission second subscriber signal second emitter 22 and launch the R emitter 23 etc. of R subscriber signal.Be the example explanation now with first emitter 21 and second emitter 22.

First emitter 21 comprises: a plurality of spread spectrum modulator 211,212,213,214,215,216 and synthesizers 217 that transmit of a plurality of carrier frequency modulator.These spread spectrum modulators the 211,212, the 213rd are with a plurality of subcode (S ₁₁, S ₁₂, S _1RDeng) this first user's data spread spectrum is formed a plurality of spread-spectrum signals.These subcodes (S wherein ₁₁, S ₁₂, S _1RDeng) be the subcode of first super-complementary-code of being produced according to above-mentioned generation super-complementary-code system 10.

A plurality of carrier frequency modulators the 214,215, the 216th are with a plurality of carrier frequency (f ₁, f ₂, f _RDeng) modulate these spread-spectrum signals.Synthesizer 217 is used for synthesizing these spread-spectrum signals through the carrier frequency modulation and forms a composite signal thereby this transmits.

Similarly, second emitter 22 comprises: a plurality of spread spectrum modulator 221,222,223, a plurality of carrier frequency modulator 224,225,226 and a synthesizer 227 that transmits.These spread spectrum modulator the 221,222, the 223rd are with a plurality of subcode (S ₂₁, S ₂₂, S _2RDeng) this second user's data spread spectrum is formed a plurality of spread-spectrum signals.These subcodes (S wherein ₂₁, S ₂₂, S _2RDeng) be the subcode of 10 second super-complementary-code that is produced of the above-mentioned generation super-complementary-code of foundation system.A plurality of carrier frequency modulators the 224,225, the 226th are with a plurality of carrier frequency (f ₁, f ₂, f _RDeng) modulate these spread-spectrum signals.Synthesizer 227 is used for synthesizing these spread-spectrum signals through the carrier frequency modulation and forms a composite signal thereby this transmits.Be sent to multipath channel 24 by the composite signal of first emitter 21 and the composite signal of second emitter 22.

With reference to shown in Figure 3, receiving system 30 is used for receiving the composite signal of this emitter 20.This receiving system 30 comprises: a plurality of carrier frequency demodulators 31,32,33, a plurality of demodulator 34,35,36, a received signal synthesizer 37 and a judgment device 38.A plurality of carrier frequency demodulators the 31,32, the 33rd are with a plurality of carrier frequency (f ₁, f ₂, f _RDeng) this composite signal of demodulation is a plurality of spread-spectrum signals.

A plurality of demodulators the 34,35, the 36th are with a plurality of subcode (S ₁₁, S ₁₂, S _1RDeng) to these spread-spectrum signal demodulation, because this receiving system 30 is the signals that are used for receiving first user, so these subcodes are identical with the subcode of first super-complementary-code of the spread spectrum modulator 211,212,213 of Fig. 2.

Received signal synthesizer 37 is used for synthesizing the spread-spectrum signal through demodulator.Carry out the soft-decision or the hard decision of data via judgment device (Decision Device) 38 again, so that obtain first user's signal.

With reference to shown in Figure 4, it shows that the present invention utilizes the code division multiple access system of super-complementary-code to adopt the emitter structural representation of OFDM mode.Fourier inversion device 411 in first emitter 41 and parallel/serial converter 412 have replaced a plurality of carrier frequency modulators 214,215,216 and the synthesizer 217 that transmits in first emitter 21 among Fig. 2.Equally, Fourier inversion device 421 in second emitter 42 and parallel/serial converter 422 have replaced a plurality of carrier frequency modulators 224,225,226 and the synthesizer 227 that transmits in second emitter 22 among Fig. 2.

With reference to shown in Figure 5, it shows that invention utilizes the code division multiple access system of super-complementary-code to adopt the receiving system structural representation of OFDM mode.Serial/parallel converter 51 and Fourier transformer 52 have replaced a plurality of carrier frequency demodulators 31,32,33 among Fig. 3.

Be applied in advantage on the code division multiple access system for understanding super-complementary-code that native system produced, with reference to figure 6 to Fig. 9, the performance results of correlation function complementary characteristic on code division multiple access system that shows super-complementary-code in illustrated mode, the super-complementary-code that uses in the present embodiment is as follows, can support four users at most, each user uses a super-complementary-code, each super-complementary-code is to be become by 4 sub-code characters, each subcode length is 4, each user is when doing signal spread-spectrum, same data are used four subcode spread spectrums simultaneously, separately transmit, to receiving terminal is made despreading of correlator after, add up again.Each user is as follows as the super-complementary-code of spreading code:

User 1:C ₁₁:+++-C ₁₂:++-+C ₁₃:+++-C ₁₄:---+-

User 2:C ₂₁:+-++ C ₂₂:+---C ₂₃:+-++ C ₂₄:-+++

User 3:C ₃₁:+++-C ₃₂:++-+C ₃₃:---+C ₃₄:++-+

User 4:C ₄₁:+-++ C ₄₂:+---C ₄₃:-+---C ₄₄:+---

In order not make the demonstration among the figure too mixed and disorderly, only the situation with first user and second user illustrates that the situation at the 3rd user and four-function family also is similar.Suppose that at this signal of first user is desired signal, and second user's signal is a interference signal from other users to first user, does not consider noise.In order to make this communication system have more generality, suppose that three data bits that first user is transmitted are+1-1+1, and continuous three data bits that second user transmitted are+1+1-1.

As shown in Figure 6, consider under single footpath and sync status the situation of system down link (Downlink) earlier.Consider Fig. 7 again, it is a situation of considering up link (Uplink), that is to say that first user and second user are non-synchronous driving data, supposes that at this second user postpones the time of a chip period (chip) than first user.Show by Fig. 6 and Fig. 7, no matter at up link or down link, as long as utilize first super-complementary-code C of first user ₁₁, C ₁₂, C ₁₃And C ₁₄Demodulation in addition can obtain first user's data, is not subjected to second user's influence fully.Similarly, as if second super-complementary-code C with second user ₂₁, C ₂₂, C ₂₃And C ₂₄Demodulation in addition can obtain second user's data, also can not be subjected to first user's influence fully.

With reference to shown in Figure 8, consider in multipath channel and synchronous situation.Suppose the system under two footpaths channels (two path), the path gain in its each path (path gain) is 1, and the delay between two paths is the time of a chip period (chip), and is the situation of down link (Downlink).With reference to figure 9, it is a situation of considering up link (Uplink), that is to say that first user and second user transmit data under asynchronous and dual path situation, supposes that at this second user postpones the time of a chip period (chip) than first user again.Show that by Fig. 8 and Fig. 9 no matter at up link or down link, multipath disturbs can not influenced to some extent to demodulation result.As long as utilize first super-complementary-code C of first user ₁₁, C ₁₂, C ₁₃And C ₁₄Demodulation in addition can obtain first user's data, is not subjected to the influence in other path of second user and first user fully.

Spread spectrum flow process by Fig. 6 to Fig. 9 shows, can understand clearly that the correlation function complementary characteristic of super-complementary-code is actually and can ideally be used on the code division multiple access system.Because the complementary characteristic of the auto-correlation function of super-complementary-code, so super-complementary-code does not have the problem (MIfree) that multipath disturbs in code division multiple access system, because the complementary characteristic of the cross-correlation function of super-complementary-code, so super-complementary-code is not having the problem of disturbing between the user (MAI free) in the code division multiple access system.And by finding in the diagram of Fig. 6 to Fig. 9, no matter under the situation of up link (Uplink) or down link (Downlink), this two specific character all exists, no matter that is to say between the user whether synchronously, can not transmit any influence is arranged signal, so the super-complementary-code of native system is the spreading code of two-way same sex transmission.

The foregoing description is used for the present invention that explains, rather than limits the invention, and in the protection range of spirit of the present invention and claim, any modification and change to the present invention makes all fall into protection scope of the present invention.

Claims (8)

1. system that produces super-complementary-code, described super-complementary-code is to have the two-way same sex not have multiple access and insert the mutual-complementing code that interference characteristic and the two-way same sex do not have the multipath interference characteristic; Interference characteristic is not in the synchronous or asynchronous channel of upstream or downstream no matter the described two-way same sex has the multiple access access, and any relative time skew cross correlation value between any two user identification code down is zero; No matter it is in the synchronous or asynchronous channel of upstream or downstream that the described two-way same sex does not have the multipath interference characteristic, any relative time skew auto-correlation submaximum value of any one user identification code down is zero; It is characterized in that this system comprises:

One orthogonal matrix library module, have one first orthogonal matrix, one second orthogonal matrix and one the 3rd orthogonal matrix, the dimension of described first orthogonal matrix, second orthogonal matrix and the 3rd orthogonal matrix is N * N, and the absolute value of its each element is 1, and N is a positive integer;

One sequence generator, with described first orthogonal matrix of cause and the second orthogonal matrix computing and produce N sequence, each sequence has N ²Individual element;

One complete complementary code generator, with the described sequence of cause and the 3rd orthogonal matrix computing and produce N complete complementary code, each complete complementary code has N basic code, and each basic code has N ²Individual element; And a super-complementary-code generator, producing a plurality of super-complementary-codes with the described basic code interacting operation of cause, each super-complementary-code has a plurality of subcodes, and each subcode has at least one element.

2. according to the system of the described generation super-complementary-code of claim 1, it is characterized in that described super-complementary-code is 2N ²Individual, each super-complementary-code has 2N ²Individual subcode.

3. according to the system of the described generation super-complementary-code of claim 1, it is characterized in that, also comprise an extended length device, be used for N complete complementary code and the 3rd orthogonal matrix computing are produced extended length N complete complementary code doubly that each basic code has N * N ²Individual element again via this super-complementary-code generator, makes each subcode have N element.

4. the emitter of a super-complementary-code, described super-complementary-code are to have the two-way same sex not have multiple access and insert the mutual-complementing code that interference characteristic and the two-way same sex do not have the multipath interference characteristic; Interference characteristic is not in the synchronous or asynchronous channel of upstream or downstream no matter the described two-way same sex has the multiple access access, and any relative time skew cross correlation value between any two user identification code down is zero; No matter it is in the synchronous or asynchronous channel of upstream or downstream that the described two-way same sex does not have the multipath interference characteristic, any relative time skew auto-correlation submaximum value of any one user identification code down is zero; It is characterized in that this emitter comprises:

A plurality of spread spectrum modulator form a plurality of spread-spectrum signals with a plurality of subcodes of super-complementary-code to the data spread spectrum; A plurality of carrier frequency modulators are modulated described spread-spectrum signal with a plurality of carrier frequencies; And

One synthesizer that transmits is used for synthetic spread-spectrum signal through the carrier frequency modulation to form a composite signal.

5. emitter according to claim 4 is characterized in that, adopts the OFDM mode, and described a plurality of carrier frequency modulators replace with Fourier inversion device and parallel/serial converter.

6. the receiving system of a super-complementary-code, described super-complementary-code are to have the two-way same sex not have multiple access and insert the mutual-complementing code that interference characteristic and the two-way same sex do not have the multipath interference characteristic; Interference characteristic is not in the synchronous or asynchronous channel of upstream or downstream no matter the described two-way same sex has the multiple access access, and any relative time skew cross correlation value between any two user identification code down is zero; No matter it is in the synchronous or asynchronous channel of upstream or downstream that the described two-way same sex does not have the multipath interference characteristic, any relative time skew auto-correlation submaximum value of any one user identification code down is zero; It is characterized in that this receiving system comprises:

A plurality of carrier frequency demodulators are a plurality of spread-spectrum signals with a plurality of these composite signals of carrier frequency demodulation;

A plurality of demodulators, a plurality of subcodes of using super-complementary-code are to the spread-spectrum signal demodulation; And

One received signal synthesizer is used for synthetic spread-spectrum signal through demodulation, with receive this user's data.

7. receiving system according to claim 6 is characterized in that, adopts the OFDM mode, and described a plurality of carrier frequency demodulators replace with serial/parallel converter and Fourier transformer.

8. code division multiple address communication system that utilizes super-complementary-code, described super-complementary-code are to have the two-way same sex not have multiple access and insert the mutual-complementing code that interference characteristic and the two-way same sex do not have the multipath interference characteristic; Interference characteristic is not in the synchronous or asynchronous channel of upstream or downstream no matter the described two-way same sex has the multiple access access, and any relative time skew cross correlation value between any two user identification code down is zero; No matter it is in the synchronous or asynchronous channel of upstream or downstream that the described two-way same sex does not have the multipath interference characteristic, any relative time skew auto-correlation submaximum value of any one user identification code down is zero; It is characterized in that, comprise described emitter of claim 4 and the described receiving system of claim 6.

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