CN100461650C - Nonvolatile multiple input multiple output wireless communications - Google Patents

Abstract

An asymmetrical multiple-input multiple-output wireless communication method comprises the following steps that the quantity of transmission antennas used for an asymmetrical multiple-input multiple-output wireless communication is confirmed; the quantity of receiving antennas used for the asymmetrical multiple-input multiple-output wireless communication is confirmed; when the quantity of the transmission antennas is more than the quantity of the receiving antennas, a space time block code technology is used for realizing the asymmetrical multiple-input multiple-output wireless communication; when the quantity of the transmission antennas is not more than the quantity of the receiving antennas, a spatial multiplexing technology is used for realizing the asymmetrical multiple-input multiple-output wireless communication.

Description

Asymmetric MIMO radio communication

Technical field

The present invention relates to wireless communication system, relate in particular to have in this wireless communication system the transmitter of high data transmission rate.

Background technology

As everyone knows, communication system is supported wireless and wire communication between wireless and/or wired one-to-two communication equipment.The scope of this communication system can be from domestic and/or international cell phone system to the internet to point-to-point family wireless network.The communication system of each type is all according to one or more communication standards and by construction and operation.For example, wireless communication system can be according to one or more communication standard operations, and these standards are including, but not limited to IEEE802.11, bluetooth, advanced mobile phone service (AMPS), digital AMPS, global system for mobile communications (GSM), code division multiple access (CDMA), Local Multipoint Distribute System (LMDS), multichannel multi-point distribution system (MMDS) and/or other standards.

Based on the type of wireless communication system, Wireless Telecom Equipment, as cell phone, twoway radio, personal digital assistant, PC, kneetop computer, home entertainment device or the like can be directly or indirectly and other Wireless Telecom Equipment communicate.For direct communication, the point-to-point communication of promptly knowing participates in tuning their receiver and the reflector of the Wireless Telecom Equipment of communication to identical channel (for example a kind of radio-frequency carrier of wireless communication system) and communicate by letter on this channel.Be radio communication indirectly, each Wireless Telecom Equipment directly communicates with relevant base station (cellular service) and/or relevant accessing points (wireless network in family or the building) by channel appointed.For set up and Wireless Telecom Equipment between communicate to connect, relevant base station and/or accessing points be each other by system controller, or by PSTN, or by the internet, and/or carry out direct communication by other wide area network.

Participate in the Wireless Telecom Equipment of radio communication for each, it comprises built-in radio transceiver (being receiver and transmitter), or links to each other with a related radio transceiver (as the base station used of wireless network, radio modem etc. in family or the building).As everyone knows, receiver links to each other with antenna, and includes low noise amplifier, one or more intermediater-frequency stage, filtration grade and data recovery level.This low noise amplifier receives by antenna and injects radiofrequency signal and with its amplification.The radiofrequency signal that these one or more intermediater-frequency stages will be amplified is mixed to convert thereof into baseband signal or intermediate-freuqncy signal with one or more local oscillations.This filtration grade filters this baseband signal or intermediate-freuqncy signal to decay unnecessary out of band signal and generate trap signal.Data are recovered level and are recovered initial data according to specific wireless communication standard from trap signal.

As everyone knows, transmitter includes data-modulated level, one or more intermediater-frequency stage and power amplifier.This data-modulated level can convert initial data to baseband signal according to specific wireless communication standard.These one or more intermediater-frequency stages mix this baseband signal to generate radiofrequency signal with one or more local oscillators.This power amplifier amplifies this radiofrequency signal before by antenna transmission.

Typically, transmitter comprises antenna with transmitting radio frequency signal, and described radiofrequency signal is received by receiver single antenna or a plurality of antenna.When receiver included two or more antenna, it can select one with received RF signal.In the case, transmitter is singly to go into singly to go out to communicate by letter with radio communication between the receiver, even this receiver comprises that a plurality of antennas are with as diversity antenna (promptly selecting one to receive the radiofrequency signal of incident).For singly going into singly to go out radio communication, transceiver includes a receiver and a transmitter.Current most data lan all adopts singly to go into as IEEE802.11, IEEE802.11a, IEEE802.11b or IEEE802.11g singly to go out radio communication.

The radio communication of other type comprises singly goes into to have more (SIMO), goes into singly (MISO) and multiple-input, multiple-output (MIMO) more.Singly going in the multiple-output wireless communication, a single transmitter is handled the radiofrequency signal that transfers to receiver.Receiver includes two or more antennas and two or more receiver channel.Each antenna received RF signal also provides it to corresponding receiver channel (for example: LNA, downward modular converter, filter and analog to digital converter etc.).The radiofrequency signal that each receiver channel processing is received is to generate digital signal, and the latter is by merging and handle the data of transmitting to recapture.

Going into singly to go out in the radio communication more, transmitter includes two or more transmission channels (for example: digital to analog converter, filter, upwards modular converter and power amplifier), each transmission channel converts the appropriate section of baseband signal to radiofrequency signal, the latter by corresponding antenna transmission to receiver.Described receiver includes the signal receiver passage, is used for receiving many radiofrequency signals from transmitter.In this example, receiver utilizes electron beam to form many radiofrequency signals is merged into single signal.

In MIMO radio communication, transmitter and receiver include a plurality of passages.In this communication, transmitter utilizes space-time encoding function parallel processing data, to generate two or more data flow.Transmitter includes multi transmission channel, to convert each data flow to many radiofrequency signals.Receiver receives many radiofrequency signals by the multiple collector passage, and described multiple collector passage utilizes space time to separate function to come retrieving data stream.The data flow of being recaptured is merged and is handled to recover initial data.

In numerous radio communication (as SISO, MISO, SIMO and MIMO), can use one or more type radio communications to improve the data throughout in the WLAN (wireless local area network).For example, than SISO communication, MIMO communication can obtain higher data transmission rate.Yet many WLAN (wireless local area network) comprise Legacy Wireless Telecom Equipment (equipment that promptly meets the legacy version wireless communication standard).Like this, but the transmitter in the mimo wireless communication should back compatible Legacy Wireless Telecom Equipment in most of existing WLAN (wireless local area network).

Moreover asymmetric multiple-input, multiple-output are meant any M transmit antenna and N the communication system that reception antenna is formed, wherein M!=N.The situation of M＜N can not considered by the 802.11n standard.Yet actual situation is M〉N.Attempting utilizing two antennas (as old-fashioned kneetop computer) when the accessing points with a plurality of antennas can this thing happens when sending a frame on the equipment.This situation also can be relevant as radio signal with the broadcasting/multileaving Greenfield frame transmission of some.

Therefore, need a kind of WLAN (wireless local area network) transmission with high data throughput, its energy back compatible Legacy equipment, and support asymmetric multiple-input, multiple-output transmission.

Summary of the invention

The asymmetric radio communication of the present invention can satisfy these and other demand.In one embodiment, an asymmetric MIMO radio communication method comprises the steps: the quantity of the transmit antenna of definite asymmetric MIMO radio communication; Determine that based on the quantity of transmit antenna this asymmetric MIMO radio communication whether can usage space multiplex technique or space-time block code technology; For space multiplexing technique, on each transmit antenna, provide different constellation point to be used for transmission; For the space-time block code technology: the very first time at interval: for the transmission on first transmit antenna provides one first constellation point; And provide one second constellation point for the transmission on second transmit antenna; And in second time interval: the reverse complex conjugate that second constellation point is provided for the transmission on first transmit antenna; And the complex conjugate that second constellation point is provided for the transmission on second transmit antenna.

In another embodiment, a kind of asymmetric MIMO radio communication method comprises the steps: to be identified for the quantity of the transmit antenna of asymmetric MIMO radio communication; Be identified for the quantity of the reception antenna of asymmetric MIMO radio communication; When the quantity of transmit antenna during, use the space-time block code technology to carry out this asymmetric MIMO radio communication more than the quantity of reception antenna; And when the quantity of the no more than reception antenna of quantity of transmit antenna, the usage space multiplex technique is realized this asymmetric MIMO radio communication.

According to one embodiment of present invention, provide a kind of asymmetric MIMO radio communication method, this method comprises the steps:

Be identified for the quantity of the transmit antenna of asymmetric MIMO radio communication;

Determine that based on the quantity of transmit antenna this asymmetric MIMO radio communication whether can usage space multiplex technique or space-time block code technology;

For space multiplexing technique, on each transmit antenna, provide different constellation point to be used for transmission;

For the space-time block code technology:

At very first time interval:

For the transmission on first transmit antenna provides one first constellation point; And

For the transmission on second transmit antenna provides one second constellation point; And

In second time interval:

For providing the oppositely comprehensive of second constellation point, the transmission on first transmit antenna changes; And

The comprehensive variation of second constellation point is provided for the transmission on second transmit antenna.

Preferably, determine this asymmetric MIMO radio communication whether can the usage space multiplex technique or the step of space-time block code technology further comprise:

Determine the quantity of reception antenna; And

Determine based on the quantity of reception antenna whether this asymmetric MIMO radio communication can usage space multiplex technique or space-time block code technology.

Preferably, the step of determining the quantity of reception antenna further comprises:

From receiving the quantity that Wireless Telecom Equipment receives reception antenna.

Preferably, this method further comprises:

When the quantity of reception antenna is equal to or greater than the quantity of transmit antenna, the usage space multiplex technique; And

When the quantity of reception antenna is less than the quantity of transmit antenna, use the space-time block code technology.

Preferably, when the quantity of transmit antenna was odd number greater than the quantity of reception antenna, this space-time block code technology comprised:

In first and second time interval, select a transmit antenna to transmit non-space-time block code constellation point; And

The transmit antenna group of remainder is turned at least one transmit antenna group, wherein this at least one transmit antenna group transmission space-time block code constellation point.

Preferably, select the step of a transmit antenna to comprise:

When interrupting to another space time coding interruption, select another antenna to transmit non-space-time block code constellation point from a space time coding.

Preferably, when the quantity of transmit antenna was even number greater than the quantity of reception antenna, this space-time block code comprised:

Transmit antenna is divided at least two groups, and each group comprises at least two transmit antennas; And

Individually carry out space-time block coding for two groups.

Preferably, this method further comprises:

When interrupting to another space time coding interruption, transmit antenna is divided at least two different groups from a space time coding.

According to an aspect of the present invention, provide a kind of asymmetric MIMO radio communication method, this method comprises the steps:

Be identified for the quantity of the transmit antenna of asymmetric MIMO radio communication;

Be identified for the quantity of the reception antenna of asymmetric MIMO radio communication;

When the quantity of transmit antenna during, use the space-time block code technology to carry out this asymmetric MIMO radio communication more than the quantity of reception antenna; And

When the quantity of the no more than reception antenna of quantity of transmit antenna, the usage space multiplex technique is realized this asymmetric MIMO radio communication.

Preferably, the step of determining reception antenna quantity comprises:

From receiving the quantity that Wireless Telecom Equipment receives reception antenna.

Preferably, when the quantity of transmit antenna was odd number greater than the quantity of reception antenna, this space-time block code technology comprised:

In first and second time interval, select a transmit antenna to transmit non-space-time block code constellation point; And

The transmit antenna group of remainder is turned at least one transmit antenna group, wherein this at least one transmit antenna group transmission space-time block code constellation point.

Preferably, select the step of transmit antenna to comprise:

When interrupting to another space time coding interruption, select another antenna to transmit non-space-time block code constellation point from a space time coding.

Preferably, when the quantity of transmit antenna was even number greater than the quantity of reception antenna, this space-time block code technology comprised:

Transmit antenna is divided at least two groups, and each group comprises at least two transmit antennas; And

Individually carry out space-time block coding for two groups.

Preferably, this method further comprises:

When interrupting to another space time coding interruption, transmit antenna is divided at least two different groups from a space time coding.

According to an aspect of the present invention, a radio frequency transmitter comprises:

Baseband processing module is used for the ejaculation data transaction is become to penetrate symbols streams; And

Transmitter is used for converting the ejaculation symbols streams to the ejaculation radiofrequency signal, and wherein this transmitter comprises transmit antenna, and this baseband processing module can be further used for:

Be identified for the quantity of the transmit antenna of asymmetric MIMO radio communication;

Determine that based on the quantity of transmit antenna this asymmetric MIMO radio communication whether can usage space multiplex technique or space-time block code technology;

For space multiplexing technique, on each transmit antenna, provide different constellation point to be used for transmission;

For the space-time block code technology:

At very first time interval:

For the transmission on first transmit antenna provides one first constellation point; And

For the transmission on second transmit antenna provides one second constellation point; And

In second time interval:

For providing the oppositely comprehensive of second constellation point, the transmission on first transmit antenna changes; And

The comprehensive variation of second constellation point is provided for the transmission on second transmit antenna.

Preferably, baseband processing module can be further used for as follows determining that this asymmetric MIMO radio communication whether can usage space multiplex technique or space-time block code technology:

Determine the quantity of reception antenna;

Determine based on the quantity of reception antenna whether this asymmetric MIMO radio communication can usage space multiplex technique or space-time block code technology.

Preferably, baseband processing module is determined the quantity of reception antenna as follows:

From receiving the quantity that Wireless Telecom Equipment receives reception antenna.

Preferably, this baseband processing module can be further used for:

When the quantity of reception antenna equals or during more than the quantity of transmit antenna, the usage space multiplex technique; And

When the quantity of reception antenna is less than the quantity of transmit antenna, use the space-time block code technology.

Preferably, when the quantity of transmit antenna was odd number greater than the quantity of reception antenna, this baseband processing module can be carried out space-time block code by following step:

In first and second time interval, select a transmit antenna to transmit non-space-time block code constellation point; And

The transmit antenna group of remainder is turned at least one transmit antenna group, wherein this at least one transmit antenna group transmission space-time block code constellation point.

Preferably, this baseband processing module can be by following step to select transmit antenna:

When interrupting to another space time coding interruption, select another antenna to transmit non-space-time block code constellation point from a space time coding.

Preferably, when the quantity of transmit antenna was even number greater than the quantity of reception antenna, this baseband processing module can be carried out space-time block code by following step:

Transmit antenna is divided at least two groups, and each group comprises at least two transmit antennas; And

Individually carry out space-time block coding for two groups.

Preferably, this baseband processing module can be further used for:

When interrupting to another space time coding interruption, transmit antenna is divided at least two different groups from a space time coding.

According to an aspect of the present invention, radio frequency transmitter comprises:

Baseband processing module is used for the ejaculation data transaction is become to penetrate symbols streams; And

Transmitter is used for converting the ejaculation symbols streams to the ejaculation radiofrequency signal, and wherein this transmitter includes transmit antenna, and this baseband processing module can be further used for:

Be identified for the quantity of the transmit antenna of asymmetric MIMO radio communication;

Be identified for the quantity of the reception antenna of asymmetric MIMO radio communication;

When the quantity of transmit antenna during, use the space-time block code technology to carry out this asymmetric MIMO radio communication more than the quantity of reception antenna; And

When the quantity of the no more than reception antenna of quantity of transmit antenna, the usage space multiplex technique is realized this asymmetric MIMO radio communication.

Preferably, the method that comprises baseband processing module can be determined the quantity of reception antenna by following method:

From receiving the quantity that Wireless Telecom Equipment receives reception antenna.

Preferably, when the quantity of transmit antenna was odd number greater than the quantity of reception antenna, this baseband processing module can be carried out space-time block code by following step:

In first and second time interval, select a transmit antenna to transmit non-space-time block code constellation point; And

The transmit antenna group of remainder is turned at least one transmit antenna group, wherein this at least one transmit antenna group transmission space-time block code constellation point.

Preferably, this baseband processing module can be selected transmit antenna by following step:

When interrupting to another space time coding interruption, select another antenna to transmit non-space-time block code constellation point from a space time coding.

Preferably, when the quantity of transmit antenna was even number greater than the quantity of reception antenna, this baseband processing module can be carried out space-time block code by following step:

Transmit antenna is divided at least two groups, and each group comprises at least two transmit antennas; And

Individually carry out space-time block coding for two groups.

Preferably, this baseband processing module can be further used for:

When interrupting to another space time coding interruption, transmit antenna is divided at least two different groups from a space time coding.

Description of drawings

Fig. 1 is the block diagram of wireless communication system of the present invention;

Fig. 2 is the block diagram of Wireless Telecom Equipment of the present invention;

Fig. 3 is the block diagram of radio frequency transmitter of the present invention;

Fig. 4 is the block diagram of radio frequency receiver of the present invention;

Fig. 5 is the flow chart of data baseband processing method of the present invention;

Fig. 6 is the flow chart that further specifies to step 120 among Fig. 5;

Fig. 7～9th, the flow chart of the different embodiment of coding scramble data among the present invention;

Figure 10 A～10B is the schematic diagram of radio frequency transmitter of the present invention;

Figure 11 A～11B is the schematic diagram of radio frequency receiver of the present invention;

Figure 12 is the schematic block diagram of channel encoder of the present invention;

Figure 13 is the schematic block diagram of component encoder of the present invention;

Figure 14 is the schematic block diagram of another embodiment of component encoder of the present invention;

Figure 15 is the schematic block diagram of the present invention's 2/5 encoder;

Figure 16 is the schematic block diagram of puncture encoder of the present invention;

Figure 17 is the schematic block diagram of another embodiment of puncture encoder of the present invention;

Figure 18 is the schematic block diagram of low-density checksum coding device of the present invention;

Figure 19 is the schematic block diagram of interleaver of the present invention;

Figure 20 is the exemplary plot of asymmetric communication of the present invention;

Figure 21 is the exemplary plot of space-time block code of the present invention;

Figure 22 is the exemplary plot that the present invention has the asymmetric communication of two antennas;

Figure 23 is the exemplary plot that the present invention has the asymmetric communication of three antennas;

Figure 24 is another exemplary plot of the asymmetric communication of the present invention with three antennas;

Figure 25 is the exemplary plot that the present invention has the asymmetric communication of four antennas;

Figure 26 is another exemplary plot of the asymmetric communication of the present invention with four antennas.

Embodiment

Figure 1 shows that the block diagram of communication system 10, this communication system 10 comprises a plurality of base stations and/or accessing points 12～16, a plurality of Wireless Telecom Equipment 18～32 and the network hardware 34.Described Wireless Telecom Equipment 18～32 can be kneetop computer 18 and 26, personal digital assistant 20 and 30, PC 24 and

32 with and/or cell phone 22 and 28.The details of described Wireless Telecom Equipment will carefully be stated in Fig. 2.

Base station and/or accessing points 12 and 16 connect 36,38 by LAN and are connected with the network hardware 34 with 40.This network hardware 34 can be router, switch, bridge, modulator-demodulator, system controller or the like, and it connects 42 for communication system 10 provides wide area network.Each base station and/or accessing points 12～16 are connected with an antenna or aerial array, communicate with the Wireless Telecom Equipment local with it.Typically, Wireless Telecom Equipment will be served to receive from communication system 10 to specific base stations or accessing points 12～14 registrations.For direct communication (being point-to-point communication), Wireless Telecom Equipment is by the channel direct communication of configuration.

Typically, the base station all is used for the system of cell phone system and similar type, and accessing points then is used in the room or the wireless network in the building.No matter the particular type of communication system, each wireless communication system includes a built-in wireless device and/or is connected to a wireless device.This wireless device include highly linear amplifier and/or programmable multistage amplifier with improve performance, reduce cost, reduced in size and/or improve broadband application.

Figure 2 shows that the example block diagram of Wireless Telecom Equipment, it includes main equipment 18～32 and a wireless device that is connected 60.For cell phone, this wireless device 60 is installed with built-in component.For personal digital assistant, main frame on knee and/or PC, this wireless device 60 can be built-in or external assembly.

As shown in the figure, this main equipment 18～32 includes processing module 50, internal memory 52, radio interface 54, inputting interface 58 and output interface 56.Processing module 50, internal memory 52 are carried out the instruction that main equipment will be carried out.For example, for cell phone, this processing module 50 is finished the corresponding communication function according to specific cellular telephony standard.

Radio interface 54 allows data to flow into or flows out wireless device 60.When wireless device 60 receives data (injecting data), this radio interface 54 provides data to processing module 50 with further processing and/or route to output interface 56.Output interface 56 provides the connection to output display unit.Described display device comprises display, monitor, loudspeaker or the like.Like this, the data that received just can be shown.Radio interface 54 also provides data from processing module 50 to wireless device 60.This processing module 50 can receive from input equipment by inputting interface 58, such as the ejaculation data of keyboard, keypad, microphone etc., or self generates these data.For the data that receive by inputting interface 58, processing module 50 can be carried out corresponding host function to these data, and/or it is routed to wireless device 60 by radio interface 54.

Wireless device 60 comprises main frame interface 62, baseband processing module 64, internal memory 66, a plurality of radio frequency transmitter 68～72, transmission module 74, a plurality of antenna 82～86, a plurality of radio frequency receiver 76～80 and local oscillating module 100.But this baseband processing module 64 utilizes the operational order in the internal memory 66 can realize digit receiver and Digital Transmission device function respectively.The function of described digit receiver will describe in detail in Figure 11 B, its include but not limited to digital intermediate frequency to conversion, the demodulation of base band, troop and separate that mapping, decoding, release of an interleave, fast fourier transform, Cyclic Prefix remove, space-time is decoded and/or regular.The function of Digital Transmission device will describe in detail in Fig. 5～19, and it includes but not limited to scramble, coding, the mapping that interlocks, troops, modulation, inverse Fourier transform, Cyclic Prefix interpolation, space-time code and/or digital baseband to intermediate frequency are changed.Baseband processing module 64 can utilize one or more treatment facilities to realize.Described treatment facility can be microprocessor, microcontroller, digital signal processor, microcomputer, CPU, field programmable gate array, programmable logic device, state machine, logical circuit, analog circuit, digital circuit and/or any can be based on the equipment of operational order processing signals (simulation and/or numeral).Internal memory 66 can be single memory device or a plurality of memory device, and it can be the equipment of read-only memory, random access memory, volatile memory, nonvolatile storage, static memory, Dram, flash memory and/or any energy storing digital information.Be noted that, when processing module 64 realized one item or multinomial function by state machine, analog circuit, digital circuit and/or logical circuit, the internal memory of storage corresponding operating instruction was embedded in these state machines, analog circuit, digital circuit and/or the logical circuit.

During operation, wireless device 60 receives from main equipment by main frame interface 62 and penetrates data 88.Baseband processing module 64 receives based on mode select signal 102 and penetrates data 88, and generates one or more ejaculation symbols streams 90.AD HOC in the mode select signal 102 expression model selection tables, the model selection table can describe in detail in the back.For example, mode select signal 102 can be the frequency band, 20 or the channel width of 22GHZ and the maximum bit rate of 54Mbps of 2.4GHZ.More generally, mode select signal 102 is further represented the special speed in 1Mbps to the 54Mbps scope.In addition, the modulation of mode select signal 102 expression particular types, it includes but not limited to Barker code modulation, BPSK, QPSK, CCK, 16QAM and/or 64QAM.As further specifying in the table 1, sign indicating number speed can be represented by amount of bits (NBPSC), the coded-bit (NCBPS) of each OFDM symbol and the data bit (NDBPS) of each OFDM symbol that each carrier wave is encoded again.

But mode select signal is the particular channelization of the information of corresponding modes in the dial gauge 1 also, and is as shown in table 2.Comprise channel number and corresponding centre frequency shown in the table 2.Mode select signal can further be indicated the energy spectral density mask value, as shown in Figure 3.Mode select signal can select to be used to refer to the speed in the table 4, and it has the frequency band of 5GHz, channel width and the maximum 54Mbps bit rate of 20MHz.If specific model selection, channelizing is illustrated in the table 5.As a further alternative, mode select signal 102 can be indicated the frequency band of 2.4GHz, channel width and the maximum 192Mbps bit rate of 20MHz, and is as shown in table 6.In table 6, many antennas can be used to obtain high bandwidth.In this example, the antenna amount that is used can be further indicated in model selection.Table 7 is depicted as the channelizing of the structure in the table 6.Table 8 is depicted as another kind of model selection, and its frequency band is that 2.4GHz, channel width are that 20MHz, maximum bit rate are 192Mbps.Comprise shown in the table 8 used 2～4 antennas from 12Mbps to the 216Mbps bitrate range, and space time encoding rate.Table 9 is depicted as the channelizing in the table 8.Mode select signal 102 can further be indicated specific operator scheme, and is as shown in table 10, and it has the channel of 40MHz and the Maximum Bit Rate of 486Mbps corresponding to the frequency band of 5GHz.As shown in table 10, the scope of this bit rate has been used 1～4 antenna and corresponding space time code check from 13.5Mbps to 486Mbps.Table 10 can further be indicated specific modulation configuration code check and NBPSC value.Table 11 provides the energy spectral density shade for table 10, and table 12 provides channelizing for table 10.

Baseband processing module 64 generates one or more ejaculation symbols streams 90 based on mode select signal 102 from dateout 88, as further specifying of Fig. 5～9.For example, be used to selected AD HOC if mode select signal 102 shows the single transmit antenna, baseband processing module 64 can generate a single ejaculation symbols streams 90.Alternatively, be two, three or four antennas if mode select signal 102 shows, baseband processing module 64 can generate two, three or four in response to the quantity of antenna and penetrate symbols streams 90 from dateout 88.

The quantity of the ejaculation symbols streams 90 that generates according to baseband processing module 64, the radio frequency transmitter 68～72 of respective numbers can be activated and convert ejaculation radiofrequency signal 92 to will penetrate symbols streams 90.Described transmission module 74 receives and penetrates radiofrequency signal 92, and each ejaculation radiofrequency signal is offered corresponding antenna 82～86.

When wireless device 60 is in receiving mode, transmission module 74 receives one or more radiofrequency signals of injecting by antenna 82～86.Transmission module 74 provides injects radiofrequency signal 94 to one or more radio frequency receivers 76～80.What radio frequency receiver 76～80 (among Fig. 4 can describe in detail) will inject that radiofrequency signal 94 converts respective numbers to injects symbols streams 96.Inject the quantity of symbols streams 96 corresponding to the AD HOC of Data Receiving (this pattern can be any in the pattern shown in table 1～12).Baseband processing module 60 receives to inject symbols streams 96 and convert thereof into injects data 98, offers main equipment 18～32 by main frame interface 62 then.

The ordinary skill of this area is appreciated that the Wireless Telecom Equipment among Fig. 2 can realize with one or more integrated circuits.For example, main equipment can realize that baseband processing module 64 and internal memory 66 can be realized with second integrated circuit with integrated circuit, and other assembly of wireless device 60 is antenna 82～86 at least, and available the 3rd integrated circuit is realized.In other example, the processing module 50 of main process equipment and baseband processing module 64 can be the common process equipment of realizing on single integrated circuit.Further, internal memory 52 and 66 can be realized on single integrated circuit, and/or realize on the common process modular integrated circuit of processing module 50 and baseband processing module 64.

Figure 3 shows that the block diagram of the execution mode of radio frequency transmitter 68～72.Radio frequency transmitter 68～72 comprises that digital filter reaches the sampling module 75 that makes progress, D/A converter module 77, analog filter 79, modular converter 81, power amplifier 83 and radio-frequency filter 85 make progress.The digital filter and the sampling module 75 that makes progress receive ejaculation symbols streams 90 and with its digital filtering, the speed of the speed to one of this symbols streams of upwards taking a sample then expection is to generate the symbols streams 87 of filtration.D/A converter module 77 converts the symbols streams 87 of filtering to analog signal 89.This analog signal comprises homophase assembly and quadrature component.

Analog filter 79 filters this analog signal 89 to generate the analog signal 91 of filtering.Up-conversion module 81 comprises a pair of blender and filter, and the analog signal 91 of this filtration is mixed with local oscillations 93 to generate high-frequency signal 95.Described local oscillations is generated by local oscillating module 100.The frequency of high-frequency signal 95 is corresponding to the frequency of radiofrequency signal 92.

Power amplifier 83 amplifying high frequency signals 95 are to generate the high-frequency signal 97 that amplifies.Radio-frequency filter 85 can be a high freguency bandpass filter, and its high-frequency signal that will amplify 97 filters to generate desired output radiofrequency signal 92.

Those having ordinary skill in the art will appreciate that, each radio frequency transmitter 68～72 comprises similar framework as shown in Figure 3, and further comprises shearing device, like this when no longer needing specific radio frequency transmitter, it can be deactivated by this way, thus not regeneration interference signal and/or noise.

Figure 4 shows that the block diagram of a radio frequency receiver 76～80.In the present embodiment, each radio frequency receiver 76～80 comprises radio-frequency filter 101, low noise amplifier (LNA) 103, programmable gain amplifier (PGA) 105, down converted module 107, analog filter 109, analog-to-digital conversion module 111 and digital filter and downsampled module 113.Radio-frequency filter 101 can be a high freguency bandpass filter, receives to inject radiofrequency signal 94 and it is filtered the radiofrequency signal of injecting of filtering to generate.Low noise amplifier 103 is injected radiofrequency signal 94 based on what gain setting 115 amplified these filtrations, and this amplifying signal is offered programmable gain amplifier 105.Programmable gain amplifier 105 offered before frequency reducing die change piece 107 further and amplifies this being injected radiofrequency signal 94.

Down converted module 107 comprises a pair of blender, adds up module and filter, is used for mixing with local oscillations to generate analog baseband signal injecting radiofrequency signal.Described local oscillations is generated by local oscillating module 100.Analog filter 109 filters this analog baseband signal, and it is provided to analog-to-digital conversion module 111, to convert thereof into digital signal.Digital filter and downsampled module 113 are filtered this digital signal, adjust sampling rate then and inject symbols streams 96 with generation.

Figure 5 shows that baseband processing module 64 will penetrate the flow chart that rf data 88 converts one or more ejaculation symbols streams 90 to.In step 110, baseband processing module 64 receives and penetrates data 88 and mode select signal 102.Any in the operator scheme of mode select signal 102 shown in can dial gauge 1～12.In step 112, baseband processing module 64 mixes described data to generate scramble data according to pseudo random sequence.Note that pseudo random sequence can be utilized generator multinomial S (x)=x ³+ x ⁴+ 1 generates from feedback conversion register.

In step 114, baseband processing module 64 is selected a coding mode based on mode select signal.In step 116, baseband processing module 64 is encoded described scrambling signal to generate code signal according to selected coding mode.Described coding can utilize link turbo encoding scheme and/or low-density checksum block encoding scheme to realize.Such encoding scheme will describe in detail with reference to Figure 12～19.Selectively, this coding can carry out as described in following Fig. 7～9.

In step 118, baseband processing module 64 is determined the quantity of transport stream based on mode select signal.For example, mode select signal is selected an AD HOC, this pattern to indicate one, two, three, four even more antennas and can be used to transmission.Correspondingly, the quantity of the transport stream antenna amount specified with respect to mode select signal.In step 120, baseband processing module 64 converts above-mentioned code signal to symbols streams according to the quantity of the transport stream in the mode select signal.This step will describe in detail in Fig. 6.

Figure 6 shows that baseband processing module 64 converts above-mentioned code signal to according to the quantity of the transport stream in the mode select signal flow chart of symbols streams.In step 122, baseband processing module 64 interlocks this coded data to generate intercrossed data by the subcarrier of many symbols and channel.Generally speaking, staggered processing is to be designed to by many symbols and transport stream to disseminate coded data.It can improve receiver and detect and the error correcting ability.In one embodiment, the staggered place is comprehended and is followed the IEEE802.11 (a) or (g) backward compatibility mode of standard.For high performance pattern (as IEEE802.11 (n)), staggered processing also can realize by multi transmission channel or stream.

In step 124, this intercrossed data of baseband processing module 64 demultiplexings is a plurality of parallel intercrossed data streams.The quantity of parallel flow is corresponding to the quantity of transport stream, and the quantity of transport stream is again corresponding to the antenna amount that AD HOC adopted that is utilized.In step 126 and 128, for the parallel flow of each intercrossed data, the described intercrossed data of baseband processing module 64 mappings is to quadrature amplitude modulation (QAM) symbol, to generate frequency domain symbol in step 126.In step 128, baseband processing module 64 converts frequency domain symbol to time-domain symbol, and the latter can utilize reverse Fourier Tranform to handle.Frequency domain symbol can comprise further that to the conversion of time-domain symbol the increase Cyclic Prefix is to remove the intersymbol interference in the receiver.Be noted that oppositely the length of fast fourier transform and Cyclic Prefix all is defined in the pattern list in table 1～12.Generally speaking, 64 reverse fast fourier transforms are to be used for the 20MHz channel, and 128 reverse fast fourier transforms are to be used for the 40MHz channel.

In step 130, the encode parallel flow time-domain symbol of described intercrossed data of baseband processing module 64 spaces and time.In the present embodiment, space and time coding can be by utilizing encoder matrix, and time-domain symbol to the corresponding symbols streams quantity of space and the parallel intercrossed data stream of time coding realizes.Selectively, space and time coding can be by utilizing encoder matrix, and time-domain symbol to the P string symbol of space and time coding M line interlacing data flow realizes, wherein, and P=M+1.In embodiments of the present invention, encoder matrix can comprise following form:

$\left[\begin{array}{ccccc}{C}_1& C_2& {\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="C200510075822E00611.png"\; state="\{\{state\}\}">C</figure-callout>}}_3& \&CenterDot;\&CenterDot;\&CenterDot;& C_{2M-1}\\ {-\mathrm{<figure-callout\; id="2"\; label="C"\; filenames="C200510075822E00611.png,C200510075822E00612.png"\; state="\{\{state\}\}">C</figure-callout>}}_2^{<figure-callout\; id="1"\; label="*\; C"\; filenames="C200510075822E00611.png,C200510075822E00612.png"\; state="\{\{state\}\}">*</figure-callout>}& C_{}^{}{}_1^{<figure-callout\; id="4"\; label="*\; C"\; filenames="C200510075822E00611.png,C200510075822E00621.png"\; state="\{\{state\}\}">*</figure-callout>}& C_{}{}_4& \&CenterDot;\&CenterDot;\&CenterDot;& C_{2M}\end{array}\right]$

Wherein, the line number of encoder matrix is corresponding to M, and the columns of encoder matrix is corresponding to P.Specific constant value in the encoder matrix can be real number or imaginary number.

Fig. 7 is the flow chart of step 116 baseband processing module 64 coding scrambling signals among Fig. 5.In step 140, baseband processing module 64 utilizes 64 conditional code convolutional encodings and generator polynomial G0=1338 and G1=1718 to generate the convolutional encoding data.In step 142, baseband processing module 64 shrinks (punctures) convolutional encoding data to generate coded data according to mode select signal with a speed.Must notice that contraction rate comprises 1/2,2/3 and/or 3/4, or the listed speed in any table 1～12.Must notice that for specific pattern, selected speed should backwards-compatible IEEE802.11 (a) and/or the rate requirement of IEEE802.11 (g).

The coding of Fig. 7 further comprises optional step 144, and in step 144, baseband processing module 64 merges convolutional encoding and outside Reed Solomon sign indicating number to generate the convolutional encoding data.Notice, step 144 can with step 140 parallel processing.

Fig. 8 is another execution mode flow chart of step 116 baseband processing module 64 coding scrambling signals among Fig. 5.In the present embodiment, in step 146, baseband processing module 64 is encoded this scrambling signal to generate coded data according to the CCK sign indicating number.This step can be carried out according to IEEE802.11 (b) and/or IEEE802.11 (g) specification.This coding comprises optional step 148, and itself and step 146 parallel processing merge CCK sign indicating number and outside Reed Solomon sign indicating number to generate coded data.

Fig. 9 is the flow chart of another execution mode of step 116 baseband processing module 64 coding scrambling signals among Fig. 5.In the present embodiment, in step 150, baseband processing module 64 utilizes 256 conditional code convolutional encodings and generator polynomial G0=5618 and G1=7538 to generate the convolutional encoding data.In step 152, baseband processing module 64 according to mode select signal with one of a plurality of speed punctured convolutional encoding data to generate coded data.Note the speed of the associative mode that contraction rate such as table 1～12 are listed.

Further comprise step 154 among Fig. 9, baseband processing module 64 merges convolutional encoding and outside ReedSolomon sign indicating number to generate the convolutional encoding data.

Figure 10 A and Figure 10 B are the block diagram of the many transmitters of the present invention.In Figure 10 A, shown in Base-Band Processing comprise that scrambler 172, channel encoder 174, interleaver 176, demodulation multiplexer 178, a plurality of symbol mapper 180～184, a plurality of inverse fast fourier transformed (IFFT)/Cyclic Prefix increases module 186～190 and space/clock coder 192.The baseband portion of transmitter further comprises schema management module 175, is used for receiving mode and selects signal 119 and partly generate set point 121 for the wireless radio transmission device, and be baseband portion generating rate selection 117.

During operation, scrambler 172 increase pseudo random sequences to penetrating data bit element 88 so that these data show as at random.Pseudo random sequence can utilize generator polynomial S (x)=x7+x4+1 to generate from the feedback shift register, is used to generate scramble data.Channel encoder 174 receives scramble data, and the new bit sequence of redundant generation.It will improve the detectability of receiver.Channel encoder 174 can run on arbitrary pattern.For example, be backwards-compatible IEEE802.11 (a) and IEEE802.11 (g), channel encoder 174 is 1/2 convolution coder and generator polynomial G0=1338 and G1=1718 for the encoding rate with 64 states.The output of convolution coder can be compressed into 1/2,2/3 and 3/4 according to the Speedometer Drive (for example table 1～12) of appointment.Be the CCK pattern of backwards-compatible IEEE802.11 (b) and IEEE802.11 (g), channel encoder 174 is the CCK sign indicating number, such as among the IEEE802.11 (b) definition.For obtaining higher data rate (as shown in table 6,8 and 10), channel encoder 174 can use identical convolution code or more powerful coding, comprise have more polymorphic convolution code, parallel link (TURBO) sign indicating number and/or low-density checksum (LDPC) region-position code.Further, any coding all can merge with outside Reed Solomon sign indicating number.Based on the equilibrium of performance, backwards-compatible and low reaction time, in these codings one or multinomially should be best.Concatenated coding and low-density parity check can be described in further detail with reference to Figure 12～19.

The data of interleaver 176 received codes, and it is propagated by many symbols and transport stream.It will improve the detection and the error correcting ability of receiver.In the present embodiment, interleaver 176 can be followed the backward compatibility mode of IEEE802.11 (a) or IEEE802.11 (g) standard.For reaching high performance mode (as shown in table 6,8 and 10), interleaver 176 can insert data by transport stream.Demodulation multiplexer 178 will change M parallel flow into to transmit from the sequence interleaving circulation of interleaver 176.

Each sign changer 180～184 receives a corresponding data passage from demodulation multiplexer 178.Each sign changer 180～182 (for example: standards such as BPSK, QPSK, 16QAM, 64QAM, 256QAM) is transformed to quadrature amplitude modulation (QAM) symbol according to Speedometer Drive (as table 1～12) with bit element flow.Backwards-compatible for reaching IEEE802.11 (a), can adopt Gray code (Gray coding).

The figure shift that each sign changer 180～184 is generated all provides to IFFT/ Cyclic Prefix increase module 186～190, the module 186～190 that increases Cyclic Prefix realizes conversion and the increase prefix of frequency domain to time domain, and it allows to remove the intersymbol interference in the receiver.Be noted that the length of IFFT/ Cyclic Prefix all is defined in the pattern list 1～12.Generally speaking, 64 IFFT are applied to the 20MHz channel, and 128 IFFT are applied to the 40MHz channel.

Space/clock coder 192 receives the M parallel channel of time-domain symbol and converts thereof into the P output symbol.In the present embodiment, the quantity of M input channel equals the quantity of P output channel.In another embodiment, the quantity of output channel P is M+1.For each passage, space/clock coder adopts the symbol of following matrix multiplex (MUX) input:

$\left[\begin{array}{ccccc}{C}_1& C_2& {\mathrm{<figure-callout\; id="3"\; label="C"\; filenames="C200510075822E00611.png"\; state="\{\{state\}\}">C</figure-callout>}}_3& \&CenterDot;\&CenterDot;\&CenterDot;& C_{2M-1}\\ {-\mathrm{<figure-callout\; id="2"\; label="C"\; filenames="C200510075822E00611.png,C200510075822E00612.png"\; state="\{\{state\}\}">C</figure-callout>}}_2^{<figure-callout\; id="1"\; label="*\; C"\; filenames="C200510075822E00611.png,C200510075822E00612.png"\; state="\{\{state\}\}">*</figure-callout>}& C_{}^{}{}_1^{<figure-callout\; id="4"\; label="*\; C"\; filenames="C200510075822E00611.png,C200510075822E00621.png"\; state="\{\{state\}\}">*</figure-callout>}& C_{}{}_4& \&CenterDot;\&CenterDot;\&CenterDot;& C_{2M}\end{array}\right]$

Notice that the line number of this matrix is corresponding to the quantity of input channel, its columns is corresponding to the quantity of output channel.

Figure 10 B is depicted as the wireless device part of transmitter, and it comprises that a plurality of digital filterings/sampling module 194～198, analog filter 206～216, I/Q modulator 218～222, radio frequency amplifier 224～228, radio-frequency filter 230～234 and antenna 236～240 make progress.Received by the digital filtering/sampling module 194～198 that makes progress respectively from space/clock coder 192P output.

During operation, the quantity of movable radio channel is corresponding to the quantity of P output.For example, if only produce a P output channel, then have only a wireless radio transmission device to activate.The quantity that persons of ordinary skill in the art may appreciate that output channel can change between any numerical value of expecting one.

Digital filtering/upwards sampling module 194～198 filters corresponding symbol, and adjusts sampling rate with consistent with the sampling rate of D/A converter module 200～204.D/A converter module 200～204 becomes corresponding homophase and orthogonal simulation signal with the conversion of signals of digital filtering and upwards sampling.Analog filter 208～214 filters the homophase and/or the quadrature component of corresponding analog signal, and the extremely corresponding I/Q modulator 218～222 of signal of filtration is provided.I/Q modulator 218～222 is based on the local oscillations that local oscillator 100 is generated, and being used for upwards changing i/q signal is radiofrequency signal.

Radio frequency amplifier 224～228 amplifies this radiofrequency signal, and this radiofrequency signal is filtered by radio-frequency filter 230～234 before transmitting by antenna 236～240.

Figure 11 A and 11B are depicted as the block diagram of another execution mode of receiver of the present invention.Figure 11 A is depicted as the simulation part of this receiver, and it comprises a plurality of receive paths.Each receive path comprises antenna, radio-frequency filter 252～256, low noise amplifier 258～260, i/q demodulator 264～268, analog filter 270～280, analog to digital converter 282～286 and digital filtering and downsampled module 288～290.

During operation, antenna receives and injects radiofrequency signal, and it is radio-frequency filter 252～256 bandpass filtering mistakes.Corresponding low noise amplifier 258～260 amplifies this and crosses filtered signal, and provides it to corresponding i/q demodulator 264～268.The i/q demodulator 264～268 of the local oscillations that is generated based on local oscillator 100 is a base band inphase quadrature analog signal with the radiofrequency signal down converted.

Corresponding analog filter 270～280 filters this inphase quadrature analog signal respectively.Analog to digital converter 282～286 is a digital signal with this inphase quadrature analog signal conversion.Digital filtering and downsampled module 288～290 are filtered this digital signal and are adjusted sampling rate with consistent with Base-Band Processing speed, and it will describe in detail in Figure 11 B.

Figure 11 B is depicted as the baseband processing module of receiver.This baseband processing module comprises that space/temporal decoder 294, a plurality of fast Fourier transform (FFT)/Cyclic Prefix remove module 296～300, a plurality of symbolic solution conversion module 302～306, Port Multiplier 308, separate inserter 310, channel decoder 312 and descrambling frequency module 314.This baseband processing module further comprises schema management module 175.The function that space/temporal decoder 294 implementation spaces/clock coder 192 are opposite receives the P input from receiver channel, and generates the M output channel.The M output channel removes module 296～300 by fast Fourier transform (FFT)/Cyclic Prefix and handles to generate frequency domain symbol.Fast Fourier transform (FFT)/Cyclic Prefix removes module 296～300 and carries out the function opposite with inverse fast fourier transformed (IFFT)/Cyclic Prefix increase module 186～190.

Symbol de-maps module 302～306 utilizes the reverse process of sign map module 180～184 to convert frequency domain symbol to data.The symbols streams that Port Multiplier 308 merging are separated after the mapping is single passage.

Deinterlacer 310 utilizes the above-mentioned single passage of the reverse functions release of an interleave of interleaver 176.The release of an interleave data are carried then to channel decoder 312, and it realizes the reverse functions of channel encoder 174.Descrambling frequency module 314 receives decoded data, and the opposite function of realization and scrambler 172, injects data 98 with generation.The baseband portion of transmitter further comprises schema management module 175, and its receiving mode is selected signal 119, and sets 121 for radio receiver partly generates, and is baseband portion generating rate selection 117.

Figure 12 shows that the block diagram of channel encoder 174 as the turbo encoder.In the present embodiment, this turbo encoder receives the input bit, and revises these bits at 321 places, utilizes component encoder 320～322 to handle then, and is again that it is staggered to generate respective coding output.According to specific sign reversing (BPSK, QPSK, 8PSK (phase shift keying), 64QAM, 16QAM or 16APSK (amplitude modulation phase shift keying)), the turbo encoder will be done in the same way in order to generate coded data.For example, suppose π ₀And π ₁Be respectively the staggered of the most remarkable bit (MSB) and least remarkable bit (LSB), for 2 bit symbol and π _L ^-1Block, L=0 are its inverse, and be then amended staggered as follows:

$\mathrm{\&pi;}\&prime;\&prime;l\left(i\right)=\left(\begin{array}{c}i:i\mathrm{<figure-callout\; id="2"\; label="mod"\; filenames="C200510075822E00611.png,C200510075822E00612.png"\; state="\{\{state\}\}">mod</figure-callout>}2=0\\ \mathrm{\&pi;}-l\left(i\right):i\mathrm{<figure-callout\; id="2"\; label="mod"\; filenames="C200510075822E00611.png,C200510075822E00612.png"\; state="\{\{state\}\}">mod</figure-callout>}2=1\end{array}\right)$ And

$\mathrm{\&pi;l}\left(i\right)=\left(\begin{array}{c}i:i\mathrm{<figure-callout\; id="2"\; label="mod"\; filenames="C200510075822E00611.png,C200510075822E00612.png"\; state="\{\{state\}\}">mod</figure-callout>}2=1\\ \mathrm{\&pi;}\left(i\right):i\mathrm{<figure-callout\; id="2"\; label="mod"\; filenames="C200510075822E00611.png,C200510075822E00612.png"\; state="\{\{state\}\}">mod</figure-callout>}2=0\end{array}\right)$

Figure 13 shows that the block diagram of component encoder 320～322 among Fig. 2 of the present invention, it can be used as encoding rate is 1/2 encoder.As shown in the figure, component encoder 320～322 comprises that totalling module 325,329,335,337 and digital single cycle postpone 327,331,333.

Figure 14 shows that the block diagram of component encoder 320～322 another execution modes, it adopts encoding rate is that to generate encoding rate be 2/5 encoder for 1/2 encoder 345.In the present embodiment, to be transferred into encoding rate be 1/2 encoder 345 and add up module 339 for two continuous binary bit inputs 341,342.Encoding rate be 2/5 encoder output as shown in the figure.

Figure 15 represents the general utility functions of Figure 14.Encoding rate is that 2/5 encoder 347 can be used as the puncture encoder 347 shown in Figure 16 and Figure 17, and it has corresponding QPSK conversion.

Figure 18 shows that the schematic diagram of channel encoder 174 as low-density checksum (LDPC) encoder.In the present embodiment, this encoder comprises low-density checksum coding device 174, interleaver 176 and grey scale mapping module 177.Block length can be 2000, and message length can be 1600.In this example, low-density checksum binary bit matrix H=[H1, H2], wherein H1 is an irregular 400x1600 low density matrix, and wherein the power of 1400 row is that the power of 3 and 200 row is 7, and the power of all row is 14.And 1 distribution is pseudorandom, to satisfy the hardware execution mode.Matrix H 2 is matrixes of a 400x400, and it provides long-channel, does not have the loop in the two-way chart that redundant bit node and check-node are constituted.

$\mathrm{<figure-callout\; id="2"\; label="H"\; filenames="C200510075822E00611.png,C200510075822E00612.png"\; state="\{\{state\}\}">H</figure-callout>}2=\left|\begin{array}{c}100...00\\ 11\_...00\\ \_11...00\\ ...\\ 000...10\\ 000...11\end{array}\right|$

Parity matrix provides simple code.This coding is not lower than 6 loop.During the number of degrees of this two-way chart distribute and are listed in the table below.Total amount of edge is 6399 in the chart.

The bit node number of degrees (amount of edge of being sent from a bit node)	Number of nodes
		1	1
2	399
		3	1400
7	200
		The check-node number of degrees

15	1
		16	399

Figure 19 shows that special staggered 351,353 and QPSK conversion 355, the encoder that this QPSK conversion 355 can be among Figure 18 utilizes.In the present embodiment, code check can be 1/2, and the LDPC sign indicating number is symmetrical.Similarly, this is staggered as shown in the figure.

Figure 20 shows that the asymmetric communication schematic diagram between accessing points 361 and Wireless Telecom Equipment (as PC) 363.In this example, in accessing points 361 4 transmit antennas are arranged, its available M represents in PC 363 2 antennas are arranged, and its available N represents.In this example, M〉N.

Shown in Figure 21 is the space-time block code schematic diagram, and it has drawn the functional relation between time, frequency and space (being antenna).As shown in the figure, frequency is divided into a plurality of subcarriers (as 64 expression 20MHz channels, 128 expression 40MHz channels).Also have, the space is divided into many antennas.In this figure, only painted two antennas, but can be with more.Time is divided into a plurality of symbols.Like this, to each time interval, each subcarrier on each antenna is supported an additional character.Space-time block code will be described further with reference to Figure 22～26.

Shown in Figure 22 is the asymmetric radio communication schematic diagram of double antenna.Such communication can utilize single space multiplexing technique to realize, wherein the different information of each antenna transmission.Selectively, also can adopt space-time block code.In this example, when speed was the 1Alamouti sign indicating number, symbol disposed as shown in the figure, and s0 is first constellation point here, and it is transmitted on the subcarrier k, and second constellation point is transmitted in subcarrier k+1.

Shown in Figure 23 is the asymmetric radio communication schematic diagram of triantennary.In this example, at each OFDM subcarrier pointer k, the transmission that is encoded as shown in the figure, * represents a complex conjugate here.Adopt this configuration, speed is that 1Alamouti space-time block code (STBC) stream can be together with the stream transmission that is not encoded on each OFDM subcarrier k, and this transmission has the coding delay of two symbol periods.

Shown in Figure 24 is another execution mode schematic diagram of the asymmetric radio communication of triantennary.It is similar to the communication among Figure 23, except STBC is that to be applied to mutual antenna right.Decoding delay still is two symbol periods.As shown in the figure, in first double sign cycle, this STBC be utilize antenna 0,1}, in the next double sign cycle be 0,2}, again the next one be 2,3}.Note, utilize chnnel coding (for example constraint length=6 convolution code) intersection position can improve the availability of minimum speed limit.

Shown in Figure 25 is the asymmetric radio communication schematic diagrames of four antennas.In this figure, the coding of some classifications is performed to guarantee that reliable transmission is at least two stations.And each the OFDM sub-carrier index k that transmits two speed and be 1Alamouti space-time block code (STBC) stream can be as shown in the figure and by construction.This coding delay is two symbol periods.

Shown in Figure 26 is another execution mode schematic diagram of the asymmetric radio communication of four antennas.Communication class shown in itself and Figure 25 seemingly, except space-time block code is that to be used to change antenna right.This decoding delay is two symbol periods.For example, space-time block code first two symbol periods be crossed antenna 0,1} and 2,3}, be then 0,2} and 1,3}.Notice that utilize channel code (for example constraint length is 6 convolution codes) intersection bit, it can improve the energy of minimum speed limit.

Persons of ordinary skill in the art may appreciate that term " constitutionally " or " approximately " can be used for herein, offer corresponding term with the acceptable tolerance of industry.The acceptable margin of tolerance of such industry is from being lower than 1% to 20%, and corresponding but be not limited to components values, integrated circuit processing variation, variations in temperature, the rise and fall times and/or heat and make an uproar.Persons of ordinary skill in the art may appreciate that term used herein " be operably connected " comprise by another assembly, element, circuit or module directly be connected indirectly.For indirect connection, intervention package, element, circuit or module are not revised the information of signal, but can adjust its current stage, voltage level and/or energy level.Persons of ordinary skill in the art may appreciate that infer to connect (promptly an element is continuous with another element by inferring) comprise between two elements with the direct of " being operably connected " same way as be connected indirectly.Those of ordinary skill in the art be further appreciated that terminology used here " not second to " show the comparison between two or more elements, project, the signal, but a kind of expected relationship is provided.For example, but when this expected relationship be that signal 1 has bigger magnitude than signal 2, then when the magnitude of signal 1 magnitude, or when the magnitude of signal 2 magnitude less than signal 1 greater than signal 2, with regard to available " not second to ".

The different embodiment of multiple-input, multiple-output receiver in wireless communication system has been listed in aforementioned discussion.For knowing those skilled in the art,, also can derive other embodiment not breaking away under the essence situation of the present invention.

The model selection table:

Table 1:2.4GHz, 20/22MHz channel width, the maximum bit rate of 54Mbps

Code

Rate Modulation Rate NBPSC NCBPS NDBPS EVM Sensitivity ACR AACR

Barker

1 BPSK

Barker

2 QPSK

5.5 CCK

6 BPSK 0.5 1 48 24 -5 -82 16 32

9 BPSK 0.75 1 48 36 -8 -81 15 31

11 CCK

12 QPSK 0.5 2 96 48 -10 -79 13 29

18 QPSK 0.75 2 96 72 -13 -77 11 27

24 16-QAM 0.5 4 192 96 -16 -74 8 24

36 16-QAM 0.75 4 192 144 -19 -70 4 20

48 64-QAM 0.666 6 288 192 -22 -66 0 16

54 64-QAM 0.75 6 288 216 -25 -65 -1 15

Table 2: the channelizing of table 1

Channel frequency (MHz)

1 2412

2 2417

3 2422

4 2427

5 2432

6 2437

7 2442

8 2447

9 2452

10 2457

11 2462

12 2467

Table 3: the energy spectral density of table 1 (PSD) mask

PSD mask 1

Frequency offset dBr

-9MHz to 9MHz 0

+/- 11MHz -20

+/- 20MHz -28

+/- 30MHz and

greater -50

Table 4:5GHz, 20MHz channel width, the maximum bit rate of 54Mbps

Code

Rate Modulation Rate NBPSC NCBPS NDBPS EVM Sensitivity ACR AACR

6 BPSK 0.5 1 48 24 -5 -82 16 32

9 BPSK 0.75 1 48 36 -8 -81 15 31

12 QPSK 0.5 2 96 48 -10 -79 13 29

18 QPSK 0.75 2 96 72 -13 -77 11 27

24 16-QAM 0.5 4 192 96 -16 -74 8 24

36 16-QAM 0.75 4 192 144 -19 -70 4 20

48 64-QAM 0.666 6 288 192 -22 -66 0 16

54 64-QAM 0.75 6 288 216 -25 -65 -1 15

Table 5: the channelizing of table 4

Frequency Frequency

Channel (MHz) Country Channel (MHz) Country

240 4920 Japan

244 4940 Japan

248 4960 Japan

252 4980 Japan

8 5040 Japan

12 5060 Japan

16 5080 Japan

36 5180 USA/Europe 34 5170 Japan

40 5200 USA/Europe 38 5190 Japan

44 5220 USA/Europe 42 5210 Japan

48 5240 USA/Europe 46 5230 Japan

52 5260 USA/Europe

56 5280 USA/Europe

60 5300 USA/Europe

64 5320 USA/Europe

100 5500 USA/Europe

104 5520 USA/Europe

108 5540 USA/Europe

112 5560 USA/Europe

116 5580 USA/Europe

120 5600 USA/Europe

124 5620 USA/Europe

128 5640 USA/Europe

132 5660 USA/Europe

136 5680 USA/Europe

140 5700 USA/Europe

149 5745 USA

153 5765 USA

157 5785 USA

161 5805 USA

165 5825 USA

Table 6:2.4GHz, 20MHz channel width, the maximum bit rate of 192Mbps

ST

TX Code

Rate Antennas Rate Modulation Code Rate NBPSC NCBPS NDBPS

12 2 1 BPSK 0.5 1 48 24

24 2 1 QPSK 0.5 2 96 48

48 2 1 16-QAM 0.5 4 192 96

96 2 1 64-QAM 0.666 6 288 192

108 2 1 64-QAM 0.75 6 288 216

18 3 1 BPSK 0.5 1 48 24

36 3 1 QPSK 0.5 2 96 48

72 3 1 16-QAM 0.5 4 192 96

144 3 1 64-QAM 0.666 6 288 192

162 3 1 64-QAM 0.75 6 288 216

24 4 1 BPSK 0.5 1 48 24

48 4 1 QPSK 0.5 2 96 48

96 4 1 16-QAM 0.5 4 192 96

192 4 1 64-QAM 0.666 6 288 192

216 4 1 64-QAM 0.75 6 288 216

Table 7: the channelizing of table 6

Channel frequency (MHz)

1 2412

2 2417

3 2422

4 2427

5 2432

6 2437

7 2442

8 2447

9 2452

10 2457

11 2462

12 2467

Table 8:5GHz, 20MHz channel width, the maximum bit rate of 192Mbps

TX ST Code Code

Rate Antennas Rate Modulation Rate NBPSC NCBPS NDBPS

12 2 1 BPSK 0.5 1 48 24

24 2 1 QPSK 0.5 2 96 48

48 2 1 16-QAM 0.5 4 192 96

96 2 1 64-QAM 0.666 6 288 192

108 2 1 64-QAM 0.75 6 288 216

18 3 1 BPSK 0.5 1 48 24

36 3 1 QPSK 0.5 2 96 48

72 3 1 16-QAM 0.5 4 192 96

144 3 1 64-QAM 0.666 6 288 192

162 3 1 64-QAM 0.75 6 288 216

24 4 1 BPSK 0.5 1 48 24

48 4 1 QPSK 0.5 2 96 48

96 4 1 16-QAM 0.5 4 192 96

192 4 1 64-QAM 0.666 6 288 192

216 4 1 64-QAM 0.75 6 288 216

Table 9: the channelizing of table 8

Frequency Frequency

Channel (MHz) Country Channel (MHz) Country

240 4920 Japan

244 4940 Japan

248 4960 Japan

252 4980 Japan

8 5040 Japan

12 5060 Japan

16 5080 Japan

36 5180 USA/Europe 34 5170 Japan

40 5200 USA/Europe 38 5190 Japan

44 5220 USA/Europe 42 5210 Japan

48 5240 USA/Europe 46 5230 Japan

52 5260 USA/Europe

56 5280 USA/Europe

60 5300 USA/Europe

64 5320 USA/Europe

100 5500 USA/Europe

104 5520 USA/Europe

108 5540 USA/Europe

112 5560 USA/Europe

116 5580 USA/Europe

120 5600 USA/Europe

124 5620 USA/Europe

128 5640 USA/Europe

132 5660 USA/Europe

136 5680 USA/Europe

140 5700 USA/Europe

149 5745 USA

153 5765 USA

157 5785 USA

161 5805 USA

165 5825 USA

Table 10:5GHz, 40MHz channel width, the maximum bit rate of 486Mbps

TX ST Code Code

Rate Antennas Rate Modulation Rate NBPSC

13.5Mbps 1 1 BPSK 0.5 1

27Mbps 1 1 QPSK 0.5 2

54Mbps 1 1 16-QAM 0.5 4

108Mbps 1 1 64-QAM 0.666 6

121.5Mbps 1 1 64-QAM 0.75 6

27Mbps 2 1 BPSK 0.5 1

54Mbps 2 1 QPSK 0.5 2

108Mbps 2 1 16-QAM 0.5 4

216Mbps 2 1 64-QAM 0.666 6

243Mbps 2 1 64-QAM 0.75 6

40.5Mbps 3 1 BPSK 0.5 1

81Mbps 3 1 QPSK 0.5 2

162Mbps 3 1 16-QAM 0.5 4

324Mbps 3 1 64-QAM 0.666 6

365.5Mbps 3 1 64-QAM 0.75 6

54Mbps 4 1 BPSK 0.5 1

108Mbps 4 1 QPSK 0.5 2

216Mbps 4 1 16-QAM 0.5 4

432Mbps 4 1 64-QAM 0.666 6

486Mbps 4 1 64-QAM 0.75 6

Table 11: the energy spectral density of table 10 (PSD) mask

PSD mask 2

Frequency offset dBr

-19MHz～19MHz 0

+/-21MHz -20

+/-30MHz -28

The 40MHz of+/-and higher by-50

Table 12: the channelizing of table 10

Frequency Frequency

Channel (MHz) Country Channel (MHz) County

242 4930 Japan

250 4970 Japan

12 5060 Japan

38 5190 USA/Europe 36 5180 Japan

46 5230 USA/Europe 44 5520 Japan

54 5270 USA/Europe

62 5310 USA/Europe

102 5510 USA/Europe

110 5550 USA/Europe

118 5590 USA/Europe

126 5630 USA/Europe

134 5670 USA/Europe

151 5755 USA

159 5795 USA

As an example of the gain that can obtain from mimo systems, channel metrics can be used.In this example, suppose that K subchannel ofdm system is at each tone average transmission energy all.The equal homenergic of the NxN multiple-input, multiple-output capacity of each subcarrier (promptly do not have at one's leisure poor) is:

$C_k={\log }_2\left(\det [I_N+\frac{\mathrm{\&rho;}}{N}{H}_k^H{H}_k]\right)$

K-number of tones wherein; The quantity of K-tone; Hk-NxN channel matrix (each tone); The N-antenna amount; ρ=SNR/ κ=standardization receiver SNR, and

$\mathrm{\&kappa;}=\frac{1}{{\mathrm{<figure-callout\; id="2"\; label="KN"\; filenames="C200510075822E00611.png,C200510075822E00612.png"\; state="\{\{state\}\}">KN</figure-callout>}}^2}\underset{k=0}{\overset{K-1}{\mathrm{\&Sigma;}}}\underset{m=0}{\overset{N-1}{\mathrm{\&Sigma;}}}\underset{n=0}{\overset{N-1}{\mathrm{\&Sigma;}}}{H}_k^{*}(n,m)H_k(n,m)$

Correspondingly, the singular value of the channel matrix of each subchannel has determined the capacity of this subchannel, and wherein singular value decomposition can be defined as:

$H_k=U_k{\mathrm{\&Sigma;}}_k{V}_k^H\mathrm{with}{\mathrm{\&Sigma;}}_k=\left[\begin{array}{ccc}{\mathrm{\&sigma;}}_{1k}& & \\ & *& \\ & & {\mathrm{\&sigma;}}_{\mathrm{Nk}}\end{array}\right]$

The capacity of k subchannel can be expressed as:

$C_k=\underset{n=0}{\overset{N-1}{\mathrm{\&Sigma;}}}{\log }_2(1+\frac{\mathrm{\&rho;}}{N}{\mathrm{\&sigma;}}_{n,k}^2)$

Can draw, when singular value is equal equivalent time, maximum capacity.

From this example as can be known, the multiple-input, multiple-output performance gain that can expect comprises: (a) under the state of signal-to-noise of appropriateness, multiple-input, multiple-output can obtain the suitable improvement of data rate, and wherein the raising of data rate and N (quantity of transmit antenna) are proportional, and can obtain higher signal to noise ratio.Notice that when N increased, it is very violent that the minimizing of scope can become.(b) N should select based on considering of reality, is such as but not limited to, compared to the processing complexity and the maximum target speed of other technology.In one embodiment, Zui Da N is 4.

The present invention advocates the priority of following three unsettled temporary patent applications according to united states patent law the 119th (e): one is application on February 19th, 2004, provisional application number is 60/545,854, name is called " wireless local area network receiver with high data throughput "; It two is on March 25th, 2004 application, and application number is 60/556,264, and name is called " multiple-input, multiple-output wireless LAN communication "; It three is on June 1st, 2004 application, and provisional application number is 60/575,920, and name is called " asymmetric MIMO radio communication ".

Claims (10)

1. an asymmetric MIMO radio communication method is characterized in that this method comprises the steps:

Be identified for the quantity of the transmit antenna of asymmetric MIMO radio communication;

Determine that based on the quantity of transmit antenna this asymmetric MIMO radio communication whether can usage space multiplex technique or space-time block code technology;

The Base-Band Processing receiving mode is selected signal to generate set point and is the selection of baseband portion generating rate;

For space multiplexing technique, on each transmit antenna, provide different constellation point to be used for transmission;

For the space-time block code technology:

At very first time interval:

For the transmission on first transmit antenna provides first constellation point; And

For the transmission on second transmit antenna provides second constellation point; And

In second time interval:

The reverse complex conjugate of second constellation point is provided for the transmission on first transmit antenna; And

The complex conjugate of second constellation point is provided for the transmission on second transmit antenna.

2. the method for claim 1 is characterized in that, determine this asymmetric MIMO radio communication whether can the usage space multiplex technique or the step of space-time block code technology further comprise:

Determine the quantity of reception antenna; And

Determine based on the quantity of reception antenna whether this asymmetric MIMO radio communication can usage space multiplex technique or space-time block code technology.

3. method as claimed in claim 2 is characterized in that, determines that the step of the quantity of reception antenna further comprises:

From receiving the quantity that Wireless Telecom Equipment receives reception antenna.

4. method as claimed in claim 2 is characterized in that, this method further comprises:

When the quantity of reception antenna is equal to or greater than the quantity of transmit antenna, the usage space multiplex technique; And

When the quantity of reception antenna is less than the quantity of transmit antenna, use the space-time block code technology.

5. method as claimed in claim 4 is characterized in that, this method further comprises:

When the quantity of transmit antenna was odd number greater than the quantity of reception antenna, this space-time block code technology comprised:

In first and second time interval, select a transmit antenna to transmit non-space-time block code constellation point; And the transmit antenna group of remainder turned at least one transmit antenna group, this at least one transmit antenna group transmission space-time block code constellation point wherein.

6. method as claimed in claim 4 is characterized in that, this method further comprises:

When the quantity of transmit antenna was even number greater than the quantity of reception antenna, this space-time block code technology comprised:

Transmit antenna is divided at least two groups, and each group comprises at least two transmit antennas; And two groups individually carried out space-time block coding.

7. a radio frequency transmitter is characterized in that, this radio frequency transmitter comprises:

Baseband processing module is used for the ejaculation data transaction is become to penetrate symbols streams; And

Transmitter is used for converting the ejaculation symbols streams to the ejaculation radiofrequency signal, and wherein this transmitter comprises transmit antenna, and this baseband processing module can be further used for:

According to mode select signal with speed punctured convolutional encoding data to generate coded data;

Be identified for the quantity of the transmit antenna of asymmetric MIMO radio communication;

Determine that based on the quantity of transmit antenna this asymmetric MIMO radio communication whether can usage space multiplex technique or space-time block code technology;

For space multiplexing technique, on each transmit antenna, provide different constellation point to be used for transmission;

For the space-time block code technology:

At very first time interval:

For the transmission on first transmit antenna provides first constellation point; And

For the transmission on second transmit antenna provides second constellation point; And

In second time interval:

The reverse complex conjugate of second constellation point is provided for the transmission on first transmit antenna; And

The complex conjugate of second constellation point is provided for the transmission on second transmit antenna.

8. radio frequency transmitter as claimed in claim 7 is characterized in that, baseband processing module can be further used for as follows determining that this asymmetric MIMO radio communication whether can usage space multiplex technique or space-time block code technology:

Determine the quantity of reception antenna;

Determine based on the quantity of reception antenna whether this asymmetric MIMO radio communication can usage space multiplex technique or space-time block code technology.

9. radio frequency transmitter as claimed in claim 8 is characterized in that, baseband processing module is determined the quantity of reception antenna as follows:

From receiving the quantity that Wireless Telecom Equipment receives reception antenna.

10. a radio frequency transmitter is characterized in that, this radio frequency transmitter comprises:

Baseband processing module is used for the ejaculation data transaction is become to penetrate symbols streams; And

Transmitter is used for converting the ejaculation symbols streams to the ejaculation radiofrequency signal, and wherein this transmitter includes transmit antenna, and this baseband processing module can be further used for:

According to mode select signal with speed punctured convolutional encoding data to generate coded data;

Be identified for the quantity of the transmit antenna of asymmetric MIMO radio communication;

Be identified for the quantity of the reception antenna of asymmetric MIMO radio communication;

When the quantity of transmit antenna during, use the space-time block code technology to carry out this asymmetric MIMO radio communication more than the quantity of reception antenna; And

When the quantity of the no more than reception antenna of quantity of transmit antenna, the usage space multiplex technique is realized this asymmetric MIMO radio communication.

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