CA2375879A1 - Dielectric resonator configuration for microwave-multipole bandpass filters - Google Patents
Dielectric resonator configuration for microwave-multipole bandpass filters Download PDFInfo
- Publication number
- CA2375879A1 CA2375879A1 CA002375879A CA2375879A CA2375879A1 CA 2375879 A1 CA2375879 A1 CA 2375879A1 CA 002375879 A CA002375879 A CA 002375879A CA 2375879 A CA2375879 A CA 2375879A CA 2375879 A1 CA2375879 A1 CA 2375879A1
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- Prior art keywords
- dielectric
- dielectric resonator
- wave
- resonator
- coupling
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- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
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Classifications
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
- H01P1/00—Auxiliary devices
- H01P1/20—Frequency-selective devices, e.g. filters
- H01P1/207—Hollow waveguide filters
- H01P1/208—Cascaded cavities; Cascaded resonators inside a hollow waveguide structure
- H01P1/2084—Cascaded cavities; Cascaded resonators inside a hollow waveguide structure with dielectric resonators
Abstract
The invention relates to a dielectric resonator configuration which uses two dielectric spacers in order to separate the dielectric resonator from two en d plates. The resonator configuration provides a very high unloaded Q-factor f or a mixed electromagnetic double wave (HEM11.delta. wave) and a strong modulation and coupling of the (HEM11.delta. wave). A negative and a positiv e cross coupling between non-adjacent waves can thus be attained, and N = 2k ( k = 2, 3, 4 )-pole bandpass filters having quasi elliptical properties can be realized. This resonator configuration also makes it possible to prevent a self-maintaining discharge for filters which operate with high capacity and low-pressure gas and to attain an improved wave separation for multichannel filters.
Description
Dielectric Resonator Configuration for Microwave-Multipole Bandpass Filters Mixed electromagnetic waves (HEM waves) exhibit a degeneration with respect to the axis of rotation (z-axis), i.e. two waves having identical natural resonance frequency, in a cylindrical dielectric resonator which is situated in a metal screen cavity.
The HEM wave with the lowest resonance frequency is the HEM,IS wave. With aid of a coupling screw which is inserted into the screen, it is possible to couple the energy between the two HEM,Is waves and to cause the energy in the resonator to be split into a pair of orthogonal waves. A
coupling of this type makes it possible to realize a two-pole filter with only one resonator. In conventional resonator configurations in which, for example, a cylindrical dielectric resonator is placed on a base plate, the HEM,IS wave exhibits a low unloaded Q-factor (Qo factor). Moreover, it is difficult to attain a sufficiently strong coupling between the HEM"s wave and the coaxial cable that leads to a measuring device.
A dielectric resonator having dielectric spacers is known finm WO-A1-9912225, said spacers spatially separating the dielectric resonator from the end plates of a screen housing.
A resonance Q-factor can be improved thereby that the spacers are dielectric.
Further steps for improving the resonsance quality or further features which are causally responsible for 2 0 improving a resonance factor cannot be found in the aforementioned prior art.
Therefore, it is the object of the present invention to create an arrangement of a dielectric resonator with which it is possible to attain a high unloaded Q-factor for a HEM"s wave and, at the same time, attain a decreased loss effect of the end plates of a screen housing.
This object is solved with the characterizing features of claim 1.
With this resonator configuration, a very high unloaded Q-factor (Qo factor), a strong modulation of the HEM"s wave, a strong coupling between the two HEM,IS waves and a strong coupling between the HEM,IS wave and a coaxial cable or an antenna can be attained for the HEM"s wave. A negative and a positive cross coupling can also be attained therewith between the non-adjacent waves both along the direction of the z-axis and in direction of the xy-plane. With these cross couplings, it is possible to obtain N = 2k (k = 2, 3, 4,...)-pole bandpass filters having quasi-elliptical properties.
The construction and the functioning of the resonator configuration according to the invention will be described in greater detail in the following with reference to an example of an embodiment and the drawings, showing:
Fig. 1 a schematic side view of a resonator configuration according to the invention, wherein the dielectric resonator is separated from its two end plates by two dielectric spacers;
Fig. 2a the electric field distribution in the meridian plane cp = 0°
for the HEM"s wave;
Fig. 2b the magnetic field distribution in the meridian plane cp = 90°
for the HEMI,s wave;
Fig. 3 a schematic view of the coupling of an HEM"s wave with a coaxial cable and a waveguide;
Fig. 4a a schematic side view of a quasi-elliptical four-pole filter with two dielectric 2 0 resonators which are arranged along the main axis (z-axis);
Fig. 4b a top view onto the common plate with the aperture slits that are used for the coupling;
2 5 Fig. 4c a top view onto the upper resonator, wherein a dual-mode modulating device, a dual-mode coupler and an input antenna are inserted from the upper plate;
Fig. 4d a top view onto the lower resonator, wherein the dual-mode modulating device, the dual-mode coupler and an output antenna are inserted from the 3 0 lower plate;
Fig. 5 a schematic top view onto a quasi-elliptical four-pole filter with two dielectric resonators which are arranged in the xy-plane;
Fig. 6 a schematic top view onto a quasi-elliptical eight-pole filter with four dielectric resonators which are arranged in the xy-plane;
Fig. 7 a schematic side view of a dielectric resonator structure, wherein the head of a modulating element is situated within an aperture that has been drilled into the dielectric body; and Fig. 8 a schematic side view of a dielectric resonator structure having an aperture which was drilled by the spacers through the resonator in the central part about their z-axis.
Fig. 1 shows a side view of an example of an embodiment of the resonator configuration according to the invention. A dielectric resonator 3 is thereby separated from the upper end plate 4 and the lower end plate 6 of a metal screen housing by two dielectric spacers 1 and 2.
The dielectric resonator 3 has a 4k-times (k = 1, 2,..) rotational symmetry about its z-axis, for example, with horizontal cross sections of a circle, of a square and the like. Some modifications can be made to the resonator, for example, an aperture can be drilled into the resonator body. This is taken into consideration by the designation of a quasi 4k-times 2 0 rotational symmetry.
The shape of the spacers 1 and 2, i.e. the cross section in the xy-plane, is flexible. However, it is advantageous to select the same shape for the spacer as for the dielectric resonator. The simplest is to make the resonator and the spacers from a piece of a dielectric material. The 2 5 shape of the housing wall 6 is also flexible. Usually, round walls or square walls or a combination of a round wall and a square wall can be used.
Fig. 2a shows the electric field distribution in the meridian plane cp =
0° for the HEM, Is wave.
It can be seen in this field distribution that the strongest electric field, which is indicated by 3 0 thick arrows, is located in the free space between the dielectric resonator and the upper and lower end plates. This produces a sufficiently strong coupling and modulation by using electric sensors.
The HEM wave with the lowest resonance frequency is the HEM,IS wave. With aid of a coupling screw which is inserted into the screen, it is possible to couple the energy between the two HEM,Is waves and to cause the energy in the resonator to be split into a pair of orthogonal waves. A
coupling of this type makes it possible to realize a two-pole filter with only one resonator. In conventional resonator configurations in which, for example, a cylindrical dielectric resonator is placed on a base plate, the HEM,IS wave exhibits a low unloaded Q-factor (Qo factor). Moreover, it is difficult to attain a sufficiently strong coupling between the HEM"s wave and the coaxial cable that leads to a measuring device.
A dielectric resonator having dielectric spacers is known finm WO-A1-9912225, said spacers spatially separating the dielectric resonator from the end plates of a screen housing.
A resonance Q-factor can be improved thereby that the spacers are dielectric.
Further steps for improving the resonsance quality or further features which are causally responsible for 2 0 improving a resonance factor cannot be found in the aforementioned prior art.
Therefore, it is the object of the present invention to create an arrangement of a dielectric resonator with which it is possible to attain a high unloaded Q-factor for a HEM"s wave and, at the same time, attain a decreased loss effect of the end plates of a screen housing.
This object is solved with the characterizing features of claim 1.
With this resonator configuration, a very high unloaded Q-factor (Qo factor), a strong modulation of the HEM"s wave, a strong coupling between the two HEM,IS waves and a strong coupling between the HEM,IS wave and a coaxial cable or an antenna can be attained for the HEM"s wave. A negative and a positive cross coupling can also be attained therewith between the non-adjacent waves both along the direction of the z-axis and in direction of the xy-plane. With these cross couplings, it is possible to obtain N = 2k (k = 2, 3, 4,...)-pole bandpass filters having quasi-elliptical properties.
The construction and the functioning of the resonator configuration according to the invention will be described in greater detail in the following with reference to an example of an embodiment and the drawings, showing:
Fig. 1 a schematic side view of a resonator configuration according to the invention, wherein the dielectric resonator is separated from its two end plates by two dielectric spacers;
Fig. 2a the electric field distribution in the meridian plane cp = 0°
for the HEM"s wave;
Fig. 2b the magnetic field distribution in the meridian plane cp = 90°
for the HEMI,s wave;
Fig. 3 a schematic view of the coupling of an HEM"s wave with a coaxial cable and a waveguide;
Fig. 4a a schematic side view of a quasi-elliptical four-pole filter with two dielectric 2 0 resonators which are arranged along the main axis (z-axis);
Fig. 4b a top view onto the common plate with the aperture slits that are used for the coupling;
2 5 Fig. 4c a top view onto the upper resonator, wherein a dual-mode modulating device, a dual-mode coupler and an input antenna are inserted from the upper plate;
Fig. 4d a top view onto the lower resonator, wherein the dual-mode modulating device, the dual-mode coupler and an output antenna are inserted from the 3 0 lower plate;
Fig. 5 a schematic top view onto a quasi-elliptical four-pole filter with two dielectric resonators which are arranged in the xy-plane;
Fig. 6 a schematic top view onto a quasi-elliptical eight-pole filter with four dielectric resonators which are arranged in the xy-plane;
Fig. 7 a schematic side view of a dielectric resonator structure, wherein the head of a modulating element is situated within an aperture that has been drilled into the dielectric body; and Fig. 8 a schematic side view of a dielectric resonator structure having an aperture which was drilled by the spacers through the resonator in the central part about their z-axis.
Fig. 1 shows a side view of an example of an embodiment of the resonator configuration according to the invention. A dielectric resonator 3 is thereby separated from the upper end plate 4 and the lower end plate 6 of a metal screen housing by two dielectric spacers 1 and 2.
The dielectric resonator 3 has a 4k-times (k = 1, 2,..) rotational symmetry about its z-axis, for example, with horizontal cross sections of a circle, of a square and the like. Some modifications can be made to the resonator, for example, an aperture can be drilled into the resonator body. This is taken into consideration by the designation of a quasi 4k-times 2 0 rotational symmetry.
The shape of the spacers 1 and 2, i.e. the cross section in the xy-plane, is flexible. However, it is advantageous to select the same shape for the spacer as for the dielectric resonator. The simplest is to make the resonator and the spacers from a piece of a dielectric material. The 2 5 shape of the housing wall 6 is also flexible. Usually, round walls or square walls or a combination of a round wall and a square wall can be used.
Fig. 2a shows the electric field distribution in the meridian plane cp =
0° for the HEM, Is wave.
It can be seen in this field distribution that the strongest electric field, which is indicated by 3 0 thick arrows, is located in the free space between the dielectric resonator and the upper and lower end plates. This produces a sufficiently strong coupling and modulation by using electric sensors.
Fig. 2b shows the magnetic field distribution in the meridian plane cp =
90° for the HEM"s wave. The strongest magnetic field is found within the dielectric resonator in this field distribution. The magnetic field on the two end plates is relatively weak.
This field distribution results in a very low loss for the two end plates. This gives the resonator housing a very good Q-factor. This is in contrast to a conventional resonator configuration in which, for example, the dielectric resonator is arranged directly on the lower end plate. In this case, a strong magnetic field is found on the lower end plate which results therein that the lower end plate causes a strong loss.
Fig. 3 is a schematic representation of a design according to the invention in order to couple the HEM~IS wave of a dielectric resonator 11 with a coaxial cable 12 and a waveguide 13.
For the coupling with the coaxial cable, the coaxial cable is coupled by the aperture that opens on the end plate through a coupling antenna 14 which is connected with the inner guide of the coaxial cable. For the coupling with the waveguide, the lower end plate 1 S is arranged on the broad side 16 of the waveguide. An aperture 17 is opened in the centre of the broad side 16 by the waveguide through the lower end plate 15. A coupling antenna 18 is used in order to couple the resonator with the waveguide. A dielectric ring 19 is used to form an insulation between the coupling antenna and the wall of the waveguide.
A dielectric screw 20 having a low dielectricity constant and a slight loss is connected with the antenna 2 0 18. It can be adjusted from the underside of the waveguide.
To realize the bandpass filters with quasi-elliptical properties, positive and negative cross couplings are required between non-adjacent waves. The cross coupling can be realized by the resonator configuration according to the invention both along the direction of the z-axis 2 5 and in the xy-plane. The negative or positive cross coupling is attained by the positioning of the direction of the wave polarization in the same or the opposite direction during coupling.
This is obtained by a suitable arrangement of input and output antennas and by dual-mode couplers. Some examples for creating bandpass filters with quasi-elliptical response are noted in the following.
Fig. 4a is a schematic side view of a quasi-elliptical four-pole bandpass filter which uses two resonators 21a and 21b which are arranged along the direction of the z-axis.
Figs. 4b and 4c are top views onto the upper or lower resonators 21a or 21b, respectively. An input antenna 22a and an output antenna 22b are coupled with the upper or lower resonators, respectively.
Dual-mode couplers 23a and 23b and dual-mode modulating devices 24a and 24b are inserted from the upper or lower plates for the upper or lower resonators, respectively. Fig.
4d is the top view onto the common plate with the slits 25 and 26 provided for the coupling.
90° for the HEM"s wave. The strongest magnetic field is found within the dielectric resonator in this field distribution. The magnetic field on the two end plates is relatively weak.
This field distribution results in a very low loss for the two end plates. This gives the resonator housing a very good Q-factor. This is in contrast to a conventional resonator configuration in which, for example, the dielectric resonator is arranged directly on the lower end plate. In this case, a strong magnetic field is found on the lower end plate which results therein that the lower end plate causes a strong loss.
Fig. 3 is a schematic representation of a design according to the invention in order to couple the HEM~IS wave of a dielectric resonator 11 with a coaxial cable 12 and a waveguide 13.
For the coupling with the coaxial cable, the coaxial cable is coupled by the aperture that opens on the end plate through a coupling antenna 14 which is connected with the inner guide of the coaxial cable. For the coupling with the waveguide, the lower end plate 1 S is arranged on the broad side 16 of the waveguide. An aperture 17 is opened in the centre of the broad side 16 by the waveguide through the lower end plate 15. A coupling antenna 18 is used in order to couple the resonator with the waveguide. A dielectric ring 19 is used to form an insulation between the coupling antenna and the wall of the waveguide.
A dielectric screw 20 having a low dielectricity constant and a slight loss is connected with the antenna 2 0 18. It can be adjusted from the underside of the waveguide.
To realize the bandpass filters with quasi-elliptical properties, positive and negative cross couplings are required between non-adjacent waves. The cross coupling can be realized by the resonator configuration according to the invention both along the direction of the z-axis 2 5 and in the xy-plane. The negative or positive cross coupling is attained by the positioning of the direction of the wave polarization in the same or the opposite direction during coupling.
This is obtained by a suitable arrangement of input and output antennas and by dual-mode couplers. Some examples for creating bandpass filters with quasi-elliptical response are noted in the following.
Fig. 4a is a schematic side view of a quasi-elliptical four-pole bandpass filter which uses two resonators 21a and 21b which are arranged along the direction of the z-axis.
Figs. 4b and 4c are top views onto the upper or lower resonators 21a or 21b, respectively. An input antenna 22a and an output antenna 22b are coupled with the upper or lower resonators, respectively.
Dual-mode couplers 23a and 23b and dual-mode modulating devices 24a and 24b are inserted from the upper or lower plates for the upper or lower resonators, respectively. Fig.
4d is the top view onto the common plate with the slits 25 and 26 provided for the coupling.
5 Modulating elements 27 and 28 can be used to set the coupling coefficients kz3 and k,4.
Since the directions of the wave polarization for the wave 1 (M 1 ) and the wave 4 (M4) are the same, then k,4 is negative.
Fig. 5 is the schematic top view onto a quasi-elliptical four-pole bandpass filter having two resonators 31a and 31b which are arranged in the xy-plane. In this arrangement, the wave polarization is arranged in a direction of 45° relative to the middle line of the common side wall which makes it possible to attain a cross coupling. The negative cross coupling k,4 is attained by the arrangement of the input antenna 32a and the output antenna 32b and the dual-mode couplers 33a and 33b shown in Fig. 5.
Fig. 6 is the schematic top view onto a quasi-elliptical eight-pole bandpass filter having four resonators which are arranged in the xy-plane. Three cross couplings (k36, k2., and k,8) are established with this design. In these cross couplings, k36 and k2, are negative and k,8 is positive.
In a low-pressure gas, a self maintaining discharge can occur when a high-frequency electric field is applied, if the applied field is strong enough that it sends out secondary electrons and if the emitted secondary electrons jump back and forth between the emitted electrodes in resonance with the applied field. If the dielectric resonator is to be used for high-capacity 2 5 applications in a vacuum or a low-pressure atmosphere, then self maintaining discharges of this type must be avoided. With the resonator configuration according to the invention, a self maintaining discharge of this type can be easily avoided. The principle is shown in Fig.
7. The head of a modulating element or an antenna 42 is placed in an aperture 41 which was drilled into the dielectric resonator body once the modulation has been completed. The 3 0 electric field within the dielectric body is much less than that of the two ends of the dielectric resonator.
Another important point when using filters, in particular for mufti-channel filters, is the wave separation. It is necessary to keep all undesirable resonance frequencies in all channel filters outside of the operating frequency band. To attain this, the undesirable resonsance frequencies must generally be pushed as far away as possible from the operating resonance frequency. This can also be attained with the resonator configuration according to the invention.
The adjacent waves of the HEM"s wave in the resonator configuration according to the invention are the TEo~s wave on the side of the lower frequency and the HEMIZS
wave on the side of the higher frequency. It was found that the strengths of the electric fields for the TEo,s wave, HEM,IS wave and the HEM,zs wave in the centre of the resonator are quite different. The electric field is very weak for the TEo,s wave, not very strong for the HEM"s wave and very strong for the HEM,zs wave in the centre of the resonator. Thus, removing a cylinder stopper 51 from the centre of the resonator and the spacers, as shown in Fig. 8, changes the resonance frequency of these three waves in various ways. The resonance frequency of the TEols wave remains almost unchanged. A very slight increase might occur.
On the other hand, with the HEM,IS wave a moderate increase occurs. And with the HEM,zs wave, there is a great increase.
Since the directions of the wave polarization for the wave 1 (M 1 ) and the wave 4 (M4) are the same, then k,4 is negative.
Fig. 5 is the schematic top view onto a quasi-elliptical four-pole bandpass filter having two resonators 31a and 31b which are arranged in the xy-plane. In this arrangement, the wave polarization is arranged in a direction of 45° relative to the middle line of the common side wall which makes it possible to attain a cross coupling. The negative cross coupling k,4 is attained by the arrangement of the input antenna 32a and the output antenna 32b and the dual-mode couplers 33a and 33b shown in Fig. 5.
Fig. 6 is the schematic top view onto a quasi-elliptical eight-pole bandpass filter having four resonators which are arranged in the xy-plane. Three cross couplings (k36, k2., and k,8) are established with this design. In these cross couplings, k36 and k2, are negative and k,8 is positive.
In a low-pressure gas, a self maintaining discharge can occur when a high-frequency electric field is applied, if the applied field is strong enough that it sends out secondary electrons and if the emitted secondary electrons jump back and forth between the emitted electrodes in resonance with the applied field. If the dielectric resonator is to be used for high-capacity 2 5 applications in a vacuum or a low-pressure atmosphere, then self maintaining discharges of this type must be avoided. With the resonator configuration according to the invention, a self maintaining discharge of this type can be easily avoided. The principle is shown in Fig.
7. The head of a modulating element or an antenna 42 is placed in an aperture 41 which was drilled into the dielectric resonator body once the modulation has been completed. The 3 0 electric field within the dielectric body is much less than that of the two ends of the dielectric resonator.
Another important point when using filters, in particular for mufti-channel filters, is the wave separation. It is necessary to keep all undesirable resonance frequencies in all channel filters outside of the operating frequency band. To attain this, the undesirable resonsance frequencies must generally be pushed as far away as possible from the operating resonance frequency. This can also be attained with the resonator configuration according to the invention.
The adjacent waves of the HEM"s wave in the resonator configuration according to the invention are the TEo~s wave on the side of the lower frequency and the HEMIZS
wave on the side of the higher frequency. It was found that the strengths of the electric fields for the TEo,s wave, HEM,IS wave and the HEM,zs wave in the centre of the resonator are quite different. The electric field is very weak for the TEo,s wave, not very strong for the HEM"s wave and very strong for the HEM,zs wave in the centre of the resonator. Thus, removing a cylinder stopper 51 from the centre of the resonator and the spacers, as shown in Fig. 8, changes the resonance frequency of these three waves in various ways. The resonance frequency of the TEols wave remains almost unchanged. A very slight increase might occur.
On the other hand, with the HEM,IS wave a moderate increase occurs. And with the HEM,zs wave, there is a great increase.
Claims (6)
1. Arrangement of a dielectric resonator for a microwave-multipole bandpass filter in a metal screen housing which has an upper and a lower end plate, wherein the dielectric resonator has a main axis and is separated by two dielectric spacers from the end plates, so that there is an open space between the dielectric resonator and the end plates, characterized therein that the dielectric resonator (3) has 4k-times rotational symmetry or quasi 4 k-times rotational symmetry about the main axis (z), where k is a whole natural number.
2. Arrangement according to claim 1, characterized therein that the dielectric spacers (1 and 2) have a dielectric constant which is between 1 and the value of the dielectric constant of the dielectric resonator (3).
3. Arrangement according to claim 1 or 2, characterized therein that the dielectric resonator (3) has a dielectric constant between 9 and 500.
4. Arrangement according to one of the claims 1 to 3, characterized therein that the dielectric resonator (3) and the dielectric spacers (1 and 2) are made from a piece of dielectric material.
5. Arrangement according to one of the claims 1 to 4, characterized therein that an antenna (14) or a dual-mode coupler is placed in the open area between the dielectric resonator (3) and the end plates (1, 2) in the area of a strong electric field.
6. Arrangement according to one of the claims 1 to 4, characterized therein that the lower end plate (15) is arranged on a broad side (16) of the waveguide (13) and the dielectric resonator (3) is coupled with the waveguide (13) via a coupling antenna (18) through an aperture (17) in the centre of the broad side (16).
Applications Claiming Priority (3)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| DE1999127798 DE19927798A1 (en) | 1999-06-18 | 1999-06-18 | The electrical resonator configuration for microwave multipole bandpass filters |
| DE19927798.2 | 1999-06-18 | ||
| PCT/DE2000/001936 WO2000079640A1 (en) | 1999-06-18 | 2000-06-13 | Dielectric resonator configuration for microwave-multipole bandpass filters |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| CA2375879A1 true CA2375879A1 (en) | 2000-12-28 |
Family
ID=7911651
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CA002375879A Abandoned CA2375879A1 (en) | 1999-06-18 | 2000-06-13 | Dielectric resonator configuration for microwave-multipole bandpass filters |
Country Status (5)
| Country | Link |
|---|---|
| EP (1) | EP1190466A1 (en) |
| JP (1) | JP2003502974A (en) |
| CA (1) | CA2375879A1 (en) |
| DE (1) | DE19927798A1 (en) |
| WO (1) | WO2000079640A1 (en) |
Family Cites Families (10)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CA1168718A (en) * | 1981-05-11 | 1984-06-05 | Slawomir J. Fiedziuszko | Miniature dual-mode, dielectric-loaded cavity filter |
| JPH0630402B2 (en) * | 1986-02-07 | 1994-04-20 | 三菱電機株式会社 | Duplexer |
| JPH02150808U (en) * | 1989-05-22 | 1990-12-27 | ||
| US5191304A (en) * | 1990-03-02 | 1993-03-02 | Orion Industries, Inc. | Bandstop filter having symmetrically altered or compensated quarter wavelength transmission line sections |
| CA2048404C (en) * | 1991-08-02 | 1993-04-13 | Raafat R. Mansour | Dual-mode filters using dielectric resonators with apertures |
| DE4241027C2 (en) * | 1992-12-05 | 1997-03-20 | Bosch Gmbh Robert | Tunable dielectric resonator |
| DE4316334A1 (en) * | 1993-05-15 | 1994-11-17 | Forschungsgesellschaft Fuer In | Dielectric resonator |
| JP3738916B2 (en) * | 1995-04-18 | 2006-01-25 | 株式会社村田製作所 | Dielectric resonator |
| DE19617698C1 (en) * | 1996-05-03 | 1997-10-16 | Forschungszentrum Juelich Gmbh | Dual-mode two-pole filter |
| JP3503482B2 (en) * | 1997-09-04 | 2004-03-08 | 株式会社村田製作所 | Multi-mode dielectric resonator device, dielectric filter, composite dielectric filter, combiner, distributor, and communication device |
-
1999
- 1999-06-18 DE DE1999127798 patent/DE19927798A1/en not_active Withdrawn
-
2000
- 2000-06-13 JP JP2001505102A patent/JP2003502974A/en not_active Withdrawn
- 2000-06-13 EP EP00949093A patent/EP1190466A1/en not_active Withdrawn
- 2000-06-13 WO PCT/DE2000/001936 patent/WO2000079640A1/en not_active Application Discontinuation
- 2000-06-13 CA CA002375879A patent/CA2375879A1/en not_active Abandoned
Also Published As
| Publication number | Publication date |
|---|---|
| DE19927798A1 (en) | 2001-01-04 |
| EP1190466A1 (en) | 2002-03-27 |
| JP2003502974A (en) | 2003-01-21 |
| WO2000079640A1 (en) | 2000-12-28 |
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Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| FZDE | Discontinued |