CA2039427A1 - Paging receiver - Google Patents
Paging receiverInfo
- Publication number
- CA2039427A1 CA2039427A1 CA 2039427 CA2039427A CA2039427A1 CA 2039427 A1 CA2039427 A1 CA 2039427A1 CA 2039427 CA2039427 CA 2039427 CA 2039427 A CA2039427 A CA 2039427A CA 2039427 A1 CA2039427 A1 CA 2039427A1
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- signal
- receiver
- radio
- intermediate frequency
- local oscillator
- Prior art date
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Abstract
The present invention relates to a radio receiver comprising means for receiving a radio signal, first means for beating the signal to zero intermediate frequency in phase and quadrature shifted signals, means for amplifying the in phase and quadrature zero shifted intermediate frequency signals, second means for beating the amplified intermediate frequency signals to predetermined nonzero intermediate frequency in phase and quadrature shifted signals, means for summing said non-zero signals, and means for applying the summed signals to a discriminator to obtain an output signal.
Description
~3~
FIELD~OF THE INVENTION:
This invention relates to radio receivers, and particularly to systems and circuits which can enhance the operation of paging receivers.
S BACKGROUND TO THE INVE_TION~
A conventional superheterodyne receiver (superhet) is based upon the mixing of a received signal with a local oscillator ('IL.O."~ signal to yield a new (intermediat~ frequency or ''I.F.-I) signal which is the diff rence or sum o~ the L.O. and off-air signal frequencies. Tuning of the receiver is effected by varying the local oscillator frequency, thereby changing the frequency of the off air signal which when mixed with the L.O. signal, will yield a signal at a fixed I.F.
A disadvantage of the superheterodyne receiver is that received signals having a frequency higher or lower than the L.O. frequency and differing from the L.O. frequency by the I.F. either positively or negatively will mix to yield signals at the I.F.
This is known as the reception o~ the "imaye" and may be partially overcome by the use of a higher intermediate frequency. This is often followed by a second conversion to a lower frequency where adjacent channel filtering is performed. Double superheterodyne receivers commonly have the first I.F. at 10.7 MHz so that the image frequency is 21.4 MHz away from the desired signal.
In order to save battery power, pager receivers "hibernate" or "sleep'7 for certain periods of time, turning themselves on regularly at predetermined intervals in order to check for addressing from a transmitter. One such form of time division multiplexed addressing is that specified in CCITT 584-1 paging format, also known as POCSAG.
disadvantage of this form of time division addre~sing is that power consumption is constant regardless of ;~)3~
channel traf~ic. Another disadvantage is that if the receiver is required to receive large amounts of data to be transmitted during off peak hours it is necessary in current state of the art pagers to S continuously operate, according to the paging code format.
Current state of the art radio pagers generally have their featllres and functions defined by firmware designed into the product, and most have a level of progra-mmability, using special attachments, to provide for selection of alternate response characteristics from a small range of options offered. A disadvantage of this is that all of the receiver response characteristics have to be 1~ defined at the time of design and the receiver cannot be modified to meet the requirements of a specific user or service provider.
Current state of the art radio pagers generally include vibrators within the body of the pager so that the user may be silently alerted to the receipt of a page. For maximum effectiveness, it is necessary for such device to be firmly coupled to the wearer, as is the case when worn on a belt. The disadvantage of this is that when the pager is not so carried, the vibrator has limited effectiveness and an alternative form of alert is desirable.
Radio paging receivers commonly use replaceable Alkaline batteries or rechargable batteries of the same ~orm interchangeably. The detection of low battery reserve is generally determined by evaluation of the terminal battery voltage under load. A disadvantage of this is that disposable battery discharge characteristics differ from those of rechargeable batteries and accurate detection of low battery reserve for both types using a common detection method is generally only accurate for one type.
~39~
AFC (Automatic Frequency Control~ is very desirable on UHF (Ultra High Frequency) receivers operating above 500 MHz. At these frequencies the frequency errors in the crystal oscillators used to generate the local oscillator signals in the receiver amount to a few parts per million, and are comparable with, and can exceed, the frequency tolerance o~ the receiver (for maximum sensitivity)~ These errors result from sensitivity to temperature and from long term frequency drift caused by aging of the crystal.
AFC is widely used on analog systems. FGr such receivers on channel center, the integral of the deviation over a period of a few hundred milliseconds or less is zero, and because transmission (and reception~ is continuous, capacitors can be used to integrate and store the AFC feed back signal.
Simple analog systems cannot be used in receivers which are strobed (for channel sampling? or which are designed to be used with digital, time dependent addressing techniques (such as CCITT
584-1). There are three principal difficulties:
a) In digital systems, the FSK (Frequency Shift Keyed) modulated carrier may contain very low frequency components due to long streams of l's or 0's.
b) The periods between samples can be as long as one second so that analog techniques to store feedback signals (such as sample and hold~ are marginal and error prone.
c) To minimize power consumption, the receiver should be prealigned to minimize the period time required by the receiver to sample the channel.
SUMMARY OF THE PRESENT INVENTION-one embodiment of the present invention is 3S a novel form of superheterodyne receiver which does not have an image frequency.
~3~2~
In this embodiment, near and adjacent signal rejection filtering is largely achieved and the requirements for filtering are much reduced over that of the prior art. Further, low cost highly miniaturize IF filter elements, widely used in conventional superheterodyne receivers, can be used.
This rec iver, unlike conventional single stage zero I . F. receivers, will reproduce analog frequency modulated signals, essential requirements for voice or ~ast digital signals.
The receiver of the present invention can be used in a digital radio pager which can have the following important novel features, structures and methods of operation:
1. Operation according to CCITT-584-1 paging format but with fully compliant extensions whereby battery saving can be substantially improved, including a means for the receiver power up infrequently but at defined times to provide for reception of data even when switched off.
FIELD~OF THE INVENTION:
This invention relates to radio receivers, and particularly to systems and circuits which can enhance the operation of paging receivers.
S BACKGROUND TO THE INVE_TION~
A conventional superheterodyne receiver (superhet) is based upon the mixing of a received signal with a local oscillator ('IL.O."~ signal to yield a new (intermediat~ frequency or ''I.F.-I) signal which is the diff rence or sum o~ the L.O. and off-air signal frequencies. Tuning of the receiver is effected by varying the local oscillator frequency, thereby changing the frequency of the off air signal which when mixed with the L.O. signal, will yield a signal at a fixed I.F.
A disadvantage of the superheterodyne receiver is that received signals having a frequency higher or lower than the L.O. frequency and differing from the L.O. frequency by the I.F. either positively or negatively will mix to yield signals at the I.F.
This is known as the reception o~ the "imaye" and may be partially overcome by the use of a higher intermediate frequency. This is often followed by a second conversion to a lower frequency where adjacent channel filtering is performed. Double superheterodyne receivers commonly have the first I.F. at 10.7 MHz so that the image frequency is 21.4 MHz away from the desired signal.
In order to save battery power, pager receivers "hibernate" or "sleep'7 for certain periods of time, turning themselves on regularly at predetermined intervals in order to check for addressing from a transmitter. One such form of time division multiplexed addressing is that specified in CCITT 584-1 paging format, also known as POCSAG.
disadvantage of this form of time division addre~sing is that power consumption is constant regardless of ;~)3~
channel traf~ic. Another disadvantage is that if the receiver is required to receive large amounts of data to be transmitted during off peak hours it is necessary in current state of the art pagers to S continuously operate, according to the paging code format.
Current state of the art radio pagers generally have their featllres and functions defined by firmware designed into the product, and most have a level of progra-mmability, using special attachments, to provide for selection of alternate response characteristics from a small range of options offered. A disadvantage of this is that all of the receiver response characteristics have to be 1~ defined at the time of design and the receiver cannot be modified to meet the requirements of a specific user or service provider.
Current state of the art radio pagers generally include vibrators within the body of the pager so that the user may be silently alerted to the receipt of a page. For maximum effectiveness, it is necessary for such device to be firmly coupled to the wearer, as is the case when worn on a belt. The disadvantage of this is that when the pager is not so carried, the vibrator has limited effectiveness and an alternative form of alert is desirable.
Radio paging receivers commonly use replaceable Alkaline batteries or rechargable batteries of the same ~orm interchangeably. The detection of low battery reserve is generally determined by evaluation of the terminal battery voltage under load. A disadvantage of this is that disposable battery discharge characteristics differ from those of rechargeable batteries and accurate detection of low battery reserve for both types using a common detection method is generally only accurate for one type.
~39~
AFC (Automatic Frequency Control~ is very desirable on UHF (Ultra High Frequency) receivers operating above 500 MHz. At these frequencies the frequency errors in the crystal oscillators used to generate the local oscillator signals in the receiver amount to a few parts per million, and are comparable with, and can exceed, the frequency tolerance o~ the receiver (for maximum sensitivity)~ These errors result from sensitivity to temperature and from long term frequency drift caused by aging of the crystal.
AFC is widely used on analog systems. FGr such receivers on channel center, the integral of the deviation over a period of a few hundred milliseconds or less is zero, and because transmission (and reception~ is continuous, capacitors can be used to integrate and store the AFC feed back signal.
Simple analog systems cannot be used in receivers which are strobed (for channel sampling? or which are designed to be used with digital, time dependent addressing techniques (such as CCITT
584-1). There are three principal difficulties:
a) In digital systems, the FSK (Frequency Shift Keyed) modulated carrier may contain very low frequency components due to long streams of l's or 0's.
b) The periods between samples can be as long as one second so that analog techniques to store feedback signals (such as sample and hold~ are marginal and error prone.
c) To minimize power consumption, the receiver should be prealigned to minimize the period time required by the receiver to sample the channel.
SUMMARY OF THE PRESENT INVENTION-one embodiment of the present invention is 3S a novel form of superheterodyne receiver which does not have an image frequency.
~3~2~
In this embodiment, near and adjacent signal rejection filtering is largely achieved and the requirements for filtering are much reduced over that of the prior art. Further, low cost highly miniaturize IF filter elements, widely used in conventional superheterodyne receivers, can be used.
This rec iver, unlike conventional single stage zero I . F. receivers, will reproduce analog frequency modulated signals, essential requirements for voice or ~ast digital signals.
The receiver of the present invention can be used in a digital radio pager which can have the following important novel features, structures and methods of operation:
1. Operation according to CCITT-584-1 paging format but with fully compliant extensions whereby battery saving can be substantially improved, including a means for the receiver power up infrequently but at defined times to provide for reception of data even when switched off.
2. Automatic Frequency Control of the pager which is able to operate on FSR data without regard to the length of consecutive equal data states transmitted, and which can operate on a time division multiplex address scheme such as CCITT 584-1.
operation according to CCITT 5B4-1 Paging format but with fully compliant extension~
whereby unlimited instructions can be transmitted to one or more than one pager, so as to tailor its response or operating characteristics to suit those of individual users or service providexs.
4. Meanings of buttons or keys which constitute the users means of operating the pager can have thei.r function altered, and the new meaning illustrated or indicated by the use of images presented on a dot matrix or other form or :
, 2~39~
programmable display, in close proximity to the control button.
5. A holster designed to carry the pager has an integral clip for attachment to the wearer's apparel, in which is installed a vibrator. A
detection means is included so that the alerting means, being audible, optical or vibrational can be automatically changed according to th~ users programmed preference when in or out of the holster.
6. A means for detecting the rate oP
change of the battery terminal voltage or internal resistance to provide for accurate low battery detection can be provided ~or either alkaline or rechargeable batteries.
An "intelligent" automatic frequency control (AFC) system can be provided in which the discriminator output level is integrated for a specific period, starting a fixed period after a logical transition. If data remains good (iOe. the state i5 retained for a minimum data period) the integrated voltage is stored and compared with a similar sample taken for the other logical state.
The AFC signal is generated, proportional to the difference between these two samples, and the correction signal applied t~ a varactor in the local oscillator circuit, to control the frequency.
A "Script" method for controlling the pager response, comprised of a special escape sequence (e.g. a non-printable character) followed by a short form "language" to determine pager actions, can be used.
Messages are sent via a computer to one or more pocket pager devices. The pager simply acquires the message without response and displays it on request.
Alternatively the unit can be used with or as a scheduler, which can be dynamically loaded .
,:
~399L2~
with new information by a secretary or dispatcher.
This information be conveyed building, nation or continent wide depending upon thP extent of the paging system accessed by the secretary. Preferably the pager is in the form of a small billfold (e.g. is credit card sized), and is generally used to forward messages to the user, at the same level of urgency as for telephone answering slips. A user could permit a limited number of persons to know the sequence whereby the device ~ould be made to beep.
In accordance with an embodiment of the invention a radio receiver is comprised of apparatus for receiving a radio signal first apparatus for beating the signal to zero intermediate frequency in phase and quadrature shifted signals~ apparatus for amplifying the in phase and quadrature shifted zero intermediate frequency signals, second apparatus for beating the amplified intermediate frequency signals to predetermined non-zero intermediate freguency in phase and quadrature shifted signals, apparatus for summing said non-zero signals, and apparatus for applying the summed signal to a discriminator to obtain an output signal.
In accordance with another embodiment of the invention, a radio receiver is comprised of apparatus for receiving and bandpass filtering a radio signal of predetermined frequency, a first local oscillator for generating a local oscillator signal having a ~requency which is the same as the radio signal, apparatus for phase shifting the local oscillator signal by 90, a first mixer for receiving the radio signal and the local oscillator signal and for providing a first in phase zero intermediate frequency signal, a second mixer for receiving the radio signal. and the phase shifted local oscillator signal and for providing a second quadrature shifted zero intermediate frequency signal~ low pass filter 2~
apparatus for filtering the intermediate frequency signals, a second local oscillator for yeneratinq a predetermined frequency local oscillator signal, apparatus for phase shifting the predetermined frequency local oscillator signal by 90 to provide a non-zero phase shi~ted local oscillator signal, a third mixer for receiving the in phase zero intermediat~ frequency signal and the predetermined frequency local oscillator signal and for generating a non-zero intermediate frequency signal, a fourth mixer for receiving the quadrature shifted zero intermediate frequency signal and the non-zero phase shifted local oscillator signal and for generating a non-zero quadrature shifted intermediate frequency signal, apparatus for summing the non-zero intermediate frequency signal and the non-zero quadrature shifted intermediate frequency signal, to form a summed non-zero intermediate frequency signal, and apparatus for discriminating the summed signal to provide an output signal.
In accordance with another embodiment o~
the invention, a superheterodyne F.M. radio receiver is comprised of a first local oscillator which includes a varactor for adjusting its frequency, a discriminator, and an automatic frequency control (AFC) circuit for generating an AFC signal, the AFC
circuit comprising a first counter/regisker for storing the AFC signal as a digital signal, a digital to analog converter (DAC) for receiving an output of said counter/register, and apparatus for applying the~
output signal of the DAC to the varactor, whereby the AFC signal stored in the counter/register controls frequency adjustment of the first local oscillator.
In accordance with another embodiment of the invention, a radio page signal receiver is in combination with a belt clip with a vibrator alert apparatus fixed to the belt clip for applying 8 ~ 3~ 7 vibration against the body of a wearer upon receipt of an alerting signal, and optionally a battery for powering ths vibrator alert apparatus retained by the belt clip, apparatus in the belt clip for removably S retaining the removable radio receiver, and apparatus for coupling a vibrator alert enable signal from the receiver to the vibrator alert apparatus upon the receiver being retained in said belt clip.
In accordance with another embodiment of the invention, a page signal receiver is comprised of a battery, low and high load pPripherals connected to the receiver, apparatus for operating a high load peripheral, a low battery ressrve detector, and apparatus for substituting a low load peripheral for a high load peripheral upon detection of low battery reserve.
In accordance with anotAer embodiment of the invention, ~ radio page receiver is comprised of apparatus for receiving high and low priority messages from a transmitter, apparatus for alerting and displaying the high priority messages, and apparatus for storing the low priority messages and for being enabled to display the low priority messages on demand by a user.
In accordance with another embodiment of the invention, a low battery detection circuit for electronic apparatus is comprised of a voltage comparator for sampling battery terminal voltage respectively under ].ight and heavy loading, and for indicating a low battexy condition when the rate of change of the sampled voltage or internal resistance is greater than a predetermined limit~
In accordance with another embodiment of the invention, a radio pager is comprised of apparatus for receiving a transmitted signal from a transmitter, apparatus for extracting a command signal and a message signal from the transmitted ~3~
signal, and apparatus for operating the receiver in response to the command to control how the message signal is handled.
In accordance with another embodiment of the invention, a paging receiver includes apparatus ~or recognizing time slot bits in each of a plurality of time frames, and powering on in one of the time slots upon the detection of one of said time slot bits.
BRIEF INTRODUCTION TO THE DRAWINGS:
A better understanding of the invention will be obtained by reference to the detail~d description below, in conjunction with the following drawings, in which:
Figure 1 is a block schematic of a the intermediate frequency stages of a radio receiver according to an embodiment of the inventivn, FigurP 2 is a block schematic of a radio receiver particularly oP the AFC loop, Figures 3, 4 and 5 are diagrams illustrating the structure of signals used in embodiments of the invention, Figure 6 is a graph illustrating lifetime characteristics o~ alkaline and NiCd batteries, and Figure 7 is a block diagram of a low battery detection system.
DESCRIPTION OF THE PREFERRED EMBODIMEN?So The new receiver, shown in Figure 1, is a double superheterodyne. A xeceived off-air siynal from antenna 1 passes through a first bandpass filter 2, an amplifier 3 and a second bandpass filter 4, as in the prior art. The signal is then applied to two mixers 5 and 6. A local oscillator 7 is tuned exactly to the desired signal frequency, the output signal of which is mixed in mixer 5 with the off-air signal. The local oscillator output signal is also mixed with the off-air signal in mixer 2 after being ~)3~27 phase shifted by 90 in phase shifter 8. The result at the output of mixer 5 is one of the resultant signals, which is the de~ired signal mixed down to a base band signal centered at 0 Hz. The negatiYe S frequency components are preserved in the quadrature channel, at the output of mixer 6.
The output signals of m:ixers 5 and 6 are filtared with simple R-C gyrator or active filter elements g and 10, which pass the low frequency desired signalO Aft~r being amplified in amplifiers 11 and 12, the signals in the two channels are applied respectively to mixers 13 and 14. A local oscillator 15 of preferably 455 kHz has its signal applied to mixer 13 and its signal applied to mixer 14 through 90~ phase shifter 16. This up converts the signals in the two channels from zero intermediate frequency to 455 kHz. The output signals from the mixers 13 and 14 in the two channels are summed in adder 17, then pass band filtexed in filter 18 using conventional components such as ceramic or L-C filters. The output of filter 18 is a frequency modulated signal containing the same information as the received signal but with a carrier frequency equal to the second local o~cillator frequency, 455 kKz.
The up-converted signal at the output of filter 18 is amplified to a square wave in a limiting amplifier 19, and the square wave signal is then applied to a frequency discriminator 20. The modulating signal is extracted from the modulated carrier by continuous comparison of the frequencies of the local oscillator (455 kHz) and the modulated signal in the frequency discriminator.
The resuLting output signal is passed through filter 21 for application to circuits which use the modulating signal.
2~3~
The function of the receiver is described mathematically below.
Let the received signal xc(t) be represented by xc(t) = A~ Cos (Wct-~(t)) where Ac is the carrier amplitude Wc is the carrier radian frequency ~(t) is the time varying phase containing the modulating signal.
Let the 1st local oscillator signal Aoi(t) be:
Aoi(t)=Ao Cos~WOt) Let the quadrature LO signal Aoq(t) be:
Aoq(t)=Ao Sin(Wot) At the output of mixer Ml the signal is:
AcCS(Wc+~(t)), Aoicos(wot) 1~ After filtering this becomes AoiAC Cos ((Wc-Wo)t+~(t)) Similarly, output signal from mixer M2, after filtering is AoiAc sin ((Wc-Wo)t+~(t)) Let the 2nd LO signal xki(t) be Aki(t)=Ak C09(Wkt) and its quadrature signal be A~q(t)=Ak Sin(Wkt) At the mixer M3 output the signal is AoAc Cos((Wc-WO)t+~(t)).AkCes(Wkt) = AoAcAc(1 Cos~(wc-wo-wk)-~(t))+lcos(~c-wo-~k)t+~(t)) Similarly, the output signal at mixer M4 O/P i5 given by:
AoACAk(l Cos((wc-wo-wk)t~(t))-lco5 (WC-WO-W~) t+~(t)) By differencing the output of mixers M3, M4 vO = AoACAk Cos((wc-wo-wk)t+~(t)) ' ` ', ~3~
This signal is the same as ths input signal but with the carrier ~r~uency shifted by the amount ~Wo~Wc If WO=WC then the output is exactly s centered at Wk.
In the above analysis phases of signals have been taken as arbitrary and therefore ignored.
Advantages of the receiver are as follows:
l. Because the first IF is zero the receiver does not have an image frequency.
2. Near and adjacent channel signal rejection filtering is largely achieved in the 455 KHz section filter and the requirements for ~iltering in the zero IoF~ section are much reduced over those required in a single stage zero I.F. receiver.
Further, low cost, highly miniature 455 KHz filter elements, widely used in conventional superheterodyne receivers, can be used.
operation according to CCITT 5B4-1 Paging format but with fully compliant extension~
whereby unlimited instructions can be transmitted to one or more than one pager, so as to tailor its response or operating characteristics to suit those of individual users or service providexs.
4. Meanings of buttons or keys which constitute the users means of operating the pager can have thei.r function altered, and the new meaning illustrated or indicated by the use of images presented on a dot matrix or other form or :
, 2~39~
programmable display, in close proximity to the control button.
5. A holster designed to carry the pager has an integral clip for attachment to the wearer's apparel, in which is installed a vibrator. A
detection means is included so that the alerting means, being audible, optical or vibrational can be automatically changed according to th~ users programmed preference when in or out of the holster.
6. A means for detecting the rate oP
change of the battery terminal voltage or internal resistance to provide for accurate low battery detection can be provided ~or either alkaline or rechargeable batteries.
An "intelligent" automatic frequency control (AFC) system can be provided in which the discriminator output level is integrated for a specific period, starting a fixed period after a logical transition. If data remains good (iOe. the state i5 retained for a minimum data period) the integrated voltage is stored and compared with a similar sample taken for the other logical state.
The AFC signal is generated, proportional to the difference between these two samples, and the correction signal applied t~ a varactor in the local oscillator circuit, to control the frequency.
A "Script" method for controlling the pager response, comprised of a special escape sequence (e.g. a non-printable character) followed by a short form "language" to determine pager actions, can be used.
Messages are sent via a computer to one or more pocket pager devices. The pager simply acquires the message without response and displays it on request.
Alternatively the unit can be used with or as a scheduler, which can be dynamically loaded .
,:
~399L2~
with new information by a secretary or dispatcher.
This information be conveyed building, nation or continent wide depending upon thP extent of the paging system accessed by the secretary. Preferably the pager is in the form of a small billfold (e.g. is credit card sized), and is generally used to forward messages to the user, at the same level of urgency as for telephone answering slips. A user could permit a limited number of persons to know the sequence whereby the device ~ould be made to beep.
In accordance with an embodiment of the invention a radio receiver is comprised of apparatus for receiving a radio signal first apparatus for beating the signal to zero intermediate frequency in phase and quadrature shifted signals~ apparatus for amplifying the in phase and quadrature shifted zero intermediate frequency signals, second apparatus for beating the amplified intermediate frequency signals to predetermined non-zero intermediate freguency in phase and quadrature shifted signals, apparatus for summing said non-zero signals, and apparatus for applying the summed signal to a discriminator to obtain an output signal.
In accordance with another embodiment of the invention, a radio receiver is comprised of apparatus for receiving and bandpass filtering a radio signal of predetermined frequency, a first local oscillator for generating a local oscillator signal having a ~requency which is the same as the radio signal, apparatus for phase shifting the local oscillator signal by 90, a first mixer for receiving the radio signal and the local oscillator signal and for providing a first in phase zero intermediate frequency signal, a second mixer for receiving the radio signal. and the phase shifted local oscillator signal and for providing a second quadrature shifted zero intermediate frequency signal~ low pass filter 2~
apparatus for filtering the intermediate frequency signals, a second local oscillator for yeneratinq a predetermined frequency local oscillator signal, apparatus for phase shifting the predetermined frequency local oscillator signal by 90 to provide a non-zero phase shi~ted local oscillator signal, a third mixer for receiving the in phase zero intermediat~ frequency signal and the predetermined frequency local oscillator signal and for generating a non-zero intermediate frequency signal, a fourth mixer for receiving the quadrature shifted zero intermediate frequency signal and the non-zero phase shifted local oscillator signal and for generating a non-zero quadrature shifted intermediate frequency signal, apparatus for summing the non-zero intermediate frequency signal and the non-zero quadrature shifted intermediate frequency signal, to form a summed non-zero intermediate frequency signal, and apparatus for discriminating the summed signal to provide an output signal.
In accordance with another embodiment o~
the invention, a superheterodyne F.M. radio receiver is comprised of a first local oscillator which includes a varactor for adjusting its frequency, a discriminator, and an automatic frequency control (AFC) circuit for generating an AFC signal, the AFC
circuit comprising a first counter/regisker for storing the AFC signal as a digital signal, a digital to analog converter (DAC) for receiving an output of said counter/register, and apparatus for applying the~
output signal of the DAC to the varactor, whereby the AFC signal stored in the counter/register controls frequency adjustment of the first local oscillator.
In accordance with another embodiment of the invention, a radio page signal receiver is in combination with a belt clip with a vibrator alert apparatus fixed to the belt clip for applying 8 ~ 3~ 7 vibration against the body of a wearer upon receipt of an alerting signal, and optionally a battery for powering ths vibrator alert apparatus retained by the belt clip, apparatus in the belt clip for removably S retaining the removable radio receiver, and apparatus for coupling a vibrator alert enable signal from the receiver to the vibrator alert apparatus upon the receiver being retained in said belt clip.
In accordance with another embodiment of the invention, a page signal receiver is comprised of a battery, low and high load pPripherals connected to the receiver, apparatus for operating a high load peripheral, a low battery ressrve detector, and apparatus for substituting a low load peripheral for a high load peripheral upon detection of low battery reserve.
In accordance with anotAer embodiment of the invention, ~ radio page receiver is comprised of apparatus for receiving high and low priority messages from a transmitter, apparatus for alerting and displaying the high priority messages, and apparatus for storing the low priority messages and for being enabled to display the low priority messages on demand by a user.
In accordance with another embodiment of the invention, a low battery detection circuit for electronic apparatus is comprised of a voltage comparator for sampling battery terminal voltage respectively under ].ight and heavy loading, and for indicating a low battexy condition when the rate of change of the sampled voltage or internal resistance is greater than a predetermined limit~
In accordance with another embodiment of the invention, a radio pager is comprised of apparatus for receiving a transmitted signal from a transmitter, apparatus for extracting a command signal and a message signal from the transmitted ~3~
signal, and apparatus for operating the receiver in response to the command to control how the message signal is handled.
In accordance with another embodiment of the invention, a paging receiver includes apparatus ~or recognizing time slot bits in each of a plurality of time frames, and powering on in one of the time slots upon the detection of one of said time slot bits.
BRIEF INTRODUCTION TO THE DRAWINGS:
A better understanding of the invention will be obtained by reference to the detail~d description below, in conjunction with the following drawings, in which:
Figure 1 is a block schematic of a the intermediate frequency stages of a radio receiver according to an embodiment of the inventivn, FigurP 2 is a block schematic of a radio receiver particularly oP the AFC loop, Figures 3, 4 and 5 are diagrams illustrating the structure of signals used in embodiments of the invention, Figure 6 is a graph illustrating lifetime characteristics o~ alkaline and NiCd batteries, and Figure 7 is a block diagram of a low battery detection system.
DESCRIPTION OF THE PREFERRED EMBODIMEN?So The new receiver, shown in Figure 1, is a double superheterodyne. A xeceived off-air siynal from antenna 1 passes through a first bandpass filter 2, an amplifier 3 and a second bandpass filter 4, as in the prior art. The signal is then applied to two mixers 5 and 6. A local oscillator 7 is tuned exactly to the desired signal frequency, the output signal of which is mixed in mixer 5 with the off-air signal. The local oscillator output signal is also mixed with the off-air signal in mixer 2 after being ~)3~27 phase shifted by 90 in phase shifter 8. The result at the output of mixer 5 is one of the resultant signals, which is the de~ired signal mixed down to a base band signal centered at 0 Hz. The negatiYe S frequency components are preserved in the quadrature channel, at the output of mixer 6.
The output signals of m:ixers 5 and 6 are filtared with simple R-C gyrator or active filter elements g and 10, which pass the low frequency desired signalO Aft~r being amplified in amplifiers 11 and 12, the signals in the two channels are applied respectively to mixers 13 and 14. A local oscillator 15 of preferably 455 kHz has its signal applied to mixer 13 and its signal applied to mixer 14 through 90~ phase shifter 16. This up converts the signals in the two channels from zero intermediate frequency to 455 kHz. The output signals from the mixers 13 and 14 in the two channels are summed in adder 17, then pass band filtexed in filter 18 using conventional components such as ceramic or L-C filters. The output of filter 18 is a frequency modulated signal containing the same information as the received signal but with a carrier frequency equal to the second local o~cillator frequency, 455 kKz.
The up-converted signal at the output of filter 18 is amplified to a square wave in a limiting amplifier 19, and the square wave signal is then applied to a frequency discriminator 20. The modulating signal is extracted from the modulated carrier by continuous comparison of the frequencies of the local oscillator (455 kHz) and the modulated signal in the frequency discriminator.
The resuLting output signal is passed through filter 21 for application to circuits which use the modulating signal.
2~3~
The function of the receiver is described mathematically below.
Let the received signal xc(t) be represented by xc(t) = A~ Cos (Wct-~(t)) where Ac is the carrier amplitude Wc is the carrier radian frequency ~(t) is the time varying phase containing the modulating signal.
Let the 1st local oscillator signal Aoi(t) be:
Aoi(t)=Ao Cos~WOt) Let the quadrature LO signal Aoq(t) be:
Aoq(t)=Ao Sin(Wot) At the output of mixer Ml the signal is:
AcCS(Wc+~(t)), Aoicos(wot) 1~ After filtering this becomes AoiAC Cos ((Wc-Wo)t+~(t)) Similarly, output signal from mixer M2, after filtering is AoiAc sin ((Wc-Wo)t+~(t)) Let the 2nd LO signal xki(t) be Aki(t)=Ak C09(Wkt) and its quadrature signal be A~q(t)=Ak Sin(Wkt) At the mixer M3 output the signal is AoAc Cos((Wc-WO)t+~(t)).AkCes(Wkt) = AoAcAc(1 Cos~(wc-wo-wk)-~(t))+lcos(~c-wo-~k)t+~(t)) Similarly, the output signal at mixer M4 O/P i5 given by:
AoACAk(l Cos((wc-wo-wk)t~(t))-lco5 (WC-WO-W~) t+~(t)) By differencing the output of mixers M3, M4 vO = AoACAk Cos((wc-wo-wk)t+~(t)) ' ` ', ~3~
This signal is the same as ths input signal but with the carrier ~r~uency shifted by the amount ~Wo~Wc If WO=WC then the output is exactly s centered at Wk.
In the above analysis phases of signals have been taken as arbitrary and therefore ignored.
Advantages of the receiver are as follows:
l. Because the first IF is zero the receiver does not have an image frequency.
2. Near and adjacent channel signal rejection filtering is largely achieved in the 455 KHz section filter and the requirements for ~iltering in the zero IoF~ section are much reduced over those required in a single stage zero I.F. receiver.
Further, low cost, highly miniature 455 KHz filter elements, widely used in conventional superheterodyne receivers, can be used.
3. This receiver, unlike conventional single stage zero I.F. receivers will reproduce analog frequency modulated signals, an essential requirement for voice or fast digital signals.
4. The frequency errors introduced by the second I.F. conversion are eliminated hecause discrimination is achieved by frequency comparisor1 of the received F~ signal with the second local oscillator signal.
This makes the architecture inherently better suited for use in a synthesized first local oscillator receiver since, unlike conventional superheterodyne receivers, there is no frequency error contribution from the second I.F'. stage.
A novel type o~ automatic frequency control (AFC) has been designed which solves the problems referred to earlier in this specification.
It should be noted that the AFC embodiment described ;
below can be used with the zero I . F. superheterodyne embodiment described above, or with a conventional superheterodyne circuit~
With re~erence to Figure ~, certain S elements of a conventional radio are an antenna 50 which feeds off air input signal to an RF amplifier 51, the output of which is applied to a mixer 52. A
varactor controlled crystal oscillator 53 provides a local oscillator signal to mixer 52. The output signal at an intermediate frequency passes through an IF band pass filter 54, the output of which is applied to the input o~ a second mixer 55. A second crystal controlled oscillator 56 provides a local oscillator ~ignal to mixer 55. The output signal of mixer 55 at a second IF frequency is applied to discriminatQr 57.
An analog voltage output of discriminator 57 is applied with a discriminator reference signal to the input of a voltage controlled oscillator 58.
The analog voltage derived ~rom the discriminator circuit indicates the instantaneous RF input deviation by the voltage differential between the analog discriminator output voltage and the ref rence voltage.
The output signal of the voltage controlled oscillator provides an output clock signal, the fre~uency of which is proportional to the absolute differential voltage at its input. Thus the voltage controlled oscillator 58 provides a rectifyillg action.
The discriminator output signal and the reference are also applied to the input of a comparator circuit 59, the output o~ which indicates the polarity of the deviation of the RF input relative to the locally defined channel center.
The resulting polarity signal output from comparator 59 is applied to a transition detection ~3~
circuit 60, which generates an output pulse at each transition of the polarity signal, the period of which is less than a bit. The output pulse is a sampling signal and, because it i5 generated by s transitions, an exactly equal number of l's and o s in the RF input are sampled.
Transition detection logic circuit 60 also stores the direction of the last transition in a latch, the state of which is maintained during receiver power down periods. Thus the alternating sampling continues uninterrupted by power down periods.
After a short delay to accommodate the RF
data transitionl the sampling pulse enables an up/down counter 61, the direction of the count being controlled by the polarity signal.
In each sample period, the counter 61 accumulates a number of counts proportional to the frequency differential as determined by the discriminator since the input of the counter is connected to the output of the voltage controlled oscillator 58. If the O's and l's are balanced (i.e.
the radio is centered on a channel), the counter contents will oscillate about the initial value.
However if the radio is unbalanced, the counter will accumulate a larger count for one state and the counter will overflow or underflow at a rate determined by the imbalance and the size of the counter.
The high N bits o~ the counter 61 are continuously loaded into a DAC counter/registe.r 62.
The output of the DAC counter is input to a digital to analog inverter 63. The output of DAC 63 is an analog signal which is applied to the varactor of the first local oscillator 53.
Thus a quanti2ed feedback loop is created. Provided the polarity of the loop is 1~ ~
2~3~ '7 negative, and provided other well known loop stability criteria are satisfied, a feedback loop is created which can store the feedback signal indefinitely, and which can operate uninterrupted S over many strobed periods.
The feedback loop is digital and stores the values corresponding to the ~FC fesdback signal as a binary value in the counter/register 62. The output of the DAC, applied to the varactor in the first local oscillator circuit, provides means for frequency adjustment of the first local oscillator by the binary value stored in the register. Provided power is maintained to the register, the feedback signal can be preser~ed indefinitely and without degradation. In a pre~erred embodiment, the register is formed of ~MOS transistors with negligible standby pvwer consumption and the DAC is powered up and down at the same time as the radio.
A second mode of operation can be as follows. The high order N bits of the accumulator are not imposed on the N bits o~ the DAC counter.
Instead, the existence of an underflow or an overflow of the accumulator is stored in an overflow/underflow detect circuit 64. At the end o~ the radio enable time, the DAC counter is "nudgedl' to count one bit in khe direction of the over~low/underflow or is left unchanged. The bene~it of this i5 that no AFC
adjustment is made while the radio is operational.
To prevent "dickering" of the contents of the bits applied to the DAC, hysteresis is built into the counter at a bit position 61A defined by the desired loop characteristics. The nature of the hysteresis is such that, aeter a transition at the defined counter bit (in the counter chain), two count inputs to that bit in the opposite direction are necessary to cause a reversal. For example, if the bit counted up to a "1", then two down count pulses ~3~2~
are necessary to cause the bit to downcount to "O".
The effect of this is to provide hysteresis, the magnitude of which is equal ko the modulus to the section of the counter below the d~fined hysteresis s bit position.
A noise detector 65 is also preferred to be used to monitor the data signal from the radio discriminator and, in the event that noise is detected, indicating that the AFC is unreliable, the AFC circuit disabled.
The AFC control system described above may also be used to provide an offset to adjust either for manu~acturing tolerances or, if a means of temperature sensing is available to the control processor, for approximate temperature compensation for the combined crystal and crystal oscillator temperature coefficients.
The followiny describes an Embodied Command Language that can be used to provide digital ~0 radio paging systems and receivers with enhanced control o~ the decoding and interpretation o~ message information sent to a receiving device~
The embedded command language instructions are encoded into the message being sent to the receiving device. The structure of the embodied command language will not interfere with the normal operation of a radio paging system and does not require any change to the structure of the radio paging system control equipment ox data input devices.
The described embedded command language features are based on the use of the POCSAG digital paging protocol as de~ined in the CCIR Recommendation 584-1 (or Radio Paging Code. No. 1 "RPCl".
Standard radio paging systems provide for the delivery of messages to remote receivers. these messages are initiated by suitable input devices:
17 23D3~2'~
(a) Touch Tone telephones can yenerate numeric information such as telephone numbers or coded messages using digits only.
(b) Computerized device~ (Page Entry Terminals "PET" or terminal devices connected directly to the paging terminal~ can generate complete alphanumeri~ messa~es.
A major factor in the economic benefits from operating a paging/messaging sy,stem is being able to provide a wide range of information with the smallest amount of data sent over the system/network.
The use of embedded command language instructions enable the use of standard message formats contained within the receiving device which can be completed with message information sent to the receiving device.
Figure 3 shows the structure of the POCSAG transmission protocol, in which:
Batch represents one complete POCSAG protocol cycl~;
Preamble i5 a synchronizing sequence of data reversals;
SCW is a unique 32 bit data s~quence after which follows eight individual data frames F0 through F7;
CW0-CW1 each frame ~0-F7 consists of two code words (shown in Figure 4);
MSG represents a single information bit that defines how the following 20 bits of information are to be used, either as address or data information;
Access/Data This 20 field represents either 20 bits of lB address bits and 2 function bits.
The two function bits FNI FN2 identify four possible types of paging service (see Table 1) 18 2~ii3~39~
FN1 FN2 Service_Function 0 0 Numeric messages 0 1 No message~ ~tone~
1 0 No messages ~tonej 1 1 Alphanumeric messages Table 1 Function Bit Assignments If this code word represents a message code word the 20 bits of data can be formatted in two ways.
(a) As numeric information only and coded as shown in Table 2 which is based on Binary Coded Decimal (BCD).
4~bit Combination Displayed Character Bit No. 4 3 2 1 O O O O O
~ 0 1 0 2 ~ 0 ~ 1 9 1 0 1 0 Spare 1 1 0 0 Space 1 1 0 1 Hyphen 1 1 1 0] close bracket 1 1 1 1~ open bracket Table 2 ~ Numeric only character set (b) As alphanumeric information coded in seven bit code based on the CCITT
Alphabet No. 5 (ASC11) Based on coding ~ormats shown in (a) and (b~ above the system can send up to 5 numeric characters or 2-6/7 alphanumeric characters in each data code word.
Checkbits This 10 bit data ~ield is used in the error detection and correction process of the POCSAG protocol.
PAR represents a single parity bit used in the error detection process.
The embodied command language tECL) provides a means to transmit, to a receiving device, messages containing encoded instructions within the normal protocol of the messages. When decoded, these instructions specify the way in. which the information, contained in the message, is handled by the receiving device. These instructions are in a format that will allow future, virtually unlimited extensions of the embodied command language, and yet remain fully compliant with current protocols for messaging. The format conforms with the POCSAG code word structure shown in Figure 4.
Receiving devices with this capability may be programmed to respond to address and messages (normal operation), and by virtue of the ECL, address specific commands, and system wide or group specific commands. Multi-recipient codes (addresses) are referred to as broadcast address codes (BAC~s)o the paging network will reserve at least 8 unique BAC's, one corresponding to each of the POCSAG time slots (F0-F7 shown in Figure 3~.
Figure 5 ~hows an embedded command 2S language instruction containQd within a typical POCSAG message, in which:
ADDRESS CODE WORD: is the standard POCSAG
code word representing the receiving device address.
HEADER CODE WORD: is a special cade word struct.ured to alert the receiviny device that this code word may contain embodied command language instructions.
INSTRUCTION CODE WORD: additional (unlimited) operational message code words whi.ch provide 20 binary bits that may be used for further instructions or data or gating keys.
~3~
MESSAGE CODE WORDS: message code words which may be standard numeric or alphanumPric or which may be interpreted by the receiving device in the manner defined by the embedded commands received S in the previous message code words.
The ECL is coded by the sending device (e.g. PET) in binary and structured to conform with the POCSAG data code word format. ~y this method and ECL instruction/s can be sent ~y the paging network to either numeric or alphanumeric receiving devices.
With reference to Figure 3, 20 bits of data contained in the first data code word (CWO or CW1) following the address code word of the receiving device, is called the ECL header code word. the 5 header code word contain~ the following elements;
(i) Embodied Command Language Key (ii3 Embodied Command Language Instructions These elements of the ECL header code word are extracted from the header code word as follows:
Each receiving device contains a command key mask (CKM) which is logically ANDed with the header code word in each correctly addressed message.
The resultant 2Q bit binary value (MRES) is compared with the command key code word (CKCW). If the comparison is true, the CKM is complimented and then ANDed with the header code word. The rasulting digital word embodied command language instruction (ECLl), the length of which is determined by the command key format, is used to provide instructions and or parameters, as may be defined by the network operator. It is allowable for the receiver to have more than one CKM and/or CKCW. (see Table 3 for one example).
21 ~39~
Header Code word 1 1 0 1 0 1 0 0 1 1 0 0 0 1 1 1 0 1 1 0 Mask (CKM) 0 0 0 0 1 1 1 ~ 1 0 0 0 1 1 1 0 0 0 0 0 Result (MRES) 0 0 0 0 0 1 0 0 1 0 0 0 0 1 1 0 0 0 0 0 Compliment Instruction (ECL) 1 1 0 1 0 0 0 0 0 1 0 0 0 0 0 1 0 1 1 0 Table 3 The format and function of the MRES word may be system operator defined. It could, for example, be used to provide immediate instruction or alternatively could be logically operated upon using a code pri~ate to the receiver (such as the serial number) to provide more secure access to some or all of the features.
The MRES word is assembled from the command language header by setting command language key bits to a known state so that the variable bits are those in the balance of the header. Note that if the service provider chooses to use the enkire 20 bit code space of the command language header of the command language key, there will be no com~and message word, since all bits are defined.
Interpretation of the command message word is not defined but it is envisaged that control o-f the receiver by off air commands will fall into three categories;
1. Class 1 Commands Instructions within this category temporarily alter the behaviour of the receiver, most probably for the specific message attached. This could include beeper overrides, display timeouts, etc.
An important instruction could be to add another address to the receiver's current addresses 22 ~3~2'7 to allow multiple receivers to be updated with specific information, after which the new address would be discarded.
Another important instruction could be to S use the combination of a subsequent ~essage code word combined with a receiver private code word (such as the serial number) to decode a message which is encrypted.
Another important instruction could be to store the subsequent message data in specific areas of memory to provide for updating of one data base in a receiver containing several data bases.
Another instruction could be to combine the subsequent message data with one of a number of "forms" stored within the receiver.
Another important instruction could be to substitute data stored within the receiver in place of the transmitted command(s) and data contained with the embodied command language instruction, for the purpose o~ data compression.
2. Class 2 Commands This instruction group commands the receiving device to modi~y its internal parameters and preferably requires confirmation from the user.
These commands include changing the default operational settings of the receiving device as well as providing updates to certain information.
3. Class 3 Comman~s Commands of this class are preferably limited to those which radically change the behaviour of the receiving device such as baud rate or permanent addresses, and require the user to confirm the integrity of the received message using encoded character sequences sent to the receiving device, which can be used by the service provider to confirm receipt of the command. The service provider can ' then send a further co~mand to the receiving device which then verifies and enables the previous command.
Extended POCSAG fgr enhanced battery savinq As noted above, in order to provide a paging receiver with reasonable operating performance for extended periods from internal battery supplies~
a power saving mechanism is used. The POCSAG
protocol allows each receiver to remain in an idle (powered down) state with a 14/17 du~y cycle. During each power up period the receiver must search for a preamble or other recognizable POCSAG ~ormat. The basic POCSAG data format consists of eight groups o~
two code words. These group~ correspond to individual time slots (Frames F0-F7). Once the receiving device has attained batch synchronization, by correctly detecting the unique sync code word (SCW
Figure 3) it now only needs to listen to data in the time slot (F0-F7) that may contain its own address.
Predict_ve Address Slot Wake-Up Inhibit The pagers have a capability to l'sleep"
on command (iOe. go to low power mode) for a dynamically controlled period of time. The command take the form of a special address that a~fects all pagers preprogrammed to so respond with a time slot address corresponding to the frame in which the command is transmitted. The sleep period should be integral numbers of batches (typically 4-32 seconds, approx.) as determined by the contents of a message word in the second code word of the time frame. In the absence of a sleep command, the pagers should operate in the standard POCSAG format.
By slightly increasing call latency, the paging terminal accumulates a "Que" of pending payes.
Groups of batches are assembled and "packed" so as to both make optimum use of the air time and such that some of the time slot addresses may be deactivated because no page~ are containe~ in the group for those ~3~a~2'7 pagers. Deactivation messages are pre~erably included with the batch.
In non-busy systems, pagexs pre~erably should sleep for some arbitrarily high fraction of S time ~for a 16 second sleep time this should be 15/16)~ By re-allocation of addresses, pagers with a 24 hour pattern of use are pre~erably put on a frequently used time slot, and others put into a low duty cycle mode.
Non-compatible pagers should not respond to the special address and thus would not be affected. Similarly, compatible pagers missing the sleep command because of errors, or out-of-range conditions or a non-compatible system, default to the POCSAG standard sampling rate. This system may therefore be considered to be a transparent overlay to a standard POCSAG system.
Electronic On/Off In the past, paging receivers had ON/OFF
switches which entirely removed the battery power from the internal electronics within the pager. With the development of very low power logic, it has become possible to develop pagers in which the internal logic is switched to a very low current state. Thus, previously received messages can be retained in memory and real time clocks (used to time stamp incoming messages) can continue to operate in the OFF state. Some pagers also have the capability to automatically turn ON and OFF at preset times.
A separate issue is the growing requirement to send large amounts of data over paging systems. The loading of such systems is such that demand is high in peak business hours and light at other times. Radio common carriers have an obvious incentive to offer data services but generally do not have the system capacity to provide this at peak traffic periods. Depending on the urgency o~ the ~:3399~2'7 data, it would be desirable to transmit most of this data during off peak times (such as overnight). the electrsnic ON/OFF system of this invention has the above capabilities and also has the ability to resume S normal operation at preset times to provide for data base transmissions.
Data Reception W le OFF
(a) In the OFF state, the paging receiver has an internal crystal controlled clock which continues t~ operate, and a memory which i~
maintained.
(b) In response to instructions received off-air from the paging system using the script command language described elsewhere herein, the pager can be instructed to "listenl' to the channe:L at a specific time for a specific period, even if switched OFF by the user.
(c) Because of the high accuracy of the crystal clock and the fact that its accuracy i5 maintained by repeated broadcast updates from the paging system, the wake up while off periods can be short, and thus the additional power drain negligibls.
(d) Data within a single data base might be separated into various priority classes. Non urgent (low priority) data is sent of~ peak (or opportunistically), while urgent updates are sent with normal message priority. This would apply to private (insurance tariffs or real estate listings~
and public (news and stock quotes, etc.~ data base services.
he ~'Vibra-c~
An alerting vibrator is very useful in noisy envirvnments or in situations when alerts must be silent, but the alert is only reliahle when the pager is mechanically fixed against the body, æuch as on a belt.
f~;~33~ '7 We therefore take advantaga of this situation by mounting the vibrator and its associated battery in a detachable belt clip into which the pager can be held. This has two principal advantages: first, the radio pager battery is removable from the belt clip and therefore separate from the vibrator battery so that the vibrator load does not cause premature battery failure, and sacond that the pager battery can be very much smaller (such as button cells~, and battery lifetime extended.
Operation of the vibrator is txiggered by a signa:L
wi.thin the pager and is coupled to the holster by either an optical signal or a metallic contactO The pager can be operated removed from the belt clip without operating the vibrator.
Intelli~ent Low Battery Detection-.
With battery operated equipment, is desirable to be able to detect and signal to the user when the battery is approaching the end of its useful life, or in the case of a rechargeable battery, that recharging i5 necessary. Ideally, this should be done at the point in the battery discharge when at least 1-2 days o~ operation remain, so as to give the user a reasonable chance to replace or recharge the battery.
The commonly used technique to detect low battery is comparison of the terminal voltage of the battery under a specific load to a reference/ and if the terminal voltage is less, low battery is flagged.
This technique works well for a specific battery type because the battery terminal voltage with discharge is highly predictable.
However, alkaline batteries are commonly used interchangeable with rechargeable NiCd batteries and these batteries have different discharge characteristics (see Figure 6). A voltage threshold detection apparatus properly set up for an Alkaline ~)3~2~
battery would not detect low battery soon enough for NiCd batteries and vice versa.
In portable radio equipment particularly, a variety of loads are applied to the battery in normal use. The control logic and radio receiver are relatively light loads, while enunciation transducers (such as vibrator motors) are relatively heavy loads.
A near-exhausted battery usually has su~ficient capacity to continue to operate the receiver but application of a heavy load can reduce the terminal voltage to the point that a system reset is generated.
The low battery detection inventio~ makes use of a microprocessor (or microcontroller) which has an analog to digital converter, optionally combined with a conventional low battery detection system.
With reference to Figure 7, the reference voltage of comparator 75 is set to be equal to that appropriate for the lowest battery detection voltage for any battery 74 that might be used.
Microprocessor 77 monitors the output from the voltage threshold comparator 75 and in addition, measures with A/D converter 76, the battery terminal voltage under a very liyht load 78 and under a defined, higher load 78. The sampling interval ~.g.
represented by means for sampling switch 79) in the preferred embodiment is lmS.
(a) If the comparator is switched (i.e.
low battery is detected) the equipment will signal low battery to the user, regardless of other considerations.
(b) The terminal voltage samples taken by the microprocessor are processed to calculate the internal battery resistance and its derivative (i.e.
rate of change) over a period o~ hours. If either of the terminal resistance or its derivative exceed , 2~3~ 7 preprogrammed limits, low battery is signalled to the user.
(c) ~erminal voltage and internal resistance for most battery types is a function of S temperature. Allowance for temperature effects is included by virtue of the chosen lim:its.
(d) There is no attempt to introduce temperature compensation because batteries truly have limited lifetimes at temperature extremes, even if useful life would remain at a different temperature.
(e3 As a battery becomes discharged it may not be capable of continued operation under the heaviest of loads. Thus if the voltage threshold comparator is tripped under heavy load (such as a vibrator), the load can be removed and a lower current form of enunciation used such as beeper.
This would be a change of function from the user's viewpoint and would be accompanied by a message on the display indicating low battery.
(f) To eliminats confusing signalling due to recovery in the battery, the low current capability is latched and the latch reset by a system reset, or a measured terminal voltage greater than a preset threshold. This would allow the battery to recover from low temperature caused low battery condition.
(g) High load elimination may also be initiated if a measured light load terminal voltage is less than a pre-determined threshold.
(h) All the above apply to newer types of battery likely to he introduced over the next 2-5 years, such as nickel hydride rechargeable ba~teries, etc.
The activation of the programmed auto ON/OFF function is in addition to the normal function of the ON/OFF control to disable the receiving device.
3~2~
A person understanding this invention may now conceive of alternative structures and embodiments or variations of the above. All of these which fall within the scope of the claims appended S hereto are considered to be part of the present invention.
.
,
This makes the architecture inherently better suited for use in a synthesized first local oscillator receiver since, unlike conventional superheterodyne receivers, there is no frequency error contribution from the second I.F'. stage.
A novel type o~ automatic frequency control (AFC) has been designed which solves the problems referred to earlier in this specification.
It should be noted that the AFC embodiment described ;
below can be used with the zero I . F. superheterodyne embodiment described above, or with a conventional superheterodyne circuit~
With re~erence to Figure ~, certain S elements of a conventional radio are an antenna 50 which feeds off air input signal to an RF amplifier 51, the output of which is applied to a mixer 52. A
varactor controlled crystal oscillator 53 provides a local oscillator signal to mixer 52. The output signal at an intermediate frequency passes through an IF band pass filter 54, the output of which is applied to the input o~ a second mixer 55. A second crystal controlled oscillator 56 provides a local oscillator ~ignal to mixer 55. The output signal of mixer 55 at a second IF frequency is applied to discriminatQr 57.
An analog voltage output of discriminator 57 is applied with a discriminator reference signal to the input of a voltage controlled oscillator 58.
The analog voltage derived ~rom the discriminator circuit indicates the instantaneous RF input deviation by the voltage differential between the analog discriminator output voltage and the ref rence voltage.
The output signal of the voltage controlled oscillator provides an output clock signal, the fre~uency of which is proportional to the absolute differential voltage at its input. Thus the voltage controlled oscillator 58 provides a rectifyillg action.
The discriminator output signal and the reference are also applied to the input of a comparator circuit 59, the output o~ which indicates the polarity of the deviation of the RF input relative to the locally defined channel center.
The resulting polarity signal output from comparator 59 is applied to a transition detection ~3~
circuit 60, which generates an output pulse at each transition of the polarity signal, the period of which is less than a bit. The output pulse is a sampling signal and, because it i5 generated by s transitions, an exactly equal number of l's and o s in the RF input are sampled.
Transition detection logic circuit 60 also stores the direction of the last transition in a latch, the state of which is maintained during receiver power down periods. Thus the alternating sampling continues uninterrupted by power down periods.
After a short delay to accommodate the RF
data transitionl the sampling pulse enables an up/down counter 61, the direction of the count being controlled by the polarity signal.
In each sample period, the counter 61 accumulates a number of counts proportional to the frequency differential as determined by the discriminator since the input of the counter is connected to the output of the voltage controlled oscillator 58. If the O's and l's are balanced (i.e.
the radio is centered on a channel), the counter contents will oscillate about the initial value.
However if the radio is unbalanced, the counter will accumulate a larger count for one state and the counter will overflow or underflow at a rate determined by the imbalance and the size of the counter.
The high N bits o~ the counter 61 are continuously loaded into a DAC counter/registe.r 62.
The output of the DAC counter is input to a digital to analog inverter 63. The output of DAC 63 is an analog signal which is applied to the varactor of the first local oscillator 53.
Thus a quanti2ed feedback loop is created. Provided the polarity of the loop is 1~ ~
2~3~ '7 negative, and provided other well known loop stability criteria are satisfied, a feedback loop is created which can store the feedback signal indefinitely, and which can operate uninterrupted S over many strobed periods.
The feedback loop is digital and stores the values corresponding to the ~FC fesdback signal as a binary value in the counter/register 62. The output of the DAC, applied to the varactor in the first local oscillator circuit, provides means for frequency adjustment of the first local oscillator by the binary value stored in the register. Provided power is maintained to the register, the feedback signal can be preser~ed indefinitely and without degradation. In a pre~erred embodiment, the register is formed of ~MOS transistors with negligible standby pvwer consumption and the DAC is powered up and down at the same time as the radio.
A second mode of operation can be as follows. The high order N bits of the accumulator are not imposed on the N bits o~ the DAC counter.
Instead, the existence of an underflow or an overflow of the accumulator is stored in an overflow/underflow detect circuit 64. At the end o~ the radio enable time, the DAC counter is "nudgedl' to count one bit in khe direction of the over~low/underflow or is left unchanged. The bene~it of this i5 that no AFC
adjustment is made while the radio is operational.
To prevent "dickering" of the contents of the bits applied to the DAC, hysteresis is built into the counter at a bit position 61A defined by the desired loop characteristics. The nature of the hysteresis is such that, aeter a transition at the defined counter bit (in the counter chain), two count inputs to that bit in the opposite direction are necessary to cause a reversal. For example, if the bit counted up to a "1", then two down count pulses ~3~2~
are necessary to cause the bit to downcount to "O".
The effect of this is to provide hysteresis, the magnitude of which is equal ko the modulus to the section of the counter below the d~fined hysteresis s bit position.
A noise detector 65 is also preferred to be used to monitor the data signal from the radio discriminator and, in the event that noise is detected, indicating that the AFC is unreliable, the AFC circuit disabled.
The AFC control system described above may also be used to provide an offset to adjust either for manu~acturing tolerances or, if a means of temperature sensing is available to the control processor, for approximate temperature compensation for the combined crystal and crystal oscillator temperature coefficients.
The followiny describes an Embodied Command Language that can be used to provide digital ~0 radio paging systems and receivers with enhanced control o~ the decoding and interpretation o~ message information sent to a receiving device~
The embedded command language instructions are encoded into the message being sent to the receiving device. The structure of the embodied command language will not interfere with the normal operation of a radio paging system and does not require any change to the structure of the radio paging system control equipment ox data input devices.
The described embedded command language features are based on the use of the POCSAG digital paging protocol as de~ined in the CCIR Recommendation 584-1 (or Radio Paging Code. No. 1 "RPCl".
Standard radio paging systems provide for the delivery of messages to remote receivers. these messages are initiated by suitable input devices:
17 23D3~2'~
(a) Touch Tone telephones can yenerate numeric information such as telephone numbers or coded messages using digits only.
(b) Computerized device~ (Page Entry Terminals "PET" or terminal devices connected directly to the paging terminal~ can generate complete alphanumeri~ messa~es.
A major factor in the economic benefits from operating a paging/messaging sy,stem is being able to provide a wide range of information with the smallest amount of data sent over the system/network.
The use of embedded command language instructions enable the use of standard message formats contained within the receiving device which can be completed with message information sent to the receiving device.
Figure 3 shows the structure of the POCSAG transmission protocol, in which:
Batch represents one complete POCSAG protocol cycl~;
Preamble i5 a synchronizing sequence of data reversals;
SCW is a unique 32 bit data s~quence after which follows eight individual data frames F0 through F7;
CW0-CW1 each frame ~0-F7 consists of two code words (shown in Figure 4);
MSG represents a single information bit that defines how the following 20 bits of information are to be used, either as address or data information;
Access/Data This 20 field represents either 20 bits of lB address bits and 2 function bits.
The two function bits FNI FN2 identify four possible types of paging service (see Table 1) 18 2~ii3~39~
FN1 FN2 Service_Function 0 0 Numeric messages 0 1 No message~ ~tone~
1 0 No messages ~tonej 1 1 Alphanumeric messages Table 1 Function Bit Assignments If this code word represents a message code word the 20 bits of data can be formatted in two ways.
(a) As numeric information only and coded as shown in Table 2 which is based on Binary Coded Decimal (BCD).
4~bit Combination Displayed Character Bit No. 4 3 2 1 O O O O O
~ 0 1 0 2 ~ 0 ~ 1 9 1 0 1 0 Spare 1 1 0 0 Space 1 1 0 1 Hyphen 1 1 1 0] close bracket 1 1 1 1~ open bracket Table 2 ~ Numeric only character set (b) As alphanumeric information coded in seven bit code based on the CCITT
Alphabet No. 5 (ASC11) Based on coding ~ormats shown in (a) and (b~ above the system can send up to 5 numeric characters or 2-6/7 alphanumeric characters in each data code word.
Checkbits This 10 bit data ~ield is used in the error detection and correction process of the POCSAG protocol.
PAR represents a single parity bit used in the error detection process.
The embodied command language tECL) provides a means to transmit, to a receiving device, messages containing encoded instructions within the normal protocol of the messages. When decoded, these instructions specify the way in. which the information, contained in the message, is handled by the receiving device. These instructions are in a format that will allow future, virtually unlimited extensions of the embodied command language, and yet remain fully compliant with current protocols for messaging. The format conforms with the POCSAG code word structure shown in Figure 4.
Receiving devices with this capability may be programmed to respond to address and messages (normal operation), and by virtue of the ECL, address specific commands, and system wide or group specific commands. Multi-recipient codes (addresses) are referred to as broadcast address codes (BAC~s)o the paging network will reserve at least 8 unique BAC's, one corresponding to each of the POCSAG time slots (F0-F7 shown in Figure 3~.
Figure 5 ~hows an embedded command 2S language instruction containQd within a typical POCSAG message, in which:
ADDRESS CODE WORD: is the standard POCSAG
code word representing the receiving device address.
HEADER CODE WORD: is a special cade word struct.ured to alert the receiviny device that this code word may contain embodied command language instructions.
INSTRUCTION CODE WORD: additional (unlimited) operational message code words whi.ch provide 20 binary bits that may be used for further instructions or data or gating keys.
~3~
MESSAGE CODE WORDS: message code words which may be standard numeric or alphanumPric or which may be interpreted by the receiving device in the manner defined by the embedded commands received S in the previous message code words.
The ECL is coded by the sending device (e.g. PET) in binary and structured to conform with the POCSAG data code word format. ~y this method and ECL instruction/s can be sent ~y the paging network to either numeric or alphanumeric receiving devices.
With reference to Figure 3, 20 bits of data contained in the first data code word (CWO or CW1) following the address code word of the receiving device, is called the ECL header code word. the 5 header code word contain~ the following elements;
(i) Embodied Command Language Key (ii3 Embodied Command Language Instructions These elements of the ECL header code word are extracted from the header code word as follows:
Each receiving device contains a command key mask (CKM) which is logically ANDed with the header code word in each correctly addressed message.
The resultant 2Q bit binary value (MRES) is compared with the command key code word (CKCW). If the comparison is true, the CKM is complimented and then ANDed with the header code word. The rasulting digital word embodied command language instruction (ECLl), the length of which is determined by the command key format, is used to provide instructions and or parameters, as may be defined by the network operator. It is allowable for the receiver to have more than one CKM and/or CKCW. (see Table 3 for one example).
21 ~39~
Header Code word 1 1 0 1 0 1 0 0 1 1 0 0 0 1 1 1 0 1 1 0 Mask (CKM) 0 0 0 0 1 1 1 ~ 1 0 0 0 1 1 1 0 0 0 0 0 Result (MRES) 0 0 0 0 0 1 0 0 1 0 0 0 0 1 1 0 0 0 0 0 Compliment Instruction (ECL) 1 1 0 1 0 0 0 0 0 1 0 0 0 0 0 1 0 1 1 0 Table 3 The format and function of the MRES word may be system operator defined. It could, for example, be used to provide immediate instruction or alternatively could be logically operated upon using a code pri~ate to the receiver (such as the serial number) to provide more secure access to some or all of the features.
The MRES word is assembled from the command language header by setting command language key bits to a known state so that the variable bits are those in the balance of the header. Note that if the service provider chooses to use the enkire 20 bit code space of the command language header of the command language key, there will be no com~and message word, since all bits are defined.
Interpretation of the command message word is not defined but it is envisaged that control o-f the receiver by off air commands will fall into three categories;
1. Class 1 Commands Instructions within this category temporarily alter the behaviour of the receiver, most probably for the specific message attached. This could include beeper overrides, display timeouts, etc.
An important instruction could be to add another address to the receiver's current addresses 22 ~3~2'7 to allow multiple receivers to be updated with specific information, after which the new address would be discarded.
Another important instruction could be to S use the combination of a subsequent ~essage code word combined with a receiver private code word (such as the serial number) to decode a message which is encrypted.
Another important instruction could be to store the subsequent message data in specific areas of memory to provide for updating of one data base in a receiver containing several data bases.
Another instruction could be to combine the subsequent message data with one of a number of "forms" stored within the receiver.
Another important instruction could be to substitute data stored within the receiver in place of the transmitted command(s) and data contained with the embodied command language instruction, for the purpose o~ data compression.
2. Class 2 Commands This instruction group commands the receiving device to modi~y its internal parameters and preferably requires confirmation from the user.
These commands include changing the default operational settings of the receiving device as well as providing updates to certain information.
3. Class 3 Comman~s Commands of this class are preferably limited to those which radically change the behaviour of the receiving device such as baud rate or permanent addresses, and require the user to confirm the integrity of the received message using encoded character sequences sent to the receiving device, which can be used by the service provider to confirm receipt of the command. The service provider can ' then send a further co~mand to the receiving device which then verifies and enables the previous command.
Extended POCSAG fgr enhanced battery savinq As noted above, in order to provide a paging receiver with reasonable operating performance for extended periods from internal battery supplies~
a power saving mechanism is used. The POCSAG
protocol allows each receiver to remain in an idle (powered down) state with a 14/17 du~y cycle. During each power up period the receiver must search for a preamble or other recognizable POCSAG ~ormat. The basic POCSAG data format consists of eight groups o~
two code words. These group~ correspond to individual time slots (Frames F0-F7). Once the receiving device has attained batch synchronization, by correctly detecting the unique sync code word (SCW
Figure 3) it now only needs to listen to data in the time slot (F0-F7) that may contain its own address.
Predict_ve Address Slot Wake-Up Inhibit The pagers have a capability to l'sleep"
on command (iOe. go to low power mode) for a dynamically controlled period of time. The command take the form of a special address that a~fects all pagers preprogrammed to so respond with a time slot address corresponding to the frame in which the command is transmitted. The sleep period should be integral numbers of batches (typically 4-32 seconds, approx.) as determined by the contents of a message word in the second code word of the time frame. In the absence of a sleep command, the pagers should operate in the standard POCSAG format.
By slightly increasing call latency, the paging terminal accumulates a "Que" of pending payes.
Groups of batches are assembled and "packed" so as to both make optimum use of the air time and such that some of the time slot addresses may be deactivated because no page~ are containe~ in the group for those ~3~a~2'7 pagers. Deactivation messages are pre~erably included with the batch.
In non-busy systems, pagexs pre~erably should sleep for some arbitrarily high fraction of S time ~for a 16 second sleep time this should be 15/16)~ By re-allocation of addresses, pagers with a 24 hour pattern of use are pre~erably put on a frequently used time slot, and others put into a low duty cycle mode.
Non-compatible pagers should not respond to the special address and thus would not be affected. Similarly, compatible pagers missing the sleep command because of errors, or out-of-range conditions or a non-compatible system, default to the POCSAG standard sampling rate. This system may therefore be considered to be a transparent overlay to a standard POCSAG system.
Electronic On/Off In the past, paging receivers had ON/OFF
switches which entirely removed the battery power from the internal electronics within the pager. With the development of very low power logic, it has become possible to develop pagers in which the internal logic is switched to a very low current state. Thus, previously received messages can be retained in memory and real time clocks (used to time stamp incoming messages) can continue to operate in the OFF state. Some pagers also have the capability to automatically turn ON and OFF at preset times.
A separate issue is the growing requirement to send large amounts of data over paging systems. The loading of such systems is such that demand is high in peak business hours and light at other times. Radio common carriers have an obvious incentive to offer data services but generally do not have the system capacity to provide this at peak traffic periods. Depending on the urgency o~ the ~:3399~2'7 data, it would be desirable to transmit most of this data during off peak times (such as overnight). the electrsnic ON/OFF system of this invention has the above capabilities and also has the ability to resume S normal operation at preset times to provide for data base transmissions.
Data Reception W le OFF
(a) In the OFF state, the paging receiver has an internal crystal controlled clock which continues t~ operate, and a memory which i~
maintained.
(b) In response to instructions received off-air from the paging system using the script command language described elsewhere herein, the pager can be instructed to "listenl' to the channe:L at a specific time for a specific period, even if switched OFF by the user.
(c) Because of the high accuracy of the crystal clock and the fact that its accuracy i5 maintained by repeated broadcast updates from the paging system, the wake up while off periods can be short, and thus the additional power drain negligibls.
(d) Data within a single data base might be separated into various priority classes. Non urgent (low priority) data is sent of~ peak (or opportunistically), while urgent updates are sent with normal message priority. This would apply to private (insurance tariffs or real estate listings~
and public (news and stock quotes, etc.~ data base services.
he ~'Vibra-c~
An alerting vibrator is very useful in noisy envirvnments or in situations when alerts must be silent, but the alert is only reliahle when the pager is mechanically fixed against the body, æuch as on a belt.
f~;~33~ '7 We therefore take advantaga of this situation by mounting the vibrator and its associated battery in a detachable belt clip into which the pager can be held. This has two principal advantages: first, the radio pager battery is removable from the belt clip and therefore separate from the vibrator battery so that the vibrator load does not cause premature battery failure, and sacond that the pager battery can be very much smaller (such as button cells~, and battery lifetime extended.
Operation of the vibrator is txiggered by a signa:L
wi.thin the pager and is coupled to the holster by either an optical signal or a metallic contactO The pager can be operated removed from the belt clip without operating the vibrator.
Intelli~ent Low Battery Detection-.
With battery operated equipment, is desirable to be able to detect and signal to the user when the battery is approaching the end of its useful life, or in the case of a rechargeable battery, that recharging i5 necessary. Ideally, this should be done at the point in the battery discharge when at least 1-2 days o~ operation remain, so as to give the user a reasonable chance to replace or recharge the battery.
The commonly used technique to detect low battery is comparison of the terminal voltage of the battery under a specific load to a reference/ and if the terminal voltage is less, low battery is flagged.
This technique works well for a specific battery type because the battery terminal voltage with discharge is highly predictable.
However, alkaline batteries are commonly used interchangeable with rechargeable NiCd batteries and these batteries have different discharge characteristics (see Figure 6). A voltage threshold detection apparatus properly set up for an Alkaline ~)3~2~
battery would not detect low battery soon enough for NiCd batteries and vice versa.
In portable radio equipment particularly, a variety of loads are applied to the battery in normal use. The control logic and radio receiver are relatively light loads, while enunciation transducers (such as vibrator motors) are relatively heavy loads.
A near-exhausted battery usually has su~ficient capacity to continue to operate the receiver but application of a heavy load can reduce the terminal voltage to the point that a system reset is generated.
The low battery detection inventio~ makes use of a microprocessor (or microcontroller) which has an analog to digital converter, optionally combined with a conventional low battery detection system.
With reference to Figure 7, the reference voltage of comparator 75 is set to be equal to that appropriate for the lowest battery detection voltage for any battery 74 that might be used.
Microprocessor 77 monitors the output from the voltage threshold comparator 75 and in addition, measures with A/D converter 76, the battery terminal voltage under a very liyht load 78 and under a defined, higher load 78. The sampling interval ~.g.
represented by means for sampling switch 79) in the preferred embodiment is lmS.
(a) If the comparator is switched (i.e.
low battery is detected) the equipment will signal low battery to the user, regardless of other considerations.
(b) The terminal voltage samples taken by the microprocessor are processed to calculate the internal battery resistance and its derivative (i.e.
rate of change) over a period o~ hours. If either of the terminal resistance or its derivative exceed , 2~3~ 7 preprogrammed limits, low battery is signalled to the user.
(c) ~erminal voltage and internal resistance for most battery types is a function of S temperature. Allowance for temperature effects is included by virtue of the chosen lim:its.
(d) There is no attempt to introduce temperature compensation because batteries truly have limited lifetimes at temperature extremes, even if useful life would remain at a different temperature.
(e3 As a battery becomes discharged it may not be capable of continued operation under the heaviest of loads. Thus if the voltage threshold comparator is tripped under heavy load (such as a vibrator), the load can be removed and a lower current form of enunciation used such as beeper.
This would be a change of function from the user's viewpoint and would be accompanied by a message on the display indicating low battery.
(f) To eliminats confusing signalling due to recovery in the battery, the low current capability is latched and the latch reset by a system reset, or a measured terminal voltage greater than a preset threshold. This would allow the battery to recover from low temperature caused low battery condition.
(g) High load elimination may also be initiated if a measured light load terminal voltage is less than a pre-determined threshold.
(h) All the above apply to newer types of battery likely to he introduced over the next 2-5 years, such as nickel hydride rechargeable ba~teries, etc.
The activation of the programmed auto ON/OFF function is in addition to the normal function of the ON/OFF control to disable the receiving device.
3~2~
A person understanding this invention may now conceive of alternative structures and embodiments or variations of the above. All of these which fall within the scope of the claims appended S hereto are considered to be part of the present invention.
.
,
Claims (22)
1. A radio receiver comprising means for receiving a radio signal, first means for beating the signal to zero intermediate frequency in phase and quadrature shifted signals, means for amplifying the in phase and quadrature zero shifted intermediate frequency signals, second means for beating the amplified intermediate frequency signals to predetermined non-zero intermediate frequency in phase and quadrature shifted signals, means for summing said non-zero signals, and means for applying the summed signals to a discriminator to obtain an output signal.
2. A radio receiver as defined in claim 1 including means for limiting the summed signal prior to it being applied to the discriminator.
3. A radio receiver as defined in claim 1 in which the non-zero intermediate frequency is about 455 kHz.
4. A radio receiver as defined in claim 2 further including low pass filter means for filtering said in-phase and quadrature shifted zero intermediate frequency signals prior to said signals being applied to said second beating means.
5. A radio receiver as defined in claim 4 in which said first beating means is a local oscillator having a frequency which is the same as said radio signal.
6. A radio receiver comprising:
(a) means for receiving and bandpass filtering a radio signal of predetermined frequency, (b) a first local oscillator for generating a local oscillator signal having a frequency which is the same as said radio signal, (c) means for phase shifting said local oscillator signal by 90°, (d) a first mixer for receiving the radio signal and said local oscillator signal and for providing a first in phase zero intermediate frequency signal, (e) a second mixer for receiving the radio signal and said phase shifted local oscillator signal and for providing a second quadrature shifted zero intermediate frequency signals, (f) low pass filter means for filtering said intermediate frequency signal, (g) a second local oscillator for generating a predetermined frequency local oscillator signal, (h) means for phase shifting said predetermined frequency local oscillator signal by 90° to provide a non-zero phase shifted local oscillator signal, (i) a third mixer for receiving the in phase zero intermediate frequency signal and said predetermined frequency local oscillator signal and for generating a non-zero intermediate frequency signal, (j) a fourth mixer for receiving the quadrature shifted zero intermediate frequency signal and said non-zero frequency phase shifted local oscillator signal and for generating a non-zero quadrature shifted intermediate frequency signal, (k) means for summing the non-zero intermediate frequency signal and the non-zero quadrature shifted intermediate frequency signal to form a summed non-zero intermediate frequency signal, (l) means for discriminating said summed signal to provide an output signal.
(a) means for receiving and bandpass filtering a radio signal of predetermined frequency, (b) a first local oscillator for generating a local oscillator signal having a frequency which is the same as said radio signal, (c) means for phase shifting said local oscillator signal by 90°, (d) a first mixer for receiving the radio signal and said local oscillator signal and for providing a first in phase zero intermediate frequency signal, (e) a second mixer for receiving the radio signal and said phase shifted local oscillator signal and for providing a second quadrature shifted zero intermediate frequency signals, (f) low pass filter means for filtering said intermediate frequency signal, (g) a second local oscillator for generating a predetermined frequency local oscillator signal, (h) means for phase shifting said predetermined frequency local oscillator signal by 90° to provide a non-zero phase shifted local oscillator signal, (i) a third mixer for receiving the in phase zero intermediate frequency signal and said predetermined frequency local oscillator signal and for generating a non-zero intermediate frequency signal, (j) a fourth mixer for receiving the quadrature shifted zero intermediate frequency signal and said non-zero frequency phase shifted local oscillator signal and for generating a non-zero quadrature shifted intermediate frequency signal, (k) means for summing the non-zero intermediate frequency signal and the non-zero quadrature shifted intermediate frequency signal to form a summed non-zero intermediate frequency signal, (l) means for discriminating said summed signal to provide an output signal.
7. A radio receiver as defined in claim 6 further comprising means for bandpass filtering said summed signal prior to discriminating it.
8. A radio receiver as defined in claim 6 further comprising a limiter for limiting said summed signal prior to discriminating it.
9. A radio receiver as defined in claim 8 including means for amplifying said zero intermediate frequency signals.
10. A radio receiver as defined in claim 9 in which said predetermined frequency local oscillator signal is about 455 kHz.
11. A superheterodyne F.M. radio receiver comprising a first local oscillator which includes a varactor for adjusting its frequency, a discriminator, and an automatic frequency control (AFC) circuit for generating an AFC signal, said AFC
circuit comprising:
(a) a first counter/register for storing said AFC signal as a digital signal, (b) a digital to analog converter (DAC) for receiving an output of said counter/register, (c) means for applying the output signal of the DAC to the varactor, whereby the AFC signal stored in said counter/register controls frequency adjustment of said first local oscillator.
circuit comprising:
(a) a first counter/register for storing said AFC signal as a digital signal, (b) a digital to analog converter (DAC) for receiving an output of said counter/register, (c) means for applying the output signal of the DAC to the varactor, whereby the AFC signal stored in said counter/register controls frequency adjustment of said first local oscillator.
12. A radio receiver as defined in claim 11, including:
(d) voltage controlled oscillator means for receiving a differential voltage representing of an instantaneous radio frequency voltage deviation from a reference, and for generating an output clock signal which is proportional to the absolute differential, (e) comparator means for receiving said differential voltage, (f) means for applying said clock signal as an input to the counter, and an output signal of said comparator means to an up/down count control of said counter, (g) means for detecting and storing the direction of signal transition of the output signal of said comparator means, and for enabling the counter, (h) a second parallel loadable counter/register for receiving the high N bits of the current signal stored in the first counter, and for applying its count signal to said digital to analog converter.
(d) voltage controlled oscillator means for receiving a differential voltage representing of an instantaneous radio frequency voltage deviation from a reference, and for generating an output clock signal which is proportional to the absolute differential, (e) comparator means for receiving said differential voltage, (f) means for applying said clock signal as an input to the counter, and an output signal of said comparator means to an up/down count control of said counter, (g) means for detecting and storing the direction of signal transition of the output signal of said comparator means, and for enabling the counter, (h) a second parallel loadable counter/register for receiving the high N bits of the current signal stored in the first counter, and for applying its count signal to said digital to analog converter.
13. A radio receiver as defined in claim 11, including:
(d) voltage controlled oscillator means for receiving a differential voltage representing of an instantaneous radio frequency voltage deviation from a reference, and for generating an output clock signal which is proportional to the absolute differential, (e) comparator means for receiving said differential voltage, (f) means for applying said clock signal as an input to the counter, and an output signal of said comparator means to an up/down count control of said counter, (g) means for detecting and storing the direction of signal transition of the output signal of said comparator means, and for enabling the counter, (h) means for detecting overflow or underflow and for generating a count clock signal depending thereon, (i) a second counter/register for receiving said count clock signal and counting and storing up or down one bit in the direction of the overflow or underflow or left unchanged, (j) means for applying said up or down bit to said digital to analog converter at the end of an operation interval of said receiver, whereby AFC adjustment is not performed during the operational interval of said receiver.
(d) voltage controlled oscillator means for receiving a differential voltage representing of an instantaneous radio frequency voltage deviation from a reference, and for generating an output clock signal which is proportional to the absolute differential, (e) comparator means for receiving said differential voltage, (f) means for applying said clock signal as an input to the counter, and an output signal of said comparator means to an up/down count control of said counter, (g) means for detecting and storing the direction of signal transition of the output signal of said comparator means, and for enabling the counter, (h) means for detecting overflow or underflow and for generating a count clock signal depending thereon, (i) a second counter/register for receiving said count clock signal and counting and storing up or down one bit in the direction of the overflow or underflow or left unchanged, (j) means for applying said up or down bit to said digital to analog converter at the end of an operation interval of said receiver, whereby AFC adjustment is not performed during the operational interval of said receiver.
14. A radio page signal receiver in combination with a belt clip with a vibrator alert apparatus for applying vibration against a wearer upon receipt of an alerting signal and a battery for powering the vibrator alert apparatus, means in said belt clip for retaining said removable radio receiver, and means for coupling a vibrator alert enable signal from said receiver to said vibrator alert apparatus upon the receiver being retained in said belt clip.
15. A radio page signal comprising a battery, low and high load peripherals connected to the receiver, means for operating a high load peripheral, a low battery reserve detector, and means for substituting a low load peripheral for the high load peripheral upon detection of a low battery reserve.
16. A radio page receiver comprising means for receiving high and low priority messages from a transmitter, means for alerting and displaying the high priority messages, and means for storing the low priority messages and for being enabled to display the low priority messages on demand by a user.
17. A low battery detection circuit for electronic apparatus comprising a voltage comparator for sampling battery terminal voltage respectively under light and heavy loading, and for indicating a low battery condition when the rate of change of the sampled voltage or internal resistance is greater than a predetermined limit.
18. A radio pager comprising means for receiving a transmitted signal from a transmitter, means for extracting a command signal and a message signal from said transmitted signal, and means for operating said receiver in response to said command to control how said message signal is handled.
19. A pager as defined in claim 18 in which said command signal contains data for enabling said pager to operate as a scheduler.
20. A pager as defined in claim 18 in which said command signal contains data for enabling battery saving features of said pager.
21. A pager as defined in claim 18 in which said transmitted signal contains command language instructions for said pager encoded therein.
22. A paging receiver as defined in claim 19 in which said command signal causes said receiver to be powered down for a predetermined period of time.
Applications Claiming Priority (4)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| US9006919.6 | 1990-03-28 | ||
| GB909006919A GB9006919D0 (en) | 1990-03-28 | 1990-03-28 | Paging receiver |
| GB9106719A GB2242588B (en) | 1990-03-28 | 1991-03-28 | Radio receiver |
| US9106719.9 | 1991-03-28 |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| CA2039427A1 true CA2039427A1 (en) | 1991-09-29 |
Family
ID=26296853
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CA 2039427 Abandoned CA2039427A1 (en) | 1990-03-28 | 1991-03-28 | Paging receiver |
Country Status (1)
| Country | Link |
|---|---|
| CA (1) | CA2039427A1 (en) |
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US5642102A (en) * | 1991-11-12 | 1997-06-24 | Silcom Research Limited | Pager with automatic detection of insertion into holster |
-
1991
- 1991-03-28 CA CA 2039427 patent/CA2039427A1/en not_active Abandoned
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US5642102A (en) * | 1991-11-12 | 1997-06-24 | Silcom Research Limited | Pager with automatic detection of insertion into holster |
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