CA1147024A - Bridge-doubler rectifier - Google Patents

Abstract

ABSTRACT
BRIDGE-DOUBLER RECTIFIER

A full wave (RMS) bridge circuit is disclosed for regulating a nominal 200 to 240V AC bulk voltage to a nominal 300V full wave rectified DC bulk voltage for all line and load conditions. The circuit automatically adjusts to varying line voltages and operates in any one of four modes: (i) full wave bridge, (ii) phase con-trolled bridge-doubler, (iii) phase controlled doubler, or (iv) non-controlled doubler to maintain the nominal DC output voltage.

Description

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BRIDGE-DOUBLE~ RECTIFIER

The present invention relates to switched mode power supplies and more particularly to the input recti-fier and providing for phase controlled voltage regula-tion of the AC line voltage to maintain a no~inal DC
voltage to the inverter section of the power supply.

~ In recent years, switched mode power supplies have captured a significant share of the market for computer-based power supplies~ Of these units~ the off-line inverter is the rnost attractive requiring no 60 ~Iz ~ magnetic components for its operation. One section of - ~ this type o~ power supply is the input recti~ier which is used to produce a DC bulk volta~e from the AC input line. This raw DC bulk voltage is then switched at hi~h frequency by the inverter section and pulse widtn modulated to produce a stable output voltage indepen-dent o~ line and load variations.

Present designs, in response to computer system demands for "brown-out" capabilities to 66% of nominal line conditions, perrnit the bulk DC voltage to vary from approximately 170 to 360V DC, when operating frorn a "

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norninal voltage of 200 to 2~10V AC. The upper limit of 3~0~1 is compatible with the present state of transistor technology incorporating 400V high speed devices. The lower limit, however, presents somewhat of a problem in that the turns ratio of the inverter's high frequency transformer is set by the ratio of low line DC input voltage to the required DC output voltage, assuming the inverter is operating at maximum pulse width. Increasing the input voltage results in decreasing the pulse width.
Large voltage variations, therefore, result in the inverter operating at a fraction of its power switch section capability. There is a need for a circuit which will regulate this bulk voltage to a nominal value from 300 to 360V DC for all line-load conditions. It is also desirable that this circuit be efficient and not require a line frequency transformer for its operation.

The present invention provides a solutlon to the above concerns and enables regulation of the bulk DC
voltage available to the inverter to within 1% o~ the design limit when operating in the phase controlled rnodes of operation. The circuit has the further advantage of having its greatest power factor at high line condi-tions unlike conventional phase-controlled circuits which penalize the user for his "brown-out" capabilities by presenting a low power factor under normal line conditions.

SUMMARY OF THE INVENTION

Single phase and three phase embodiments of a rectifier circuit operable as a full wave bridge or as a phase controlled voltage doubler depending on the line-load conditions is disclosed. The circuit is comprisedof a full wave, diode bridge coupled to a capacitor ` filter, wherein the capacitor filter is further coupled to the bridee via a contro1~able, b~-directional current :

~4~ 4 Means (:i.e., triac, SCR pair or similar four layer devices) for tapping the filter and enabling the circuit to operate in a voltage doubler mode on al~ernate half cycles of` the line voltage. A phase control circuit is also disclosed for controlling the operation of the bi-directional current means to maintain the DC load voltage at a nominal 300 volt level over a range of varying line conditions.

The rectifier circuit is operable in four modes, depending on the line-load conditions, which are as follows: (i) full wave bridge, (ii) phase controlled bridge-doubler, (iii) phase controlled doubler or (iv) uncontrolled doubler. As the line voltage decreases with respect to the load voltage on the capacitor filter, the rectifier circuit switches from the bridge mode to the phase controlled bridge-doubler mode, to the phase con-trolled doubler mode to the uncontrolled doubler mode depending on the relative difference. Where the line voltage exceeds the load voltage, howeverl the rectifier circuit is operable in the full wave bridge mode or the bridge-doubler mode if the load hasn~t attained the nominal design value.

BRIEF DESCRIPTION OF THE DRAWINGS
.

~ igure 1 is a block diagram of prior art switched mode power supplies.

Figure 2 is a block diagram of a switched mode power supply containing the bridge-doubler circuit of the present specification.

Figure 3 is a circuit schematic of a bridge-doubler circuit for a single phase AC input.

7~3 Figure 4 ls a block diagram of the controller circuit for the single phase brldge-cloubler circuit of F'igure 3.

Figure 5a, b, c, d are representations of the various waveshapes that occur in the single phase con-troller of Figure 4.

Figure 6a and b are representations o~ the - waveshapes for the pilase controlled bridge-doubler mode of operation for Figure 3 assuming no load conditions.

10Figure 7a and b are block diagrams of various loading schemes possible for the bridge-doubler circuit.

Figure 8 is a circuit schematic of a bridge-doubler circuit for a three phase QC input.

Figure 9 is a block diagram of the controller circuit for the three phase bridge-doubler of Figure 8.
i Figure 10 is a circuit schematic for one of three sense circuits for ensuring that no two SGR's between phases are conducting at the same time in the bridge-doubler circuit of Figure 8.

DESCRIPTION OF THE PREFERR2D EMBODIME~T
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Present switched mode power supplies are simi-lar to the design shown in Figure 1. The AC input is full wave rectified and capacitor filtered and the result-ant bulk DC voltage is then switched at high frequency and pulse width modulated to provide a stable output voltage independent of line and load variations. Such systems, however, do not optimize the transfer of pot~er to the switching transistors of the inverter. While standard phase control circuits are available to pre-regulate the bulk DC voltage to a value from 300 to ~47~)Z~

360V DC, they have the consequential drawback ofrequirin~ a step-up transformer to achieve the nominal 36~ volts compatible with present 400V switching tran-sistor inverter designs. Standard phase control cir-CUitS have the fur~her dra~back in that they have theirlowest power factor during high line conditions and thus penalize the user during normal operation for his low line (i.e., brown-out) capabilities.

Referring to Figure 2, a switched mode power supply havlng a pre-regulated DC bulk voltage via the bridge-doubler circuit of the present invention is shown which circuit alleviates the need for a step-up trans~ormer and provides a high power factor during the high line, which is the normal operating condition. A
bridge-doubler circuit for a single phase~ AC input, typically 200/240V (RMS), is 5hown in Flgure 3 and a con-troller for such a doubler-clrcuit is shown in Figure 4 -- The operation of the doubler-circuit of Figure 3 will now be described in its respective four modes of operation as t;he single phase AC input varies between its maximum and minimum design values. It is to be recognized, however, that the operation of the doubler circuit for a single phase input is analogous to that for a three phase input, which case will be more fully described hereinafter.

Referring to ~igure 3, when a single phase AC
voltage VAB is impressed across the inputs A and B, the inductors Ll and L2 limit the rise time of the input cur-rent which reduces the RMS value of the current and improves the power factor of the circuit under all condi-tions.

Looking to the positive half cycle of V~B, assuming that VAB = 240V (RMS), that VAB (peak~ >

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Vxy and kno.~ that the normal peak value of VAB is 339.ll volts, diodes CRl and CRL~ are forward biased and capacitors Cl and C2 charge during the first quarter cycle and discharge through the load during the second quarter cycle when the diodes are reverse biased. In a similar manner during the negative half cycle, diodes CR2 and CR3 are forward biased, capacitors Cl and C2 charge and then discharge through the load. The voltage waveshape Vxy across modes X and Y thus appears as a full wave rectified voltage, see ~igure 6a, however~ by selecting appropriate size capacitors for Cl and C2~ the time constant for the load and capacitor combination can be adjusted to be much greater than the frequency of the AC source to minimize the ripple of Vxy and produce a relatively constant 300V
DC output. Thus, during a normal high line AC input con-dition, the circuit operates as an unregulated, capacitor filtered full wave bridge which operation is more speci-fically described in an article entitled~ ~Time Domain Analysis of the Power Factor for a Rectifier Filter System with Over/and Subcritical Inductance~ by ~rancise C.
Schwartz, IEEE l`ransactions on Industrial Electronics and Control Instrumentation, Vol. IECI 20, No. 2, May, 1973, pp. 61-68.

I~ the peak AC input voltage decreases due to "brown-out" conditions, the output Vxy decreases below the desired DC level, and depending on whether VAB (peak) Vxy or VAB (peak) ~ Vxy~ the circuit operates ei~her in a phase controlled bridge-doubler mode or in a phase controlled doubler mode~ and if VAB (peak) ~ 1/2 Vxy (desired), the circuit operates in an uncontrolled doubler mode. In any event, the circuit discontinues operating ' in the full bridge mode and triac CR5 is pulsed by the controller.

During any of the three doubler modes of opera-tion, CR5 is controllably pulsed ~'on" to act as a short circuit, and thus durlng a positive half cycle, CRl is 4~

forward biasecl an~ charge flows from A through CRl to charge Cl an(l then through CR5 to B. In a sirnilar manner during the negative half cycle, charge flows from B through CR5 to charge C2 and then through C2 to A. The DC output voltage Vxy ls now the sum of the volt-ages to which Cl and C2 charge and will be dependent on the timing of when CR5 is pulsed in relation to Vin. The ripple component on Vxy will also be greater than for the full bridge mode.

The controller of Figure 3 which determines the point in time at which CR5 is pulsed during the various doubler modes is shown in Figure ll and operates to gener-ate control pulses synchronized to the line frequency of VAB and to alter the phasing (i.e., exact timing) of these pulses and thus regulate Vxy by controlling the charge time and resultant voltages to which Cl and C2 charge.

Referring to Figure 4 and 5, the controller and its operation will now be described. The ramp generator~
coupled to the AC input VAB acts to produce a constant ramp voltage synchronized to VAB but having a fixed slope and peak voltage independent of VAB. The output voltage Vxy of the bridge-doubler circuit is next reduced by a suitable voltage divider to a level compatible with the operational error amplifier. The error amplifier then compares the reduced output signal to a constant DC
reference voltage VREF, which voltage is fixed at a value proportionate to the desired Vxy~ to determine the ` difference between VREF and the actual output voltage.
The error amplifier is further feedback coupled by an appropriate resistance, capacitance combination ~ to sta-bilize the closed loop response of the system against high frequency ripple or noise which, upon amplification, ~ could cause the system to oscillate.

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7~)~24 'l`he amplified di~ference or error signal from the error amplifier is next compared to the ramp genera-tor output by the pulse enable comparator which gener-ates a widtn modulated logic pulse, see ~igure 5c, used to enable the multiplier which is coupled to the pulse train generator, if the ramp signal is less than the error signal (i.e., high line AC input) a logic low is generated and the multiplier is disabled.
~, Referring to Figure 5b and 5d, if the ramp signal is greater than the error signal (i.e., low line AC input), a logic high is generated as long as the condition exists, the multiplier is enabled and a width modulated series of control pulses of a sufficient amplitude to turn CR5 "on"
are produced. The width modulated gate control pulses are then impressed on a suitable triac inter~ace (i.e., optical or transformer) to isolate the controller from the bridge-doubler circuit and trigger the triac "on~ with each suc-cessive pulse.
-From Figure 5b it can also be seen that as the error signal decreases due to a decreasing Vxy~ the ramp signal will intersect the error signal at an earlier time, which will cause CR5 to be pulsed "on" for a longer period of time permitting Cl and C2 to charge to higher voltage levels, and thus cause the output voltage Vxy to rise and offset the voltage drop of Vin. The increase in Vxy results because Cl and C2 are alternately permitted to charge to values in excess of that to which they would individually char~e during the full bridge mode. The spe-cific peak voltage to which Cl and C2 will charge during the controlled doubler modes is dependent on VREF, since the controller enables the trigger pulses so long as an error si~nal is produced.

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Referring ~o ~igures 3 and 6 and assuming the circuit is operating in the phase controlled bridge-doubler mode, where VAB (peak) > Vxy but V~B (peak) <
Vxy (desired)~ the charge on Cl and C2 for each half cycle will be made up of two components of charge due to the operation of the circuit first in the bridge mode up to the point in time at which CR5 is triggered and then in the doubler mode for the period of time during which CR5 is pulsed. During the bridge mode, Cl and C2 will charge at the same time to approximately the same value if Cl = C2~ whereas during the doubler portion of the operation, Cl and C2 are free to charge to VAB but are limited by the rarnp signal. From Figure 6b the respec-tive charge components for Cl and C2 can be seen in rela-tion to the input current IAB. The charge time of capa-citors C1 and C2 determined by the trigger point will thus control the increase in VCl and VC2 until VCl VC2 = Vxy (desired).

`If the circuit is operating in the phase con-trolled doubler mode, where V~B ~ Vxy~ the charge on Cl and C2 results only from the doubler component. It should again be recognized that if, l~owever, V~B decreases to the point where VAB (peak) < 1/2 ~XY (desired), CR5 is pulsed "on" continuously and the circuit will be uncontrolled until Vin increases to the point where VAB > 1/2 Vxy (de-sired) and the circuit again operates in the phase con-trolled doubler ~ode until Vin (peak) > Vxy when it oper-; ates in the phase controlled bridge-doubler mode. This assumes no load conditions, whereas under load conditions the crossover point occurs for a larger VAB.
.

It should also be noted that the bridge-doubler circuit of the present invention is capable of operating in the centertapped, unbalanced load conditions of Figures 7a and 7b. Typically~ however, the circuit will be used with a single load across X and Y where the load ~ ~7Q;~

sees Cl and C2 as one source of current. With the load-ing arra~g-rements sho~rn and assuming loads 1 and 2 are equal in si~e~ the current requirements of loads 1 and

2 don't affect the operation o~ the preferred embodiment in which Cl = C2 and Vcl = Vc2. If, however, load 1 ~
load 2, the control circuit would have to be modified to provide the proper Vcl and Vc2 by adjusting the ramp peak, VREF and control for each half cycle. In this manner, the individual charge times ~or Cl and C2 would be individually tailored to the constraints of the load condition.

While the operation of the bridge-doubler cir-cuit has been described for the single phase AC input, the circuit is equally applicable to a three phase AC
input. Given a three phase input, the circuit would be configured as in Figure 8 and instead of using a triac as the control elernent to switch to the doubler modes of operation, parallel silicon controlled rectifiers (SCR's) are used. Triacs could be used but given certain phase angles between phases and pulse width conditions, it is possible that the triac could conduct current in the wrong direction in some circumstances. SCR's are there-fore used since they are unidirectional devlces and once pulsed "on" the direction of the current flow is 2~ fixed.

, t ,' The operation of the three phase bridge-doubler is essentially the same as previously described for the single phase bridge-doubler, but now there are three single phase circuits operating 120~ out of phase with each other and thus the capacitors Cl and C2 are being pulsed three times as much as before. A possible conduction sequence for the bridge mode and doubler modes of opera-tion for the alternating inputs VAB, VAc and VBc would be as follows:

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, ~r1dp e. Ilocie __ D~ub.l~r ~ocle In~utDiod~s Con~luctln~Diod~ SC]~ Ca,:~a_t AR (posltlve c,~rc].e) CRl, CR5 CRl CR10 Cl AC " " CRl ~ CR6 CR6 CR7 C2 BC " " CR2, CR6 CR2 CR12 Cl AB (neGativ~ cycle) C~2, CT~I~ CR4 CR9 C2 AC " " CR3, CR4 CR3 CR8 Cl E3C 'I 1l CR3, CR5 CR5 C~11 C~

The controller for the three phase bridge-doubler circuit is shown in ~igure 9 and again operates essentially the same as for three single phase controllers with each controller synchronized to its respective single phase input. The controller differs in that a pulse enable gate replaces the multiplier and is used to trans-mit the control pulse at node 3 to node l if the input on node 4 is positive and to node 2 if the input on node 4 - is negative, thus alternately turning "on" one or the other of the SCRts depending on the phase of the input.
:, The technique for pulsing the SCR's is also changed slightly with the pulse enable comparator signal, still representing the time relationship for which the error signal is less than the peak ramp signal~
~-` now causing the pulse generator to produce a single pulse output as the leading edge of each pulse enable comparator signal goes "hi". In this manner, each SCR remains "on"
so long as it is forward biased and has enough holding current. The l'on" condition, therefore, sustains itself for the same period as described for the triac and the width modulated series of pulses.

While the three phase circuit operates essen-tially the same as for the single phase circuit with the above differences, it is to be further noted that 7~
-]2-it is d2sirable to ensure that no t~To SCR's are "on"
at the sarne time to avoid the shorting of the input phases. To pre~ent the shorting o~ the inputs, a sense circuit is necessary to sense the current through each SCR (i.e., current transformer, Hall Effect device or o~to-isolator) and inhibit the control pulses to each of the SCR's~ such that only one SCR can conduct at any one time. Such an inhibit operation can be accomplished with the circuit shown in Figure 10.

Referring to Figure 10 one of three circuits for sensing and inhibi~ing the three input currents is shown.
Each circuit has its D and E inputs coupled in series with each SCR combination between the bridge and the capacitor filter. Each circuit thus senses the SC~ current flow in its current transformer, which causes a proportional volt-age to be developed across resistor R. This voltage is then amplified by the high gain amplifier and used ko drive transistors Ql and Q2. The F and G inputs to the col-lectors of Ql and Q2 are further coupled between the pulse generators and pulse enable gates and by turning Ql and Q2 "on" the pulses from the pulse generators are grounded, thereby preventing the ex:Lstence or a cross conduction condition. It is to be further noted that such circuits are to be coupled in the manner shown in Figures 8 and 9 for the corresponding inputs DE~G, D'E'F'G' and DltE"F"G".

While the present invention has been described with specific reference to its preferred ernbodiments, it is to be recognized that other embodiments may be devised by those skilled in the art without departing from the spirit and scope of this invention as encompassed by the following claims.

What is claimed is:

Claims (6)

The embodiments of the invention in which an exclusive property or privilege is claimed are defined as follows:

1. A rectifier circuit comprising:
bridge means for rectifying at least one phase of an alternating input signal to a full wave signal;
capacitor means coupled to said full wave signal and having a voltage control terminal for producing an output signal, the voltage level of said output signal remaining substantially constant as the peak level of said input signal varies;
bidirectional current means having a gate and a first and second terminals, said first terminal connected to said voltage control terminal and said second terminal connected to said bridge means, for conducting current in response to a control signal; and control means coupled to said gate and producing said control signal for controlling the conduction time of said bidirectional current means, and thereby causing said rectifier to operate in a voltage doubler mode and regulate the level of said output signal, comprising;
a constant reference voltage source proportional to the constant level desired of said output signal;
ramp means coupled to said input signal for producing a ramp signal synchronized to said input signal;
error means coupled to said output signal for comparing said reference voltage to a feedback signal, said feedback signal being proportional to said output signal, and producing an error signal;
comparator means for comparing said error signal with said ramp signal and producing a pulse enable signal when-ever said ramp signal is greater than said error signal;
modulating means coupled to said pulse enable signal for phase width modulating said control signal, the con-duction time of said bidirectional current means corres-ponding to the time width of said pulse enable signal.

2. A rectifier as set forth in claim 1 wherein said bidirectional current means comprises a triac.

3. A rectifier as set forth in claim 1 wherein said bidirectional current means comprises first and second silicon controlled rectifiers (SCR), each SCR having an anode, cathode and gate terminal, said anode of said first SCR coupled to said cathode of said second SCR said cathode of said first SCR coupled to said anode of said second SCR
and said gate terminals coupled to said control signal, whereby only said first or second SCR can conduct during any given time.

4. A rectifier circuit comprising:
bridge means for rectifying a three phase alternating input signal to first, second and third full wave signals;
capacitor means coupled to said full wave signals and having a voltage control terminal for producing an output signal, the voltage level of said output signal remaining substantially constant as the peak level of said input signal varies;
first, second and third bidirectional current means respectively coupled to said first, second and third full wave signals and to said voltage control terminal and each having a gate terminal for conducting current in response to a control signal;
control means coupled to said gate terminals of said first, second and third switch means and producing first, second and third control signals for controlling the conduction time of said respective first, second and third switch means and thereby causing said rectifier to operate in a voltage doubler mode and regulate the level of said output signal comprising;
a constant reference voltage source proportional to the constant level desired of said output signal;
first, second and third ramp means each coupled to a respective one phase of said input signal for producing first, second and third ramp signals, each ramp signal synchronized to one phase of said input signal;
error means coupled to said output signal for comparing said reference voltage to a feedback signal, said feedback signal proportional to said output signal, and producing an error signal;
first, second and third comparator means, each for comparing said error signal to one of said respective first, second and third ramp signals and producing first, second and third pulse enable signals whenever said respective ramp signals are greater than said error signal;
first, second and third modulating means coupled to said respective first, second and third pulse enable signals for phase width modulating said respective first, second and third control signals, the conduction time of said first, second and third bidirectional current means corresponding to the width of said respective first, second and third pulse enable signals.

5. A rectifier as set forth in claim 4 including means coupled to said first, second and third bidirectional current means for ensuring that only one of said first, second and third bidirectional current means conducts at any given time thereby preventing shorting between said three phases.

6. A rectifier circuit comprising:
bridge means for rectifying at least one phase of an alternating input signal to a full wave signal;
capacitor means coupled to said full wave signal and having a voltage control terminal for producing an output signal, the voltage level of said output signal regulated to remain substantially constant as the peak level of said input signal varies;
bidirectional current means coupled to said bridge means and said voltage terminal and having a gate terminal for conducting current in response to a control signal; and control means coupled to said gate terminal, said input signal and said output signal for producing said control signal whenever said output signal falls below the desired constant voltage level, thereby causing said rectifier to operate in a voltage doubler mode and regulate the level of said output signal.