WO2015176263A1

WO2015176263A1 - Co-local oscillator circuit, emission system and method for determining correction coefficient of co-local oscillator circuit

Info

Publication number: WO2015176263A1
Application number: PCT/CN2014/078080
Authority: WO
Inventors: 叶四清; 李建平; 武杰
Original assignee: 华为技术有限公司
Priority date: 2014-05-22
Filing date: 2014-05-22
Publication date: 2015-11-26
Also published as: CN105409117B; CN105409117A

Abstract

Disclosed are a co-local oscillator circuit, an emission system and a method for determining the correction coefficient of the co-local oscillator circuit. The co-local oscillator circuit comprises: a forward channel, a feedback channel, a local oscillator signal source, a direct-current and even-order IMD (Inter-modulation) calculating module, and an attenuator arranged between the forward channel and the feedback channel. Wherein, according to the co-local oscillator circuit, the emission system and the method for determining the correction coefficient of the co-local oscillator circuit, a reverse direct-current correction coefficient and a reverse even-order IMD correction coefficient can be determined by means of multiple alterations of the amounts of attenuation of the attenuator and on the basis of signal values corresponding to the amounts of attenuation, thus the correction performance of the system can be improved, and further the emission performance of the system can be improved.

Description

Common local oscillator circuit, transmitting system and method for determining correction coefficient of common local oscillator circuit

The present invention relates to the field of communications, and more particularly to a common local oscillator circuit, a transmitting system, and a method of determining a correction coefficient of a common local oscillator circuit in the field of communications. Background technique

In the launch system, in order to improve system performance, a common local oscillator system architecture is usually used. The so-called "common local oscillator" refers to a local oscillator ("LO") signal input to a Quadrature Modulation Transmitter (QMTX) and an input to a quadrature demodulation receiver ( The local oscillator signal of the Quadrature Demodulating Receiver (QDRX) is the RF shunt of the same local oscillator signal. The advantage of the system architecture is that the forward and reverse local oscillator phases can be identical, which can reduce the relative phase noise of the system loop and improve the signal to noise ratio (Signal to Noise Ratio, referred to as "SNR" of the feedback signal. "), which in turn can improve the performance of the launch system.

However, in the transmitting system, the four physical quantities of the forward DC, the forward-even intermodulation (IMD), the reverse DC, and the reverse even IMD are used to compensate and correct the superposition. Together, the forward DC and forward even intermodulation cannot be distinguished from the reverse DC and reverse even IMDs, thereby failing to accurately compensate and correct the transmission system, thereby seriously affecting the performance of the transmission system. Summary of the invention

In view of this, the embodiments of the present invention provide a common local oscillator circuit, a transmitting system, and a method for determining a correction coefficient of a common local oscillator circuit, which can improve the correction performance of the system and further improve the transmission performance of the system.

In a first aspect, a common local oscillator circuit is provided. The common local oscillator circuit includes: a forward channel, configured to convert a downlink service signal into a radio frequency signal, and send the radio frequency signal to an antenna; and a feedback channel, configured to provide a pair a feedback signal for compensating the downlink service signal; a local oscillator signal source, configured to generate a local oscillator signal, wherein the two local oscillator signals formed by the local oscillator signal after being passed through the power splitter are respectively input to the forward channel and the feedback channel; An attenuator disposed between the forward channel and the feedback channel, the attenuator for changing the attenuation of the attenuator multiple times, and for injecting a portion of the input to the feedback channel The frequency signal is attenuated; and the DC and even IMD calculation module is configured to obtain the downlink service signal, the feedback signal, and the attenuation amount; and determine the reverse DC correction coefficient according to the downlink service signal, the feedback signal, and the attenuation amount And a reverse even IMD correction coefficient; the reverse DC correction coefficient and the reverse even IMD correction coefficient are output to the feedback channel.

In combination with the first aspect, in the first possible implementation of the first aspect, the DC and the even

The IMD calculation module is specifically configured to: obtain the downlink service signal and the N attenuation amounts of the attenuator, where ζ is a natural number, ι=\ , 2, ..., Ν, and Ν is a natural number; according to the feedback channel a feedback signal outputted when the attenuator has the attenuation amount %, and obtains a total DC voltage corresponding to the attenuation amount %; and determining the downlink service signal, the attenuation amount %, and the total DC voltage of the loop Reverse DC correction factor and the inverse even IMD correction factor.

With reference to the first possible implementation manner of the first aspect, in a second possible implementation manner of the first aspect, the DC and even IMD calculation module is configured according to the downlink service signal, the attenuation amount, and the total loop DC, determining the reverse DC correction coefficient and the inverse even IMD correction coefficient, including:

The DC and even IMD calculation module determines the reverse DC correction coefficient ^ and the inverse even IMD correction coefficient y ₇ according to the following equation (I)

² Ε{ ν\ '} 1 ^ΙοορΛ

α _τ ² Ε{ π =

} 1 Ϊ 2

² Ε \ ² } 1 where x represents the downlink traffic signal; {|JC| ² } represents the average of |JC| ² ; N ≥ 3; is a natural number, z = l , 2, ..., N, and N is a natural number; represents the sum of the DC components of the forward DC and the forward even IMD.

With reference to the first possible implementation manner of the first aspect, in a third possible implementation manner of the first aspect, the DC and even IMD calculation module is configured according to the downlink service signal, the attenuation amount, and the total loop DC, determining the reverse DC correction coefficient and the inverse even IMD correction coefficient, including:

The DC and even IMD calculation module determines the reverse DC correction coefficient and the inverse even IMD correction coefficient γ according to the following equation (II):

Where / is a natural number, 1 = 1, 2, L, and L is a natural number; X represents the downlink traffic signal; {| f } represents the average of | f; ^ represents the reverse DC correction coefficient; N ≥ L + 2; I is a natural number, z=l, 2, ..., N, and N is a natural number; represents the sum of the DC components of the forward DC and the forward even IMD.

With reference to the first aspect, or any one of the first to the third possible implementation manners of the first aspect, in a fourth possible implementation manner of the first aspect, the forward channel includes a front To the DC and even IMD compensation modules and the quadrature modulation transmitter, the feedback channel includes a reverse DC and even IMD compensation module and a quadrature demodulation receiver, wherein the forward DC and even IMD compensation modules are used : compensating the received downlink service signal according to the forward DC correction coefficient and the forward even IMD correction coefficient input by the DC and even IMD calculation module, and outputting the compensated downlink service signal to the orthogonal Modulating a transmitter; the quadrature modulation transmitter is configured to: modulate the compensated downlink service signal into a radio frequency signal according to the local oscillator signal, and output the radio frequency signal to the antenna and the attenuator; the orthogonal solution The receiver is configured to: demodulate the attenuated radio frequency signal according to the local oscillator signal, and output the demodulated baseband demodulated signal to the reverse DC And an even IMD compensation module; the reverse DC and even IMD compensation module is configured to: compensate the baseband demodulation signal according to the reverse DC correction coefficient and the reverse even IMD correction coefficient to generate a compensated The feedback signal.

With reference to the first aspect or any one of the possible implementation manners of the first to fourth possible implementations of the first aspect, in a fifth possible implementation manner of the first aspect, the common local oscillator circuit further A switch is included, wherein the switch is disposed in series with the attenuator and disposed between the forward channel and the feedback channel.

With reference to the first aspect, or any one of the first to the fifth possible implementation manners of the first aspect, in a sixth possible implementation manner of the first aspect, the common local oscillator circuit further The phase shifter includes: the local oscillator signal outputted by the local oscillator signal source is phase-shifted by the phase shifter and output to the feedback channel, or the radio frequency signal output by the forward channel is phase-shifted by the phase shifter Output to this feedback channel. ₃ In a second aspect, a transmitting system is provided, the transmitting system comprising: a common local oscillator circuit according to an embodiment of the invention; and an antenna for transmitting a radio frequency signal input by the common local oscillator circuit, wherein the common ground The vibration circuit includes: a forward channel for converting a downlink service signal into a radio frequency signal, and transmitting the radio frequency signal to the antenna; a feedback channel for providing a feedback signal for compensating the downlink service signal; and a local oscillator signal source, Generating a local oscillator signal, the two local oscillator signals formed by the local oscillator signal passing through the power splitter are respectively input to the forward channel and the feedback channel; the attenuator is disposed between the forward channel and the feedback channel, The attenuator is configured to change the attenuation of the attenuator multiple times, and attenuate the RF signal input to a part of the feedback channel; and the DC and even IMD calculation module is configured to acquire the downlink service signal, the feedback signal, and The attenuation amount; determining a reverse DC correction coefficient and a reverse even IMD according to the downlink traffic signal, the feedback signal, and the attenuation amount a correction coefficient; outputting the inverse DC correction coefficient and the inverse even IMD correction coefficient to the feedback channel.

In a third aspect, a method for determining a correction coefficient of a common local oscillator circuit is provided, the common local oscillator circuit comprising: a forward channel, a feedback channel, and a local oscillator signal source, wherein the forward channel is configured to use a downlink service signal Converting to an RF signal, and transmitting the RF signal to an antenna; the feedback channel is configured to provide a feedback signal for compensating the downlink service signal; the local oscillator signal source is used to generate a local oscillator signal, and the local oscillator signal passes through the power splitter The two localized local oscillator signals are respectively input to the forward channel and the feedback channel, and the method includes: providing an attenuator between the forward channel and the feedback channel, wherein the attenuator is used to change the attenuation multiple times The attenuation amount of the device, and attenuating the RF signal input to a part of the feedback channel; acquiring the downlink service signal and the N attenuation amounts of the attenuator, wherein ζ is a natural number, ι=\ , 2, .. , Ν, and Ν are natural numbers; according to the feedback channel, the feedback signal outputted when the attenuator has the attenuation amount, obtains a ring corresponding to the attenuation amount ^ The total DC DC is determined according to the downlink service signal, the attenuation amount ^ and the total DC of the loop, and the reverse DC correction coefficient and the inverse even IMD correction coefficient are determined.

With reference to the third aspect, in a first possible implementation manner of the third aspect, the reverse DC correction coefficient and the reverse even time are determined according to the downlink service signal, the attenuation amount %, and the total DC voltage of the loop IMD correction factor, including:

The reverse DC correction coefficient ^ and the inverse even IMD correction coefficient are determined according to the following equation (I); ₂ :

Where x represents the downlink traffic signal; {|JC| ² } represents the average of |JC| ² ; N≥3; is a natural number, z=l, ..., N, and N is a natural number; The sum of the DC components of the forward and even IMDs.

In conjunction with the third aspect, in a second possible implementation manner of the third aspect, the downlink traffic signal, the attenuation amount, and the total DC of the loop are determined. . _w . Determine the reverse DC correction factor and the inverse even IMD correction factor, including:

The reverse DC correction coefficient ^ and the inverse even IMD correction coefficient are determined according to the following equation (II);

(II)

Where / is a natural number, /=1, 2, L, and L is a natural number; X represents the downlink traffic signal; represents the average of |f; represents the reverse DC correction coefficient; N≥L+2; I is a natural number , z = l , 2, ... , N, and N is a natural number; represents the sum of the DC components of the forward DC and the forward even IMD.

With reference to the third aspect, the first or the second possible implementation manner of the third aspect, in a third possible implementation manner of the third aspect, the attenuator is disposed between the forward channel and the feedback channel The method includes: arranging the attenuator and the switch in series between the forward channel and the feedback channel.

With reference to the third aspect, or any one of the first to the third possible implementation manners of the third aspect, in a fourth possible implementation manner of the third aspect, the method further includes: Providing a phase shifter in series with the attenuator between the forward channel and the feedback channel, or setting the phase shifter in a path of the local oscillator signal source providing the local oscillator signal to the feedback channel; acquiring the phase shift The phase shift amount of the device; wherein, according to the downlink traffic signal, the attenuation amount ^ and the total DC of the loop. ^. , determining a reverse DC correction coefficient and a reverse even IMD correction coefficient, including: according to the phase shift amount, The downlink traffic signal, the attenuation amount ^, and the total DC of the loop. _w . Determine the reverse DC correction coefficient and the inverse even IMD correction coefficient.

Based on the above technical solution, the common local oscillator circuit, the transmitting system and the method for determining the correction coefficient of the common local oscillator circuit according to the embodiments of the present invention, by setting an attenuator between the forward channel and the feedback channel, and changing the attenuator by multiple times The amount of attenuation, which can determine the reverse DC correction coefficient and the inverse even IMD correction coefficient based on the signal value corresponding to the attenuation amount, thereby enabling forward DC, forward even IMD, reverse DC, and reverse coupling. The four physical quantities of the secondary IMD are effectively separated, and the system can be accurately compensated and corrected based on the four separate physical quantities, thereby improving the calibration performance of the system and improving the emission performance of the system. DRAWINGS

In order to more clearly illustrate the technical solutions of the embodiments of the present invention, the drawings to be used in the embodiments of the present invention will be briefly described below. It is obvious that the drawings described below are only some embodiments of the present invention, Those skilled in the art can also obtain other drawings based on these drawings without paying any creative work.

1 is a schematic block diagram of a common local oscillator circuit in accordance with an embodiment of the present invention.

2 is another schematic block diagram of a common local oscillator circuit in accordance with an embodiment of the present invention.

3A and 3B are still further schematic block diagrams of a common local oscillator circuit according to an embodiment of the present invention. 4 is still another schematic block diagram of a common local oscillator circuit in accordance with an embodiment of the present invention.

FIG. 5 is still another schematic block diagram of a common local oscillator circuit in accordance with an embodiment of the present invention.

6 is a schematic block diagram of a transmitting system in accordance with an embodiment of the present invention.

7 is a schematic flow chart of a method of determining a correction coefficient of a common local oscillator circuit in accordance with an embodiment of the present invention.

Figure 8 is another schematic flow diagram of a method of determining a correction factor for a common local oscillator circuit in accordance with an embodiment of the present invention.

Figure 9 is a schematic block diagram of an apparatus for determining a correction coefficient of a common local oscillator circuit in accordance with an embodiment of the present invention. detailed description

The technical solutions in the embodiments of the present invention will be clearly and completely described in the following with reference to the accompanying drawings in the embodiments of the present invention. It is obvious that the described embodiments are a part of the embodiments of the present invention, and It is all embodiments. All other embodiments obtained by those skilled in the art based on the embodiments of the present invention without creative efforts shall fall within the scope of the present invention.

It should be understood that the technical solutions of the embodiments of the present invention can be applied to various communication systems, such as: Global System of Mobile communication ("GSM") system, Code Division Multiple Access (Code Division Multiple Access, referred to as "CDMA") system, Wideband Code Division Multiple Access ("WCDMA") system, General Packet Radio Service ("GPRS"), Long Term Evolution (Long Term Evolution, Referred to as "LTE" system, LTE frequency division duplex ("FDD") system, LTE time division duplex ("TDD"), universal mobile communication system (Universal Mobile Telecommunication) System, referred to as "UMTS" or Global Interoperability for Microwave Access ("WiMAX") communication system.

It should also be understood that, in the embodiment of the present invention, the base station may be a base station (Base Transceiver Station, referred to as "BTS") in GSM or CDMA, or may be a base station (NodeB, referred to as "NB") in WCDMA. It may be an Evolved Node B (abbreviated as 'ΈΝΒ or e-NodeB') in LTE, and the present invention is not limited thereto.

FIG. 1 shows a schematic block diagram of a common local oscillator circuit 100 in accordance with an embodiment of the present invention. As shown in FIG. 1, the common local oscillator circuit 100 includes:

The forward channel 110 is configured to convert the downlink service signal into a radio frequency signal, and send the radio frequency signal to the antenna;

The feedback channel 120 is configured to provide a feedback signal for compensating the downlink service signal; the local oscillator signal source 130 is configured to generate a local oscillator signal, and the two local oscillator signals formed by the local oscillator signal after the power splitter are respectively input to the local oscillator signal The forward channel 110 and the feedback channel 120;

The attenuator 140 is disposed between the forward channel 110 and the feedback channel 120. The attenuator 140 is configured to change the attenuation amount of the attenuator 140 a plurality of times, and perform a part of the RF signal input to the feedback channel 120. Attenuation; and

The DC and even IMD calculation module 150 is configured to acquire the downlink service signal, the feedback signal, and the attenuation amount, and determine a reverse DC correction coefficient and a reverse even time according to the downlink service signal, the feedback signal, and the attenuation amount. IMD correction coefficient; the reverse DC correction coefficient and the inverse even IMD correction coefficient are output to the feedback channel 120.

Specifically, as shown in FIG. 1, the common local oscillator circuit 100 according to an embodiment of the present invention may include: a forward channel 110, a feedback channel 120, a local oscillator signal source 130, an attenuator 140, and a DC and even IMD calculation module 150, wherein the downlink traffic signal can be input to the forward channel 110 and the DC and even IMD calculation module 150; The forward channel 110 can compensate and correct the downlink traffic signal according to the forward DC correction coefficient and the forward even IMD correction coefficient input by the DC and even IMD calculation module 150, and is based on the input of the local oscillator signal source 130. The vibration signal converts the compensated downlink service signal into a radio frequency signal; the radio frequency signal is mainly transmitted through an antenna, for example, can be sent to a terminal through an antenna, and a part of the radio frequency signal can also be input to the attenuator 140.

The attenuator 140 is disposed between the forward channel 110 and the feedback channel 120. The attenuator 140 has a plurality of attenuation values, can change the attenuation amount multiple times, and attenuate a part of the RF signal input to the attenuator 140, and Input to the feedback channel 120; the feedback channel 120 can be based on the attenuated RF signal, the local oscillator signal, and the reverse DC correction coefficient and the reverse even IMD correction coefficient input by the DC and even IMD calculation module 150 The DC and even IMD calculation module 150 inputs a feedback signal to compensate for the downlink service signal; wherein the local oscillator signal generated by the local oscillator signal source 130 can form two local oscillator signals through the power splitter, and one local oscillator signal input To the forward channel 110, another local oscillator signal is input to the feedback channel 120.

Therefore, the common local oscillator circuit of the embodiment of the present invention can determine the reverse direction according to the signal value corresponding to the attenuation amount by setting an attenuator between the forward channel and the feedback channel and changing the attenuation amount of the attenuator a plurality of times. The DC correction factor and the inverse even IMD correction coefficient, thereby being able to effectively separate the four physical quantities of forward direct current, forward even IMD, reverse direct current and reverse even IMD, and can be based on the four separate The physical quantity, which accurately compensates and corrects the system, can improve the calibration performance of the system and improve the emission performance of the system.

It should be understood that, in the embodiment of the present invention, the common local oscillator circuit can correct the feedback channel according to the determined reverse DC correction coefficient and the reverse even IMD correction coefficient, so that the feedback channel has no distortion, thereby determining forward DC. Correction factor and forward even IMD correction coefficient, thereby further effectively separating four physical quantities of forward direct current, forward even IMD, reverse direct current and reverse even IMD; and DC and even IMD calculation modules The forward DC correction coefficient and the forward even IMD correction coefficient can be further output to the forward channel to improve the correction performance and the emission performance of the system.

Hereinafter, a common local oscillation circuit according to an embodiment of the present invention will be described in detail by taking a common local oscillation circuit shown in FIG. 2 as an example. Specifically, as shown in FIG. 2, the forward channel 110 includes a forward DC and even IMD compensation module 111 and a quadrature modulation transmitter 112, and the feedback channel 120 includes reverse DC and even IMD. a compensation module 121 and a quadrature demodulation receiver 122, wherein

The forward DC and even IMD compensation module 111 is configured to: compensate the received downlink service signal according to the forward DC correction coefficient and the forward even IMD correction coefficient input by the DC and even IMD calculation module 150, And outputting the compensated downlink service signal to the orthogonal modulation transmitter 112;

The quadrature modulation transmitter 112 is configured to: modulate the compensated downlink service signal into a radio frequency signal according to the local oscillator signal, and output the radio frequency signal to the antenna and the attenuator 140; the quadrature demodulation receiving The machine 122 is configured to: demodulate the attenuated radio frequency signal according to the local oscillator signal, and output the demodulated baseband demodulated signal to the reverse DC and even IMD compensation module 121;

The reverse DC and even IMD compensation module 121 is configured to: compensate the baseband demodulated signal according to the reverse DC correction coefficient and the reverse even IMD correction coefficient to generate the compensated feedback signal.

In the embodiment of the present invention, as shown in FIG. 2, the orthogonal modulation transmitter 112 is a type of a transmitter, and the orthogonal modulation transmitter 112 may include a Quadrature Modulator ("QM" for short). And Power Amplifier (referred to as "PA"). The input of the QM may be an analog baseband signal, for example, an I signal and a Q signal. The two signals are modulated by the local oscillator signal to obtain a radio frequency signal, and the radio frequency signal is amplified by the PA. .

In the embodiment of the present invention, the orthogonal demodulation receiver 122 is a type of a receiver, and the orthogonal demodulation receiver 122 may include a Low Noise Amplifier (LNA) and an orthogonal Demodulator (Quadature Demodulator, referred to as "QDM"). The input and output signals of the LNA are both radio frequency signals, and the LNA functions to amplify the radio frequency signal to a certain amplitude to meet the QDM input signal amplitude requirement; the QDM input signal is an amplified radio frequency signal, The RF signal is demodulated by the local oscillator signal to obtain an analog baseband signal, such as an I signal and a Q signal. The reverse DC and even IMD compensation module 121 is mainly used to compensate the baseband demodulation signal to generate a compensated feedback signal.

It should be understood that the reverse DC and even IMD compensation module 121 typically compensates for digital signals. In this case, the reverse DC and even IMD compensation module 121 may include an analog to digital converter to convert the analog baseband signal input by the quadrature demodulation receiver 122 into a digital baseband signal, but the invention is not limited thereto. this.

It should be understood that in the embodiment of the present invention, the forward direct current may represent a carrier leakage signal output by a quadrature modulator in the transmitter, and the carrier leakage signal is a complex constant. For example, even if the input signal of the quadrature modulator is 0, the quadrature modulator outputs this carrier leakage signal. The carrier leakage signal usually has two sources, one source is the local oscillator signal of the quadrature modulator leaking to the output of the quadrature modulator; the other source is the number of I and Q signals set at the front end of the quadrature modulator. DC distortion of the analog converter. The DC distortion of the digital-to-analog converter refers to a non-zero DC signal that is output when the input of the digital-to-analog converter is zero.

It should be understood that in the embodiment of the invention, the reverse DC may represent the DC distortion of the quadrature demodulator output in the feedback receiver, which is also a complex constant. For example, even if the quadrature demodulator input signal is 0, the quadrature demodulator outputs this DC distortion. The DC distortion is caused by the DC of the quadrature demodulator and the DC distortion of the I and Q analog-to-digital converters. The DC distortion of the analog-to-digital converter refers to when the input of the analog-to-digital converter is 0. When outputting a non-zero DC signal.

It should also be understood that since the carrier leakage signal corresponds to the DC signal in the transmitted baseband signal, and an opposite DC signal can be added to the baseband signal to correct the carrier leakage signal, the carrier leakage signal can also It is called transmitting DC distortion. In addition, in a transmitting system with a feedback channel, the carrier leakage signal can also be referred to as forward DC to distinguish it from feedback DC or reverse DC.

It should be understood that the embodiment of the present invention is only described by taking the common local oscillator circuit shown in FIG. 2 as an example, but the present invention is not limited thereto. For example, the forward channel or the feedback channel may further include other functional modules and the like.

In the embodiment of the present invention, since an attenuator is disposed between the forward channel and the feedback channel, the attenuator has a plurality of attenuation amounts, so that a plurality of equations can be listed to forward DC and forward even IMD Effective separation from the four quantities of reverse DC and reverse even IMD.

Specifically, in the embodiment of the present invention, optionally, the DC and even IMD calculation module 150 is specifically configured to:

Obtaining the downlink service signal and the N attenuation amounts of the attenuator, where ζ is a natural number, =1, 2, ..., Ν, and Ν is a natural number; Obtaining, according to the feedback channel, a feedback signal outputted when the attenuator has the attenuation amount %, acquiring a total DC d _loop corresponding to the attenuation amount (X!, i;

The reverse DC correction coefficient and the inverse even IMD correction coefficient are determined according to the downlink traffic signal, the attenuation amount %, and the total DC of the loop.

Specifically, in the embodiment of the present invention, the DC equation of the front reverse loop can be as shown in the following equation (1):

Where ^^ denotes the total DC of the loop and is a known quantity; ^ denotes the forward DC correction coefficient; d _fi denotes the reverse DC correction coefficient; α denotes the Downlink Traffic signal to the Feedback Signal DC amplification factor, also known as loop DC amplification factor, because the DC amplification factor corresponds to the attenuation of the attenuator, therefore, the "attenuation amount of the attenuator can also be expressed, and the attenuation amount is a known amount; Forward even IMD correction coefficient, w is a natural number, m=l, 2, ..., M, and M is a natural number; indicates a reverse even IMD correction coefficient, / is a natural number, /=1, 2, L, And L is a natural number; X represents the downlink traffic signal; represents the average of |, and thus } and {| f } are known quantities.

It should be understood that the natural numbers M and L may be determined according to factors such as circuit distortion characteristics, correction accuracy, or circuit implementation cost, which are not limited by the embodiment of the present invention.

It is assumed that the sum of the DC components of the forward DC correction and the forward even IMD is, where, is determined by the following equation (2):

Then the above equation (1) can be expressed by the following equation (3): dioo _{P + DC} ( 3 )

If the attenuator can set N attenuations, where , , is a natural number,

2, ..., Ν, and Ν are natural numbers, then according to the attenuation amount, the total DC of the loop corresponding to the attenuation amount can be obtained. _w , from which the total DC equations (4.1) to (4.N) of the N loops can be constructed:

} + ^d fi = ^d loo _P , 2 (4.2 )

+ ^d fi = ^d loop,N ( 4.N )

It is not difficult to prove that when N=L+2, the coefficient matrix of the above equation (5) is full rank, that is, the above equation (5) has a certain solution, so that 1 η− _+DC and L ^1 can be solved. ^, one L+2 unknowns. Therefore, when N=L+2, the above equation (5) appears as a suitable system of equations with a unique solution; when N≥L+2, the above equation (5) appears as a system of overdetermined equations, which is unsuitable. Fixed solution, but with a unique Least Square solution.

Usually, the / in the above equation (5) takes only the even term, the most common of which is /=2, and the above equation (5) can be expressed as the following equation (6):

It should be understood that for the actual device, the above solution problem is essentially a fitting problem of nonlinear characteristics, so it is not excluded that when the highest nonlinear order is fixed, some odd-order terms are added while using even-order terms. The possibility of getting better performance. However, it is preferable to use a specific nonlinear model, which needs to be determined according to the characteristics of the device, but this is not the protection of the present invention.

In addition, it should be understood that if you do not know ( ι = \, 2, ..., Ν), but if you know the amplitude difference of the DC transmission characteristics of the attenuator between different attenuation files, you can still have the above equation (4.1 ) to (4.Ν) to solve.

Specifically, assume a known quantity 〃 ₂ = « ₂ / , μ ₃

/a, , then the above Equations (4.1) to (4.N) can be expressed by the following equations (7.1) to (7.N):

^N^ IMD ₊ DC +∑// |W f ^E {\ ^X ) ^{+ ά} β = ^d loo _P ,N ( 7.N )

1=1 Assume that the unknowns ^ and satisfy the following equations (8) and (9):

= (9) Then, the above equations (7.1) to (7.Ν) can be expressed as the following equations ( 10.1 ) to ( 10.N): o _pA (10.1) dloo _P , 2 ( 10.2 )

+∑ ί^{Η ^/ } + ^ = ^d loo ( 10.N)

1=1

It can be seen from the above equations (10.1) to (10.N) that the unknown quantity of the above equation includes 1 4, L ^ and 1 ^, and the total number of unknowns is still L + 2. Therefore, when N ≥ L + 2, the equations represented by the above equations (10.1) to (10.N) have certain solutions.

It should be understood that, in the embodiment of the present invention, according to the L and 1 ^, the reverse DC correction coefficient and the reverse even IMD correction coefficient may be determined, and the reverse even IMD of the feedback channel may still be Reverse DC is corrected, but the correction is different.

Specifically, it can be recorded that the baseband signal transmitted in the forward direction is the digital signal of the baseband signal; the I signal and the Q signal outputted by the receiver in the feedback channel after quadrature demodulation are respectively sampled by the analog-to-digital converter ADC. / («) signals and signals, signals and signals form a digital complex signal 3⁄4 («), which is represented by the following equation (11):

u(n) = i(n) + jq(n) (11) If the DC and even IMD calculation modules are determined according to the above equations (4.1) to ( 4.N ) The reverse DC correction coefficient ^ and the reverse even IMD correction coefficient and the attenuation of the attenuator are set such that the process of compensating the reverse even IMD and the reverse DC of the receiver in the feedback channel is as follows (12) ) shows:

Where d _fl (/ = 1~ ) are the inverse DC correction coefficient and the inverse even IMD correction coefficient calculated according to the equations (4.1) to (4.N), respectively; χ _τ ή indicates the baseband signal) Delay τ version of the sample; r represents the delay of the complex signal from the forward baseband signal to the receiver output, the r may not be an integer; the compensated signal is also a complex signal. If the DC and even IMD calculation modules determine the inverse DC correction coefficient ^ and the inverse even IMD correction coefficient _i according to the above equations ( 10.1 ) to ( 10.N), and the attenuation of the attenuator is set to % Then, the process of compensating the reverse even IMD and the reverse DC of the receiver in the feedback channel is as shown in the following equation (13):

= u(n) -ά _β -^ (") ί ( 13 ) where ^ and 4 (/ = 1~ ) are the inverse DC corrections calculated according to the equations (10.1) to (10.N), respectively. Coefficient and inverse even IMD correction factor; χ _Τ (η) has the meaning as described above. If the DC and even IMD calculation modules are based on the above equations ( 10.1 ) to ( 10.N), the reverse DC correction is determined. The coefficient ^ and the inverse even IMD correction factor 〖, and the attenuation of the attenuator is set to / = 2~ N , then the process of compensating the reverse even IMD and the reverse DC of the receiver in the feedback channel is as follows (14) shown: i 2 2 ~ Ν ( 14 )

The meaning of each parameter is as described above, and details are not described herein again.

Therefore, in the embodiment of the present invention, optionally, the DC and even IMD calculation module 150 determines the downlink traffic signal, the attenuation amount ^, and the total DC voltage of the loop. ^. , Determine the reverse DC school

Where x represents the downlink traffic signal; {|JC| ² } represents the average of |JC| ² ; N≥3; is a natural number, z=l, 2, ..., N, and N is a natural number; The sum of the DC components of the direct current and forward even IMD.

It should be understood that, in the embodiment of the present invention, the common local oscillator circuit can correct the feedback channel according to the determined reverse DC correction coefficient and the reverse even IMD correction coefficient, so that the feedback channel has no distortion, thereby determining forward DC. Correction factor and forward even IMD correction coefficient, thereby further effectively separating four physical quantities of forward direct current, forward even IMD, reverse direct current and reverse even IMD; and DC and even IMD calculation modules The forward DC correction coefficient and the forward even IMD correction coefficient can be further output to the forward channel to improve the correction performance and the emission performance of the system. Those skilled in the art can also determine the forward DC correction coefficient and the forward even IMD correction coefficient according to other methods, but this is not within the protection scope of the present invention, and the embodiment of the present invention is not limited thereto.

In the embodiment of the present invention, optionally, the DC and even IMD calculation module 150 is configured according to the downlink traffic signal, the attenuation amount, and the total DC DC of the loop. ^. , Determine the reverse DC correction coefficient and the reverse even IMD correction factor, including:

The DC and even IMD calculation module 150 determines the reverse DC correction coefficient ^ and the inverse even IMD correction coefficient _Y1 according to the following equation (II):

(II)

Where / is a natural number, /=1, 2, L, and L is a natural number; X represents the downlink traffic signal; {| f} represents the average value of | f; ^ represents the reverse DC correction coefficient; N ≥ L+ 2; I is a natural number, z = l, 2, ..., N, and N is a natural number; represents the sum of the DC components of the forward DC and the forward even IMD. Therefore, the common local oscillator circuit of the embodiment of the present invention can determine the reverse direction according to the signal value corresponding to the attenuation amount by setting an attenuator between the forward channel and the feedback channel and changing the attenuation amount of the attenuator a plurality of times. The DC correction factor and the inverse even IMD correction coefficient, thereby being able to effectively separate the four physical quantities of forward direct current, forward even IMD, reverse direct current and reverse even IMD, and can be based on the four separate The physical quantity, which accurately compensates and corrects the system, can improve the calibration performance of the system and improve the emission performance of the system.

In the embodiment of the present invention, optionally, as shown in FIGS. 3A and 3B, the common local oscillator circuit 100 further includes a switch 160, wherein the switch 160 is disposed in series with the attenuator 140 in the forward channel 110 and Between the feedback channels 120.

Specifically, for example, as shown in FIG. 3A, the radio frequency signal output from the quadrature modulation transmitter 112 is output to the attenuator 140 via the switch 160. Similarly, as shown in FIG. 3B, the RF signal output by the orthogonal modulation transmitter 112 is mainly transmitted through an antenna, and a part of the RF signal is input to the attenuator 140. After the attenuation, the RF signal is output through the switch 160 to the positive The demodulation receiver 122 is delivered.

By the two states of the switch 160 being turned on and off, the DC equations of the front reverse loops in the two states can be respectively obtained, that is, in the case where the attenuation amount of the attenuator 140 is constant, more DC can be obtained. Equation, to better determine the four correction coefficients of the reverse DC correction coefficient and the inverse even IMD correction coefficient.

In the embodiment of the present invention, optionally, as shown in FIGS. 4 and 5, the common local oscillator circuit 100 further includes a phase shifter 170, wherein the local oscillator signal output by the local oscillator signal source 130 is phase shifted by the phase shifter The phase shifter 170 is phase-shifted and outputted to the feedback channel 120, or the RF signal outputted by the forward channel 110 is phase-shifted by the phase shifter 170 and output to the feedback channel 120.

It should be understood that adding a phase shifter in the common local oscillator circuit according to an embodiment of the present invention is equivalent to changing the phase of the signal, and also obtaining a front reverse loop of the phase shifter with different phase shift amounts. The DC equation can be solved to separate the IQ image distortion of the forward and feedback channels. Therefore, in the embodiment of the present invention, on the one hand, not only the four correction coefficients of the forward DC correction coefficient, the forward even IMD correction coefficient, the reverse DC correction coefficient, and the reverse even IMD correction coefficient can be determined, on the other hand, It is also possible to separate the IQ image distortion of the forward channel and the feedback channel, thereby improving the correction performance of the system and improving the emission performance of the system.

It should be understood that the embodiment of the present invention is only described by taking the common local oscillator circuit shown in FIG. 4 and FIG. 5 as an example, but the present invention is not limited thereto. For example, the common local oscillator circuit according to the embodiment of the present invention may not be set as The switch 160 shown in FIG. 4 or FIG. 5; for example, the common local oscillation circuit according to the embodiment of the present invention may not be provided with the attenuator 140 as shown in FIG. 4 or FIG. 5, but only the phase shifter 170.

Therefore, the common local oscillator circuit of the embodiment of the present invention can determine the reverse direction according to the signal value corresponding to the attenuation amount by setting an attenuator between the forward channel and the feedback channel and changing the attenuation amount of the attenuator a plurality of times. The DC correction factor and the inverse even IMD correction coefficient, thereby being able to effectively separate the four physical quantities of forward direct current, forward even IMD, reverse direct current and reverse even IMD, and can be based on the four separate On the other hand, by setting the phase shifter in the common local oscillator circuit, it is also possible to separate the IQ image distortion of the forward channel and the feedback channel, which can accurately compensate and correct the system, thereby improving the correction performance of the system. And can improve the system's launch performance.

Figure 6 shows a schematic block diagram of a transmitting system 200 in accordance with an embodiment of the present invention. As shown in Figure 6, the launch system includes:

a common local oscillator circuit according to an embodiment of the present invention;

An antenna for transmitting a radio frequency signal input by the common local oscillator circuit,

Wherein, the common local oscillator circuit comprises:

a forward channel, configured to convert a downlink service signal into a radio frequency signal, and send the radio frequency signal to the antenna;

a feedback channel, configured to provide a feedback signal for compensating the downlink service signal;

a local oscillator signal source, configured to generate a local oscillator signal, wherein the two local oscillator signals formed by the local oscillator signal after being passed through the power splitter are respectively input to the forward channel and the feedback channel;

An attenuator disposed between the forward channel and the feedback channel, the attenuator for repeatedly varying the attenuation of the attenuator and attenuating the RF signal input to a portion of the feedback channel; and

a DC and an even IMD calculation module, configured to acquire the downlink service signal, the feedback signal, and the attenuation amount; and determine a reverse DC correction coefficient and a reverse even IMD according to the downlink service signal, the feedback signal, and the attenuation amount a correction coefficient; the inverse DC correction coefficient and the inverse even IMD correction coefficient are output to the feedback channel.

Therefore, in the transmitting system of the embodiment of the present invention, by setting an attenuator between the forward channel and the feedback channel, and by changing the attenuation amount of the attenuator a plurality of times, the signal value corresponding to the attenuation amount can be determined to determine the reverse direction. The DC correction factor and the inverse even IMD correction coefficient, thereby being able to effectively separate the four physical quantities of forward direct current, forward even IMD, reverse direct current and reverse even IMD, and can be based on the four separate Physical quantity, accurate compensation and correction of the system, which can improve the system The calibration performance is improved and the system's emission performance can be improved.

In the embodiment of the present invention, the DC and even IMD calculation module is specifically configured to: obtain the downlink service signal and the N attenuation amounts of the attenuator, where ζ is a natural number, =1, 2, ... , Ν, and Ν is a natural number;

Obtaining a total DC of the loop corresponding to the attenuation amount according to the feedback signal outputted by the feedback channel when the attenuator has the attenuation amount %;

In the embodiment of the present invention, optionally, the DC and even IMD calculation modules are configured according to the downlink service signal, the attenuation amount, and the total DC of the loop. . _w ., determining the reverse DC correction coefficient and the inverse even IMD correction coefficient, including:

The DC and even IMD calculation module determines the reverse DC correction coefficient ^ and the inverse even IMD positive coefficient γ ₇ according to the following equation (I)

Where x represents the downlink traffic signal; {|JC| ² } represents the average of |jf; N≥3; is a natural number, z=l, 2, ..., N, and N is a natural number; The sum of the DC components of the forward and even IMDs.

In the embodiment of the present invention, optionally, the DC and even IMD calculation module determines the reverse DC correction coefficient and the reverse couple according to the downlink service signal, the attenuation amount, and the total DC voltage of the loop. Secondary IMD correction factor, including:

The DC and even IMD calculation module determines the reverse DC correction system according to the following equation (II)

Where / is a natural number, /=1, 2, L, and L is a natural number; X represents the downlink traffic signal; {| f } represents the average of |f; ^ denotes the reverse DC correction coefficient; N≥L+ 2; I is a natural number, z=l, 2, ..., N, and N is a natural number; represents the sum of the DC components of the forward DC and the forward even IMD.

In an embodiment of the present invention, optionally, the forward channel includes a forward DC and even IMD compensation module and a quadrature modulation transmitter, and the feedback channel includes a reverse DC and even IMD compensation module and quadrature demodulation Receiver, wherein

The forward DC and even IMD compensation module is configured to: compensate the received downlink service signal according to the forward DC correction coefficient and the forward even IMD correction coefficient input by the DC and even IMD calculation module, and The compensated downlink service signal is output to the orthogonal modulation transmitter; the orthogonal modulation transmitter is configured to: modulate the compensated downlink service signal into a radio frequency signal according to the local oscillator signal, and output the radio frequency signal To the antenna and the attenuator;

The quadrature demodulation receiver is configured to: demodulate the attenuated radio frequency signal according to the local oscillator signal, and output the demodulated baseband demodulated signal to the reverse DC and even IMD compensation module ;

The reverse DC and even IMD compensation module is configured to: compensate the baseband demodulated signal according to the reverse DC correction coefficient and the reverse even IMD correction coefficient to generate the compensated feedback signal.

In the embodiment of the present invention, optionally, the common local oscillator circuit further includes a switch, wherein the switch is disposed in series with the attenuator and disposed between the forward channel and the feedback channel.

In an embodiment of the present invention, the common local oscillator circuit further includes a phase shifter, wherein the local oscillator signal output by the local oscillator signal source is phase-shifted by the phase shifter and output to the feedback channel, or The RF signal output by the forward channel is phase-shifted by the phase shifter and output to the feedback channel.

It should be understood that the common local oscillator circuit 210 in the transmitting system according to the embodiment of the present invention may correspond to the common local oscillator circuit 100 in the embodiment of the present invention. For brevity, no further details are provided herein.

Therefore, in the transmitting system of the embodiment of the present invention, by setting an attenuator between the forward channel and the feedback channel, and by changing the attenuation amount of the attenuator a plurality of times, the signal value corresponding to the attenuation amount can be determined to determine the reverse direction. The DC correction factor and the inverse even IMD correction coefficient, thereby being able to effectively separate the four physical quantities of forward direct current, forward even IMD, reverse direct current and reverse even IMD, and can be based on the four separate The physical quantity, which accurately compensates and corrects the system, can improve the calibration performance of the system and improve the emission performance of the system. A common local oscillator circuit and a transmitting system according to an embodiment of the present invention are described in detail above with reference to FIGS. 1 through 6. Hereinafter, the correction for determining the common local oscillator circuit according to an embodiment of the present invention will be described in detail with reference to FIGS. 7 through 9. Method and device for coefficients.

FIG. 7 shows a schematic flow diagram of a method 200 of determining a correction factor for a common local oscillator circuit in accordance with an embodiment of the present invention. As shown in FIG. 7, the common local oscillator circuit includes: a forward channel, a feedback channel, and a local oscillator signal source, wherein the forward channel is configured to convert a downlink service signal into a radio frequency signal, and send the radio frequency signal to the antenna; The feedback channel is used for the feedback signal for compensating the downlink service signal; the local oscillator signal source is used for generating the local oscillator signal, and the two local oscillator signals formed by the local oscillator signal after passing through the power splitter are respectively input to the forward direction The channel and the feedback channel are characterized in that the method 500 includes:

S510, an attenuator is disposed between the forward channel and the feedback channel, wherein the attenuator is configured to change the attenuation of the attenuator multiple times, and attenuate the RF signal input to a part of the feedback channel;

S520: Obtain the downlink service signal and the N attenuation amounts of the attenuator, where ζ· is a natural number, =1, 2, ..., Ν, and Ν is a natural number;

S530. Acquire a loop total DC corresponding to the attenuation amount % according to the feedback signal outputted by the feedback channel when the attenuator has the attenuation amount. ^. ;

S540. According to the downlink service signal, the attenuation amount, and the total DC of the loop. _w . Determine the reverse DC correction factor and the inverse even IMD correction factor.

Therefore, the method for determining the correction coefficient of the common local oscillator circuit according to the embodiment of the present invention can set the attenuator between the forward channel and the feedback channel, and by changing the attenuation amount of the attenuator multiple times, according to the attenuation amount. The signal value, the inverse DC correction coefficient and the reverse even IMD correction coefficient are determined, thereby being able to effectively separate the four physical quantities of forward direct current, forward even IMD, reverse direct current and reverse even IMD, and capable of Based on these four separate physical quantities, the system is accurately compensated and corrected, thereby improving the correction performance of the system and improving the emission performance of the system.

In the embodiment of the present invention, optionally, the downlink traffic signal, the attenuation amount, and the total DC of the loop. . . _w, determining a reverse current correction coefficient and even-order IMD reverse correction coefficient, comprising: the following equation (the I), a correction coefficient for determining the current reverse ^ and the even-order IMD reverse correction coefficient; _2:

In the embodiment of the present invention, optionally, the downlink traffic signal, the attenuation amount, and the total DC of the loop. . . _w, determining a reverse current correction coefficient and even-order IMD reverse correction coefficient, comprising: the following equation (II), a correction coefficient for determining the current reverse ^ and the even-order IMD reverse correction coefficient; ^:

Where / is a natural number, /=1, 2, L, and L is a natural number; X represents the downlink traffic signal; {| f} represents the average value of | f; ^ represents the reverse DC correction coefficient; N ≥ L+ 2; is a natural number, z = l, 2, ..., N, and N is a natural number; represents the sum of the DC components of the forward DC and the forward even IMD.

In the embodiment of the present invention, optionally, the attenuating device is disposed between the forward channel and the feedback channel, including:

The attenuator and the switch are arranged in series between the forward channel and the feedback channel.

In the embodiment of the present invention, optionally, as shown in FIG. 8, the method 500 further includes:

S550, a phase shifter connected in series with the attenuator is disposed between the forward channel and the feedback channel, or the phase shifter is disposed in a path of the local oscillator signal source providing the local oscillator signal to the feedback channel; S560 Obtaining the phase shift amount of the phase shifter;

The determining the reverse DC correction coefficient and the inverse even IMD correction coefficient according to the downlink service signal, the attenuation amount %, and the total DC of the loop, include:

S541, according to the phase shift amount, the downlink service signal, the attenuation amount, and the total DC of the loop d _{loop i} , determining the reverse DC correction coefficient and the inverse even IMD correction coefficient.

It should be understood that, in various embodiments of the present invention, the size of the sequence numbers of the above processes does not mean the order of execution, and the order of execution of each process should be determined by its function and internal logic, and should not be taken to the embodiments of the present invention. The implementation process constitutes any limitation.

It should also be understood that the common local oscillator circuit applied by the method 500 according to the embodiment of the present invention may correspond to the common local oscillator circuit 100 in the embodiment of the present invention, or may correspond to the total transmit system 200 in the embodiment of the present invention. The local oscillator circuit 210 is not described herein for brevity.

As shown in FIG. 9, an embodiment of the present invention further provides an apparatus 700 for determining a correction coefficient of a common local oscillator circuit, the apparatus 700 including a processor 710, a memory 720, and a bus system 730. The processor 710 and the memory 720 are connected by a bus system 730, where the memory 720 is used to store instructions, and the processor 710 is configured to execute instructions stored in the memory 720;

The common local oscillator circuit includes: a forward channel, a feedback channel, and a local oscillator signal source, wherein the forward channel is configured to convert the downlink service signal into a radio frequency signal, and send the radio frequency signal to the antenna; a feedback signal for compensating the downlink service signal; the local oscillator signal source is configured to generate a local oscillator signal, and the two local oscillator signals formed by the local oscillator signal after being passed through the power splitter are respectively input to the forward channel and the feedback Channel; the processor 710 is used to:

An attenuator is disposed between the forward channel and the feedback channel, wherein the attenuator is configured to change the attenuation of the attenuator multiple times, and attenuate the RF signal input to a portion of the feedback channel;

Obtaining the downlink service signal and the N attenuation amounts of the attenuator, where z is a natural number, =1, 2, ..., N, and N is a natural number;

Obtaining a total DC of the loop corresponding to the attenuation amount according to the feedback signal outputted by the feedback channel when the attenuator has the attenuation amount;

And determining a reverse DC correction coefficient and a reverse even IMD correction coefficient according to the downlink service signal, the attenuation amount %, and the total DC voltage of the loop. Therefore, the apparatus for determining the correction coefficient of the common local oscillator circuit according to the embodiment of the present invention can set the attenuator between the forward channel and the feedback channel, and by changing the attenuation amount of the attenuator a plurality of times, according to the attenuation amount. The signal value, the inverse DC correction coefficient and the reverse even IMD correction coefficient are determined, thereby being able to effectively separate the four physical quantities of forward direct current, forward even IMD, reverse direct current and reverse even IMD, and capable of Based on these four separate physical quantities, the system is accurately compensated and corrected, thereby improving the correction performance of the system and improving the emission performance of the system.

It should be understood that, in the embodiment of the present invention, the processor 710 may be a central processing unit ("CPU"), and the processor 710 may also be other general-purpose processors, digital signal processors (DSPs). , an application specific integrated circuit (ASIC), an off-the-shelf programmable gate array (FPGA) or other programmable logic device, discrete gate or transistor logic device, discrete hardware component, and the like. The general purpose processor may be a microprocessor or the processor or any conventional processor or the like.

The memory 720 can include read only memory and random access memory and provides instructions and data to the processor 710. A portion of memory 720 may also include non-volatile random access memory. For example, the memory 720 can also store information of the device type.

The bus system 730 can include, in addition to the data bus, a power bus, a control bus, and a status signal bus. However, for clarity of description, various buses are labeled as bus system 730 in the figure.

In the implementation process, the steps of the foregoing methods may be completed by an integrated logic circuit of hardware in the processor 710 or an instruction in the form of software. The steps of the method disclosed in the embodiments of the present invention may be directly implemented as a hardware processor, or may be performed by a combination of hardware and software modules in the processor. The software modules can be located in random memory, flash memory, read only memory, programmable read only memory or electrically erasable programmable memory, registers, etc., which are well established in the art. The storage medium is located in the memory 720. The processor 710 reads the information in the memory 720 and combines the hardware to perform the steps of the above method. To avoid repetition, it will not be described in detail here.

Optionally, as an embodiment, the processor 710 is configured according to the downlink service signal, the attenuation, and the total DC of the loop 4. ^. , Determine the reverse DC correction factor and the inverse even IMD correction factor, including:

Optionally, as an embodiment, the processor 710 is configured to determine the downlink traffic signal, the attenuation amount, and the total DC of the loop. ^. , Determine the reverse DC correction factor and the inverse even IMD correction factor, including:

The reverse DC correction coefficient ^ and the inverse even IMD correction coefficient are determined according to the following equation (II):

Where x represents the downlink traffic signal; {|JC| ² } represents the average of μ| ² ; Ν ≥ 3 ; is a natural number, , 2, ..., Ν, and Ν is a natural number; The sum of the DC components of the even IMD.

Optionally, as an embodiment, the processor 710 is configured to set an attenuator between the forward channel and the feedback channel, including: the attenuator and the switch are disposed in series between the forward channel and the feedback channel.

Optionally, as an embodiment, the processor 710 is further configured to:

Providing a phase shifter in series with the attenuator between the forward channel and the feedback channel, or setting the phase shifter in a path of the local oscillator signal source providing the local oscillator signal to the feedback channel;

Obtaining the phase shift amount of the phase shifter;

The processor 710 determines a reverse DC correction coefficient and a reverse even IMD correction coefficient according to the downlink service signal, the attenuation amount, and the total DC d _{loop i of the loop} , including:

The reverse DC correction coefficient and the inverse even IMD correction coefficient are determined according to the phase shift amount, the downlink traffic signal, the attenuation amount %, and the total loop DC of the loop. Therefore, the apparatus for determining the correction coefficient of the common local oscillator circuit according to the embodiment of the present invention can set the attenuator between the forward channel and the feedback channel, and by changing the attenuation amount of the attenuator a plurality of times, according to the attenuation amount. The signal value, the inverse DC correction coefficient and the reverse even IMD correction coefficient are determined, thereby being able to effectively separate the four physical quantities of forward direct current, forward even IMD, reverse direct current and reverse even IMD, and capable of Based on these four separate physical quantities, the system is accurately compensated and corrected, thereby improving the correction performance of the system and improving the emission performance of the system.

It should be understood that in the embodiment of the present invention, "B corresponding to A" means that B is associated with A, and 8 can be determined based on A. However, it should be understood that determining B according to A does not mean that B is determined only on the basis of A, but also based on A and/or other information.

Those of ordinary skill in the art will appreciate that the elements and algorithm steps of the various examples described in connection with the embodiments disclosed herein can be implemented in electronic hardware, computer software or a combination of both, in order to clearly illustrate hardware and software. Interchangeability, the composition and steps of the various examples have been generally described in terms of function in the above description. Whether these functions are performed in hardware or software depends on the specific application and design constraints of the solution. A person skilled in the art can use different methods for implementing the described functions for each particular application, but such implementation should not be considered to be beyond the scope of the present invention.

A person skilled in the art can clearly understand that, for the convenience and brevity of the description, the specific working process of the system, the device and the unit described above can refer to the corresponding process in the foregoing method embodiment, and details are not described herein again.

In the several embodiments provided herein, it should be understood that the disclosed systems, devices, and methods may be implemented in other ways. For example, the device embodiments described above are merely illustrative. For example, the division of the unit is only a logical function division. In actual implementation, there may be another division manner, for example, multiple units or components may be combined or Can be integrated into another system, or some features can be ignored, or not executed. In addition, the mutual coupling or direct coupling or communication connection shown or discussed may be an indirect coupling or communication connection through some interface, device or unit, or an electrical, mechanical or other form of connection. The components displayed for the unit may or may not be physical units, ie may be located in one place, or may be distributed over multiple network units. Some or all of the units may be selected according to actual needs to achieve the objectives of the embodiments of the present invention.

In addition, each functional unit in various embodiments of the present invention may be integrated in one processing unit. It is also possible that each unit physically exists alone, or two or more units may be integrated in one unit. The above integrated unit can be implemented in the form of hardware or in the form of a software functional unit.

The integrated unit, if implemented in the form of a software functional unit and sold or used as a standalone product, may be stored in a computer readable storage medium. Based on such understanding, the technical solution of the present invention contributes in essence or to the prior art, or all or part of the technical solution may be embodied in the form of a software product stored in a storage medium. A number of instructions are included to cause a computer device (which may be a personal computer, server, or network device, etc.) to perform all or part of the steps of the methods described in various embodiments of the present invention. The foregoing storage medium includes: a U disk, a removable hard disk, a read-only memory (ROM), a random access memory (RAM), a magnetic disk or an optical disk, and the like, which can store program codes. .

The above is only the specific embodiment of the present invention, but the scope of the present invention is not limited thereto, and any equivalent person can be easily conceived within the technical scope of the present invention. Modifications or substitutions are intended to be included within the scope of the invention. Therefore, the scope of the invention should be determined by the scope of the claims.

Claims

Rights request

A common local oscillator circuit, wherein the common local oscillator circuit comprises:

a forward channel, configured to convert a downlink service signal into a radio frequency signal, and send the radio frequency signal to an antenna;

a feedback channel, configured to provide a feedback signal for compensating the downlink service signal; a local oscillator signal source, configured to generate a local oscillator signal, where the local oscillator signals formed by the local oscillator signal after being passed through the power splitter are respectively input to The forward channel and the feedback channel;

An attenuator disposed between the forward channel and the feedback channel, the attenuator for varying the attenuation of the attenuator multiple times, and attenuating a portion of the RF signal input to the feedback channel ; with

a DC and an even IMD calculation module, configured to: obtain the downlink service signal, the feedback signal, and the attenuation amount; determine a reverse DC correction according to the downlink service signal, the feedback signal, and the attenuation amount a coefficient and a reverse even IMD correction coefficient; outputting the reverse DC correction coefficient and the inverse even IMD correction coefficient to the feedback channel.

2. The common local oscillator circuit according to claim 1, wherein said direct current and even time

The IMD calculation module is specifically used to:

Obtaining the downlink service signal and the N attenuation amounts of the attenuator, wherein, , are natural numbers, =1, 2, ..., Ν, and Ν is a natural number;

Determining the reverse DC correction coefficient and the inverse even IMD correction coefficient according to the downlink traffic signal, the attenuation amount %, and the total loop DC of the loop.

The common local oscillator circuit according to claim 2, wherein the DC and even IMD calculation module determines the location according to the downlink service signal, the attenuation amount %, and the total loop DC of the loop. The reverse DC correction coefficient and the reverse even IMD correction coefficient include:

The DC and even IMD calculation module determines the reverse DC correction coefficient ^ and the secondary IMD correction system y ₂ according to the following equation (I):

Where x represents the downlink traffic signal; {|JC| ² } represents the average of |jf; Ν ≥ 3; , is a natural number, z = l , 2, ..., N, and N is a natural number; The sum of the DC components of the direct current and forward even IMD.

The DC and even IMD calculation module determines the reverse DC correction coefficient ^ and the reverse even IMD correction coefficient _γι according to the following equation (II):

Where / is a natural number, /=1, 2, L, and L is a natural number; X represents the downlink traffic signal; {| f } represents the average of |f; ^ represents the reverse DC correction coefficient; N≥ L+2; I is a natural number, ι=\ , 2, ... , N, and N is a natural number; represents the sum of the DC components of the forward DC and the forward even IMD.

The common local oscillator circuit according to any one of claims 1 to 4, wherein the forward channel comprises a forward DC and even IMD compensation module and a quadrature modulation transmitter, the feedback channel Including reverse DC and even IMD compensation modules and quadrature demodulation receivers, wherein

The forward DC and even IMD compensation module is configured to: compensate the received downlink service signal according to the forward DC correction coefficient and the forward even IMD correction coefficient input by the DC and even IMD calculation modules And outputting the compensated downlink service signal to the orthogonal modulation transmitter;

The quadrature modulation transmitter is configured to: modulate the compensated downlink service signal into a radio frequency signal according to the local oscillator signal, and output the radio frequency signal to the antenna and the attenuator; The quadrature demodulation receiver is configured to: demodulate the attenuated radio frequency signal according to the local oscillator signal, and output the demodulated baseband demodulation signal to the reverse DC and even IMD Compensation module

The reverse DC and even IMD compensation module is configured to: according to the reverse DC correction coefficient And the reverse even IMD correction coefficient, the baseband demodulation signal is compensated to generate the compensated feedback signal.

The common local oscillation circuit according to any one of claims 1 to 5, wherein the common local oscillation circuit further includes a switch, wherein the switch is disposed in series with the attenuator Between the forward channel and the feedback channel.

The common local oscillator circuit according to any one of claims 1 to 6, wherein the common local oscillator circuit further includes a phase shifter, wherein the local oscillator output by the local oscillator signal source The signal is phase-shifted by the phase shifter and output to the feedback channel, or the radio frequency signal output by the forward channel is phase-shifted by the phase shifter and output to the feedback channel.

8. A launch system, comprising:

a common local oscillator circuit according to any one of claims 1 to 7;

An antenna, the antenna is configured to transmit a radio frequency signal input by the common local oscillator circuit.

9. A method for determining a correction coefficient of a common local oscillator circuit, the common local oscillator circuit comprising: a forward channel, a feedback channel, and a local oscillator signal source, wherein the forward channel is configured to convert a downlink service signal into Radio frequency signal, and transmitting the radio frequency signal to the antenna; the feedback channel is configured to provide a feedback signal for compensating the downlink service signal; the local oscillator signal source is used to generate a local oscillator signal, where the local oscillator signal passes The two local oscillator signals formed after the power splitter are respectively input to the forward channel and the feedback channel, wherein the method includes:

Providing an attenuator between the forward channel and the feedback channel, wherein the attenuator is configured to change an attenuation amount of the attenuator a plurality of times, and perform a part of the radio frequency signal input to the feedback channel Attenuation

Obtaining the downlink service signal and the N attenuation amounts of the attenuator, wherein, , are natural numbers, =1, 2, ..., N, and N is a natural number;

And determining a reverse DC correction coefficient and a reverse even IMD correction coefficient according to the downlink traffic signal, the attenuation amount, and the total DC of the loop.

10. The method according to claim 9, wherein the according to the downlink service signal, the attenuation amount, and the total DC of the loop. ^. , Determine the reverse DC correction factor and the inverse even IMD correction factor, including:

Determining the reverse DC correction coefficient ^ and the reverse even IMD according to the following equation (I) Calibration system

Where x represents the downlink traffic signal; {|JC| ² } represents the average of μ| ² ; Ν ≥ 3; , is a natural number, , 2, ..., Ν, and Ν is a natural number; The sum of the DC components of the forward and even IMDs.

The method according to claim 9, wherein the determining the reverse DC correction coefficient and the reverse even IMD according to the downlink service signal, the attenuation amount, and the total DC of the loop Correction factor, including:

Determining the reverse DC correction coefficient ^ and the inverse even IMD correction coefficient according to the following equation (II);

Where / is a natural number, 1 = 1, 2, L, and L is a natural number; X represents the downlink traffic signal; {| f} represents the average of | f; ^ represents the reverse DC correction coefficient; N ≥ L+2; I is a natural number, ι=\, 2, ..., N, and N is a natural number; represents the sum of the DC components of the forward DC and the forward even IMD.

The method according to any one of claims 9 to 11, wherein the providing an attenuator between the forward channel and the feedback channel comprises:

The method according to any one of claims 9 to 12, wherein the method further comprises:

Providing a phase shifter in series with the attenuator between the forward channel and the feedback channel, or setting the path in a path in which the local oscillator signal source supplies the local oscillator signal to the feedback channel Obtaining a phase shift amount of the phase shifter;

The determining the reverse DC correction coefficient and the inverse even IMD correction coefficient according to the downlink service signal, the attenuation amount, and the total DC d _{loop i of the loop} , including:

And according to the phase shift amount, the downlink service signal, the attenuation amount, and the total DC of the loop. . , determining the reverse DC correction coefficient and the inverse even IMD correction coefficient.