WO2006067681A2 - Quadrature phase mismatch compensation in a receiver - Google Patents

Quadrature phase mismatch compensation in a receiver Download PDF

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Publication number
WO2006067681A2
WO2006067681A2 PCT/IB2005/054229 IB2005054229W WO2006067681A2 WO 2006067681 A2 WO2006067681 A2 WO 2006067681A2 IB 2005054229 W IB2005054229 W IB 2005054229W WO 2006067681 A2 WO2006067681 A2 WO 2006067681A2
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phase
predetermined signal
receiver
signal sequence
wireless channel
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PCT/IB2005/054229
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French (fr)
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WO2006067681A3 (en
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Xuecheng Qian
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Koninklijke Philips Electronics N.V.
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Publication of WO2006067681A3 publication Critical patent/WO2006067681A3/en

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    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
    • H03D3/00—Demodulation of angle-, frequency- or phase- modulated oscillations
    • H03D3/007—Demodulation of angle-, frequency- or phase- modulated oscillations by converting the oscillations into two quadrature related signals
    • H03D3/009—Compensating quadrature phase or amplitude imbalances
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
    • H03D2200/00—Indexing scheme relating to details of demodulation or transference of modulation from one carrier to another covered by H03D
    • H03D2200/0041—Functional aspects of demodulators
    • H03D2200/0082—Quadrature arrangements

Definitions

  • the present invention relates to a receiver in the field of wireless communication, and particularly, to a phase compensation method and apparatus for wireless communication receiver.
  • the heterodyne receiver is a well-known receiver structure in the field of wireless communication.
  • the signal received from the antenna is amplified by a low noise amplifier after passing through a radio frequency (RF) filter, then is switched to intermediate frequency (IF) to be further filtered and amplified therein, and next is down- switched to a baseband by a mixer.
  • RF radio frequency
  • IF intermediate frequency
  • FIG. 1 A typical structure of this type of receiver is shown in Fig. 1.
  • Usually the performance of this type of receiver is fine, but needs an IF filter, which is expensive and hard to integrate, thus having the shortcoming of high cost and large bulk.
  • a plurality of other types of receiver structures such as direct conversion and low IF receiver structures, have been widely applied to a new generation of wireless communication receiver.
  • the RF signal is directly switched to a baseband whose center frequency is zero, so it can be regarded as a simple heterodyne receiver of "IF being zero". Therefore, the direct conversion receiver is also referred to as zero IF receiver.
  • the structure of a typical zero IF receiver is shown in Fig.
  • the RF signal received by the antenna first passes through the filtering of a RF filter 10, then is amplified by low noise amplifier (LNA) 20, and thereafter is divided in two, which are switched respectively to baseband through mixers 31, 32, then complete analog-to-digital conversion respectively through analog-to-digital converters (ADC) 61, 62 and be sent to digital signal processing unit 90 for follow-up digital signal processing, and wherein low-pass filters 41, 42, 71 and 72 are needed to filter the out-of-band noise and interference.
  • ADC automatic gain controllers
  • ADC automatic gain controllers
  • the zero IF receiver shown in Fig. 2 as it omits the IF circuit needed by the conventional heterodyne receiver, enjoys obvious advantage in terms of the system complexity, cost, bulk, power consumption, and the like.
  • phase mismatch the phase difference between two local oscillator signals may vary within a certain range, such phenomenon of deviating from the phase difference of 90 degrees is called phase mismatch, which can cause image interference and thus reducing the performance of receiver.
  • the object of the present invention is to provide a phase compensation method and apparatus for wireless communication receiver.
  • the phase compensation method and apparatus compensate for the phase mismatch in time domain, thus no excessive hardware cost and power consumption will incur.
  • the method that performs phase compensation for received signal of a receiver includes the steps of: (a) acquiring from the received signal a predetermined signal sequence that undergoes wireless channel fading;
  • the wireless communication receiver includes a phase estimation means and a phase compensation means, wherein a receiving means is for receiving signal and acquiring therefrom the predetermined signal sequence that undergoes wireless channel fading.
  • the phase estimation means is for estimating the receiver's phase-related mismatch information based on the predetermined signal sequence that undergoes wireless channel fading and a corresponding known predetermined signal sequence, while the phase compensation means is for performing compensation recovery to the received signal in time domain based on the estimated phase-related mismatch information.
  • phase compensation method and apparatus of the present invention estimate and compensate for the mismatched phase in time domain and the design is comparative simple, thus will not incur excessive hardware cost and power consumption.
  • Fig. 1 is a block diagram of the structure of a conventional heterodyne receiver
  • Fig. 2 is a block diagram of the structure of a conventional zero IF receiver
  • Fig. 3 is a structural block diagram of an embodiment of the present invention being applied to a zero IF receiver
  • Fig. 4 is a detailed block diagram of the phase estimation module in the zero IF receiver illustrated in Fig. 3;
  • Fig. 5 is the structural figure of the phase compensation module in the zero IF receiver illustrated in Fig. 3;
  • Fig. 6 is the structural block diagram of an embodiment of the present invention being applied to a heterodyne receiver. Throughout the drawings, the same reference numerals indicate similar or corresponding features or functions.
  • the useful signal received by the antenna is usually located in certain bandwidth of radio frequency, and the useful signal is usually expressed as:
  • the I and Q signals outputted thereby could be represented respectively as:
  • ⁇ is the mismatched phase caused by a non-ideal local oscillator signal
  • Cp 1 and mismatched phase ⁇ are both unknown, so ⁇ 3 is also unknown.
  • A(t) and B(t) could be obtained from the foreknown signal sequence.
  • the values of Cp 1 and ⁇ 3 could be calculated by expressions (5) and (6) based on expressions (1) and (2), utilizing A(t) and B(t), and the signals I (t) and Q (t) actually received by the receiver:
  • the A(t) and B(t) of the user signal could be calculated using expressions (3) and (4).
  • User signals recovered in this manner can eliminate the influence brought by mismatched phase ⁇ .
  • the estimation of the sine and cosine functions of ⁇ L and ⁇ 3 can also be used to replace the direct estimation of ⁇ L and ⁇ 3 .
  • the I signal received consecutively at two times ti and t 2 can be used to estimate COs(Cp 1 ) and Sm(Cp 1 ) , and the following can be obtained according to expression (1):
  • I O 1 ) an d I (t 2 ) are respectively the I signals received at times ti and t 2 during the transmission of training sequence signal, while A(t L ) , B(t L ) and A(t 2 ) ,
  • B(t 2 ) are respectively the values taken at ti and t 2 by the training signal before modulation.
  • cos( ⁇ 3 ) and sin(cp 3 ) can also be obtained via the Q signals received during the transmission of training sequence signal, and the specific algorithm is shown as expressions (9) and (10):
  • Q O 1 ) and Q (t 2 ) are the Q signals received at ti and t 2 during transmission of training sequence signal.
  • the above Cp 1 and ⁇ 3 obtained based on expressions (5) and (6) or cos( ⁇ 1 ) ,
  • the phase compensation method of the receiver of the present invention mainly lies in utilizing foreknown signal sequences such as training sequence to estimate the mismatched phase so as to perform proper phase compensation when receiving user signal subsequently. Therefore, the embodiment of a receiver designed according to the above method is illustrated in Fig. 3. As compared with the traditional zero IF receiver in Fig. 2, the zero IF receiver provided by the embodiment of the present invention adds a phase estimation module 101 and a phase compensation module 102; wherein the RF signal received by the antenna is first filtered by a RF filter 10, then is divided in two by the low noise amplifier
  • phase estimation module 101 comprises a phase transient estimation module 111 and a phase mean value calculation module 121.
  • the phase transient estimation module 111 carries out expressions (5) and (6) to estimate Cp 1 and ⁇ 3 on the basis of the I and Q receiving signals outputted by low-pass filters 71, 72 and the foreknown training sequence, or carries out expressions (7) ⁇ (10) to estimate COs(Cp 1 ) , Sm(Cp 1 ) and cos( ⁇ 3 ) , sin( ⁇ 3 ) .
  • the phase mean value calculation module 121 averages the output results of the phase transient estimation module 111, then utilizes the mean value to calculate Sm(Cp 3 -(P 1 ) and outputs the averaged Cp 1 , ⁇ 3 and sin (9 3 -P 1 ) , or 008(9 ⁇ , sm ( ⁇ i) > cos( ⁇ 3 ) , sin( ⁇ 3 ) and Sm(Cp 3 -(P 1 ) to the phase compensation module 102.
  • the phase compensation module 102 on the basis of the I and Q receiving signals outputted by the low-pass filters 71, 72, and the mismatched phase outputted by phase mean value calculation module 121 and the corresponding trigonometric function value, carries out expressions (3) and (4) to acquire the phase compensated digital baseband signal.
  • Fig. 5 is the structural figure of the phase compensation module 102 in the zero IF receiver illustrated in Fig. 3, wherein the functional relationship in expressions (3) and (4) carried out by the phase compensation module 102 is shown, but the proportionality factor "2" in expressions (3) and (4) is omitted, because omitting this factor will not affect the performance of the receiver.
  • phase estimation module 101 and phase compensation module 102 could be separate digital circuit chips, or be integrated into the digital signal processing unit 90.
  • the range of mismatched phase ⁇ could be any phases
  • Fig. 6 is the structural block diagram of an embodiment of the present invention being applied to a heterodyne receiver, wherein the phase estimation module 101' and phase compensation module 102' respectively have basically the same function and structure with the phase estimation module 101 and phase compensation module 102 in the embodiment of Fig. 3, so will not be described in details here.
  • phase compensation method and apparatus for the receiver of the present invention perform phase compensation in time domain, so the image interference caused by the non-ideal circuit can be pretty easily. Further, it will not incur excessive hardware cost and power consumption.
  • phase compensation method and apparatus of the receiver as disclosed by the present invention can be further modified in various aspects on the basis of not breaking away from the contents of the present invention. Therefore, the scope of protection of the present invention shall be determined by the attached Claims.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Digital Transmission Methods That Use Modulated Carrier Waves (AREA)

Abstract

The present invention provides a phase compensation method and apparatus for wireless communication receiver. The phase compensation method and apparatus estimate the receiver's phase -related mismatch information based on the predetermined signal sequence that has been through wireless channel fading (e.g. training sequence) and a corresponding known predetermined signal sequence, and perform compensation for the received signal in time domain based on the estimated phase-related mismatch information, thus eliminating the problem of phase mismatching. Since the solution is fairly easy to implement, so no excessive hardware cost and power consumption will incur.

Description

PHASE COMPENSATION METHOD AND APPARATUS FOR RECEIVER
FIELD OF THE INVENTION
The present invention relates to a receiver in the field of wireless communication, and particularly, to a phase compensation method and apparatus for wireless communication receiver.
BACKGROUND OF THE INVENTION
At present, the heterodyne receiver is a well-known receiver structure in the field of wireless communication. In a heterodyne receiver, the signal received from the antenna is amplified by a low noise amplifier after passing through a radio frequency (RF) filter, then is switched to intermediate frequency (IF) to be further filtered and amplified therein, and next is down- switched to a baseband by a mixer. A typical structure of this type of receiver is shown in Fig. 1. Usually the performance of this type of receiver is fine, but needs an IF filter, which is expensive and hard to integrate, thus having the shortcoming of high cost and large bulk.
In recent years, a plurality of other types of receiver structures, such as direct conversion and low IF receiver structures, have been widely applied to a new generation of wireless communication receiver. In a direct conversion receiver, the RF signal is directly switched to a baseband whose center frequency is zero, so it can be regarded as a simple heterodyne receiver of "IF being zero". Therefore, the direct conversion receiver is also referred to as zero IF receiver. The structure of a typical zero IF receiver is shown in Fig. 2, wherein the RF signal received by the antenna first passes through the filtering of a RF filter 10, then is amplified by low noise amplifier (LNA) 20, and thereafter is divided in two, which are switched respectively to baseband through mixers 31, 32, then complete analog-to-digital conversion respectively through analog-to-digital converters (ADC) 61, 62 and be sent to digital signal processing unit 90 for follow-up digital signal processing, and wherein low-pass filters 41, 42, 71 and 72 are needed to filter the out-of-band noise and interference. Sometimes, as the circumstances require, automatic gain controllers (AGC) 51, 52 need to be added before ADC 61, 62 to reduce the dynamic variation range of signal. The zero IF receiver shown in Fig. 2, as it omits the IF circuit needed by the conventional heterodyne receiver, enjoys obvious advantage in terms of the system complexity, cost, bulk, power consumption, and the like.
In an ideal state, the phases of local oscillator signal at the input end of two mixers 31, 32 in the above zero IF receiver should differ by 90 degrees, thus the frequency spectrum will not generate distortion when the modulation signal is changed into baseband signal. However, in actual application, it is quite difficult to acquire highly accurate phase difference of 90 degrees. Besides, as the local oscillator signal contains noises, the phase difference between two local oscillator signals may vary within a certain range, such phenomenon of deviating from the phase difference of 90 degrees is called phase mismatch, which can cause image interference and thus reducing the performance of receiver.
At present, there have been multiple compensation methods for reducing or eliminating phase mismatch, but most of them, such as the one provided by the US patent application titled "Adjusting a receiver", whose inventor is Tommi Auranen and was published on January 16, 2003 under the number of US20030012305 Al, need additional analog circuits and corresponding digital control circuits when being implemented, thus increasing not only the hardware cost but the system power consumption as well. Besides, there are other compensation methods, such as the one provided by the US patent application titled "Quadrature transceiver substantially free of adverse circuitry mismatch effects", whose inventor is Jian Gu and was published on April 17, 2003 under the number of US20030072393 Al, are carried out in frequency domain. Under this circumstance, the processing of signal usually switches from time domain to frequency domain first, and then switches back to time domain after being compensated in frequency domain. To the receivers inherently having no time-frequency transform (or inverse switch), using this type of compensation method needs to add extra switch circuit, thus increasing the complexity of the receiver circuit.
Therefore, a cost-effective and easy-to-apply compensation solution with low power consumption is needed to solve the problem of phase mismatch.
OBJECT AND SUMMARY OF THE INVENTION
The object of the present invention is to provide a phase compensation method and apparatus for wireless communication receiver. The phase compensation method and apparatus compensate for the phase mismatch in time domain, thus no excessive hardware cost and power consumption will incur.
To achieve the above object, the method that performs phase compensation for received signal of a receiver provided by the present invention includes the steps of: (a) acquiring from the received signal a predetermined signal sequence that undergoes wireless channel fading;
(b) estimating the receiver's phase-related mismatch information based on the predetermined signal sequence that undergoes wireless channel fading and a corresponding known predetermined signal channel; and (c) performing compensation recovery to the received signal in time domain based on the estimated phase-related mismatch information.
To achieve the above object, the wireless communication receiver provided by the present invention includes a phase estimation means and a phase compensation means, wherein a receiving means is for receiving signal and acquiring therefrom the predetermined signal sequence that undergoes wireless channel fading. The phase estimation means is for estimating the receiver's phase-related mismatch information based on the predetermined signal sequence that undergoes wireless channel fading and a corresponding known predetermined signal sequence, while the phase compensation means is for performing compensation recovery to the received signal in time domain based on the estimated phase-related mismatch information.
Because the above phase compensation method and apparatus of the present invention estimate and compensate for the mismatched phase in time domain and the design is comparative simple, thus will not incur excessive hardware cost and power consumption.
Other objects and attainments together with a fuller understanding of the invention will become apparent and appreciated by referring to the following description and claims taken in conjunction with the accompanying drawings.
BRIEF DESCRIPTION OF THE DRAWINGS
The invention is explained in further detail, and by way of example, with reference to the accompanying drawings wherein:
Fig. 1 is a block diagram of the structure of a conventional heterodyne receiver; Fig. 2 is a block diagram of the structure of a conventional zero IF receiver;
Fig. 3 is a structural block diagram of an embodiment of the present invention being applied to a zero IF receiver;
Fig. 4 is a detailed block diagram of the phase estimation module in the zero IF receiver illustrated in Fig. 3;
Fig. 5 is the structural figure of the phase compensation module in the zero IF receiver illustrated in Fig. 3;
Fig. 6 is the structural block diagram of an embodiment of the present invention being applied to a heterodyne receiver. Throughout the drawings, the same reference numerals indicate similar or corresponding features or functions.
DETAILED DESCRIPTION OF THE INVENTION
To clearly describe the present invention, following is first a theoretical analysis of the design principle of the phase compensation method and apparatus for wireless communication receiver of the present invention, then is an introduction to the structural feature of the specific embodiment of the present invention in combination of Fig. 3 to Fig.
6.
In wireless communication system, the useful signal received by the antenna is usually located in certain bandwidth of radio frequency, and the useful signal is usually expressed as:
S(t) = A(t)cos(wct + φ1) - B(t) sin(wct + φ1 ) ,
Wherein A(t) and B(t) are baseband signals for modulating RF carrier signals w cos(wct + φL) and sin(wct -Kp1 ) , wherein, φι is carrier phase, while fc = — - is carrier
2π frequency.
After the user signal received by the antenna is mixed, the I and Q signals outputted thereby could be represented respectively as:
I(t) = S(t) * cos(wct) = -A(t)[cos(φ1) + cos(2wct + φ1)] B(t)[sin(φ1) + sin(2wct + φ1)] >
Q(t) = S(t) * sin(wct + θ) = S(t) * cos(wct + θ--) = S(t) * cos(wct + φ2)
= - A(t)[cos(φ! - φ2) + cos(2wct + Cp1 + φ2 )] — B(t)[sin(φ1 - φ2) + sin(2wct + Cp1 + φ2 )] , Where, θ is the mismatched phase caused by a non-ideal local oscillator signal,
Figure imgf000006_0001
In the above I(t) and Q(t) , the components at 2wc could be easily filtered through a low-pass filter, so the output signals after low-pass filtering are: I(t) = -A(t)cos(φ1)--B(t)sin(φ1), (D
Q(t) = -A(t)cos(φ1-φ2)--B(t)sin(φ1-φ2) = -A(t)cos(φ3)--B(t)sin(φ3), (2)
Where, φ3 =φι -φ2 =φι -(Θ-— ) = φι -θ + — .
And the following equations could be easily obtained based on expressions (1) and
(2): Λ(t) = 2[I (t) sin(φ3) - Q (t) SJn(Cp1)] (3) sinCφj-φJ
B = 2[I (t)cos(φ3)-Q (t)cos(φL)] (4) sinCψj-φJ
Under usually circumstances, Cp1 and mismatched phase θ are both unknown, so φ3 is also unknown. However, during the transmission of foreknown signal sequence (e.g. training sequence), A(t) and B(t) could be obtained from the foreknown signal sequence. Thus, during the transmission of foreknown signal sequence, the values of Cp1 and φ3 could be calculated by expressions (5) and (6) based on expressions (1) and (2), utilizing A(t) and B(t), and the signals I (t) and Q (t) actually received by the receiver:
Cp1
φ,
Figure imgf000006_0002
When the values of Cp1 and φ3 are learned, as long as
φ3-φ1=-φ2= θ≠nπ , and n is an integer, then during the transmission of
unknown user signal, the A(t) and B(t) of the user signal could be calculated using expressions (3) and (4). User signals recovered in this manner can eliminate the influence brought by mismatched phase θ .
In addition to the above method, the estimation of the sine and cosine functions of φL and φ3 can also be used to replace the direct estimation of φL and φ3. For example, during the transmission of the foreknown training sequence signal, the I signal received consecutively at two times ti and t2 can be used to estimate COs(Cp1) and Sm(Cp1) , and the following can be obtained according to expression (1):
CQS(CP1) (t i )] , ( 7 )
Figure imgf000007_0001
SIn(CP1) o ( 8 )
Figure imgf000007_0002
Where, I O1) and I (t2) are respectively the I signals received at times ti and t2 during the transmission of training sequence signal, while A(tL) , B(tL) and A(t2) ,
B(t2) are respectively the values taken at ti and t2 by the training signal before modulation.
Likewise, cos(φ3) and sin(cp3) can also be obtained via the Q signals received during the transmission of training sequence signal, and the specific algorithm is shown as expressions (9) and (10):
Figure imgf000007_0003
Wherein, Q O1 ) and Q (t2) are the Q signals received at ti and t2 during transmission of training sequence signal. The above Cp1 and φ3 obtained based on expressions (5) and (6) or cos(φ1) ,
Sm(Cp1) and cos(φ3) , sin(φ3) obtained based on expressions (7) ~ (10), can all be estimated many times during the transmission of training sequence and calculate the mean value to acquire more accurate result.
It could be seen from the above analysis that the phase compensation method of the receiver of the present invention mainly lies in utilizing foreknown signal sequences such as training sequence to estimate the mismatched phase so as to perform proper phase compensation when receiving user signal subsequently. Therefore, the embodiment of a receiver designed according to the above method is illustrated in Fig. 3. As compared with the traditional zero IF receiver in Fig. 2, the zero IF receiver provided by the embodiment of the present invention adds a phase estimation module 101 and a phase compensation module 102; wherein the RF signal received by the antenna is first filtered by a RF filter 10, then is divided in two by the low noise amplifier
20 after performing certain gain compensation, and the two are respectively switched to baseband through mixers 31, 32, and then respectively pass through low-pass filters 41, 42, automatic gain controllers 51 52 and analog-to-digital converters 61, 62 in turn; the out-of- band noise and interference is filtered from the analog-to-digital converted baseband digital signal through low-pass filters 71, 72, then the interference such as the image caused phase mismatching generated by the local oscillator 80 at the input end of mixers 31, 32 is eliminated through phase estimation module 101 and phase compensation module 102; and in the end, the output signal of phase compensation module 102 is sent to digital signal processing unit 90 for conventional follow-up digital signal processing. Fig. 4 and Fig. 5 are respectively the detailed block diagram of the phase estimation module 101 and the structural figure of the phase compensation module 102 in the zero IF receiver illustrated in Fig. 3, wherein the phase estimation module 101 comprises a phase transient estimation module 111 and a phase mean value calculation module 121. The phase transient estimation module 111 carries out expressions (5) and (6) to estimate Cp1 and φ3 on the basis of the I and Q receiving signals outputted by low-pass filters 71, 72 and the foreknown training sequence, or carries out expressions (7) ~ (10) to estimate COs(Cp1) , Sm(Cp1) and cos(φ3) , sin(φ3) . The phase mean value calculation module 121 averages the output results of the phase transient estimation module 111, then utilizes the mean value to calculate Sm(Cp3-(P1) and outputs the averaged Cp1 , φ3 and sin (93-P1) , or 008(9^ , sm(ψi) > cos(φ3) , sin(φ3) and Sm(Cp3-(P1) to the phase compensation module 102.
The phase compensation module 102, on the basis of the I and Q receiving signals outputted by the low-pass filters 71, 72, and the mismatched phase outputted by phase mean value calculation module 121 and the corresponding trigonometric function value, carries out expressions (3) and (4) to acquire the phase compensated digital baseband signal. Fig. 5 is the structural figure of the phase compensation module 102 in the zero IF receiver illustrated in Fig. 3, wherein the functional relationship in expressions (3) and (4) carried out by the phase compensation module 102 is shown, but the proportionality factor "2" in expressions (3) and (4) is omitted, because omitting this factor will not affect the performance of the receiver.
The phase estimation module 101 and phase compensation module 102 could be separate digital circuit chips, or be integrated into the digital signal processing unit 90. In the above embodiment, the range of mismatched phase θ could be any phases
except (n + — )π (n is an integer). When θ = 0 , the receiver is in an ideal state having no
TC TC phase mismatching, and under this situation, φ3 -φL = θ = — , so the phase φL can be
estimated through a traditional method and then be used to recover user signal.
The above embodiment introduces the present invention taking the application in the zero IF receiver as an example, but the phase compensation method and apparatus for the receiver of the present invention can further be applied to other types of receivers. Fig. 6 is the structural block diagram of an embodiment of the present invention being applied to a heterodyne receiver, wherein the phase estimation module 101' and phase compensation module 102' respectively have basically the same function and structure with the phase estimation module 101 and phase compensation module 102 in the embodiment of Fig. 3, so will not be described in details here.
The above phase compensation method and apparatus for the receiver of the present invention perform phase compensation in time domain, so the image interference caused by the non-ideal circuit can be pretty easily. Further, it will not incur excessive hardware cost and power consumption.
Those skilled in the art should understand that the phase compensation method and apparatus of the receiver as disclosed by the present invention can be further modified in various aspects on the basis of not breaking away from the contents of the present invention. Therefore, the scope of protection of the present invention shall be determined by the attached Claims.

Claims

CLAIMS:
1. A method of phase compensation for signal received by a receiver, the method comprising the steps of: (a) acquiring from the received signal a predetermined signal sequence that undergoes wireless channel fading;
(b) estimating the receiver's phase-related mismatch information based on the predetermined signal sequence that undergoes wireless channel fading and a corresponding known predetermined signal channel; and (c) performing compensation recovery to the received signal in time domain based on the estimated phase-related mismatch information.
2. The method as stated in claim 1, wherein the predetermined signal sequence is training sequence.
3. The method as stated in claim 1, wherein the step (b) utilizes I and Q signals of the predetermined signal sequence that undergoes wireless channel fading and the known predetermined signal sequence to estimate the phase -related mismatch information.
4. The method as stated in claim 3, wherein the estimation of the mismatched phase and the related information in step (b) employs the following expressions:
Figure imgf000010_0001
Wherein, φι is modulated signal carrier phase, φ3 = φ1 - θ + — , θ is mismatched
phase, A(t) and B(t) are the known predetermined signal sequence, I (t) and Q (t) are I and Q signals of the predetermined signal sequence that undergoes wireless channel fading.
5. The method as stated in claim 1, wherein the phase-related mismatch information comprises the related trigonometric function values of the mismatched phase.
6. The method as stated in claim 5, wherein the step (b) utilizes the I and Q signals of the predetermined signal sequence that undergoes wireless channel fading at two different times and the known predetermined signal sequence of the two different times to estimate the related trigonometric function values of the mismatched phase.
7. The method as stated in claim 6, wherein the estimation of the related trigonometric function values of the mismatched phase in the step (b) employs the following expressions:
cosCφ,)^1^6^-1^6^, Sm(CP1)= 2[I'(ti)A(^)-I^)A(ti)]; A(I1)B(I2) -A(I2)B(I1) Υl A(I1)B(I2) -A(I2)B(I1)
= 2[Q'(tl)B(t2)-Q'(t2)B(tl)] = 2[Q'(t1)A(t2)-Q'(t2)A(t1)]
Kψ3) A(t1)B(t2)-A(t2)B(t1) ' Ψ3 A(t1)B(t2)-A(t2)B(t1)
Wherein, Cp1 is modulated signal carrier phase, φ3=φ1-θ-l — , θ is mismatched
phase, A(tL), B(tL) and A(t2), B(t2) are the corresponding values taken by the known predetermined signal sequence at times U and t2, I (tL) and I (t2) are respectively the values taken at times ti and t2 by the I signal of the predetermined signal sequence that undergoes wireless channel fading, Q (tL) and Q (t2) are respectively the values taken at times ti and t2 by the Q signal of the predetermined signal sequence that undergoes wireless channel fading.
8. The method as stated in claim 1, wherein the compensation recovery to the received signal in the step (c) employs the following expressions:
2[I' (t)sin(φ3)- Q' (t) Sm(Cp1)]
A(t) =
Un(Ip3-(P1)
29r[τl'm(t) m COS(Cp3)- Q(I)COS(P1)]
B(t) =
Sm(P3-P1)
Where, A(t) and B(t) are the received signals after compensation, I (t) and Q (t) are the I and Q signals of the received signal.
9. A receiver for wireless communication system, comprising: a receiving means, for receiving signal and acquiring therefrom a predetermined signal sequence that undergoes wireless channel fading; a phase estimation means, for estimating receiver's phase-related mismatch information based on the predetermined signal sequence that undergoes wireless channel fading and a corresponding known predetermined signal sequence; and a phase compensation means, for performing compensation recovery to the received signal in time domain based on the estimated phase -related mismatch information.
10. The receiver as stated in claim 9, wherein the phase estimation means comprises: a phase transient estimation means, for estimating carrier phase and the receiver's mismatched phase information on the basis of the known predetermined signal sequence and the I and Q signals of the predetermined signal sequence that undergoes wireless channel fading; and a phase mean value calculation means, for calculating related trigonometric function value on the basis of the carrier phase and the receiver' s mismatched phase information estimated by the phase transient estimation means.
11. The receiver as stated in claim 9, wherein the predetermined signal sequence is training sequence.
12. A mobile terminal for wireless communication system, comprising: a receiver, the receiver comprising: a receiving means, for receiving signal and acquiring therefrom a predetermined signal sequence that undergoes wireless channel fading; a phase estimation means, for estimating the receiver's phase-related mismatch information based on the predetermined signal sequence that undergoes wireless channel fading and a corresponding known predetermined signal sequence; and a phase compensation means, for performing compensation recovery to the received signal in time domain based on the estimated phase -related mismatch information; and a signal processing means, for follow-up processing of the received signal being compensated.
13. The mobile terminal as stated in claim 12, wherein the predetermined signal sequence is training sequence.
PCT/IB2005/054229 2004-12-24 2005-12-14 Quadrature phase mismatch compensation in a receiver WO2006067681A2 (en)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
CN200410104489.3 2004-12-24
CN200410104489 2004-12-24

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US7856065B2 (en) 2007-05-02 2010-12-21 Telefonkaktiebolaget Lm Ericsson (publ) Method and apparatus for correcting IQ imbalance in an OFDM receiver
WO2011144076A2 (en) * 2011-05-25 2011-11-24 华为技术有限公司 Method and device for processing uplink random access signal
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EP2779435A1 (en) * 2013-03-15 2014-09-17 Analog Devices Technology Circuit architecture for I/Q mismatch mitigation in direct conversion
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CN115086111A (en) * 2021-03-15 2022-09-20 大唐移动通信设备有限公司 Wireless signal carrier phase tracking method and related device
CN115086111B (en) * 2021-03-15 2023-11-10 大唐移动通信设备有限公司 Wireless signal carrier phase tracking method and related device

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