WO2002033823A1 - Fast current control of inductive loads - Google Patents

Fast current control of inductive loads Download PDF

Info

Publication number
WO2002033823A1
WO2002033823A1 PCT/GB2001/004640 GB0104640W WO0233823A1 WO 2002033823 A1 WO2002033823 A1 WO 2002033823A1 GB 0104640 W GB0104640 W GB 0104640W WO 0233823 A1 WO0233823 A1 WO 0233823A1
Authority
WO
WIPO (PCT)
Prior art keywords
switch
diode
voltage
circuit arrangement
current
Prior art date
Application number
PCT/GB2001/004640
Other languages
French (fr)
Inventor
Kenneth Vincent
Peter J. Knight
Original Assignee
Trw Limited
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Trw Limited filed Critical Trw Limited
Priority to EP01976472A priority Critical patent/EP1327304B1/en
Priority to AT01976472T priority patent/ATE298472T1/en
Priority to DE60111643T priority patent/DE60111643T2/en
Priority to AU2001295741A priority patent/AU2001295741A1/en
Publication of WO2002033823A1 publication Critical patent/WO2002033823A1/en
Priority to US10/418,960 priority patent/US7433171B2/en

Links

Classifications

    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01F—MAGNETS; INDUCTANCES; TRANSFORMERS; SELECTION OF MATERIALS FOR THEIR MAGNETIC PROPERTIES
    • H01F7/00—Magnets
    • H01F7/06—Electromagnets; Actuators including electromagnets
    • H01F7/08—Electromagnets; Actuators including electromagnets with armatures
    • H01F7/18—Circuit arrangements for obtaining desired operating characteristics, e.g. for slow operation, for sequential energisation of windings, for high-speed energisation of windings
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01F—MAGNETS; INDUCTANCES; TRANSFORMERS; SELECTION OF MATERIALS FOR THEIR MAGNETIC PROPERTIES
    • H01F7/00—Magnets
    • H01F7/06—Electromagnets; Actuators including electromagnets
    • H01F7/08—Electromagnets; Actuators including electromagnets with armatures
    • H01F7/18—Circuit arrangements for obtaining desired operating characteristics, e.g. for slow operation, for sequential energisation of windings, for high-speed energisation of windings
    • H01F7/1805—Circuit arrangements for holding the operation of electromagnets or for holding the armature in attracted position with reduced energising current
    • H01F7/1811—Circuit arrangements for holding the operation of electromagnets or for holding the armature in attracted position with reduced energising current demagnetising upon switching off, removing residual magnetism

Definitions

  • the present invention is concerned with the fast control of current in
  • inductive electrical loads such as solenoids, particularly but not exclusively in
  • Inductive loads such as solenoid coils, are typically controlled by means of
  • a switch such as a switching transistor, connected in series with the load across a
  • low side is normally connected to ground/chassis and the other side (referred to
  • a sensing element for purposes of monitoring/measuring the current through the load, a sensing element
  • said first switch comprises a switching
  • transistor and said high-voltage drop energy dissipation path comprises a voltage regulating diode, such as a Zener diode, in parallel with the switching path of said
  • the switching transistor is a field-effect transistor such as a
  • the switching transistor is a field-effect transistor
  • the voltage regulating diode is connected, in series with a first diode, between its drain and gate terminals.
  • the second switch can, for example, comprise a MOSFET in series with a
  • said second switch is
  • control loop to have software controlled phase relationships between channels.
  • control loop to have a software controlled oscillation frequency
  • control channels are under the control of software.
  • the control channels can be any type of software.
  • Electromagnetic emissions from the current can be changed dynamically over time. Electromagnetic emissions from the current
  • control circuit are composed mainly of harmonics of the control frequency.
  • Fig. 1 is a basic circuit diagram of a known switching arrangement for
  • Fig. 2 is a basic circuit diagram of one embodiment of an arrangement in
  • Fig.3 shows typical responsive curves illustrating the dissipation of
  • Fig. 4 is a circuit diagram of a possible modification to the circuit of Fig. 3;
  • Fig. 5 is a basic circuit diagram of a multi-solenoid switching arrangement
  • Fig. 6 shows an electro-hydraulic (EFIB) braking system to which the present
  • FIG. 1 there is shown the basic circuit of a typical known
  • the current I L is monitored by detecting the voltage drop across
  • FIG. 2 shows one embodiment of a circuit
  • a MOSFET switching transistor T 2 is included in series with the recirculation diode D, to enable the conduction of the recirculation path through D,
  • recirculation path is broken. This can be arranged to take place, for example, when
  • Fig 4 shows an alternative arrangement to the Zener diode D 2 of Fig. 2 where
  • the present circuit provides a means whereby, in the event of high
  • the constant-voltage-drop diode D can be
  • recirculation switch T 2 can be used for a plurality of solenoid drives at once, for
  • FIG. 5 shows a second load L,', which is switchable by means of a second MOSFET T,', with its current being monitored by a current sensor
  • braking demand signals are generated electronically at a travel sensor 10 in response
  • ECU brake actuator unit
  • valves 18a, 18b and 18c, 18d respectively of a vehicle via pairs of valves 18a, 18b and 18c, 18d.
  • solenoid controlled accumulator valve 26 For use, for example, in emergency
  • the system includes a master cylinder 28 coupled mechanically to the
  • valves 18a, 18b, and the two pairs of valves 18c, 18d are of valves 18a, 18b, and the two pairs of valves 18c, 18d.
  • the system of the present invention for enabling fast switching can be applied
  • solenoids are under the control of a single ECU such as in the case of the solenoid
  • valves 18a-18d, 26, 32,34 and 30a, 30b in Fig. 6 (or sub-groups thereof), the
  • diode T 2 is common to all solenoids in the group or sub-group.

Landscapes

  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Electronic Switches (AREA)
  • General Induction Heating (AREA)
  • Control Of Stepping Motors (AREA)
  • Control Of Electric Motors In General (AREA)

Abstract

A circuit arrangement for the fast dissipation of the stored magnetic energy in an inductive load (4) controlled by a first switch (T1), comprising a high voltage-drop energy dissipation path (D2) disposed across the first switch (T1) and a second switch (T2) by which a constant-voltage diode drop path (D1) across the load (L1) can be selectively opened.

Description

DESCRIPTION
FAST CURRENT CONTROL OF INDUCTIVE LOADS
The present invention is concerned with the fast control of current in
inductive electrical loads, such as solenoids, particularly but not exclusively in
automotive electronic control systems.
Inductive loads, such as solenoid coils, are typically controlled by means of
a switch, such as a switching transistor, connected in series with the load across a
voltage supply. In automotive applications, one side of the load(referred to as the
"low side") is normally connected to ground/chassis and the other side (referred to
as the "high side") is coupled to the non-grounded side of the voltage supply. For the
purpose of monitoring/measuring the current through the load, a sensing element
such as a resister is placed in series with the load and the voltage drop across this
resistor is measured.
Traditional technology often used current sensing near the load driving
transistor, such that current monitoring was only available when the drive was turned
on. When the level of the monitored current was to be used for control of the
switching transistor, this arrangement therefore had poor control.
Some known arrangements have used high side control of the load using P
channel MOSFET devices, but these are relatively expensive.
As is well known, the current in an inductive load decays with time when the
voltage supply is removed and special circuitry must be provided to dispose of this
current. The conventional practice is to achieve this by the provision of a recirculating diode disposed in parallel with the load which turns on automatically
to provide a current path back to the supply. However, the rate at which a diode
disposed across the load in this manner can dissipate the recirculating current is
relatively poor and the current in the load therefore falls off only slowly (see curve
X in Fig. 3 of the attached drawings).
Known means for achieving faster control of the current turn-off in inductive
loads have typically used two MOSFET devices per channel, which has an attendant
cost.
In accordance with the present invention, fast dissipation of the stored
magnetic energy in an inductive load controlled by a first switch is enabled by the
provision of a high- voltage-drop energy dissipation path across said first switch and
a second switch by which a constant-voltage diode drop path across the load can be
selectively opened.
In one preferred embodiment, said first switch comprises a switching
transistor and said high-voltage drop energy dissipation path comprises a voltage regulating diode, such as a Zener diode, in parallel with the switching path of said
switching transistor.
Advantageously, the switching transistor is a field-effect transistor such as a
MOSFET, and the voltage regulating diode is connected between its source and drain
terminals.
In another embodiment, the switching transistor is a field-effect transistor,
such as a MOSFET, and the voltage regulating diode is connected, in series with a first diode, between its drain and gate terminals.
The second switch can, for example, comprise a MOSFET in series with a
second diode across the series combination of the inductive load and a current
sensing element.
In some particularly advantageous embodiments, said second switch
commonly controls the opening of a plurality of said constant- voltage diode drop
paths across a plurality of respective inductive loads, each of which is switchable by
a respective first switch across which there is disposed a respective high- voltage-drop
energy dissipation path.
A number of other advantageous features can be obtained using a circuit
arrangement in accordance with the present invention;
(a) Phase locked current control. A small amount of ripple is allowed on the
incoming demand signal, which causes the control loop to synchronise its control
oscillation to that of an incoming PWM signal. This allows the external current
control loop to have software controlled phase relationships between channels.
(b) Frequency locked current control. A small amount of ripple is allowed on
the incoming demand signal, which causes the control loop to synchronise its control
oscillation to that of the incoming PWM signal. This allows the external current
control loop to have a software controlled oscillation frequency.
(c) Phase staggered control. The phase of individual current control channels
is under the control of software. By software control, the control channels can be
phase staggered. This results in the energise part of the control cycles being distributed evenly through time. The total current demand of the circuit is therefore
more evenly distributed. The high frequency current demands of the circuit are
reduced, and the frequency is raised. The reduction in peaks and the higher overall
frequency allows for easier filtering and reduced electromagnetic emissions, without
any additional hardware costs.
(d) Spread spectrum control. The frequency of the current control channels
is under the control of software. By software control, the control channel frequencies
can be changed dynamically over time. Electromagnetic emissions from the current
control circuit are composed mainly of harmonics of the control frequency. By
dynamically changing the frequency of control, all resulting emissions are modulated
over a wider bandwidth. This reduces the peak energy of the emissions over a set
measurement bandwidth, without any additional hardware costs.
The invention is described further hereinafter, by way of example only, with
reference to the accompanying drawings, in which:-
Fig. 1 is a basic circuit diagram of a known switching arrangement for
controlling and monitoring the current through an inductive load;
Fig. 2 is a basic circuit diagram of one embodiment of an arrangement in
accordance with the present invention for controlling and monitoring the current
through an inductive load;
Fig.3 shows typical responsive curves illustrating the dissipation of
recirculating current in a known system and in a system in accordance with this
invention; Fig. 4 is a circuit diagram of a possible modification to the circuit of Fig. 3;
Fig. 5 is a basic circuit diagram of a multi-solenoid switching arrangement
incorporating the present invention; and
Fig. 6 shows an electro-hydraulic (EFIB) braking system to which the present
invention is applicable.
Referring first to Fig. 1 , there is shown the basic circuit of a typical known
arrangement for controlling/monitoring the current IL through an inductive load L,,
such as the coil of a solenoid-operated valve. The current through the coil L,, is
switched on/off by a MOSFET T, driven by a controller in accordance with a
demand signal D. The current IL is monitored by detecting the voltage drop across
a resistor Rl5 disposed in series with the coil L using a differential amplifier A[
coupled back to the controller C, to form an analogue control loop. A recirculation
diode D( is connected in parallel with the series connection of the resistor R, and load
L]. In use of this circuit arrangement, when the MOSFET T, is turned off, the stored
energy in the coil results in a current flow which is dissipated in the voltage drop
across the recirculation diode D,. However, as mentioned hereinbefore, the rate of
dissipation of this current by the diode D, is relatively slow and typically follows a
path such as that defined by curve X in Fig. 3
Reference is now made to Fig. 2 which shows one embodiment of a circuit
arrangement in connection with the present invention, wherein components having
the same function are given the same reference numerals as in Fig. 1.
In this case, a MOSFET switching transistor T2 is included in series with the recirculation diode D, to enable the conduction of the recirculation path through D,
to be controlled by the ECU via a matching amplifier A2. Thus, when the switch T2
is closed, the diode D, provides a constant-voltage drop recirculation path in the
normal way. However, when the switch T2 is open-circuit, then the normal
recirculation path is broken. This can be arranged to take place, for example, when
it is detected via R, that the current IL on the load L, is too high (above a
predetermined threshold). In this case, the recirculation currents which are de-
energising the load L_ are dissipated to ground by way of a high voltage drop energy
dissipator, such as a Zener diode D2 disposed across the MOSFET T,. This allows
the stored magnetic energy in the inductive load L to be dissipated from the load at
a much greater rate than using the constant voltage drop diode D, and a curve such
as that shown at Y in Figure 3 can be obtained.
Fig 4 shows an alternative arrangement to the Zener diode D2 of Fig. 2 where
the series combination of a Zener diode D3 and diode D4 is disposed across the drain-
gate terminals of the MOSFET T,. A similar characteristic curve Y can be obtained
by this arrangement.
Thus, the present circuit provides a means whereby, in the event of high
induced currents in the switched load, the constant-voltage-drop diode D, can be
replaced by the high- voltage-drop Zener arrangement D, by opening the switch T2.
A particular advantage of this arrangement is that the same single
recirculation switch T2 can be used for a plurality of solenoid drives at once, for
example as shown in Fig. 5. Fig. 5 shows a second load L,', which is switchable by means of a second MOSFET T,', with its current being monitored by a current sensor
R,' and coupled by an analogue control loop to its own controller C,' which receives
an input demand from the common ECU. It will be noted that both of the
recirculation diodes D, and D,' in this circuit are coupled to the supply voltage Ub by
way of the same, single MOSFET switch T2 This allows the advantageous
arrangement of Fig 2 to be added economically to existing load drives with one driver
T, per channel plus just one stored switch T2 This is possible because, from the
viewpoint of channels which do not currently need the fast current decay, it does not
matter if the recirculation path via T2 is temporarily lost, for example by a 1 ms
pulsed opening of T2, to enable fast current decay via D2 for a channel which does
need it.
Fig. 6 shows a typical electrohydraulic (EHB) braking system to which the
present invention is applicable. In the electrohydraulic braking system of Fig. 6,
braking demand signals are generated electronically at a travel sensor 10 in response
to operations of a foot pedal 12, the signals being processed in an electronic control
unit (ECU) 14 for controlling the operation of brake actuators 16a, 16b at the front
and back wheels respectively of a vehicle via pairs of valves 18a, 18b and 18c, 18d.
The latter valves are operated in opposition to provide proportional control of
actuating fluid to the brake actuators 16 from a pressurised fluid supply accumulator
20, maintained from a reservoir 22 by means of a motor-driven pump 24 via a
solenoid controlled accumulator valve 26. For use, for example, in emergency
conditions when the electronic control of the brake actuators is not operational for some reason, the system includes a master cylinder 28 coupled mechanically to the
foot pedal 12 and by which fluid can be supplied directly to the front brake actuators
16a in a "push through" condition. In the push-through condition, a fluid connection
between the front brake actuators 16a and the cylinder 28 is established by means of
digitally operating, solenoid operated valves, 30a, 30b. Also included in the system
are further digitally operating valves 32, 34 which respectively connect the two pairs
of valves 18a, 18b, and the two pairs of valves 18c, 18d.
The system of the present invention for enabling fast switching can be applied
to any of the solenoids in the arrangement of Fig. 6. Advantageously, where groups
of solenoids are under the control of a single ECU such as in the case of the solenoid
valves 18a-18d, 26, 32,34 and 30a, 30b in Fig. 6 (or sub-groups thereof), the
arrangement of Fig. 5 can be advantageous where a single switched recirculation
diode T2 is common to all solenoids in the group or sub-group.

Claims

1. A circuit arrangement for the fast dissipation of the stored magnetic energy
in an inductive load controlled by a first switch, comprising a high-voltage-drop
energy dissipation path disposed across said first switch and a second switch by
which a constant-voltage diode drop path across the load can be selectively opened.
2. A circuit arrangement as claimed in claim 1, wherein said first switch
comprises a switching transistor and said high-voltage drop energy dissipation path
comprises a voltage regulating diode in parallel with the switching path of said
switching transistor.
3. A circuit arrangement as claimed in claim 2 wherein the switching
transistor is a field effect transistor and the voltage regulating diode is connected
between its source and drain terminals.
4. A circuit arrangement as claimed in claim 2 wherein the switching
transistor is a field effect transistor and the voltage regulating diode is connected, in
series with a first diode, between its drain and gate terminals.
5. A circuit arrangement as claimed in any of claims 1 to 4, wherein said
second switch comprises a field effect transistor in series with a second diode across
the series combination of the inductive load and a current sensing element.
6. A circuit arrangement as claimed in any of claims 1 to 5, wherein said
second switch commonly controls the opening of a plurality of said constant-voltage
diode drop paths across a plurality of respective inductive loads, each of which is
switchable by a respective first switch across which there is disposed a respective high-voltage-drop energy dissipation path.
PCT/GB2001/004640 2000-10-21 2001-10-17 Fast current control of inductive loads WO2002033823A1 (en)

Priority Applications (5)

Application Number Priority Date Filing Date Title
EP01976472A EP1327304B1 (en) 2000-10-21 2001-10-17 Fast current control of inductive loads
AT01976472T ATE298472T1 (en) 2000-10-21 2001-10-17 FAST CURRENT REGULATOR FOR INDUCTIVE LOADS
DE60111643T DE60111643T2 (en) 2000-10-21 2001-10-17 FAST CURRENT CONTROLLER FOR INDUCTIVE LOADS
AU2001295741A AU2001295741A1 (en) 2000-10-21 2001-10-17 Fast current control of inductive loads
US10/418,960 US7433171B2 (en) 2000-10-21 2003-04-18 Fast current control of inductive loads

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
GB0025832A GB2368210A (en) 2000-10-21 2000-10-21 Controllable current decay rate for hydraulic brake system solenoids
GB0025832.7 2000-10-21

Related Child Applications (1)

Application Number Title Priority Date Filing Date
US10/418,960 Continuation US7433171B2 (en) 2000-10-21 2003-04-18 Fast current control of inductive loads

Publications (1)

Publication Number Publication Date
WO2002033823A1 true WO2002033823A1 (en) 2002-04-25

Family

ID=9901739

Family Applications (1)

Application Number Title Priority Date Filing Date
PCT/GB2001/004640 WO2002033823A1 (en) 2000-10-21 2001-10-17 Fast current control of inductive loads

Country Status (8)

Country Link
US (1) US7433171B2 (en)
EP (1) EP1327304B1 (en)
AT (1) ATE298472T1 (en)
AU (1) AU2001295741A1 (en)
DE (1) DE60111643T2 (en)
ES (1) ES2244664T3 (en)
GB (1) GB2368210A (en)
WO (1) WO2002033823A1 (en)

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Also Published As

Publication number Publication date
GB0025832D0 (en) 2000-12-06
ES2244664T3 (en) 2005-12-16
AU2001295741A1 (en) 2002-04-29
US20040057183A1 (en) 2004-03-25
ATE298472T1 (en) 2005-07-15
US7433171B2 (en) 2008-10-07
GB2368210A (en) 2002-04-24
EP1327304B1 (en) 2005-06-22
DE60111643T2 (en) 2006-05-18
EP1327304A1 (en) 2003-07-16
DE60111643D1 (en) 2005-07-28

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