WO2001069878A1 - Method of selecting a position of a fft window in a cofdm receiver - Google Patents

Method of selecting a position of a fft window in a cofdm receiver Download PDF

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Publication number
WO2001069878A1
WO2001069878A1 PCT/GB2001/001140 GB0101140W WO0169878A1 WO 2001069878 A1 WO2001069878 A1 WO 2001069878A1 GB 0101140 W GB0101140 W GB 0101140W WO 0169878 A1 WO0169878 A1 WO 0169878A1
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WIPO (PCT)
Prior art keywords
fft
window
active portion
symbol
selecting
Prior art date
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PCT/GB2001/001140
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French (fr)
Inventor
Thomas Foxcroft
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Conexant Digital Infotainment Limited
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Publication date
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Publication of WO2001069878A1 publication Critical patent/WO2001069878A1/en

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Classifications

    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2662—Symbol synchronisation
    • H04L27/2665—Fine synchronisation, e.g. by positioning the FFT window
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2662—Symbol synchronisation

Definitions

  • This invention relates to a receiver, for use where the transmitted signal is modulated using COFDM (Coded Orthogonal Frequency Division Multiplexing) , and in particular to a receiver for broadcast digital terrestrial television signals.
  • COFDM Coded Orthogonal Frequency Division Multiplexing
  • the European DVB-T Digital Video Broadcasting - Terrestrial standard for digital terrestrial television (DTT) uses Coded Orthogonal Frequency Division Multiplexing (COFDM) of transmitted signal, which are therefore grouped into blocks and frames.
  • COFDM Coded Orthogonal Frequency Division Multiplexing
  • FFT Fast Fourier Transform
  • the area close to the transmission path may include objects such as tall buildings, which cause echoes. That is, a signal may be received at a receiver multiple times, once on a direct path from the transmitter, and then, after short delays, as echoes.
  • the DVB-T standard may be used in a single frequency network of transmitters. That is, a single receiver can receive the same signal on the same frequency, from multiple transmitters.
  • DVB-T COFDM symbols include a cyclic prefix guard interval to each active symbol. Specifically a portion of each active symbol is repeated before that active symbol .
  • the echoes may be of various amplitudes and delays, and the first received component may not be the strongest. Also the delay between the first received component and the last may be greater than the guard interval and thus some ISI may occur.
  • the invention advantageously seeks to minimise the effects of the echoes.
  • Figure 1 is a schematic illustration of a part of a receiver circuit in accordance with the invention.
  • Figure 2 shows the power in unused carriers of a Fast Fourier Transform output for varying window positions, in a first case.
  • Figure 3 shows the power in unused carriers of a Fast Fourier Transform output for varying window positions, in a second case.
  • Figure 4 shows the power in unused carriers of a
  • Figure 5 illustrates a process in accordance with an embodiment of the invention.
  • Figure 6 illustrates a stage in the process of
  • Figure 1 shows a section of a receiver circuit relevant to the present invention.
  • the receiver will include an antenna (not shown) , and a tuner (not shown) for receiving the signals and down converting to an intermediate frequency.
  • COFDM Coded Orthogonal Frequency Division Multiplexing
  • the receiver further includes a further mixer stage 10 for down-converting to baseband, and a resampler 12, for obtaining digital samples synchronised to the incoming signal .
  • the down- conversion mixer frequency and resampler rate are locked to the incoming IF frequency and transmitter sample rate respectively.
  • Output signals from the resampler 12 are filtered by a low pass filter 13 to removed unwanted mixer components and then supplied to a guard interval removal block 14 which removes the cyclic components which precede each active symbol.
  • the output of the guard interval removal block 14 is supplied to an FFT processor 16 which outputs to an equalisation and decoding block 18 and also an FFT side bin power measurement block 20, which will be described further below.
  • the result is supplied to a window position selection block 22, also to be described further below.
  • the equalisation .and decoding block 18 compensates for the channel and recovers the originally transmitted bit stream, in a generally conventional way.
  • the output of the FFT processor 16 has 2048 carriers of which only 1705 (in the case of DVB-T 2k mode) carry transmitted information.
  • the lowpass filter 13 will reduce to a negligible level energy in the 343 unused carriers which are divided essentially equally either side of the used carriers.
  • a correctly positioned FFT window will result in no additional energy in the unused carrier positions.
  • the start of the FFT window position can be placed anywhere within the guard interval (cyclic prefix) and this will still be the case. However, if the start of the FFT window position is placed outside the guard interval, this is no longer true, since the window now encompasses samples from the adjacent symbol, and so ISI results.
  • Figure 2 shows the variation in the ISI level 25 as a function of offset in the FFT window position. If echoes are present then the variation of ISI level as a function of offset in the FFT window position can be obtained approximately by superposition.
  • Figure 3 shows the case in which there is one additional echo, of an amplitude equal to that of the main- signal, whose delay is within the guard interval length.
  • Figure 3a shows the respective ISI levels 32, 34 resulting from the main signal and the echo.
  • Figure 3b shows the resulting overall ISI level 36.
  • the optimal FFT window position as marked would then be such that it produces zero ISI .
  • Figure 4 shows the case of an additional echo of smaller amplitude than the main signal, but with a delay greater than the Guard Interval length.
  • Figure 4a shows the respective ISI levels 42, 44 resulting from the main signal and the echo.
  • Figure 4b then shows the resulting overall ISI level 46.
  • the level of ISI can be determined by the energy that exists in some or all of the unused carrier locations by the FFT side bin power measurement block 20. Although it may be optimal to calculate the power in all of the unused carriers, other methods are also possible. For example, it may be advantageous to exclude those unused carriers closest to the active window, in order to avoid the effects of the active portion bleeding through into the unused carriers. As another example, it may be advantageous to measure the power in unused carriers to only one side of the window.
  • an initial estimate of the FFT window location is made by using one of a number of standard methods .
  • the system further specifies a range of possible offsets from that estimated position, over which ISI measurements are to be taken, so that the optimum position can be selected from within that range.
  • the range is preferably chosen with reference to the maximum expected delay time of a significant echo.
  • the range is preferably chosen with reference to knowledge about the system in which the receiver is to be used. For example, the range may be twice the guard interval.
  • Figure 6 shows one symbol period of a received signal.
  • one symbol 62 includes a guard interval 64 and an active portion 66.
  • Figure 6 also shows the estimated window position 68.
  • a first chosen active window 70 is then defined, the first chosen active window 70 being offset from the estimated window position 68, being earlier by half the total range of offsets whose ISI is to be measured.
  • the system also stores the values of a number of samples 72 at the start of the chosen active window 70, and stores the values of the same number of samples 74 after the end of the chosen active window 70.
  • the FFT is performed in the usual manner, the carrier output values are stored, and the power in some or all of the unused carriers is measured.
  • the FFT calculation is not simply repeated for other window positions, but the algorithm calculates each successive advance in position in an iterative manner, sample by sample.
  • the FFT output for an advance in FFT window position of one sample is repeatedly calculated, in the following manner. First the frequency contribution of the earliest sample of the previous FFT window position, that is, the first of the samples 72, is subtracted from all of carriers of the previous FFT output . Then the phase of each output carrier of the previous FFT is rotated by an amount equivalent to having advanced the FFT window position by one sample. Then, the frequency contribution of the next new sample after the end of the FFT window, that is, the first of the samples 74, is added to each output carrier of the previous FFT as if it had been calculated as part of a full FFT. The power measurement, and hence the ISI measurement, can then be made for the next offset FFT window position. This algorithm is successively applied, sample by sample, for the range of offsets required for each symbol, until the offset window position includes all of the samples 74 and none of the samples 72. The results can then be averaged over a number of symbols for greater accuracy.
  • the optimal window position may be found, and subsequently tracked with feedback to the guard interval removal block.
  • the graph resembles that of Figure 3, in the sense that there is a range of window positions which produce apparently equally good ISI values, a further selection can be made to determine the optimal position.
  • a position may be chosen which improves the ease with which the resultant signal may be handled in the succeeding equalisation block, based on expected pattern of echoes.
  • the optimal window position may be near the right-hand end of a range of window positions which produce apparently equally good ISI values, in order that the equalisation block can most easily deal with pre-echoes .
  • COFDM receiver and a method of operation thereof, which allow optimal selection of a FFT window position.

Abstract

A television receiver circuit is disclosed which includes an ISI measurement circuit and a method for varying the selected FFT window position, in order to minimise the amount of ISI, comprising the steps of: receiving a COFDM signal made up of symbols, each symbol comprising an active portion and a guard portion; removing the guard portion from each symbol to leave the active portion; applying a Fast Fourier Transform (FFT) to the active portion, the FFT processor having a number of carriers greater than the number of samples in the active portion; and selecting a position of a FFT window, in order to minimise the amount of energy in carrier locations of the FFT processor outside the active portion.

Description

METHOD OF SELECTING A POSITION OF A FFT WINDOW IN A COFDM RECEIVER TECHNICAL FIELD OF THE INVENTION
This invention relates to a receiver, for use where the transmitted signal is modulated using COFDM (Coded Orthogonal Frequency Division Multiplexing) , and in particular to a receiver for broadcast digital terrestrial television signals. BACKGROUND OF THE INVENTION
The European DVB-T (Digital Video Broadcasting - Terrestrial) standard for digital terrestrial television (DTT) uses Coded Orthogonal Frequency Division Multiplexing (COFDM) of transmitted signal, which are therefore grouped into blocks and frames. After reception in the television receiver the signals are sampled for example using a resampler, and are mixed down to baseband. The start of each active symbol is found, and then the active symbols are applied to an Fast Fourier Transform (FFT) processor for extraction of the modulated signals. It is necessary to transmit the DTT signals over transmission paths which are of uncertain quality. In particular the area close to the transmission path may include objects such as tall buildings, which cause echoes. That is, a signal may be received at a receiver multiple times, once on a direct path from the transmitter, and then, after short delays, as echoes.
Further, the DVB-T standard may be used in a single frequency network of transmitters. That is, a single receiver can receive the same signal on the same frequency, from multiple transmitters.
As is well known, these factors can cause inter- symbol interference (ISI) in the receiver. To minimise this problem, DVB-T COFDM symbols include a cyclic prefix guard interval to each active symbol. Specifically a portion of each active symbol is repeated before that active symbol . The echoes may be of various amplitudes and delays, and the first received component may not be the strongest. Also the delay between the first received component and the last may be greater than the guard interval and thus some ISI may occur. For optimal demodulation performance, it is necessary to select a Fast Fourier Transform window that minimises the amount of ISI experienced. SUMMARY OF THE INVENTION According to a first aspect of the invention, there is provided a COFDM receiver circuit which includes an ISI measurement circuit and a mechanism for varying the selected FFT window position.
According to a second aspect of the invention, there is provided a method of varying an FFT window position to minimise the effects of ISI.
Thus, rather than attempting to detect the positions of echoes, and then deal with them, the invention advantageously seeks to minimise the effects of the echoes.
BRIEF DESCRIPTION OF DRAWINGS
Figure 1 is a schematic illustration of a part of a receiver circuit in accordance with the invention.
Figure 2 shows the power in unused carriers of a Fast Fourier Transform output for varying window positions, in a first case.
Figure 3 shows the power in unused carriers of a Fast Fourier Transform output for varying window positions, in a second case. Figure 4 shows the power in unused carriers of a
Fast Fourier Transform output for varying window positions, in a third case.
Figure 5 illustrates a process in accordance with an embodiment of the invention. Figure 6 illustrates a stage in the process of
Figure 5. DETAILED DESCRIPTION OF PREFERRED EMBODIMENTS
Figure 1 shows a section of a receiver circuit relevant to the present invention.
Typically, in the exemplary case of a digital terrestrial television signal receiver for example receiving signals using the DVB-T standard with Coded Orthogonal Frequency Division Multiplexing (COFDM) , the receiver will include an antenna (not shown) , and a tuner (not shown) for receiving the signals and down converting to an intermediate frequency.
The receiver further includes a further mixer stage 10 for down-converting to baseband, and a resampler 12, for obtaining digital samples synchronised to the incoming signal . The down- conversion mixer frequency and resampler rate are locked to the incoming IF frequency and transmitter sample rate respectively. Output signals from the resampler 12 are filtered by a low pass filter 13 to removed unwanted mixer components and then supplied to a guard interval removal block 14 which removes the cyclic components which precede each active symbol. The output of the guard interval removal block 14 is supplied to an FFT processor 16 which outputs to an equalisation and decoding block 18 and also an FFT side bin power measurement block 20, which will be described further below. The result is supplied to a window position selection block 22, also to be described further below.
The equalisation .and decoding block 18 compensates for the channel and recovers the originally transmitted bit stream, in a generally conventional way.
■ Specifically, in this example, the output of the FFT processor 16 has 2048 carriers of which only 1705 (in the case of DVB-T 2k mode) carry transmitted information. The lowpass filter 13, will reduce to a negligible level energy in the 343 unused carriers which are divided essentially equally either side of the used carriers. In the absence of echoes, a correctly positioned FFT window will result in no additional energy in the unused carrier positions. In fact, the start of the FFT window position can be placed anywhere within the guard interval (cyclic prefix) and this will still be the case. However, if the start of the FFT window position is placed outside the guard interval, this is no longer true, since the window now encompasses samples from the adjacent symbol, and so ISI results. These ISI samples create impulse noise on the wanted window. The frequency spectrum of each of these impulses is of constant amplitude, and so they add constant energy in all the bins, including previously empty bins. Therefore, the energy in these bins is a measure of the amount of ISI.
For example, if the start of the FFT window position is placed one sample outside the guard interval, this is equivalent to a single impulse of noise which results in a constant power level across all the FFT output carriers. Further displacement outside the guard interval results in increased noise levels across all carriers.
Figure 2 shows the variation in the ISI level 25 as a function of offset in the FFT window position. If echoes are present then the variation of ISI level as a function of offset in the FFT window position can be obtained approximately by superposition. Figure 3 shows the case in which there is one additional echo, of an amplitude equal to that of the main- signal, whose delay is within the guard interval length. Figure 3a shows the respective ISI levels 32, 34 resulting from the main signal and the echo. Figure 3b then shows the resulting overall ISI level 36. The optimal FFT window position as marked would then be such that it produces zero ISI .
Figure 4 shows the case of an additional echo of smaller amplitude than the main signal, but with a delay greater than the Guard Interval length. Figure 4a shows the respective ISI levels 42, 44 resulting from the main signal and the echo. Figure 4b then shows the resulting overall ISI level 46. In this case there exists one position with minimum but not zero ISI . The level of ISI can be determined by the energy that exists in some or all of the unused carrier locations by the FFT side bin power measurement block 20. Although it may be optimal to calculate the power in all of the unused carriers, other methods are also possible. For example, it may be advantageous to exclude those unused carriers closest to the active window, in order to avoid the effects of the active portion bleeding through into the unused carriers. As another example, it may be advantageous to measure the power in unused carriers to only one side of the window.
In order to obtain the information contained in the graphs shown in Figures 2, 3 and 4 one possibility would be, for each COFDM symbol, to perform an FFT for a range of offsets of the FFT window position, the range preferably being at least twice the guard interval. Then this would have to be averaged over a number of COFDM symbols to obtain a graph with suitable accuracy. This represents a very significant overhead of processing.
A preferred method of calculation in accordance with, the invention is shown in Figure 5. There are a number of possible variants of the scheme shown, but all embody the present invention. First, an initial estimate of the FFT window location is made by using one of a number of standard methods . The system further specifies a range of possible offsets from that estimated position, over which ISI measurements are to be taken, so that the optimum position can be selected from within that range. The range is preferably chosen with reference to the maximum expected delay time of a significant echo. Thus, the range is preferably chosen with reference to knowledge about the system in which the receiver is to be used. For example, the range may be twice the guard interval.
Figure 6 shows one symbol period of a received signal. As is well known, one symbol 62 includes a guard interval 64 and an active portion 66. Figure 6 also shows the estimated window position 68. A first chosen active window 70 is then defined, the first chosen active window 70 being offset from the estimated window position 68, being earlier by half the total range of offsets whose ISI is to be measured.
The system also stores the values of a number of samples 72 at the start of the chosen active window 70, and stores the values of the same number of samples 74 after the end of the chosen active window 70.
For the first chosen active window position, the FFT is performed in the usual manner, the carrier output values are stored, and the power in some or all of the unused carriers is measured.
In accordance with this preferred embodiment of the invention, the FFT calculation is not simply repeated for other window positions, but the algorithm calculates each successive advance in position in an iterative manner, sample by sample.
. Thus , the FFT output for an advance in FFT window position of one sample is repeatedly calculated, in the following manner. First the frequency contribution of the earliest sample of the previous FFT window position, that is, the first of the samples 72, is subtracted from all of carriers of the previous FFT output . Then the phase of each output carrier of the previous FFT is rotated by an amount equivalent to having advanced the FFT window position by one sample. Then, the frequency contribution of the next new sample after the end of the FFT window, that is, the first of the samples 74, is added to each output carrier of the previous FFT as if it had been calculated as part of a full FFT. The power measurement, and hence the ISI measurement, can then be made for the next offset FFT window position. This algorithm is successively applied, sample by sample, for the range of offsets required for each symbol, until the offset window position includes all of the samples 74 and none of the samples 72. The results can then be averaged over a number of symbols for greater accuracy.
The result of adding the powers of some or all of the unused carriers for each FFT window position is then stored and can be used to produce a graph similar to those shown in Figures 2, 3 and 4.
Having calculated a graph of the sort shown in Figures 2, 3 and 4, the optimal window position may be found, and subsequently tracked with feedback to the guard interval removal block. When the graph resembles that of Figure 3, in the sense that there is a range of window positions which produce apparently equally good ISI values, a further selection can be made to determine the optimal position. For example, a position may be chosen which improves the ease with which the resultant signal may be handled in the succeeding equalisation block, based on expected pattern of echoes. For example, if the environment is such that rapidly arriving pre-echoes are a possibility, the optimal window position may be near the right-hand end of a range of window positions which produce apparently equally good ISI values, in order that the equalisation block can most easily deal with pre-echoes .
There is thus described a COFDM receiver, and a method of operation thereof, which allow optimal selection of a FFT window position.

Claims

1. A method of processing a received COFDM signal, the method comprising: selecting a position of a FFT window, in order to minimise the effects of inter-symbol interference in the FFT output .
2. A method of processing a received signal, the received signal made up of symbols, each symbol comprising an active portion and a guard portion, the method comprising: removing the guard portion from each symbol to leave the active portion; and applying a Fast Fourier Transform (FFT) to the active portion, the FFT processor having a number of carriers greater than the number of samples in the active portion; and further comprising: selecting a position of a FFT window, in order to minimise the effects of inter-symbol interference in the FFT output .
3. A method of processing a received signal, the received signal made up of symbols, each symbol comprising an active portion and a guard portion, the method comprising: removing the guard portion from each symbol to leave the active portion; and applying a Fast Fourier Transform (FFT) to the active portion, the FFT processor having a number of carriers greater than the number of samples in the active portion; and further comprising: selecting a position of a FFT window, in order to minimise the amount of energy in carrier locations of the FFT processor outside the active portion.
4. A method of processing a received signal, the received signal made up of symbols, each symbol comprising an active portion and a guard portion, the method comprising: removing the guard portion from each symbol to leave the active portion; and further comprising: selecting a first Fast Fourier Transform (FFT) window position; applying a FFT to the active portion, the FFT processor having a number of carriers greater than the number of samples in the active portion, and the FFT window being at the selected first FFT window position; calculating a power in unused carriers of the FFT; repeatedly applying an FFT to the active portion, the FFT window being at further FFT window positions, and calculating the power in unused carriers of the FFT with the FFT window being at the further FFT window positions; and selecting an active position of the FFT window, in order to minimise said power in unused carriers of the FFT.
5. A method of processing a received signal, the received signal made up of symbols, each symbol comprising an active portion and a guard portion, the method comprising: removing the guard portion from each symbol to leave the active portion; and further comprising: selecting a first Fast Fourier Transform (FFT) window position; storing the values of samples within the window at a first end of the first window position; storing the values of samples outside the window at a second end of the first window position; applying a FFT to the active portion, the FFT processor having a number of carriers greater than the number of samples in the active portion, and the FFT window being at the selected first FFT window position; calculating a power in unused carriers of the FFT; (a) discarding a contribution to said power from a sample at the first end of the window; (b) including a contribution to said power from a sample at the second end of the window; and
(c) calculating a power in unused carriers of the FFT after steps (a) and (b) ; repeating steps (a) - (c) ; selecting an active position of the FFT window, in order to minimise said power in unused carriers of the FFT.
6. A COFDM receiver, comprising a FFT processor, and means for selecting a position of a FFT window, in order to minimise the effects of inter-symbol interference in the FFT output .
PCT/GB2001/001140 2000-03-15 2001-03-15 Method of selecting a position of a fft window in a cofdm receiver WO2001069878A1 (en)

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GB0006217A GB2365714A (en) 2000-03-15 2000-03-15 Minimising effects of inter-symbol interference in receiver
GB0006217.4 2000-03-15

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Cited By (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP1330091A1 (en) * 2002-01-22 2003-07-23 STMicroelectronics S.A. Method of selecting a position of a FFT window in a COFDM receiver
WO2005002164A1 (en) * 2003-06-30 2005-01-06 Nokia Corporation Faster fine timing operation in multi-carrier system
FR2868640A1 (en) * 2004-03-31 2005-10-07 St Microelectronics Sa COFDM DEMODULATOR WITH OPTIMAL POSITIONING OF FFT ANALYSIS WINDOW
EP1416693A3 (en) * 2002-10-28 2006-11-15 Sony United Kingdom Limited Symbol timing recovery in a multicarrier receiver
US7769094B2 (en) 2006-11-10 2010-08-03 Telefonaktiebolaget L M Ericsson (Publ) Arrangement and method for reducing the impact of interfering signals in a communication system
WO2010138590A3 (en) * 2009-05-26 2011-04-21 Qualcomm Incorporated Method and apparatus for selecting the placement of the sampling window
JP2013229763A (en) * 2012-04-25 2013-11-07 Nippon Hoso Kyokai <Nhk> Reception apparatus and program

Families Citing this family (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US8675631B2 (en) 2005-03-10 2014-03-18 Qualcomm Incorporated Method and system for achieving faster device operation by logical separation of control information
US8165167B2 (en) 2005-03-10 2012-04-24 Qualcomm Incorporated Time tracking for a communication system
US7623607B2 (en) * 2005-10-31 2009-11-24 Qualcomm Incorporated Methods and apparatus for determining timing in a wireless communication system
US8948329B2 (en) 2005-12-15 2015-02-03 Qualcomm Incorporated Apparatus and methods for timing recovery in a wireless transceiver

Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0837582A2 (en) * 1996-10-18 1998-04-22 Alpine Electronics, Inc. Symbol synchronization in a DAB receiver
EP0841787A2 (en) * 1996-11-07 1998-05-13 Kabushiki Kaisha Kenwood Synchronisation in a multicarrier receiver
US5848107A (en) * 1995-08-16 1998-12-08 U. S. Philips Corporation Transmission system with improved symbol processing
WO1999017493A1 (en) * 1997-09-30 1999-04-08 Samsung Electronics Co., Ltd. Fft window position recovery apparatus and method for ofdm system receiver

Family Cites Families (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
KR100230271B1 (en) * 1997-01-10 1999-11-15 윤종용 The fine fft window position recovery apparatus for ofdm system
KR100230332B1 (en) * 1997-08-30 1999-11-15 윤종용 FFT window position recovery apparatus for OFDM system receiver and method thereof
DE60029687T2 (en) * 1999-06-22 2007-10-18 Matsushita Electric Industrial Co., Ltd., Kadoma Symbol clock synchronization in multi-carrier receivers

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US5848107A (en) * 1995-08-16 1998-12-08 U. S. Philips Corporation Transmission system with improved symbol processing
EP0837582A2 (en) * 1996-10-18 1998-04-22 Alpine Electronics, Inc. Symbol synchronization in a DAB receiver
EP0841787A2 (en) * 1996-11-07 1998-05-13 Kabushiki Kaisha Kenwood Synchronisation in a multicarrier receiver
WO1999017493A1 (en) * 1997-09-30 1999-04-08 Samsung Electronics Co., Ltd. Fft window position recovery apparatus and method for ofdm system receiver

Cited By (14)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US7203244B2 (en) 2002-01-22 2007-04-10 Stmicroelectronics S.A. COFDM demodulator with an optimal FFT analysis window positioning
FR2835136A1 (en) * 2002-01-22 2003-07-25 St Microelectronics Sa COFDM DEMODULATOR WITH OPTIMAL FFT ANALYSIS WINDOW POSITIONING
EP1330091A1 (en) * 2002-01-22 2003-07-23 STMicroelectronics S.A. Method of selecting a position of a FFT window in a COFDM receiver
EP1416693A3 (en) * 2002-10-28 2006-11-15 Sony United Kingdom Limited Symbol timing recovery in a multicarrier receiver
WO2005002164A1 (en) * 2003-06-30 2005-01-06 Nokia Corporation Faster fine timing operation in multi-carrier system
US7577087B2 (en) 2003-06-30 2009-08-18 Nokia Corporation Faster fine timing operation in multi-carrier system
FR2868640A1 (en) * 2004-03-31 2005-10-07 St Microelectronics Sa COFDM DEMODULATOR WITH OPTIMAL POSITIONING OF FFT ANALYSIS WINDOW
WO2005096581A1 (en) * 2004-03-31 2005-10-13 Stmicroelectronics Sa Cofdm demodulator with optimal fft analysis window positioning
US7680195B2 (en) 2004-03-31 2010-03-16 Stmicroelectronics S.A. COFDM demodulator with an optimal FFT analysis window positioning
US7961803B2 (en) 2004-03-31 2011-06-14 Stmicroelectronics S.A. COFDM demodulator with an optimal FFT analysis window positioning
US7769094B2 (en) 2006-11-10 2010-08-03 Telefonaktiebolaget L M Ericsson (Publ) Arrangement and method for reducing the impact of interfering signals in a communication system
WO2010138590A3 (en) * 2009-05-26 2011-04-21 Qualcomm Incorporated Method and apparatus for selecting the placement of the sampling window
US8655294B2 (en) 2009-05-26 2014-02-18 Qualcomm Incorporated Method and apparatus for position signal assisted window placement
JP2013229763A (en) * 2012-04-25 2013-11-07 Nippon Hoso Kyokai <Nhk> Reception apparatus and program

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