RU2724794C1 - Method of transmitting information using a substituting logical ternary noise-resistant code - Google Patents

Abstract

FIELD: information transmission system.SUBSTANCE: invention relates to systems for transmitting information and can be used to increase noise immunity of received messages and digital signals in interference conditions. Symbols S(i = 0, 1, 2) of ternary code are duplicated by corresponding symbols T(i = 0, 1, 2), which are represented by pulse-width modulation (PWM) with corresponding values of pulse duration: T, T= 1.5Tand T= 2T, where Tis duration of initial symbols of binary code "1" and "0". Essence of the invention is also that generated PWMpulses T, T= 1.5Tand T= 2Tis filled in the next step of encoding the binary Barker code symbols, respectively, and with a duration of each of them (τ), 4 times smaller than T. To expand the signal spectrum, each of the Barker codes is used, complemented at the end of the code structure with a binary symbol "1", filling the initially formed pauses in a single spreading code sequence. As a result, broadband communication is realized. Also, it seems necessary when using algorithms of fast Fourier transform (FFT) in data transmission systems, which is oriented only for certain duration of bits.EFFECT: technical result consists in simultaneous meeting of two requirements: reduced redundancy of transmitted symbols of digital code and high noise-immunity of reception thereof based on a transition before modulating the signal with a pulse sequence, having not two code symbols "1" and "0", and three symbols S(i = 0, 1, 2) of the ternary code, which are in form of amplitude-pulse modulation (APM) with corresponding values of pulse amplitude: A, Aand A.3 cl, 8 dwg

Description

The invention relates to telecommunication systems and can be used in data transmission systems over communication channels. It is aimed at resolving the existing set of contradictions in this field of science and technology, which arise due to the need to further increase the transmission speeds of information under the existing restrictions on the budget of communication channels, which leads to a deterioration in the reliability of its reception.

A crisis of such a plan is already becoming a reality when transmitting information from spacecraft (SC) used for remote sensing of the Earth (ERS) and from many other highly informative data sources. Due to existing international contradictions, fierce competition, and in some cases claims to world domination, it can become a global problem in the transition to the use of modern means of electronic warfare (REP). Also, similar problems are now and without the use of REP means leading to an accelerating increase in the number of radio stations operating in the short-wave range, when due to their large number the level of mutual interference grows, and the task of spectrum allocation under conditions of strict regulation of its use has become difficult to solve. At the same time, the struggle to increase the reliability indicators of the information obtained, which was previously successfully solved due to excessive noise-resistant coding, also leads to failures, since the operability of known methods is determined by the boundary in the form of an indicator of the probability of distortion of bits P _b ≤10 ^-2 . The more real values of P _b differ from this boundary (10 ^-2 ) in the direction of its decrease, the higher the corrective ability of known noise-resistant codes [7]. However, in a number of cases, the number of which is growing rapidly, this value becomes larger than the border: P _b > 10 ^-2 , as a result of which the already introduced redundant noise-resistant codes become harmful - their use leads to even greater deterioration of the information received compared to that situation, when error-correcting coding is absent. Among developed countries, this situation is becoming increasingly critical for the Russian Federation due to the fact that since 1991, for economic reasons, the development and production of high-performance antenna systems has stopped. Consequently, unconventional solutions to this problem, which do not require large expenses for their implementation, are of particular relevance. Such proposals currently exist, and they focus on the following two main components:

1) to distributed structural-algorithmic transformations (SAP) used in the transmission and reception of information [1, 2, 4, 5, 8];

2) on methods of mathematical processing using the constructive theory of finite fields and adaptive nonlinear filtering [12, 13, 14].

The present invention relates to the field of distributed structural-algorithmic transformations (SAP) used in the transmission and reception of information. It summarizes the previous experience in the development of inventions [1, 2, 4, 5, 8] and defines a new direction for their improvement associated with the use of information not only narrow-band, but also broadband communication channels [6, 9].

Its use allows to increase the reliability of information transfer without introducing structural redundancy in the transmitted messages, to detect errors occurring during transmission, both single and multiple, thereby increasing the reliability of the received data. When applied, it becomes possible to increase, if necessary, the speed of information transfer and ensure its secrecy on the basis of new reserves in the form of replacing one data presentation system (number system) with another - more economical, taking into account the specific features of the transmitted information.

The well-known "Methods of transmitting information and systems for their implementation" (patent RU No. 2475861 with priority dated April 27, 2013 [1] and patent RU No. 2581774 with priority dated September 30, 2014 [2]).

The patent [1] provides a sequence of operations by which the algorithm of economical noise-resistant coding is implemented, and also one of the possible options for the implementation of the patent based on logic circuits is presented. Plots explaining the basic logical operations and forming the basis of the proposed transition from traditional binary coding to its replacement code based on duplicate ternary symbols S ₂ (T ₂ ), S ₁ (T ₁ ) and S ₀ (T ₀ ) are shown in FIG. 1 and 2. Structural diagrams of devices that implement the method [1] are shown in FIG. 3 and 4. Moreover, in FIG. 4 is a logical diagram of a ternary code generator 5 based on symbols S ₂ (T ₂ ), S ₁ (T ₁ ), and S ₀ (T ₀ ). In FIG. 4 are represented by letters a) to f) informational sections that coincide with the corresponding designations used in the designations of the diagrams shown in FIG. 1 and FIG. 2.

The main objective of the patent [1] was to show the possibility of a fairly simple implementation of the possibility of transition from binary code to the proposed ternary coding based on the binary logic of the existing element base.

The disadvantage of the invention [1] lies in the fact that the potentialities of the proposed ternary coding have not been fully disclosed. In particular, new properties of the proposed ternary code were not announced and demonstrated from the point of view of combining the principles of narrowband and broadband in one technical solution. In the existing theory and practice of information transfer, options for their separate use are considered. At the same time, broadband communication was singled out as an independent area for improving telecommunication systems (TCS), which was originally oriented to military systems that ensure stealth and noise immunity of information transmission (Noise-like signals in information transmission systems / Edited by VB Pestryakov. - M .: Sov. Radio, 1973. - 424 p. [6], Semenov AM, Sikarev A.A. Broadband - M .: Voenizdat, 1970. - 280 p. [9]). The transition to broadband communication proposed therein is carried out by filling in the initial modulating pulse sequence of the symbols “1” and “0” of the initial binary code with a duration of T ₀ , a broadband pulse signal with a duration of τ ₀ : τ ₀ << T ₀ and, accordingly, the base signal B = T ₀ / τ ₀ [6]. However, they do not consider the possibility of preliminary translation of the initial positional binary code into another more economical system for presenting data and transmitted messages. At the same time, cost-effectiveness is considered from the point of view of reducing the redundancy of the transmitted symbols of digital signals, reducing the density of changes in the modulation state of the carrier radio frequency [3] with constant indicators of the amount of transmitted information and data transfer rates. In the previous inventions [1, 2, 4, 8] it was shown that such symbols can be not only the traditionally used “1” and “0” binary codes, but also ternary code symbols represented, for example, by conditional symbols S ₂ (T ₂ ), S ₁ (T ₁ ) and S ₀ (T ₀ ) [2].

In the patent [2], which was awarded the diploma of Rospatent in the nomination “100 best inventions of Russia 2016”, the proposed ternary code with the symbols S ₂ (T ₂ ), S ₁ (T ₁ ) and S ₀ (T ₀ ) was used for a new purpose - to increase the information load on the carrier frequency emitted by the transmitter, for which the simultaneous (complex) modulation in amplitude, frequency and phase was used. In addition, there was ensured “comparability of the results of the relative phase modulation demodulation (OFM) with base two, applied over the main communication channel, and the proposed ternary phase modulation with base two (FM ₂ ³ ), the basis of which are logic noise-resistant codes with base three, presented symbols S ₂ (T ₂ ), S ₁ (T ₁ ) and S ₀ (T ₀ ) "(paragraph 4 of the claims). However, to realize this possibility, an additional (duplicate) channel for transmitting information is required, which cannot always be provided in a variety of practical applications. The essence of the proposed logical error-correcting coding of generated messages by the replacement ternary code in its original form is as follows [1, 2].

The basis of the method is the transformation formulas F associated with replacing the sequence of characters a _i0 , a _il , ..., a _{in the} binary alphabet A = {0,1} with sequences of characters d _i0 , d _i1 , ..., d _{im of the} alphabet D = {00, 11 , 10, 001, 101} based on the following coding logic:

The proposed encoding establishes a logical correspondence between the binary characters represented in brackets and their ternary equivalents S ₀ , S ₁ and S ₂ .

In addition, when receiving signals S ₀ , S ₁ and S ₂ provide their duplication by the signals T ₀ , T ₁ and T ₂ (Fig. 1 (a) and Fig. 2 (f)). As a result of this, two modulating sequences are formed based on the signals S ₀ , S ₁ , S ₂ and the signals T ₀ , T ₁ , T ₂ . Moreover, if the signals S ₀ , S ₁ , S _{2 are} presented in the form of pulse-amplitude modulation into three states (AIM ₃ ), then the signals T ₀ , T ₁ , T ₂ corresponding to them are displayed in the form of pulse-width modulation (PWM ₃ ), which also has three allowed positions of the pulse durations T ₀ , T ₁ = 1.5T ₀ , T ₂ = 2T ₀ , where T ₀ is the time duration of the symbols “1” and “0” of the source binary code. As a result of this, the stream of digital data generated for transmitting, which is initially displayed by the sequences of symbols “1” and “0” of the binary code, after transcoding into a logic noise-resistant ternary code with the symbols S ₂ (T ₂ ), S ₁ (T ₁ ) and S ₀ ( T ₀ ), represent two duplicate streams at the level of the primary (pulse) modulation: AIM ₃ and PWM ₃ . The possibility of such a representation of the initial stream of transmitted symbols at the level of primary (pulse) modulation by two copies using AIM ₃ and PWM ₃ has no analogues except for the source [1] and [2]. Their structural diagrams are shown in FIG. 3 and 4. In the most general form, a structural diagram of a system for implementing the proposed method, including both transmitting and receiving sides, is shown in FIG. 3. In relation to the on-board radio telemetry system (BRTS), the transmitting side contains: sensors - 1 ₁ , 1 ₂ , ..., 1 _N , the outputs of each of which are connected to the corresponding N inputs of the signal compression and synchronization unit 2, the output of which is connected to the input of the transmitter 3 Block 2 compaction and synchronization of signals contains a switch 4, N inputs of which are inputs of block 2, the shaper 5 of the logical ternary code and the shaper 6 of the clock signals. The output 7 of the switch 4 is connected to the first input of the shaper 5 of the logical ternary code, the first output 8 of which is the output of block 2, and the second output 9 is connected to the input of the shaper 6 of the clock signals, the output of which is connected to the (N + 1) input of the switch 4. Output the transmitter 3 through the communication channel 10, subject to interference 11, is connected to the input of the receiver 12.

The receiving side contains a receiver 12 having three outputs - one service output 22 connected to the input of the synchronization signal selector 13, and two information connected to the first inputs 25, 26 of the demodulators 15 and 14 of the information signals, respectively, the second inputs of which are combined and connected to the first output 23 of the synchronization signal selector 13, the second output of which is connected to the combined second inputs of the corrector 18 and 19 of transmission errors, the first inputs of which are connected to the outputs of the corresponding demodulators 14 and 15 of information signals through the corresponding decryptors 16 and 17 of the information signals, the outputs of the corrector 18 and 19 transmission errors are connected to the first and second inputs of the former 20 of the general message flow, the output of which is connected to the input of the decomposer 21, the N outputs of which 27 ₁ 27 ₂ , ..., 27 _N are the outputs of the system. In FIG. 4 is a structural diagram of a logical ternary code generator 5 based on the symbols S _i (T _i ), i = 0, 1, 2, and FIG. 3 and FIG. 4 are diagrams explaining his work. In this case, the plots presented in FIG. 1, and denoted by the letters “a” to “m”, are considered the beginning of the diagrams, and the diagrams shown in FIG. 2, and indicated by the letters "m" to "f" are their continuation. In order to present them as a whole, it is necessary to combine the images shown in FIG. 1 and FIG. 2, at the level of the diagram indicated by the repeated letter “m”. The same lettering is shown in FIG. 4. It defines those cross-sections of transformations of the logical ternary code generator 5 based on the symbols S _i (T _i ), i = 0, 1, 2, which correspond to the diagrams shown in FIG. 1 and FIG. 2.

The block diagram of shaper 5 logical ternary code (. Figure 4) comprises: synthesizer 28, the fundamental frequency of high stability code transformations repetition pulse sequence in which the time intervals between the pulses are equal to T _0/4, the divider 29 into two basic pulse repetition rate, resulting in the formation of intervals between pulses T _0/2 , the generator 30 of the synchronizing meander, as well as the synchronizer 31, at the output of which form highly stable binary code symbol boundaries of the generated group signal, multiples of T ₀ . The group signal generated at the output 7 of the switch 4 (Fig. 3) may, for example, be the result of temporary data compression, supplemented by synchronization words and other service parameters.

At the output of the synchronizer 31, a binary video signal is generated from a sequence of binary symbols “0” and “1” (Fig. 1 (diagram “g”)) with increased stability of the moments of change (following) of binary symbols of a group telemetry signal (GTS).

In addition, the generator 5 of the logical ternary code based on the symbols S _i (T _i ), i = 0, 1, 2, (Fig. 4) contains: logical elements “NOT” 32, “AND” 33 ₁ , 33 ₂ , and 33 ₃ , “Prohibition” 38, “OR” 39, four triggers 34 ₁ , 34 ₂ , 34 ₃ and 34 ₄ , five formers 35 ₁ , 35 ₂ , 35 ₃ , 35 ₄ , 35 ₅ converted sequences of clock pulses, each of which consists of series-connected differentiating elements 36 ₁ , 36 ₂ , 36 ₃ , 36 ₄ , 36 ₅ and limiters 37 ₁ , 37 ₂ , 37 ₃ , 37 ₄ , 37 ₅ , as well as a decoder 40, a signal modulator 41 and a signal shaper 42 Prohibition X) (Fig. 2, plot “o”). The input 7 of the logical ternary code generator 5 is the source binary code represented by the diagram “c” (Fig. 1), and the diagrams “f” and “o” are informational 8 (Fig. 1 “f”) and service 9 (fig. . 1 (“o”, mark X)) prohibiting the outputs of the driver 5, respectively.

As a result of the proposed transformations, the binary code of the group signal generated by the switch 4, composed of a sequence of binary symbols “0” and “1”, is converted into a ternary code represented by the symbols “S ₀ ”, “S ₁ ” and “S ₂ ”, which are associated with pulse-amplitude modulation (AIM ₃ ), and the symbols "T ₀ ", "1.5T ₀ " and "2T ₀ ", which are pulse-width modulation (PWM ₃ ). The proposed logical rule for converting a binary code into a ternary replacement code has one inaccuracy, which, when implemented, leads to one of the exceptions to the adopted logical error-correcting coding rule, which is marked on the diagrams “n” and “o” (Fig. 2) with a dashed line and marked the letter X. The exception is that the time interval corresponding to the symbol "2T ₀ ", when the proposed conversion of binary to ternary code is indicated by double pulses (plot "o"), separated from each other by T _0/4 . In the shaper 5 of the logical ternary code, they are isolated in the shaper 42 of the signals and used to count in the shaper 6 clock signals the number of code combinations of the form "101". The decoder 40 twin pulses spaced apart by T _0/4 is converted with PAM ₃ in amplitude corresponding «S _2", and when the PWM ₃ - in the time interval "2T _0". As a result of this, at the output 8 of the signal modulator 41 a signal is generated that is simultaneously modulated both in amplitude (AIM) and pulse duration (PWM) (Fig. 2 (diagram "f")).

As a result of this, instead of only one type of primary pulse modulation of the transmitted information, for example, AIM, PWM, or KIM, two of them will be used together: AIM ₃ and PWM ₃ . Such an opportunity appears for the first time when using substitute logical economical noise-resistant coding. It is economical for the reason that the number of generated ternary symbols “S ₀ , T ₀ ”, “S ₁ , T ₁ ” and “S ₂ , T ₂ ” will be reduced on average in k = log ₂ 3 = 1.6 times, as shown in FIG. 5. In the original binary sequence there were 16 bits, and after transcoding into the proposed logical economical error-correcting code, the number of ternary symbols “S _i , T _i ”, i = 0, 1, 2 is 10. At the same time, the time interval for the presentation of the transmitted code sequence of pulses decreased from 16 τ ₀ , where τ ₀ = T ₀ , to 15 τ ₀ . As a result of this, when transcoding messages (in our example, the original 16-bit binary), a kind of separation gap appears, which can be additionally used to increase the accuracy of synchronization and highlighting information words. This also includes one of the advantages (essential characteristic) of the proposed transmission method using substitute logical economical noise-resistant coding.

In accordance with the existing theory of information transfer, this essential characteristic of the claimed method can be considered from various positions of its novelty. The first of them is data compression during transmission, which differs from known methods not only in that it is “compression without distortion”, i.e. compression, in which additional errors do not appear when transmitting information due to a reduction in the redundancy of the transmitted information. The second theoretical position is that data compression should lead to the use of error-correcting coding, and all error-correcting codes known before the invention [1] are redundant [7]. Moreover, in accordance with the theory of error-correcting coding [7], redundancy can only be introduced (artificially generated and added to the transmitted code structures). This well-known theoretical position was destroyed with the advent of patents [4] and [8]. Their basis is the use not of special input, but of internal redundancy of the transmitted information, which, for example, appears in the presence of a correlation between neighboring values of the transmitted information. Almost all known sources of information possess such properties. At the same time, some of them, for example, streaming video, radio engineering measurements (telemetry, navigation information) have pronounced properties of the correlation dependence between adjacent values. So, for example, when transmitting video information and telemetry, the internal redundancy of the transmitted data is more than 90%.

It was shown in [4] that such a possibility of economical low-redundant noise-resistant coding, requiring, in the general case, introducing into each of the transmitted messages only one additional binary symbol “1” or “0”, appears when converting the initial values of the transmitted messages into residual images As a result, from the traditional positional representation of data, they are moving to a more economical number system in the form of a system of residual classes (RNS) [10, 11]. This character may not be entered when using the technology of "check characters for parity of bits in a word." In accordance with the new concept, it can be additionally loaded with the function of distinguishing between two states of code structures, the probability of occurrence of which is equal to: P = 1 / n, where n = N / 2 is a value equal to half the number of binary digits that represent words or messages.

In the second case (patent [8]), one of the variants of non-redundant noise-resistant coding is used, which, in terms of increasing the noise immunity of the communication channel, is equivalent to presenting data in the RNS [4, 10, 11, 12], but does not require the introduction of additional characters in the original code sequence words or messages. It was shown in [8] that this idea can be implemented in the simplest way, the essence of which is to divide the original N-bit code structure into two code segments of lower bit capacity, for example, into the lower and upper halfwords with their subsequent permutation in places with a new one formed ( encoded) word or message. But at the same time, as a kind of payment for simplification, you will have to pay with the absence of one of the additional capabilities to control the reliability of their reception.

Thus, the proposed method can be considered as a continuation of the topic related to increasing the efficiency of information transfer based on its additional economical coding at the next stage of SAP, which precedes signal modulation, patents [1, 2, 4, 5, 8]. Moreover, in addition to the processes of parallelizing the operations of generating and transmitting information based on the unconventional representation of data in the RNS [4], an additional procedure is used for the simultaneous use of two signals of primary pulse modulation. A similar method of parallelizing the streams of transmitted symbols has been developed in relation to the process of secondary modulation (modulation of the carrier frequency of radio signals), which follows the operation of primary modulation. A known method of parallelizing the flows of the generated digital group signal is associated with the formation of its quadrature components: in-phase (Q (t)) and quadrature (I (t))) (Feer K. Wireless digital communication. Methods of modulation and expansion of the spectrum (Wireless Digital Communications: Modulation and Spread Spectrum Applications). - M.: Radio and Communications, 2000. - 552 p. - ISBN 5-256-01444-7 [3]). Moreover, the stream of binary codes “1” and “0” formed for transmitting binary code symbols, which is a digital group signal (DCH), is divided into two components, one of which is conditional “odd” bits (in-phase bit stream (Q (t) ), and the second “even” bits (quadrature stream of divided bits (I (t)). The need to use a similar method of dividing the original stream of binary symbols of digital group signals (DGS) have to deal with high data rates in high-speed radio links (VRL) , for example, when transmitting information from spacecraft (SC) remote sensing of the Earth (ERS).

The fact is that the spacecraft’s profitability is determined by its ability to transmit a larger stream of information per unit time, therefore, at present, the required transmission speed is several times higher than the current performance of the element base (EB), on the basis of which they create on-board electronic equipment (REA) satellites. The phased separation of the initial generated CCH stream represented by binary code into sub-flows reduces the performance requirements of the RE CE. The resulting technical output effect is determined by the degree of parallelization of the CGS of the initial stream. Until now, the main method of deep parallelization, which is necessary for the implementation of a telecommunication system (TCS) based on the existing RE CE, has been associated only with the possibility of multiple separation of the source stream in accordance with the method of K. Feer, which involves sequential division of the source code sequence into even and odd bits.

The essential characteristics of the proposed method also consist in providing such reproduction of copies of the transmitted data stream and symbols of various codes. But its difference lies in the fact that parallelization of data streams on the transmitting side is carried out even before the modulation operation: first, by unconventionally representing the values of words or messages with their residual images, which is described in detail in the patent [4], and then also based on replacing the time of information transmission of logical economical noise-resistant coding with ternary symbols S ₂ (T ₂ ), S ₁ (T ₁ ) and S ₀ (T ₀ ). As a result of this transformation of the structures of the transmitted data are carried out in various information sections of the path for generating messages and transmitted information, and not only at the final stage associated with the secondary modulation of the transmitted signals [3]. In addition, the distinctive features of the present invention are associated with the need to combine similar structural-algorithmic transformations (CAD) related to the coding and modulation of signals into a single consistent information system, which forms the basis for the synthesis of various problem-oriented structural-code (CCC) and signal-code constructions (CCC). Its consistency is in accordance with the intent of the present invention as follows. It is necessary to ensure compatibility of the various proposed distributed methods of SAP-i, where i are the various information sections of the path for generating the transmitted information, while realizing the possibility of using the existing SAPs without loss in efficiency in the form of data compression algorithms, their noise-resistant coding using known methods, scrambling, encryption, randomization, and creating additional opportunities for parallelizing the generated data streams of high-speed information. Moreover, each of the information sections of the SAP-i implementation should be a corresponding element of the conveyor process of conversion on the transmitting side, and restoration with sequential correction of transmission errors and distortions when receiving information. This principle of the formation, transmission and reception of information provides the best conditions for the implementation of an integrated system for protecting the transmitted information from interference, foreign technical intelligence (ITR) and information technology impact (ITV) [15].

The well-known "Method of transmitting information and a system for its implementation" ([4], patent RU 2586605). In it, for additional parallelization of the paths for forming copies of the transmitted information, an unconventional representation of data and messages using their residual images is used. In this case, the initial data and / or message stream is divided into sub-streams, each of which consists of residual images, which are independent information elements of lower bit depth. Thus, one more option is obtained for additional duplication of the initial stream of transmitted data and / or messages. As a result of this, a deeply parallelized structure for presenting data and / or messages with new CCMs and CCMs is created, as a result of which the information load of the carrier frequency of the transmitted signal is increased.

In patents RU 2475861 C1, publ. 03/22/2013, bull. No. 16 [1] and RU 2480840 C1, publ. 04/25/2013, bull. No. 21 [5] methods of reverse CAD operation and signal demodulation with complex modulation are developed. The proposed algorithm for transcoding the source binary code with the characters "1" and "0" is as follows. Given a sequence of binary characters <10101000111100101> ₂ (N ₁ = 17). It is necessary to translate it into a new alphabetical coding using the upper and lower partitions (ℜ1 and ℜ2):

ℜ1, ℜ2: S ₂ S ₂ S ₁ S ₀ S ₁ S ₀ S ₀ S ₀ S ₁ S ₁ S ₂ - a new sequence of 11 characters S _i (i = 0, 1, 2) used to transmit information.

As a result of encoding, the last binary character of the previous encoded package S _i repeats the first binary character of the subsequent ternary package S _{i + 1} (duplicate binary characters are highlighted in bold and circled). If at reception these conditions are not provided, then this indicates an error. Error correction is provided with reliable reception of S ₂ characters, which are uniquely decrypted in the form of the source code combination of the binary code "101": S ₂ ⇔ (101).

The proposed method for recovering transmitted information is as follows. Suppose that, as a result of demodulation, the following fragment of the sequence of ternary signals S _{i is} restored:

1 The first data recovery operation in the source binary code is to extract S ₂ signals that can be unambiguously decrypted: S ₂ ↔ “101”. As a result of this, in the received sequence (2), a sign of receiving the symbol S _{2 is formed} , which is allocated to control the reliability of receiving the symbols S ₁ in the time interval between adjacent symbols S ₂ :

2 Conversion to binary code of the entire sequence of received ternary characters begins with the fact that they write in binary code the result of unambiguous decoding of S ₂ characters:

To control the reliability of receiving S ₁ symbols in the time interval between adjacent S ₂ symbols, the following rule is used: the number of S ₁ symbols must be even.

3 Then, using the first of the received signs of receiving the symbol S ₂ , they begin to decipher the ternary symbol S ₁ following it, which is associated with not one, but two code combinations composed of binary symbols: S ₁ ↔ “10” and “001 ". Since, according to the condition for generating the proposed ternary code, the last binary character of the previous decryption 101 should be the first character of the subsequent decryption of the ternary character (in the given signal reception S ₁ ), then the code combination 10 should be selected as a replacement candidate. Choosing the appropriate next code combination corresponding to the received signal S ₁ is determined by the last binary character obtained by decoding the previous signal of the ternary code S ₂ (matching characters are shown in bold).

Next, the next restored ternary symbol corresponds to the signal S ₀ , which also has two possible decryption options: S ₀ ↔ "00" and "11". Since the previous decoding 10 ended with the binary character “0”, the next signal S ₀ must be replaced by a binary code combination consisting of two characters “0” - 00. Similarly, the next restored ternary character S ₁ ↔ “10” and “001” must be replaced by binary code 001. Then two characters S ₀ ↔ “00” and “11” follow in a row and, since the decoding of the previous binary code combination ended with the character “1”, the two subsequent ternary characters S ₀ must be replaced by a sequence consisting of two characters “1” - 11. The fact that the decryption was done correctly is evidenced by the fact that the next ternary character will again be S ₂ ↔ “101”, which starts with the same binary character “1”, which is obtained at the end of the previous decryption of the signal S ₀ . The subsequent recovery process of transmitted messages in traditional binary code is similar. The correcting ability of the proposed code lies in the fact that the entire chain of ternary symbols recovered during reception is determined by the reference signals S ₂ ↔ "101".

4 The following operation assumes that the adopted sequence of ternary symbols S ₁ and S ₀ , allowing ambiguous decryption

replaced with a binary code so that the last binary decryption symbol of the previous symbol S _i , where i = 0, 1, 2, coincides with the first decryption symbol of the subsequent symbol S ₁ or S ₀ .

As a result of this, for sequence (6), the following restored source binary code sequence is obtained:

where the "dots" are divided among themselves the results of decoding the symbols S ₁ and S _{0 of the} ternary code.

Then, the matching binary symbols at the boundaries of the decoding of ternary signals S _i , where i = 0, 1, 2, are combined and replaced with one corresponding binary symbol:

where matching characters are highlighted and underlined, which combine and replace with a single binary character.

As a result, the following fragment of the original binary code sequence will be restored:

The sequence of generated ternary symbols S _i , where i = 0, 1, 2 with primary AIM ₃ and ternary symbols T _i , where i = 0, 1, 2 with primary PWM ₃ are combined into a single pulse sequence of video signals (Fig. 2 "f" ) During their subsequent secondary modulation of the type: AIM ₃ - AM ₃ and AIM ₃ - FM ₃ , as well as PWM ₃ - FM ₂ ^{(3), the} modulated signal transmitted to the communication channel will have the form, a conditional illustration of which is shown in (Fig. 5) . The illustration shown in FIG. 5, allows to draw the following conclusion: 1) the use of ternary symbols S ₂ (T ₂ ), S ₁ (T ₁ ) and S ₀ (T ₀ ), allows, on average, to reduce their number by 1.6 times compared to binary code; 2) there is a certain regularity of the sequence of characters S ₁ in the intervals enclosed between adjacent signals S ₂ : the number of signals S ₁ can only be even.

A distinctive feature of the patents [2] and [3] was also that they were focused on narrow-band communication channels.

In broadband communications, as noted earlier, code binary sequences are introduced into the information pulses corresponding to the symbols “1” and “0” of the source binary code, which, upon reception based on correlation processing or matched filtering, give the main peak corresponding to the sum of their energies at minimum energy that is diverted to the side lobes. As a result of this, a signal under noise can be extracted [6].

Additional essential characteristics of the invention are as follows.

In the present invention, the possibility of combining narrow-band and broadband communication systems is realized, which can be realized by replacing the binary code with the characters "1" and "0" with a logical non-redundant noise-resistant ternary coding with the characters S ₂ (T ₂ ), S ₁ (T ₁ ) and S ₀ (T ₀ ) (Fig. 2 (B)). To switch to broadband communication, the need for which appears when it is necessary to increase the secrecy and noise immunity of information transmission, code codes are entered into the generated pulse sequence consisting of PWM ₃ pulses with durations τ ₀ , T ₁ = 1.5τ ₀ , T ₂ = 2τ ₀ pseudo-random sequences (PSP). In their quality, for example, Barker codes with lengths of code structures 7, 5 and 3 are used (Fig. 2 (B)). Moreover, in the pulses corresponding to the symbol T ₂ = 2τ ₀ , enter the Barker code of length 7 in direct form: 1110010 (Fig. 2 (B)). Similarly, the pulses corresponding to the symbols T ₁ = 1.5τ ₀ are filled with a Barker code of length 5 in the inverse form: 00010. Finally, pulses with a duration of τ ₀ corresponding to the clock pulses of generating the symbols of the source binary code (Fig. 1 (c) ) and equal symbols T _{0 of the} proposed ternary code, identical by decoding to symbols S ₀ , substitute a Barker code of length in direct form 3: 110 (Fig. 2 (B)). Moreover, the duration of the substituted characters “0” and “1” of the Barker codes (τ _0Б ) is 4 times less than the original binary code (τ ₀ ): τ _0Б = 1/4 τ ₀ .

которые всегда независимо от исходной кодовой группы кодов Баркера заканчиваются следующей последовательностью бит:

Это стало возможным благодаря тому, что кодовая последовательность Баркера длины 5 в предлагаемом изобретении представлена в инверсном виде: 00010. Ее прямая форма 11101 не подходит, поскольку при подстановке символа «1» для заполнения неиспользовавшегося последнего промежутка времени τ_0Б=1/4 τ₀, не будет выполнено условие окончания предыдущего и начала следующего информационного импульса ШИМ₃.Then, Barker code sequences 1110010, 00010 and 110, which by definition have an odd number of bits, are supplemented to the nearest even number by filling in the remaining pauses at the end of each of them with binary code symbols “1” corresponding to a duration of τ _0Б = 1/4 τ ₀ . As a result of this, the time intervals highlighted in FIG. 2 (B) ovals, complement the characters "1", resulting in the following code combinations:

which always, regardless of the source code group of Barker codes, end with the following sequence of bits:

This became possible due to the fact that the Barker code sequence of length 5 in the present invention is presented in the inverse form: 00010. Its direct form 11101 is not suitable, since when substituting the symbol “1” for filling the last unused period of time, τ _0Б = 1/4 τ ₀ , the condition for the end of the previous and the beginning of the next information pulse of PWM ₃ will not be fulfilled.

As a result of this, when receiving, there is an additional opportunity for identifying information fronts of PWM3 pulses based on the allocation of code groups

всегда выделенная кодовая группа

будет являться признаком границ импульсов ШИМ₃ (фиг. 6 (а, б, в, г)), которые идентифицируют, как символы логического помехоустойчивого троичного кода Т₂, Т₁, Т₀, Т₁, Т₂ (фиг. 6(г)). В результате этого обеспечивают возможность идентификации границ символов Т₂, Т₁, Т₀ и восстановления исходной импульсной информационной последовательности ШИМ₃ (фиг. 6 (г)). Однако такой способ восстановления исходной импульсной информационной последовательности ШИМ₃ (фиг. 6 (г)) является дублирующим. Он не может быть основным из-за снижения значений показателя помехоустойчивости передачи информации, что связано с сокращением длительности символов «1» и «0» замещающих кодов Баркера.When receiving thus formed expanding code sequences, for example,

always allocated code group

will be a sign of the boundaries of the PWM ₃ pulses (Fig. 6 (a, b, c, d)), which are identified as symbols of a logical noise-immune ternary code T ₂ , T ₁ , T ₀ , T ₁ , T ₂ (Fig. 6 ( d)). As a result of this, it is possible to identify the boundaries of the symbols T ₂ , T ₁ , T ₀ and restore the original pulse information sequence of the PWM ₃ (Fig. 6 (g)). However, this method of restoring the original pulse information sequence of the PWM ₃ (Fig. 6 (g)) is duplicate. It cannot be the main one due to a decrease in the noise immunity indicator of information transmission, which is associated with a reduction in the duration of the symbols “1” and “0” of the replacement Barker codes.

To eliminate this drawback with a large level of interference, when their power is equal to or greater than the power of the received useful signal, correlation processing of the reconstructed digital data is used, from which the binary code symbols “1” are additionally entered on the transmitting side (Fig. 6 (e)) for direct allocation of Barker code sequences of length 7, 5 and 3 (Fig. 6 (e)), or matched filtering of the signal-to-noise mixture (Fig. 6 (g)). As a result, based on the selection of the largest amplitude signals that are obtained by correlation processing (Fig. 6 (e)), or by matched filtering (Fig. 6 (g)), the specified amplitudes of the reconstructed information AIM ₃ and time intervals corresponding to PWM ₃ (Fig. 6 (h)).

An existing and additional option for using Barker codes of lengths 3, 5, and 7 to fill in the initial PWM ₃ information pulses obtained as a result of the transition to ternary coding. Its essential characteristics are to use the following Barker codes of length 7, 5, and 3 as substitute binary coding: 0001101 (inverse form for n = 7), 11101 (direct form for n = 5) 001 (inverse form for n = 3). Then, to fill the unused last time interval of the PWM ₃ pulses with τ _0Б = 1/4 τ _0, use the binary symbol "0". Then the impulse boundaries An existing and additional option for using Barker codes of length 3, 5, and 7 to fill in the initial information pulses of PWM ₃ obtained as a result of the transition to ternary coding. Its essential characteristics are to use the following Barker codes of length 7, 5, and 3 as substitute binary coding: 0001101 (inverse form for n = 7), 11101 (direct form for n = 5) 001 (inverse form for n = 3). Then the boundaries of the PWM ₃ pulses at reception are determined based on the appearance of the code group: 010.

As a result of this, an information reception mode corresponding to broadband principles for organizing the transmission and reception of information is implemented.

The essential characteristics of the invention are, therefore, also that the time intervals corresponding to the pulse sequence generated using the inventions [1] and [2] in the form of PWM _{3 of} different conditional polarity (Fig. 2 and Fig. 6 (a) ) are filled with binary symbols “0” and “1” corresponding to Barker codes of length 3, 5 and 7. Moreover, a pulse of different polarity corresponding to symbols S _i (T _i ) (i = 0, 1, 2) of the proposed ternary codes of the corresponding duration are filled with binary symbols “0” and “1” corresponding to Barker codes of length 3, 5 and 7, in accordance with the following rule:

1) a PWM pulse ₃ , having a time duration T ₂ = 2τ ₀ , is filled with a Barker code of length 7, presented, for example, in direct form: 1110010;

2) a PWM pulse ₃ , having a time duration T ₁ = 1.5τ ₀ , is filled with a Barker code of length 5, presented, for example, in inverse form: 00010;

3) a PWM pulse ₃ , having a time duration T ₀ = τ ₀ , is filled with a Barker code of length 3, presented, for example, in direct form: 110.

Then, when receiving the pulse boundary, the PWM ₃ is determined based on the occurrence of the code bit 101 in the transmitted sequence.

Also, the essential characteristics of the invention are that they use opposite in design Barker codes 7, 5 and 3: Barker codes of length 7 and 3 in inverse form, and the Barker code of length 5 in direct form. Then, when receiving the pulse boundary, the PWM ₃ is determined based on the appearance in the transmitted sequence of bits of the inverse code combination 010.

The use of various forms of filling pulses PWM ₃ with Barker codes of length 7, 5 and 3 expands the organization of the proposed method of transmitting information.

In FIG. 3 shows a diagram of the implementation of the proposed economical noise-resistant coding using a ternary replacement code with symbols S _i (T _i ) (i = 0, 1, 2) in general form. However, it does not provide a clear definition of how to interpret it in relation to existing equipment. This interferes with the extended use of the developed methods.

One of the possible implementations of the proposed method, which is oriented to the information collection and processing unit (BSOI) of the onboard radio telemetry system (BRTS) of the spacecraft (SC), is presented in FIG. 7.

In this embodiment, the BSOI (Fig. 7) contains: a telemetric frame forming unit (BFTK) - 1, random access memory (RAM) - 2, a microcontroller - 3, a communication unit with on-board measurement and information transmission equipment - 4, a logical ternary shaper codes with symbols S ₂ (T ₂ ), S ₁ (T ₁ ) and S ₀ (T ₀ ) - 5, Barker code generator - 6, read-only memory manager (ROM) of the telemetry frame generation unit - 7, microcontroller ROM manager - 8, ROM ROM - 9, 11, ROM ROM - 10, 12, the system bus of the information processing unit (BSOI) - 13, the system bus of the command exchange trunk (MCO) - 14, the on-board time unit (BBV) - 20, including a time sensor (DV) - 15 and a highly stable frequency generator (HFG) - 16, the terminal device (OS) of the main command exchange (MCO) - 17, the frequency generator OU MKO - 18, the long-term memory (DZU) - 19, and also the following inputs / outputs: 21 - input d signal “External second mark” of GNSS GLONASS / GPS, 22 - input “Initial time setting”, 23 - output to a radio transmitting device (RPDU) and information exchange bus: 24 - with an information collection module (MCI), 25 - with another airborne equipment (BA) of the spacecraft (SC).

The BFTK trunk consists of 2 RS485 buses (primary or backup). The physical layer of the RS485 bus complies with the EIA-485 standard. Exchange with the devices of the information collection module (ISI) is carried out in full duplex mode. On the first bus, the BFTK generates information request signals to the MSI devices, and on the second bus it receives information from the MSI devices connected to the trunk. The exchange is carried out by packages of the “UART” type, which are understood as universal asynchronous transmissions of reception and transmission. The “UART” structure of the package is shown in FIG. 8 (A). In this case, a non-redundant error-correcting coding method can be implemented [8], the essence of which is that in the transmitted 8-bit word X _i , two code segments are distinguished - the younger A _i and the older B _i half-word (Fig. 8 (B)), which are rearranged in a UART-type package (Fig. 8 (A)). As a result of this, instead of the values of X _i , the change of which with time is shown in FIG. 8 in the form of an upper graph, coded values of C _i are obtained, whose time behavior is shown in FIG. 8 as a bottom graph. The following conclusions can be drawn from it: 1) the scale for representing the values of the telemetered parameter X _i (TMP), limited by the capacity of the transmitted words, is used more efficiently; 2) the choice of the scale for representing the values of X _i can be made without fear of distortion in the form of an “off-scale” effect of the telemetered parameter (TMP) values, as a result of which one of the main problems of practical metrology can be solved most simply.

These findings can be explained based on the following examples shown in FIG. 8 (B) (upper graph): the initial range of changes in the TMP values was 550 units, while the acceptable scale of representation W = 0- (2 ^N -1) is determined by the bit depth N of the binary code (at N = 10Ш = 0 -1023) used for transmission, as a result, the potentialities of a 10-bit binary code are used with a coefficient k ₁ = 550/1024 = 0.54). The reason for this choice, worsening the accuracy of television measurements in k ₂ = 1 / k ₁ = 1.86 times, lies in the fact that in a number of cases, for example, with information-measuring support for testing aircraft, it is a priori not possible select the required sensor gain. As a result, it is not possible to reconcile the changes in the values of the controlled TMP with the bit grid of representing its data with a digital code due to the uncertainty of the change in the sensor readings over time. When used as a preliminary proposed economical non-redundant noise-tolerant one, associated, for example, with the selection of half-words from the generated code word and their subsequent interchanging (Fig. 8 (B) (lower graph)) the metrological problem of the optimal matching of the digital values of the sensor with the discharge word representation grid -measurements are decided automatically as a side technical effect. The coefficient of its use will be equal to the limiting value k _1max = _1024/1024 = 1. As a result, the standard “UART” -type package will be used, in addition to the main function and for an additional purpose, to increase the noise immunity of data transmission based on the first stage of economical noise-resistant coding associated with the selection and permutation of half-words. In this case, the proposed logical ternary code with the symbols S ₂ (T ₂ ), S ₁ (T ₁ ) and S ₀ (T ₀ ) will represent the next (second) stage of economical noise-resistant coding.

Subsequent operations that form the basis of the work proposed to implement the method of the on-board information transfer system are as follows.

Each MCI device has its own address on the trunk, which is set by cross-connection in the cable connectors connected to the devices.

The work of BFTK is as follows. It generates request packages "Code" containing the address of the local device in the MCI, represented by the first (junior) information 7 bits of the binary code word. At the same time, the sign “Start” or “Phasing” is transmitted in the 8th category of this word (meaning “0” - “Start”; “1” - “Phasing”). In this case, the presentation scale W = 0- (2 ⁷ -1) = 0-127 and the first stage of non-redundant noise-resistant coding involves, for example, dividing the original 7-bit binary word X _i into two code segments: 4 bits in the senior segment ( and _cm = 4) and 3 digits in the younger ( a _ml = 3), after which they are rearranged in places, resulting in C _i . The eighth digit is added to the encoded information word C _i , which is the sign of “Start” or “Phasing” (value “0” - “Start”; “1” - “Phasing”), resulting in subsequent passage of new words C _i with the added 8th digit will not have differences from what is used in existing practice, the transmission of TMI. Thus, it is supposed to implement internal noise-resistant coding to ensure the protection of on-board devices from distortion on the internal information exchange highways. The main source of distortions of this kind with respect to spacecraft is the aging of CEA elements and hard cosmic radiation, which significantly accelerates this process, as well as various information and technical effects (ITW), can be applied to military and dual-purpose spacecraft, as well as in fierce competition in the further exploration of outer space between leading countries claiming leadership.

By the “Start” command in the MSI devices, the channels for selecting local switches (LK _i ), i = 1, 2, 3, ... are switched from the previous one, for example, LK _i to the next LK _{i + 1} . By the “Phasing” command, the local device of the LC _{i + 1} in the MSI devices “resets” the channel counter.

In response to the request, the local MSI device issues an “Inf” package in the form of a binary eight-bit code word, which represents information from the output of the interrogated channel of the local MSI device. The word "Inf" follows the least significant forward. In this case, the data presentation scale is determined by the range Ш = 0- (2 ⁸ -1) = 0-255 and preliminary additional coding of the information prepared for transmission over the radio channel will consist in dividing the generated byte words into two 4-bit words and _{cm =} and and _ml = 4, which are then rearranged with the formation of a new codeword C _i , which then will be transferred instead of the original word X _i , the standard package of the type "UART" (Fig. 8 (A)).

Information received from the MSI devices is stored in the internal RAM of the BSOI, which is called the “mirror”. In it, to store information of each channel of any of the MSI devices, a separate RAM cell is provided. The sensor network polling program, which determines the periodic sequence of “Code” signals, is constructed in such a way that the contents of each RAM cell are updated with the polling frequency specified for this type of device.

Filling out the issued telemetric (TM) frame with information from the sensor network occurs from the internal RAM of the BSOI by interrupts following the word frequency of the issued frame, which determines its specified information content.

Writing information to the memory is carried out in blocks of 512 bytes. Filling the block with information corresponds to the information part of the telemetric frame. Access to the memory blocks for writing or reading information is carried out according to the signs, the rules for the formation of which are determined by the current operating mode of the memory. For any operating mode, the BSOI memory stores a pointer defining the address of the current record (ATZ) and a pointer corresponding to the address of the current read (ATCH). A pointer to the ATZ is a pointer to the address to which a newly formed block of information will be written. In this case, the ATCH pointer is an address pointer from which a new block of information will be read.

Information is recorded in a circular recording mode - a mode in which each subsequent recording starts with the address following the last recording address of the previous section and continues continuously until the state or mode of the television measurement system (STI) changes. When filling the entire volume of the memory, recording continues from the zero address of the memory, thereby destroying previously recorded information.

Reading of information from the BSOI memory takes place in the form of reverse playback, which is a mode in which playback is performed from the address of the last recorded information in a ring. When implementing the “PLAY” mode, only the transmission sequence of the frames recorded in the memory changes, the structure of the TM frame does not change.

BFTK receives and records in the memory of the BSOI arrays of digital TMI. The logic of the BSOI information exchange with the BCU for MCOs, the used message formats, the amount and frequency of transmitted and received information, the use of response word features, the procedure for dealing with violation of messaging, the procedure for processing the MCO text are agreed upon by a separate protocol.

Each BSOI kit contains one terminal device connected to the MCO via two information transmission lines (LPI) (main LPI and backup LPI). The address of the OSU BSOI on the MCO is set using cross-connector. This is the order of operation of the on-board telemetry system in its usual mode of transmitting TMI over a narrow-band communication channel.

However, in some cases, including during emergency situations and with ITV, requiring an increase in the reliability of receiving TMI, it may be on a command from the microcontroller 8, the transition to the mode of "broadband communication". In this case, a Barker code generator 6 is connected to the logical ternary code generator 5 with the symbols S ₂ (T ₂ ), S ₁ (T ₁ ), and S ₀ (T ₀ ), as a result of which the PWM ₃ pulses are uniquely matched to the generated pulses the symbols S ₂ (T ₂ ), S ₁ (T ₁ ) and S ₀ (T ₀ ) of the ternary code are substituted with Barker codes of length 7, 5 and 3, respectively. As a result of this, the information transfer speed will be reduced by 4 times, but it will be possible to use its correlation reception in ground stations or in specially designed consoles to them.

The technical effect resulting from the implementation of the invention will be comprehensive:

1) internal highways of information exchange will be protected from possible distortions and interference;

2) the metrological problem of inefficient use of the allocated limited bit grid for the presentation of data and messages and “off-scale” values of the measured parameters will be solved in the simplest way, thereby significantly increasing the reliability of the information received;

3) it will be possible to use the second stage of cost-effective noise-resistant coding with a ternary code with symbols S ₂ (T ₂ ), S ₁ (T ₁ ) and S ₀ (T ₀ ) to increase the carrier frequency modulation efficiency based on the simultaneously generated two-dimensional pulse modulation AIM ₃ and PWM ₃ , as well as for the transition, if necessary, to the transmission of information in broadband mode.

As a result of the development, the proposed method can be described by the following claims.

1. A method of transmitting information, which consists in collecting signals from message sources, synchronizing them over time, generating a compressed signal from collected synchronized messages represented by an N-bit binary code, and performing the following operations on generating and transmitting information on them: reducing data and message redundancy , interleaving bits and error-correcting coding with the introduction of redundant binary code check characters, the primary modulation used to convert binary code characters to a pulsed binary code having two states, conventionally designated as “low” and “high” level, corresponding to the characters “0” and "1" of the source binary code, secondary modulation based on the change in the state of the carrier frequency of the radio signal according to the law of change in the amplitudes and edges of the pulses obtained during primary modulation, characterized in that they form economical signal-code constructions designed to increase the efficiency of telecommuns ictation systems and oriented to the following stages and informational sections of the transmission signal generation path, reflecting in a certain form the sequence of transformation and presentation of the transmitted information: the first stage is associated with a discrete representation of the source, in the general case, analog signals of the transmitted information with positional binary code with the symbols “0 "And" 1 ", in which the digitized values of the initial messages are first represented by their residual images or equivalent structural-algorithmic transformations (SAP), conventionally referred to as (SAP-1), the results of the first stage SAP (SAP-1), then, if necessary, they are subjected to the following sequentially performed transformations: bit interleaving and error-correcting coding with the introduction of redundant, check symbols, after which they proceed to the second stage of the SAP, conventionally referred to as (SAP-2), which consists in transcoding the sequence of characters of the binary code "0" and “1” to new the sequence of the signal-code construction (CQC) related to the primary modulation and the formation of the signal pulse sequence of the transmitted information, which is presented using a compressed noise-resistant logical ternary code S ₀ , S ₁ and S ₂ , with duplicate corresponding symbols T ₀ , T ₁ and T ₂ {S ₀ (T ₀ ), S ₁ (T ₁ ) and S ₂ (T ₂ )}, and they are assigned the following structural code constructions (CCC) composed of the characters “0” and “1” of the encoded binary code: S ₀ (T ₀ ) ↔ <00.11>₂; S ₁ (T ₁ ) ↔ <10,001> 2 and S ₂ (T ₂ ) ↔ <101> ₂ , where the broken brackets <> ₂ show the code structures of the symbols of the source binary code “0” and “1”, aligned with symbols of the logical ternary code with conversion during primary modulation of the symbols of the ternary code S ₀ , S ₁ and S ₂ into pulse amplitude modulation (AIM) with base 3: (AIM ₃ ), and the symbols of the ternary code duplicating them T _{0 0} <00.11 >₂; T ₁ = 1.5T ₀ ↔ <10.001> ₂ and T ₂ = 2T ₀ ↔ <101> ₂ , where T ₀ = τ ₀ - the duration of the characters "0" and "1" of the original binary code, in pulse-width modulation (PWM ₃ ) with three predefined durations T ₀ , T ₁ and T ₂ , which, when the signal is secondary modulated at the level of the carrier radio frequency with a frequency (f _n ), transform the primary amplitude-pulse modulation AIM ₃ into secondary amplitude (AM) and frequency (FM) types of modulation of the carrier radio frequency (f _n ), and the second duplicating AIM ₃ type of pulse modulation - pulse-width modulation of PWM ₃ - in phase (FM) modulation of the carrier radio frequency (f _n ), and if necessary, use the next stage of the secondary modulations - quadrature modulations of the carrier radio frequency (f _n ) use the corresponding analogs of quadratic amplitude modulation (KAM, QAM - in the English interpretation) and quadrature phase modulation (CPM, QPSK - in the English interpretation).

2. The method according to p. 1, characterized in that at the stage of secondary modulation, when the primary pulse modulation in the form of AIM ₃ based on the characters S ₀ , S ₁ and S ₂ and in the form of PWM ₃ using the characters T ₀ , T ₁ and T ₂ duplicating the symbols S ₀ , S ₁ and S ₂ are transferred to the modulation of the carrier frequency (f _n ) of the transmitted radio signal, while the pulse-amplitude modulation of the AIM _{3 of the} generated video signal is converted simultaneously to the frequency modulation (FM) of the signal with three fixed values the frequency of the transmitted signal "f ₂ = f _n -Δf _d ", "f ₁ = f _n + Δf _d " and "f ₀ = f _n ", where f _n - the value of the carrier frequency of the signal, Δf _d - the value of the frequency deviation and amplitude modulation (AM) of the carrier frequency, at which the amplitude of the radio signal carrier, modulated in frequency, also acquires three stable states A ₀ , A ₁ and A ₂ , which are uniquely associated with the symbols S ₀ (T ₀ ), S ₁ (T ₁ ) and S ₂ (T ₂ ) of the ternary code, and the second component of the generated video signal is they are used for phase modulation (FM) of the transmitted signal by, for example, changing the phase by 180 ° at the boundaries of time intervals corresponding to the ternary symbols "T ₀ ", "T ₁ " and "T ₂ ", while formed on the basis of "T ₀ " , “T ₁ ” and “T ₂ ” PWM ₃ pulses in the broadband mode are filled with Barker codes with binary characters “1” and “0” of lengths 3, 5 and 7.

3. The method according to p. 1, which consists in the fact that when selecting, based on the control command received, the broadband mode of transmitting information necessary to increase the noise immunity and secrecy of its transmission, a transition is made from narrowband to broadband, for which the generated PWM ₃ pulse signals are not used for direct modulation of the carrier frequency of the radio signal, and pre-filled with binary Barker codes with the number N _{i of} binary symbols "1" and "0" equal to 3, 5 and 7 (N ₀ = 3, N ₁ = 5 and N ₂ = 7) and durations that are 4 times less than the corresponding values of the source binary code T ₀ , which are unambiguously associated with the appearance of ternary code symbols S ₀ (T ₀ ), S ₁ (T ₁ ) and S ₂ (T ₂ ) in the generated signal, the first use of Barker codes in organizing broadband communications, the code constructs of Barker codes with N ₀ = 3 and N ₂ = 7 are represented by the direct code <110> ₂ and <1110010> ₂ , respectively, and the code construction of the Bar code kera with N ₁ = 5 in the inverse form: <00010> ₂ , while to fill the last time interval in pulses of PWM ₃ equal to T _0/4 use the symbol "1" of the binary code, as a result of which the code must be transmitted over the broadband communication channel Barker designs, supplemented by the binary code symbol “1”: <1 101 > ₂ , <000 101 > ₂ and <11100 101 > ₂ , corresponding to the durations of the generated PWM ₃ pulses - T ₀ , T ₁ and T ₂ , as a result of this, upon reception information without correlation processing of the pulse boundary of PWM ₃ - T ₀ , T ₁ and T ₂ is determined based on the allocation of the code group < 101 > ₂ in the received code sequence of bits, and in the second embodiment of the use of Barker codes for organizing broadband communications, the code constructions of Barker codes with N ₀ = 3 and c N ₂ = 7 are presented in the inverse form <001> ₂ and <0001101> ₂ , respectively, and the code structure of the Barker code with N ₁ = 5 in the direct code: <11101> ₂ , while filling in the last time interval in pulses PWM ₃ equal to T _0/4 use the binary code symbol “0”, as a result of which the Barker code constructions are to be transmitted over the broadband communication channel, supplemented by the binary code symbol “0”: <0 010 > ₂ , <111 010 > ₂ and <00011 010 > ₂ , corresponding to the durations of the generated PWM ₃ pulses - T ₀ , T ₁ and T ₂ , as a result of this, when receiving information without correlation processing, the boundaries of the PWM ₃ pulses - T ₀ , T ₁ and T _{2 are} determined based on the allocation of the code group < 010 > ₂ in the received code sequence of bits.

4 The method according to p. 1, which consists in the fact that when receiving information in the broadband mode, from the received code sequence of the transmitted information with elementary code structures represented by Barker codes with N ₀ = 3, N ₁ = 5 and N ₂ = 7, the corresponding symbols of the ternary code S ₀ (T ₀ ), S ₁ (T ₁ ) and S ₂ (T ₂ ), distinguish the code combinations “101” or “010” depending on the option chosen on the transmitting side to fill the pulse sequences of the PWM ₃ code combinations The barkers, presented in direct and inverse form, delete the last binary character in each of them, and the remaining code groups are subjected to correlation processing, as a result of which they increase the signal-to-noise ratio in the received information, eliminate or reduce the effect of multipath when it is received, and the effects on receiving device of electronic countermeasures.

5. The method according to p. 1, characterized in that the system for its implementation comprises a telemetry frame forming unit (BFTK), random access memory (RAM), a microcontroller, a communication unit with on-board equipment (BA) for measuring and transmitting information, a logical ternary shaper code with symbols S ₂ (T ₂ ), S ₁ (T ₁ ) and S ₀ (T ₀ ), Barker code generator, read-only memory manager (ROM) of the telemetry block forming unit, microcontroller ROM manager, first and second ROM memory , the first and second read-only memory of the ROM, the system bus of the information processing unit (BSOI), the system bus of the command exchange trunk (MCO), the on-board time unit (BBV), which includes a time sensor (LW) and a highly stable frequency generator (HHF) device (DU) of the main command exchange (MCO), frequency generator of the OU MCO, long-term storage device (DZU), as well as the following inputs / outputs: signal input "External second GNSS GLONASS / GPS, input “Initial time setting”, access to a radio transmitting device (RPDU), an information exchange bus with an information collection module (MCI), an information exchange bus with other on-board equipment (BA) for measuring and transmitting information from a spacecraft ( SC), while the output of the telemetric frame forming unit is connected to a radio transmitting device (RPDU), and its first, second and third system buses are connected for two-way exchange, respectively, to the system bus of the information processing unit (BOI), to the information collection module (MCI) ) and to the logical ternary code generator with symbols S ₂ (T ₂ ), S ₁ (T ₁ ) and S ₀ (T ₀ ), the second and third system buses of which are connected for two-way exchange, respectively, to the first system bus of the Barker code generator and to the dispatcher ROM manager, the second and third inputs of which are connected to exchange information with the output of the first RAM (ROM) ROM and with the output of the first electrically programmed ROM (EPR) ROM, respectively, the Barker code generator on the second system bus is connected to the first input of the ROM controller of the microcontroller, the second and third inputs of which are connected to exchange information with the output of the second RAM (ROM) of the ROM and with the output of the second electrically programmed constant ( EPP) ROM, respectively, and the second system bus of the ROM controller of the microcontroller is connected via the microcontroller to the second system bus of the BOI, the third system bus of which is connected to the operational memory, and the fourth, fifth, sixth and seventh system buses are connected, respectively, to the long-term memory, to the terminal device of the command exchange trunk (MCO), to the time sensor and to the communication unit with the BA, which is connected by the system bus to another BA of the spacecraft measurements and information transmission, while the first two inputs are used to synchronize the time sensor with signals received from the global navigation satellite system (GNSS) GLONASS / GPS as “external ", and the third to reset the counter, the fourth is connected to the output of the first local highly stable frequency generator, the second bus of the terminal device (OS) of the main command exchange (MCO) is connected to the system bus of the main command exchange (MCO), and its input is connected to the output of the second frequency generator.

In terms of reverse SAP performed on the receiving side, the closest to the proposed method is patent RU 2475861 ([1]), the essence of which is that "... when receiving information, signals of the first and second carrier frequencies are simultaneously isolated, each of which is modulated phase by a digital group signal, copies of the first and second carrier frequencies are generated by local generators, which are adjusted to the received carrier signals based on the corresponding mismatch signals generated, fill in the gaps associated with the transmission of another carrier frequency at that time, by adding carrier frequencies of local generators of the corresponding frequency to the formation of the time-continuous first and second frequencies of information transfer, they are subjected to simultaneous phase demodulation, as a result of which direct and inverse copies of video signals with binary coding logic adopted for information transfer are generated, integrity and reliability of transmitted messages are checked new addition of the formed direct and inverse copies of video signals with logical levels of binary code adopted for the transmission of information ... ”.

The requirements of the existing information transfer practice, taking into account the new economic conditions, require that, on the one hand, all new information technologies are quickly implemented, which is often hindered by the basic technical solutions implemented in existing practice, and at the same time, the modernization of existing systems and systems should be minimal on costs. In conditions of such contradictions, those technical solutions that require the introduction of a minimum of corrections at the hardware level in existing systems and telemetry systems are of particular importance. As a rule, traditional methods cannot be used to resolve such contradictions, so special relevance is felt in the search for various non-traditional reserves. Their basis is the establishment of new relationships, both logical and analytical, including between new types of modulation, which appear during the transition from binary to a more economical logical ternary code, which forms the basis of the prototype invention ([2]).

As a result, the presented invention can be characterized by the following essential characteristics:

a) it creates fundamentally new conditions for increasing the efficiency of information transmission systems based on the transition from traditional positional binary coding to a more economical ternary code;

b) as a result of its use, it becomes possible to integrate into a single justified consistent system for increasing noise immunity, structural secrecy and ensuring information protection based on distributed SAP-i, which result from combining various types of noise-resistant coding and modulation of signals.

Information Sources Used

1. The method of transmitting information and device for its implementation, patent RU No. 2475861 C1, publ. 04/25/2013

2. The method of transmitting information and a system for its implementation, patent RU No. 2581774 C2, publ. 04/20/16

3. Feer K. Wireless digital communications. Modulation and Spread Spectrum Methods (Wireless Digital Communications: Modulation and Spread Spectrum Applications). - M .: Radio and communications, 2000 .-- 552 p. - ISBN 5-256-01444-7.

4. The method of transmitting information and a system for its implementation, patent RU No. 2586605 C2, publ. 06/10/16

5. The method of transmitting information and device for its implementation, patent RU No. 2480840 C1, publ. 04/25/2013

6. Noise-like signals in information transmission systems / Ed. V.B. Pestryakova. - M .; Owls Radio, 1973.- 424 p.

7. Bleikhut R. Theory and practice of error control codes. - M .: Mir, 1986 .-- 576 p.

8. The method of transmitting information and device for its implementation, patent RU No. 2609747, publ. 2.02.17 g.

9. Semenov A.M., Sikarev A.A. Broadband M .: Military Publishing. 1970 - 280 p.

10. Torgashev V.A. The system of residual classes and the reliability of the computer. M .: Sov. Radio, 1973. 120 p.

11. Akushsky I.Ya., Yuditsky D.I. Machine arithmetic in residual classes. M .: Sov. Radio, 1968.140 s.

12. Kukushkin S.S. Finite-field theory and computer science: In 2 volumes - volume 1: Methods and algorithms, classical and non-traditional, based on the use of the constructive remainder theorem. - M.: Ministry of Defense of the Russian Federation, 2003 .-- 284 p.

13. The method of primary processing of information with the detection and correction of transmission errors, patent RU No. 2658795, publ. 06/22/2018

14. The method of primary processing of information using adaptive nonlinear filtering, patent RU No. 2672392, publ. 11/14/2018

15. Kukushkin S.S., Kuznetsov V.I., Noginov D.V., Oberemko A.G. Diploma for the II place of the “Breakthrough into the Future in the nomination“ The Best Innovative Project in the Interests of the Armed Forces of the Russian Federation ”competition under the title:“ Creation of modern high-performance hardware for transmitting information with comprehensive protection against interference, unauthorized access, foreign technical intelligence and information technical impacts ”, International military-technical forum“ Army - 2018 ”.

Claims (3)

1. A method of transmitting information, which consists in collecting signals from message sources, synchronizing them over time, generating a compressed signal from collected synchronized messages represented by an N-bit binary code, and performing the following operations on generating and transmitting information on them: reducing data and message redundancy , interleaving bits and error-correcting coding with the introduction of redundant binary code check characters, the primary modulation used to convert binary code characters to a pulsed binary code having two states, conventionally designated as “low” and “high” level, corresponding to the characters “0” and "1" of the source binary code, secondary modulation based on the change in the state of the carrier frequency of the radio signal according to the law of change in the amplitudes and edges of the pulses obtained during primary modulation, characterized in that they form economical signal-code constructions designed to increase the efficiency of telecommuns ictation systems and oriented to the following stages and informational sections of the transmission signal generation path, reflecting in a certain form the sequence of transformation and presentation of the transmitted information: the first stage is associated with a discrete representation of the source, in the general case, analog signals of the transmitted information with positional binary code with the symbols “0 ”And“ 1 ”, in which the digitized values of the initial messages are first represented by their residual images or equivalent structural-algorithmic transformations (SAP), conventionally referred to as (SAP-1), the results of the first stage SAP (SAP-1) are then subjected, if necessary the following sequentially performed conversions: bit interleaving and error-correcting coding with the introduction of redundant check symbols, after which they proceed to the second stage of the SAP, tentatively referred to as (SAP-2), which consists in transcoding the sequence of binary symbols "0" and "1" into a new one after the sequence of the signal-code construction (CSC) related to the primary modulation and the formation of the signal pulse sequence of the transmitted information, which is presented using a compressed noise-resistant logical ternary code S ₀ , S ₁ and S ₂ , with duplicate corresponding symbols T ₀ , T ₁ and T ₂ {S ₀ (T ₀ ), S ₁ (T ₁ ) and S ₂ (T ₂ )}, and they are assigned the following structural code constructions (CCC) composed of the characters “0” and “1” of the encoded binary code: S ₀ (T ₀ ) ↔ <00.11>₂; S ₁ (T ₁ ) ↔ <10,001> ₂ and S ₂ (T ₂ ) ↔ <101> ₂ , where the broken brackets <> ₂ show the code constructions of the symbols of the source binary code “0” and “1”, aligned with symbols of the logical ternary code with conversion during primary modulation of the ternary code symbols S ₀ , S ₁ and S ₂ into pulse amplitude modulation (AIM) with base 3: (AIM ₃ ), and the ternary code symbols duplicating them T ₀ ↔ <00.11 >₂; T ₁ = 1.5T ₀ ↔ <10.001> ₂ and T ₂ = 2T ₀ ↔ <101> ₂ , where T ₀ = τ ₀ - the duration of the characters "0" and "1" of the original binary code, in pulse-width modulation (PWM ₃ ) with three predefined durations T ₀ , T _{1 and} T ₂ , which, when the signal is secondary modulated at the level of the carrier radio frequency with a frequency (f _n ), transform the primary amplitude-pulse modulation AIM ₃ into the secondary amplitude (AM) and frequency ( FM) types of modulation of the carrier radio frequency (f _n ), and the second duplicating AIM ₃ type of pulse modulation — pulse-width modulation of PWM ₃ — into phase (FM) modulation of the carrier radio frequency (f _n ), and if necessary, use the next stage of secondary modulation - quadrature modulation of the carrier radio frequency (f _n ) - use the corresponding analogs of the quadratic amplitude modulation (KAM, QAM - in the English interpretation) and quadrature phase modulation (CPM, QPSK - in the English interpretation). 2. The method according to p. 1, characterized in that at the stage of secondary modulation, when the primary pulse modulation in the form of AIM ₃ based on the characters S ₀ , S ₁ and S ₂ and in the form of PWM ₃ using the characters T ₀ , T ₁ and T ₂ duplicating the symbols S ₀ , S ₁ and S ₂ are transferred to the modulation of the carrier frequency (f _n ) of the transmitted radio signal, while the pulse-amplitude modulation of the AIM _{3 of the} generated video signal is simultaneously converted to frequency modulation (FM) of the signal with three fixed frequency values the transmitted signal "f ₂ = f _n -Δf _d ", "f ₁ = f _n + Δf _d " and "f ₀ = f _n ", where f _n - the value of the carrier frequency of the signal, Δf _d - the value of the frequency deviation and the amplitude modulation (AM) of the carrier frequency, at which the amplitude of the radio signal carrier, modulated in frequency, also acquires three stable states A ₀ , A ₁ and A ₂ , which are uniquely associated with the symbols S ₀ (T ₀ ), S ₁ (T ₁ ) and S ₂ (T ₂ ) of the ternary code, and the second component of the generated video signal is used for phase modulation (FM) of the transmitted signal, for example, by changing the phase by 180 ° at the boundaries of time intervals corresponding to the ternary symbols “T ₀ ”, “T ₁ ” and “T ₂ ”. 3. The information transmission system for implementing the method according to claim 1, characterized in that it comprises a telemetry frame forming unit (BFTK), random access memory (RAM), a microcontroller, a communication unit with on-board measurement and information transmission equipment, a logical ternary code generator with symbols S ₂ (T ₂ ), S ₁ (T ₁ ) and S ₀ (T ₀ ), Barker code generator, read-only memory manager (ROM) of the telemetry block forming unit, micro-controller ROM manager, first and second ROM memory, first and the second read-only memory of the ROM, the system bus of the information processing unit (BSOI), the system bus of the command exchange trunk (MCO), the on-board time unit (BBW), which includes a time sensor (LW) and a highly stable frequency generator (HHF), a terminal device ( DT) of the main command exchange (MCO), the frequency generator of the DUT MCO, a long-term memory (DZU), as well as the following inputs / outputs: signal input “External second second mark ”GNSS GLONASS / GPS, input“ Initial time setting ”, access to a radio transmitting device (RPDU), information exchange bus with information collection module (MCI), information exchange bus with other on-board equipment (BA) of the spacecraft (SC) while the output of the telemetry frame forming unit is connected to a radio transmitting device (RPDU), and its first, second and third system buses are connected for two-way exchange, respectively, to the system bus of the information processing unit (BOI), to the information collection module (MCI) and to the shaper logical ternary code with the symbols S ₂ (T ₂ ), S ₁ (T ₁ ) and S ₀ (T ₀ ), the second and third system buses of which are connected for two-way exchange, respectively, to the first system bus of the Barker code generator and to the ROM manager of the image former , the second and third inputs of which are connected to exchange information with the output of the first random access memory (OP) of the ROM and with the output of the first electrically programmed constant (EPP ) ROM, respectively, the Barker code generator on the second system bus is connected to the first input of the ROM controller of the microcontroller, the second and third inputs of which are connected to exchange information with the output of the second random access memory (OP) of the ROM and with the output of the second electrically programmed permanent (EP) ROM, respectively, and the second system bus of the ROM controller of the microcontroller is connected via the microcontroller to the second system bus of the BOI, the third system bus of which is connected to the operational memory, and the fourth, fifth, sixth and seventh system buses are connected respectively to the long-term memory, to the terminal device of the command exchange trunk (MCO) , to the time sensor and to the communication unit with the BA, which is connected by the system bus to other on-board equipment (BA) for measuring and transmitting information from the spacecraft, the first two inputs being used to synchronize the time sensor with signals received from the GLONASS global navigation satellite system (GNSS) / GPS as “external secu” bottom mark ”, and the third to reset the counter, the fourth is connected to the output of the first local highly stable frequency generator, the second bus of the terminal device (OS) of the main command exchange (MCO) is connected to the system bus of the main command exchange (MCO), and its input is connected to the output of the second frequency generator.

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