RU2584462C2 - Method of transmitting and receiving signals presented by parameters of stepped modulation decomposition, and device therefor - Google Patents

Abstract

FIELD: information technology.

SUBSTANCE: invention relates to communication engineering and can be used in digital transmission systems. For this purpose, method involves breaking down information analogue signal into n strips and formation using Hilbert transformation of each strip analogue signal semi-permanent and variable analogue signals associated with parameters of instantaneous frequency and amplitude envelope of Hilbert's strip analogue signal. Then from variables of analogue signals at second and third stages of modulation decomposition quasi-permanent and variable analogue signals associated with parameters of instantaneous frequency and Hilbert's amplitude envelope of these variables of analogue signals are generated again. Recovered on first, second and third stages modulation decomposition parameters after digitizing are transmitted to receiving side, where analogue signal is restored on their basis.

EFFECT: high quality of transmitting information of analogue signals and reduced speed of digital signal.

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Description

Technical field

The invention relates to communication technology and can be used in digital transmission systems.

State of the art

The known method (RF Patent No. 2224359, BI No. 5 of 02.20.2004, “A method for transmitting and receiving signals represented by spectral modulation decomposition parameters and a device for its implementation”) transmitting and receiving signals represented by spectral modulation decomposition parameters, including the transmitting side at the first stage of modulation decomposition - separation by filtering the original analog signal into n frequency bands and the formation of n band analog signals, half-wave rectification of each band a tax signal, generating a Hilbert-conjugated signal from each strip analog signal and thereby obtaining a first complex signal, extracting from the first complex signal a first pair of parametric signals containing a first instantaneous frequency signal and a first Hilbert amplitude envelope signal, extracting from the first pair of parametric signals by low-pass filtering of the first pair of quasi-constant analog transmission signals, consisting of the first and second quasi-constant x analog transmission signals associated, respectively, with the signal of the first instantaneous frequency and the signal of the first Hilbert amplitude envelope, analog-to-digital conversion of each pair of quasi-constant analog transmission signals related to the first stage of modulation decomposition of each of n strip analog signals and the formation of n groups of individual digital transmission signals, each of which consists of a pair of individual digital transmission signals, combining a pair of individual digital signals ne transmitting and generating a digital group transmission signal in each of n groups of individual digital transmission signals, combining n digital group transmission signals and generating a digital linear signal, transmitting a digital linear signal via a communication line, and on the receiving side, dividing a digital linear signal into n digital group reception signals, dividing each of the digital group reception signals into pairs of individual digital reception signals and forming n groups of individual digital signals when then, at the first stage of modulation recovery, digital-to-analog conversion in each of n groups of individual digital reception signals and the formation of n groups of analog reception signals, each of which contains a pair of quasi-constant analog reception signals, consisting of the first and second quasi-constant analog reception signals, formation in each of n groups of analog reception signals of the first quasi-harmonic frequency-modulated oscillation based on the use of the first quasi-constant analogs output signal as a control frequency, amplitude modulation of the first quasi-harmonic frequency-modulated oscillation based on the use of the second quasi-constant analog signal as a modulating one and generation of n output group analog reception signals, combining of group analog reception signals and generation of a restored analog signal.

A device for transmitting and receiving signals represented by the parameters of spectral modulation decomposition (RF Patent No. 2224359, BI No. 5 of 02/20/2004 “A method for transmitting and receiving signals represented by the parameters of spectral modulation decomposition and a device for its implementation”), comprising a transmitting part , a communication line and a receiving part, the transmitting part consisting of n transmission signal processing units n connected in parallel to the input of the device, the output of each of which is connected to the corresponding input of the unit I have digital group signals, the output of which is the output of the transmitting part of the device, while each of the n signal processing blocks of the transmission contains a bandpass filter, the input of which is the input of the signal processing block of the transmission, as well as the first signal decomposition unit and the unit for combining individual digital signals, the output of which is the output of the transmission signal processing unit, while the first and second information inputs of the individual digital signal combining unit are connected, respectively, to the first and second the digital outputs of the first signal decomposition unit containing the Hilbert isolator of instantaneous frequency and amplitude envelope connected in series, the first low-pass filter and the first analog-to-digital converter, the output of which is the first digital output of the first signal decomposition unit, the first input of the Hilbert isolator of instantaneous frequency and the amplitude envelope is connected to the input of a half-wave rectifier and is the input of the first signal decomposition unit, and the output of the half-wave one rectifier is connected to the second input of the Hilbert isolator of instantaneous frequency and amplitude envelope, the second output of which is connected through the second low-pass filter to the input of the second analog-to-digital converter, the output of which is the second digital output of the first signal decomposition unit, and the receiving part consists of a digital separation unit group signals, the input of which is the input of the receiving part of the device, and each of its n outputs is connected, respectively, to the input of the corresponding block bots of reception signals, the output of each of which is connected to the corresponding input of the unit for combining the output signals, the output of which is the output of the device, each of the n blocks of the processing of the reception signals contains a separation unit for individual digital signals, the information input of which is the input of the processing unit of the reception signals, the first and second outputs of the individual digital signal separation unit are connected, respectively, to the first and second digital inputs of the first signal recovery unit, with the first digital-to-analog converter, the voltage-controlled generator and the amplitude modulator, the output of which is the output of the first signal recovery unit, and the second input of the amplitude modulator connected to the output of the second digital-to-analog converter, the input of the first digital-to-analog converter and the input of the second digital-to-analog converter , the first and second digital inputs of the first signal recovery unit.

A feature of the known method and device is that they are based on spectral-modulation decomposition of a signal with a stepwise decomposition of each of the n strip analog signals into two, four and eight upper and lower side bands and separation of the Hilbert amplitude envelope and instantaneous frequency from them, and then the quasi-constant parameters of these sidebands, some of which are used to further split the signal into sidebands. The selected parameters after digitization are transmitted to the receiving side, where they are used to restore the analog signal.

A disadvantage of the known method and device is that when each of the n strip analog signals is divided into upper and lower sidebands with the help of controlled filters, a part of the spectrum disappears in the filtering band between the managed low-pass filters and the controlled high-pass filters. Such loss of a part of the spectrum in the lower and upper sidebands reduces the accuracy of the formation of quasi-constant parameters of these sidebands, along which the information analog signal is restored on the receiving side. In addition, the inaccurate separation of the mentioned quasi-constant parameters of the side bands at the second stage of the spectral modulation decomposition further reduces the accuracy of the allocation of the quasi-constant parameters of the side bands at the third stage of the spectral modulation decomposition, because quasi-constant parameters of the second stage of decomposition are used as control parameters for the third stage of spectral modulation decomposition. All this leads to a decrease in the quality of transmission of information analog signals and does not significantly reduce the speed of a digital signal.

SUMMARY OF THE INVENTION

The task of the invention is to improve the transmission quality of information analog signals and reduce the speed of a digital signal.

The problem is solved by dividing the original analog signal into n frequency bands and generating from each analog strip signal quasi-constant and variable analog signals associated with the instantaneous frequency parameters and the Hilbert amplitude envelope of each analog strip signal. And then from the variable analog signals at the second and third stages of modulation decomposition, quasi-constant and variable analog signals associated with the parameters of the instantaneous frequency and the Hilbert amplitude envelope of these variable analog signals are again formed. The parameters selected in the first second and third stages of modulation decomposition in the form of quasi-constant analog signals after digitization are transmitted to the receiving side, where they are used to restore the analog signal.

The proposed method for transmitting and receiving signals represented by stepwise modulation decomposition parameters, including on the transmitting side at the first modulation decomposition stage — dividing by filtering the original analog signal into n frequency bands and generating n band analog signals, half-wave rectifying each band analog signal, generating from each Hilbert-band analog signal coupled to it and thus obtaining the first complex signal signal, extracting from the first complex signal a first pair of parametric signals containing a signal of the first instantaneous frequency and a signal of the first Hilbert amplitude envelope, isolating from the first pair of parametric signals by low-pass filtering the first pair of quasi-constant analog transmission signals, consisting of the first and second quasi-constant analog transmission signals, associated, respectively, with the signal of the first instantaneous frequency and the signal of the first Hilbert amplitude envelope, analog-digits Conversion of each pair of quasi-constant analog transmission signals related to the first stage of modulation decomposition of each of n strip analog signals and the formation of n groups of individual digital transmission signals, each of which consists of a pair of individual digital transmission signals, combining a pair of individual digital transmission signals and the formation of digital group transmission signal in each of n groups of individual digital transmission signals, combining n digital group signals transmitting and generating a digital linear signal, transmitting a digital linear signal via a communication line, and on the receiving side, dividing the digital linear signal into n digital group reception signals, dividing each of the digital group reception signals into pairs of individual digital reception signals, and forming n groups of individual digital reception signals, and then at the first stage of modulation recovery - digital-to-analog conversion in each of n groups of individual digital reception signals and generated n groups of analog reception signals, each of which contains a pair of quasi-constant analog reception signals, consisting of the first and second quasi-constant analog reception signals, the formation in each of n groups of analog reception signals of the first quasi-harmonic frequency-modulated oscillation based on the use of the first quasi-constant analog reception signal as a frequency control, the amplitude modulation of the first quasi-harmonic frequency-modulated oscillation based on the use the second quasi-constant analog signal as a modulating one and generating n output group analog reception signals, combining group analog reception signals and generating a reconstructed analog signal. Unlike the prototype, after the first stage of modulation decomposition, in each of the n frequency bands in the second stage of modulation decomposition, the first alternating analog signal is formed from the signal of the first instantaneous frequency and the first quasi-constant analog transmission signal, and from the signal of the first Hilbert amplitude envelope and the second quasi-constant analog the transmission signal form the second alternating analog signal, and then from the first and second alternating analog signals form, respectively, the second a swarm and a third complex signals, from which, respectively, a second and a third pair of parametric signals are extracted, consisting of a second instantaneous frequency signal and a second Hilbert amplitude envelope signal, a third instantaneous frequency signal and a third Hilbert amplitude envelope signal, and then from the second and the third pair of parametric signals allocate, respectively, the second and third pairs of quasi-constant analog transmission signals, consisting, respectively, of the third and fourth, fifth and the sixth quasi-constant analog transmission signals, and in each of the n frequency bands in the third step of the modulation decomposition of the second instantaneous frequency signal and the third quasi-constant analog transmission signal, the second Hilbert amplitude envelope signal and the fourth quasi-constant analog transmission signal, respectively, the third and fourth variable analog signals, and from the signal of the third instantaneous frequency and the fifth quasi-constant analog transmission signal, the signal of the third the fifth amplitude and the sixth quasi-constant analog transmission signal, respectively, form the fifth and sixth variable analog signals, and then pairs of the third and fourth, fifth and sixth variable analog signals form pairs of, respectively, the fourth and fifth, sixth and seventh complex signals of which the fourth and fifth, sixth and seventh pairs of parametric signals, respectively, consisting of the signal of the fourth instantaneous frequency and the signal of the fourth the Ilbert amplitude envelope, the fifth instantaneous frequency signal and the fifth Hilbert amplitude envelope signal, the sixth instantaneous frequency signal and the sixth Hilbert amplitude envelope signal, the seventh instantaneous frequency signal and the seventh Hilbert amplitude envelope signal, and then from the fourth and fifth, sixth and seventh pairs of parametric signals emit, respectively, the fourth and fifth, sixth and seventh pairs of quasi-constant analog transmission signals consisting, respectively, of the seventh and the seventh, ninth and tenth, eleventh and twelfth, thirteenth and fourteenth quasi-constant analog transmission signals, after which pairs of quasi-constant analog transmission signals related to the first, second and third stages of modulation decomposition of each of the n band-pass analog signals are subjected to analog-to-digital conversion and form n individual groups of digital transmission signals, each of which consists of B _n pairs of individual digital transmission signals which are then combined to give qi rovoy multicast signal, wherein each of the n digital baseband transmission signals are formed independently of other groups and comprise either of the individual digital transmit signals relating only to the first stage of the modulation decomposition, where B _n is 1, or the first and second steps of the modulation decompositions in which B _n is equal to 3, or from digital signals related to all three stages of the modulation decomposition, in which B _n is equal to 7, after which n digital group transmission signals are combined again and A digital digital linear signal is transmitted over the communication line, and on the receiving side, the digital linear signal is divided into n digital group reception signals, after which each of n digital group reception signals is in turn divided into B _n pairs of individual digital reception signals and n groups of individual digital reception signals, wherein each of the n groups of individual digital reception signals is formed independently of the other groups and is composed of: either pairs of individual digital reception signals related only to the first stage of the modulation recovery in which B _n is 1, or the first and second stages of modulation recovery in which B _n is equal to 3 or of the individual digital signal pairs reception pertaining to all three stages of modulation recovery in which B _n = 7 then, in each of n independent groups of individual digital reception signals, digital-to-analog conversion is performed and n independent groups of analog reception signals are generated, each of which contains B _n pairs of quasi-constant analog signals with receiving signals, after which, in the corresponding independent groups of analog receiving signals, in which B _n = 7, at the third stage of modulation signal recovery in each of the fourth, fifth, sixth and seventh pairs of quasi-constant analog receiving signals, using pairs of, respectively, the seventh and the eighth, ninth and tenth, eleventh and twelfth, thirteenth and fourteenth quasi-constant analog reception signals, respectively, form the third, fourth, fifth and sixth restored analog variables signals, moreover, in the corresponding independent groups of analog reception signals at the second stage of the modulation recovery of the signal from the third restored alternating analog signal and the third quasi-constant analog receiving signal, the fourth restored alternating analog signal and the fourth quasi-constant analog receiving signal, the fifth restored alternating analog signal and the fifth quasi-constant analog receive signal, sixth reconstructed alternating analogs of the first signal and the sixth quasi-constant analog receive signal, respectively, the second reconstructed instantaneous frequency signal, the second reconstructed Hilbert amplitude envelope signal, the third reconstructed instantaneous frequency signal and the third reconstructed Hilbert amplitude envelope signal are generated, and then using the second reconstructed instantaneous frequency signal and the signal the second restored Hilbert amplitude envelope, the signal of the third restored instantaneous frequency and the signal tr With the reconstructed Hilbert amplitude envelope, the first and second reconstructed analog signals are generated, respectively, in the corresponding independent groups of analog reception signals at the first stage of the modulation signal recovery from the first reconstructed analog signal and the first quasi-constant analog reception signal, the second reconstructed analog signal and the second quasi-constant analog reception signal, form, respectively , The signal is first reduced instantaneous frequency signal and a first reconstructed Hilbert amplitude envelope, and then using the signal of the first reduced instantaneous frequency signal and a first reconstructed Hilbert amplitude envelope is formed in the respective independent groups of analog reception signals in which B _n = 7, the output analog signal reception, while in the corresponding independent groups of analog reception signals, in which B _n = 3, at the second stage of modulation signal recovery in each of the second and third pairs of quasi-constant analog receive signals, using pairs of, respectively, the third quasi-constant analog receive signal and the fourth quasi-constant analog receive signal, the fifth quasi-constant analog receive signal and the sixth quasi-constant analog receive signal, respectively, the first and second restored variables are generated analog signals, and in the corresponding independent groups of analog reception signals at the first stage of the modulation is restored I of the signal from the first reconstructed variable analog signal and the first quasi-constant analog receive signal, the second reconstructed variable analog signal and the second quasi-constant analog receive signal, form, respectively, the signal of the first reconstructed instantaneous frequency and the signal of the first reconstructed Hilbert amplitude envelope, and then, using the signal of the first the reconstructed instantaneous frequency and the signal of the first reconstructed Hilbert amplitude envelope form in the corresponding independent groups of analog reception signals in which B _n = 3, the output analog signal of reception, while in the corresponding independent groups of analog reception signals in which B _n = 1, in the first stage of modulation signal recovery in each of the first pair of quasi-constant analog reception signals, using, respectively, the first quasi-constant analog receive signal and the second quasi-constant analog receive signal, form in the corresponding independent groups of analog receive signals, in of which B _n = 1, the output analog reception signal, after which n parallel output analog reception signals from n independent groups of analog reception signals are combined and a restored analog signal is formed.

And in the device for transmitting and receiving signals represented by the parameters of the step modulation decomposition, containing a transmitting part, a communication line and a receiving part, the transmitting part consisting of n transmission signal processing units connected in parallel to the input of the device, the output of each of which is connected to the corresponding input of the combining unit digital group signals, the output of which is the output of the transmitting part of the device, while each of the n blocks of signal processing of the transmission contains a bandpass filter, the course of which is the input of the transmission signal processing unit, as well as the first signal decomposition unit and the individual digital signal combining unit, the output of which is the output of the transmission signal processing unit, while the first and second information inputs of the individual digital signal combining unit are connected, respectively, to the first and the second digital outputs of the first signal decomposition unit containing the Hilbert isolator of instantaneous frequency and amplitude envelope connected in series, the first a low-pass filter and a first analog-to-digital converter, the output of which is the first digital output of the first signal decomposition unit, while the first input of the Hilbert isolator of the instantaneous frequency and amplitude envelope is connected to the input of the half-wave rectifier and is the input of the first signal decomposition block, and the output of the half-wave rectifier is connected to the second input of the Hilbert isolator of instantaneous frequency and amplitude envelope, the second output of which is connected through a second filter low frequency to the input of the second analog-to-digital converter, the output of which is the second digital output of the first signal decomposition unit, and the receiving part consists of a digital group signal separation unit, the input of which is the input of the receiving part of the device, and each of its n outputs is connected, respectively, to the input of the corresponding unit for processing the reception signals, the output of each of which is connected to the corresponding input of the unit for combining the output signals, the output of which is the output of the device, and each one of the n reception signal processing units contains an individual digital signal separation unit, the information input of which is an input of a reception signal processing unit, wherein the first and second outputs of the individual digital signal separation unit are connected, respectively, to the first and second digital inputs of the first signal recovery unit, containing a series-connected first digital-to-analog converter, a voltage-controlled generator and an amplitude modulator, the output of which is the output of the first signal recovery unit, and the second input of the amplitude modulator is connected to the output of the second digital-to-analog converter, the input of the first digital-to-analog converter and the input of the second digital-to-analog converter are, respectively, the first and second digital inputs of the first signal recovery unit, are additionally introduced into the transmitting part in each of n blocks of the processing of the transmission signals introduced the block of the second stage of the modulation decomposition of the signal and the block of the third stage of the modulation decomposition I of the signal, and the first, second, third and fourth analog outputs are added to the first signal decomposition block, which are connected inside the first signal decomposition block, respectively, with the output of the first low-pass filter, with the output of the second low-pass filter, the first output of the Hilbert isolator of instantaneous frequency and the amplitude envelope and the second output of the Hilbert isolator of instantaneous frequency and the amplitude envelope, while the first, second, third and fourth analog outputs of the first signal decomposition unit with are connected, respectively, with the first, second, third and fourth analog inputs of the second stage block of the modulation signal decomposition, the first, second, third and fourth digital outputs of which are connected, respectively, with the third, fourth, fifth and sixth information inputs of the individual digital signal combining unit, and the first, second, third, fourth, fifth, sixth, seventh and eighth analog outputs of the block of the second stage of modulation decomposition of the signal are connected, respectively, with the first, second, third, fourth m, fifth, sixth, seventh and eighth analog inputs of a block of the third stage of modulation signal decomposition, the first, second, third, fourth, fifth, sixth, seventh and eighth digital outputs of which are connected, respectively, with the seventh, eighth, ninth, tenth, eleventh, the twelfth, thirteenth and fourteenth information inputs of the unit for combining individual digital signals, while the first, second ... n control inputs of the transmitting part of the device are connected to the code inputs, respectively, of the first processing unit ki of transmission signals, the second transmission signal processing unit ... n the transmission signal processing unit, and inside each of the n transmission signal processing units its code input is connected to the code input of the individual digital signal combining unit, and additionally introduced into each of n blocks in the receiving part of the device the processing of the reception signals, a block of the second stage of the modulation signal recovery and a block of the third stage of the modulation signal recovery, and the first and W second adders, and the first inputs of the first and second adders are connected, respectively, with the output of the first digital-to-analog converter and the output of the second digital-to-analog converter, and the outputs of the first and second adders are connected, respectively, to the input of the voltage-controlled generator and the second input of the amplitude modulator, while the second inputs the first and second adders are connected, respectively, with the first and second analog inputs of the first signal recovery unit, which are connected, respectively, with the first and second outputs of the block of the second stage of modulation signal recovery, the first, second, third and fourth digital inputs of which are connected, respectively, with the third, fourth, fifth and sixth outputs of the separation unit of the individual digital signals, and the first, second, third and fourth analog inputs blocks of the second stage of modulation signal recovery are connected, respectively, with the first, second, third and fourth outputs of the block of the third stage of modulation signal recovery, first, second, third, the fourth, fifth, sixth, seventh and eighth digital inputs of which are connected, respectively, with the seventh, eighth, ninth, tenth, eleventh, twelfth, thirteenth and fourteenth outputs of the individual digital signal separation unit, while the first, second ... n control inputs of the receiving part the devices are connected to the code inputs, respectively, of the first receiving signal processing unit, the second receiving signal processing unit ... n the receiving signal processing unit, and inside each of the n receiving signal processing units The single input is connected to the code input of the individual digital signal separation unit.

Due to this solution to the problem, the proposed method and device for transmitting and receiving signals represented by the parameters of stepwise modulation decomposition, in contrast to the prototype, allows for modulation decomposition to use the entire spectrum of each of the n strip analog signals at each of the three steps of this modulation decomposition. As a result, the accuracy of the formation of quasi-constant parameters of modulation decomposition, according to which the information analog signal is restored at the receiving side, is increased. As a result, it is possible to improve the quality of transmission of information signals and reduce the speed of the digital signal in the channel.

List of figures

The proposed method and device are illustrated by figures, which show:

FIG. 1 is a structural diagram of a device for transmitting and receiving signals represented by parameters of a step modulation decomposition;

FIG. 2 block diagram of the second stage of modulation signal decomposition;

FIG. 3 block diagram of the third stage of modulation signal decomposition;

FIG. 4 block diagram of the second stage of modulation signal recovery;

FIG. 5 block diagram of the third stage of modulation signal recovery;

FIG. 6 diagram of a unit for combining individual digital signals;

FIG. 7 is a block diagram of a separation of individual digital signals;

FIG. 8 block diagram of a Hilbert isolator of instantaneous frequency and amplitude envelope.

The implementation of the invention

A feature of the proposed method for transmitting and receiving signals represented by the parameters of stepwise modulation decomposition, unlike the prototype, is the lack of dividing each analog strip signal into several upper and lower sidebands and isolating from them quasi-constant parameters, some of which are used to split the signal into sidebands. The basis of the proposed method is the formation of quasi-constant and variable analog signals associated with the parameters of the instantaneous frequency and the Hilbert amplitude envelope of the strip analog signal from each analog strip signal. And then from the variable analog signals at the second and third stages of modulation decomposition, quasi-constant and variable analog signals associated with the parameters of the instantaneous frequency and the Hilbert amplitude envelope of these variable analog signals are again formed. The parameters selected in the first second and third stages of modulation decomposition in the form of quasi-constant analog signals after digitization are transmitted to the receiving side, where they are used to restore the analog signal.

The method of transmitting and receiving signals represented by the parameters of the step modulation decomposition is implemented as follows. On the transmitting side, the original analog signal is separated using band-pass filters (FIG. 1) into n frequency bands and thus, n-band analog signals are generated. The number of frequency bands n can vary from 1 to 7. Limiting the number of frequency bands allows you to reduce the transmission speed of the signal in the communication line, and increasing the number of frequency bands allows you to improve the quality of the transmitted message. However, a too large increase in the number of frequency bands n (more than 7) gives a relatively insignificant increase in the quality of analog signals restored at reception with a noticeable increase in the transmission speed of a digital signal in a communication channel.

The analog strip signal in each of the n frequency bands is subjected to biannual rectification (without filtering) and modulation decomposition (MP) (Fig. 1, Fig. 8). For this, at the first stage of such an expansion, a Hilbert-conjugated signal is formed from a strip analog signal (not rectified), according to (Radio broadcasting and electroacoustics. Edited by Yu.A. Kovalgin Radio and communication, 1999, p. 75):

where S ₁ (t) is the Hilbert-conjugated signal from the strip analog signal S (t).

The Hilbert-conjugated signal is exactly the same as the original band-pass analog signal, but having a phase rotation of all its spectral components by 90 °.

Next, from the first complex signal obtained in this way, consisting of S (t) and S ₁ (t), a first pair of parametric signals is selected containing the signal of the first instantaneous frequency ω ₁ (t) and the signal of the first Hilbert amplitude envelope A ₁ (t), according to (Radio broadcasting and electroacoustics. Edited by Yu. A. Kovalgin. Radio and communications, 1999. P. 75):

Thus, to extract the signal of the first instantaneous frequency, it is necessary to perform the following operations (Fig. 8): calculate the derivatives of S (t) and S ₁ (t), after which, according to [2], multiply the signals, and then from the signal obtained as the result of the first multiplication, it is necessary to subtract the signal obtained as a result of the second multiplication, i.e.

In addition, the signal S ₁ (t) is subjected to half-wave rectification without filtering (the signal S (t) was rectified earlier), and then each of the rectified signals S (t) and S ₁ (t) is squared, after which they are added and obtained :

And finally, the signal [4] is divided by the signal [5] and we obtain the signal of the first instantaneous frequency ω ₁ (t).

To isolate the signal of the first Hilbert amplitude envelope A ₁ (t), according to [3], it is necessary to previously obtain the signal [5] to undergo the square root extraction operation (Fig. 8).

It should be noted that the Hilbert transform allows us to represent the analog signal as the product of two functions - the envelope A (t) and the cosine of the phase cosφ (t):

After that, from the signal of the first instantaneous frequency ω ₁ (t) and the signal of the first Hilbert amplitude envelope A ₁ (t) (Gonorovsky IS Radio engineering circuits and signals M. Radio and communications, 1986, p. 98, Fig. 3.24) by low-pass filtering emit two quasi-constant analog transmission signals (Fig. 1).

The first quasi-constant analog transmission signal ω _c1 (t) is a parameter - the average value of the instantaneous frequency (SZMCH) of the strip analog signal, which characterizes the weighted average frequency of the spectrum frequency of this strip analog signal.

The weighted average value of the frequency (t) ω spectrum of the speech _{communication,} broadcast and other multi-frequency signals generally do not correspond to the center frequency of the spectrum of these signals and is not determined as a half sum of the upper and lower frequencies of the spectrum (ω _in + ω _n) / 2. The weighted average value of the frequency of the spectrum is determined in the form of a more complex expression, which involves not only the frequency components of the spectrum, but also its amplitude components.

Consider this as an example of a 2-frequency signal, the first of which has a low frequency ω ₁ and amplitude Α ₁ , and the second has a higher frequency ω ₂ and amplitude A ₂ . If Α ₁ = Α ₂ (symmetric signal spectrum), then the weighted average value of the frequency spectrum is the average frequency of this spectrum _{communication} ω = (ω ₁ + ω ₂₎ / 2. If, for example, Α ₁ > Α ₂ , i.e. Since the signal spectrum is asymmetric, the weighted average value of the frequency of the spectrum is determined from the expression:

In this case, the weighted average value of the frequency (SZCh) of the spectrum will be located near the frequency ω ₁ . The weighted average of the frequency of the spectrum is associated with the property of human hearing. The fact is that hearing, in the case of a multi-frequency signal with different amplitudes, whose frequencies are relatively close to each other, perceives these frequencies not separately, but in the form of their weighted average value. In this case, the signal corresponding to the weighted average frequency of the spectrum will be located near those of the initial frequency components of the spectrum of the signals that have the largest amplitude. A person’s hearing in a narrow frequency band responds precisely to these components of the signal with a large amplitude and does not respond to frequency components with small amplitudes (masking effect). Those. a person in a narrow frequency band perceives a signal corresponding to the weighted average frequency of the spectrum. This is similar to how a human eye, when mixing for example pure red and pure yellow colors, will perceive different colors ranging from red to yellow, depending on the ratio of the amplitudes (luminances) of these two original colors.

This property of hearing allows at any time to replace the frequencies located close to each other, one frequency, which is located in close proximity to the frequency component of the original signal with the largest amplitude. This SZCH ω _sv (t) fully characterizes and is able to generate a parameter (SZMCH) in the form of the first quasi-constant analog transmission signal ω _c1 (t). The same property of hearing in relation to nearby frequencies is one of the main reasons for dividing the original analog signal into n frequency bands, because in a limited frequency band at each moment of time, the weighted average frequency of the spectrum successfully replaces the frequencies in this limited band.

The first quasi-constant analog signal is narrow-band and its transmission requires a speed of 50-100 bit / s.

The second quasiconstant analog transmission signal A _c2 (t) is also a parameter - the average value of the Hilbert amplitude envelope (NWSAR) of the strip analog signal, characterizing the weighted average value of the amplitude envelope (SZAO) of this strip analog signal. The meaning of the SZAO consists in the dependence of the envelope amplitude not only on the amplitudes of the components included in the original signal, but also on the location of these components on the frequency axis, in particular on the spectrum width of this initial signal. The second quasi-constant analog signal A _c2 (t) is also narrow-band and its transmission requires a speed of 50-100 bit / s.

After the strip analog signal at the first stage in each of the n frequency bands has undergone MP, then (Fig. 1) in each of the n frequency bands at the second stage MP, the first quasi-constant analog transmission signal is subtracted from the signal of the first instantaneous frequency ω ₁ (t) ω _c1 (t) and form the first variable analog signal ω _p1 (t) (Fig. 2). And from the signal of the first Hilbert amplitude envelope A ₁ (t), the second quasi-constant analog transmission signal A _c2 (t) is subtracted and the second alternating analog signal A _p2 (t) is formed (Fig. 2). After that, with respect to the first and second variable analog signals ω _p1 (t) and A _p2 (t), the same operations are performed as were carried out at the first stage MP with respect to the analog strip signal in each of the n frequency bands. For this, from the first and second variable analog signals ω _p1 (t) and A _p2 (t), the corresponding Hilbert-conjugated signals are generated, and from each of the second and third complex signals generated in this way, respectively, the second and a third pair of parametric signals consisting, respectively, of a second instantaneous frequency signal ω ₂ (t) and a second Hilbert amplitude envelope signal A ₂ (t), a third instantaneous frequency signal ω ₃ (t) and a third Hilbert amplitude envelope signal A ₃ (t). Then, from the second and third pairs of parametric signals (ω ₂ (t) and A ₂ (t), ω ₃ (t) and A ₃ (t), by low-pass filtering, respectively, the second and third pairs of quasi-constant analog transmission signals are isolated, consisting, respectively, of the third ω _c3 (t) and fourth A _c4 (t), fifth ω _c5 (t) and sixth A _c6 (t) quasi-constant analog transmission signals (Fig. 1, Fig. 2).

After the first and second variable analog signals ω _p1 (t) and A _p2 (t) in the second MP stage in each of the n frequency bands underwent modulation decomposition, then in each of the n frequency bands in the third MP stage (Fig. 1) from the signal of the second instantaneous frequency ω ₂ (t) and the signal of the second Hilbert amplitude envelope A ₂ (t), the third ω _c3 (t) and the fourth Α _c4 (t) quasiconstant analog transmission signals are subtracted, and, respectively, the third ω _P3 (t) and the fourth A _p4 (t) variable analog signals (Fig. 3). And from the signal of the third instantaneous frequency ω ₃ (t) and the signal of the third Hilbert amplitude envelope A ₃ (t), the fifth ω _c5 (t) and sixth A _c6 (t) quasi-constant analog transmission signals are subtracted, respectively. As a result, receive, respectively, the fifth ω _p5 (t) and sixth A _p6 (t) variable analog signals (Fig. 3). After that, from the third ω _p3 (t) and fourth A _p4 (t), fifth ω _p5 (t) and sixth A _p6 (t) variable analog signals, the corresponding signals conjugated by him according to Hilbert are formed and, from each of those thus formed, respectively, the fourth and fifth, sixth and seventh complex signals emit, respectively, the fourth and fifth, sixth and seventh pairs of parametric signals consisting, respectively, of the fourth instantaneous frequency signal ω ₄ (t) and the fourth Hilbert amplitude envelope signal A ₄ (t ), the signal of the fifth mg Ram frequencies ω ₅ (t) signal and the fifth Hilbert amplitude envelope A ₅ (t), the signal sixth instantaneous frequency ω ₆ (t) signal and the sixth Hilbert amplitude envelope A ₆ (t), the seventh instantaneous frequency ω signal ₇ (t) and signal of the seventh Hilbert amplitude envelope A ₇ (t). And then from the fourth and fifth, sixth and seventh pairs of parametric signals by low-pass filtering, respectively, the fourth and fifth, sixth and seventh pairs of quasi-constant analog transmission signals are selected, consisting, respectively, of the seventh ω _c7 (t) and the eighth A _c8 (t ), the ninth ω _c9 (t) and the tenth A _c10 (t), the eleventh ω _c11 (t) and the twelfth A _c12 (t), the thirteenth ω _c13 (t) and the fourteenth A _c14 (t), quasi-constant analog transmission signals (FIG. . 1, Fig. 3).

After that, pairs of quasi-constant analog transmission signals related to the first, second and third stages of modulation decomposition (Fig. 1) of each of the n strip analog signals are subjected to analog-to-digital conversion and n groups of individual digital transmission signals are formed, each of which consists of B _n pairs of individual digital transmission signals. Further, these B _n pairs of individual digital transmission signals are combined (Fig. 6) and receive a digital group transmission signal. Moreover, each of n digital group transmission signals is generated independently of other groups and is composed of: either individual digital transmission signals related only to the first stage of modulation decomposition, in which B _n is 1, or the first and second stages of modulation decomposition, in which B _n is 3, or from digital signals related to all three stages of decomposition, for which B _n is 7. After that, n digital group transmission signals are combined again and the generated digital linear signal is transmitted about the communication line (Fig. 1).

The independent generation of each of the n digital group transmission signals allows, in relation to groups associated with the transmission of high-frequency bands of analog signals, in certain cases to be limited to the transmission of individual digital transmission signals related only to the first stage of modulation decomposition, in which B _n is 1 or the first and the second stage of modulation decomposition, in which B _n is 3. This is due to the peculiarities of human auditory perception of high-frequency sound components. It is desirable to transmit groups of digital signals associated with the transmission of low and mid-frequency bands of analog signals using three stages of modulation decomposition, at which B _n is 7. Such flexible generation of each of n digital group transmission signals allows to reduce the transmission speed of a digital signal over a communication line without a noticeable decrease in the quality of the transmitted information.

And on the receiving side (Fig. 1), the digital linear signal is divided into n digital group reception signals, after which each of n digital group reception signals is in turn divided into B _n pairs of individual digital reception signals and n groups of individual digital reception signals are generated ( Fig. 7), wherein each of the n groups of individual digital reception signals is formed independently of the other groups and is composed of: either pairs of individual digital reception signals relating only to the first stage of modulation recovery, in which B _n is equal to 1, or the first and second stages of modulation recovery, at which B _n is 3, or from pairs of individual digital reception signals related to all three stages of modulation recovery, at which B _n is 7.

Then, in each of n independent groups of individual digital reception signals, digital-to-analog conversion is performed and n independent groups of analog reception signals are generated, each of which contains B _n pairs of quasi-constant analog reception signals.

After that, in the corresponding independent groups of analog reception signals, in which B _n = 7, in the third stage of modulation signal recovery (Fig. 1, Fig. 5) in each of the fourth, fifth, sixth and seventh pairs of quasi-constant analog reception signals, first using respectively, the seventh ω _c7 (t), the ninth ω _c9 (t), the eleventh ω _c11 (t) and the thirteenth ω _c13 (t) quasi-constant analog receive signals as frequency control, respectively, form the third, fourth, fifth and sixth quasi-harmonic frequency modulated oscillations (cosine of the phase).

And then, using the eighth A _c8 (t), tenth A _c10 (t), twelfth A _c12 (t) and fourteenth A _c14 (t) quasi-constant analog receive signals modulate in amplitude these, respectively, third, fourth, fifth and sixth quasi-harmonic frequency-modulated oscillations, and form, respectively, the third ω _p3 (t), fourth A _p4 (t), fifth ω _p5 (t) and sixth A _p6 (t) restored variable analog signals (Fig. 5).

These reconstructed variable analog signals in the corresponding independent groups of analog reception signals in the second stage of the modulation signal recovery (Fig. 1, Fig. 4) are added, respectively, with the third ω _c3 (t), fourth A _c4 (t), fifth ω _c5 ( t) and the sixth A _c6 (t) quasi-constant analog reception signals and form, respectively, the signal of the second reconstructed instantaneous frequency ω ₂ (t), the signal of the second reconstructed Hilbert amplitude envelope A ₂ (t), the signal of the third reconstructed instantaneous frequency ω ₃ (t ) and signal l third reduced Hilbert envelope of the amplitude A ₃ (t). And then, using the signals of the second ω ₂ (t) and third ω ₃ (t) of the restored instantaneous frequencies as frequency control, the first and second quasi-harmonic frequency-modulated oscillations are formed, respectively.

After that, using the signals of the second A ₂ (t) and third A ₃ (t) of the reconstructed Hilbert amplitude envelopes, these first and second quasi-harmonic frequency-modulated oscillations are modulated in amplitude and, accordingly, the first ω _p1 (t) is generated and the second A _p2 (t) reconstructed variable analog signals (Fig. 4).

These reconstructed variable analog signals in the corresponding independent groups of analog reception signals at the first stage of the modulation signal recovery (Fig. 1) are added, respectively, to the first ω _c1 (t) and second A _c2 (t) quasi-constant analog reception signals, and form, respectively , the signal of the first reconstructed instantaneous frequency ω ₁ (t) and the signal of the first reconstructed Hilbert amplitude envelope A ₁ (t).

After that, using the signal of the first reconstructed instantaneous frequency ω ₁ (t) as the control frequency, an output quasiharmonic frequency-modulated oscillation is generated, and then, using the signal of the first reconstructed Hilbert amplitude envelope A ₁ (t), this output quasiharmonic frequency is modulated in amplitude -modulated oscillation, and form in the respective independent groups of analog reception signals, in which B _n = 7, the output analog reception signal S (t) (Fig. 1).

Moreover, in the corresponding independent groups of analog reception signals, in which B _n = 3, in the second stage of modulation signal recovery (Fig. 1, Fig. 4) in each of the second and third pairs of quasi-constant analog reception signals, first using, respectively, the third ω _c3 (t) and fifth ω _c5 (t), quasi-constant analog receive signals as frequency controllers, form, respectively, the first and second quasi-harmonic frequency-modulated oscillations.

And then, using the fourth A _c4 (t) and sixth A _c6 (t) quasi-constant analog reception signals, these first and second quasi-harmonic frequency-modulated oscillations are modulated in amplitude and form, as with B _n = 7, respectively, the first ω _p1 (t) and the second A _p2 (t) restored variable analog signals (Fig. 4).

These reconstructed variable analog signals in the corresponding independent groups of analog reception signals at the first stage of the modulation signal recovery (Fig. 1) are added, respectively, to the first ω _c1 (t) and second A _c2 (t) quasi-constant analog reception signals, and form, respectively , the signal of the first reconstructed instantaneous frequency ω ₁ (t) and the signal of the first reconstructed Hilbert amplitude envelope A ₁ (t).

After that, using the signal of the first reconstructed instantaneous frequency ω ₁ (t) as the control frequency, an output quasiharmonic frequency-modulated oscillation is generated, and then, using the signal of the first reconstructed Hilbert amplitude envelope A ₁ (t), this output quasiharmonic frequency is modulated in amplitude -modulated oscillation, and form in the corresponding independent groups of analog reception signals, in which B _n = 3, the output analog reception signal S (t) (Fig. 1).

Moreover, in the corresponding independent groups of analog reception signals, in which B _n = 1, at the first stage of the modulation signal recovery (Fig. 1) in each of the first pair of quasi-constant analog reception signals, first using, respectively, the first quasi-constant analog receiving signal ω _c1 (t) as a frequency control, an output quasi-harmonic frequency-modulated oscillation is generated, and then, using the second quasi-constant analog receive signal A _c2 (t), this output quasig is modulated in amplitude a harmonic frequency-modulated oscillation, and form in the corresponding independent groups of analog reception signals, in which B _n = 1, the output analog reception signal S (t) (Fig. 1).

After that, n parallel output analog reception signals from n independent groups of analog reception signals are combined and a reconstructed analog signal is generated (Fig. 1).

The method is carried out using the device. The device for transmitting and receiving signals represented by the parameters of spectral modulation decomposition (Fig. 1) consists of series-connected transmitting part 1, communication line 2 and receiving part 3.

The transmitting part 1 consists of the first transmission signal processing unit (BOSP) 4 ₁ , the second BOSP 4 ₂ ... n-th BOSP 4 _n , the parallel inputs of which are the input of the device, and the outputs of the BOSP 4 are connected to the corresponding n inputs of the digital group signal combining unit (BOTSGS) 5, the output of which is the output of the transmitting part of the device 1 and connected to the communication line 2.

Each of n BOSP 4 (Fig. 1) contains a band-pass filter (PF) 6, the input of which is the input of BOSP 4, as well as the first signal decomposition unit (BRS) 7 ₁ , the unit for combining individual digital signals (BOICS) 8, the second stage unit modulation signal decomposition (BMSRS) 9 and the block of the third stage of modulation signal decomposition (BTSMS) 10.

The first signal decomposition unit (BRS) 7 _{1 of} each of the n BOSP 4 contains (Fig. 1) a half-wave rectifier (DPV) 11, a Hilbert isolator of instantaneous frequency and amplitude envelope (GVMCHAO) 12, the first low-pass filter (LPF) 13, and the second low-pass filter 14, a first analog-to-digital converter (ADC) 15 and a second ADC 16.

The first input of the HFMCO 12 is connected to the input of the half-wave rectifier 11 and is the input of the BRS 7 ₁ , and the output of the half-wave rectifier 11 is connected to the second input of the HMFCO 12, the first output of which is connected through the first low-pass filter 13 with the input of the first ADC 15, the output of which is the first digital output of the BRS 7 ₁ . And the second output GVMCHAO 12 is connected through the second low-pass filter 14 to the input of the second ADC 16, the output of which is the second digital output of the BRS 7 ₁ . The output of the first low-pass filter 13 and the output of the second low-pass filter 14 are connected, respectively, with the first and second analog outputs of the BRS 7 ₁ , and the first and second outputs of the high-frequency filter 12 are connected, respectively, with the third and fourth analog outputs of the BRS 7 ₁ .

The input of the BRS 7 ₁ (Fig. 1) is connected to the output of the PF 6, and the first and second digital outputs of the BRS 7 _{1 are} connected, respectively, with the first and second information inputs of the unit BOICS 8. In this case, the first, second third and fourth analog outputs of the BRS 7 _{1 are} connected, respectively, to the first, second, third and fourth analog inputs of BVSMRS 9 (Fig. 1. Fig. 2). The first, second, third and fourth digital outputs of BVSMRS 9 are connected, respectively, with the third, fourth, fifth and sixth information inputs of BOICS 8, and the first, second, third, fourth, fifth, sixth, seventh and eighth analog outputs of BVSMRS 9 are connected, respectively , with the first, second, third, fourth, fifth, sixth, seventh and eighth analog inputs of BTSMP 10 (Fig. 1. Fig. 3). The first, second, third, fourth, fifth, sixth, seventh and eighth digital outputs of the BTSMP 10 are connected, respectively, to the seventh, eighth, ninth, tenth, eleventh, twelfth, thirteenth and fourteenth information inputs of BOICS 8 (Fig. 1).

Wherein the first, second ... n control inputs of the transmitter portion 1 (V _n1, V _n2 ... V _Pn) connected with the code inputs, respectively, of the first VSDB 4 _1, the second VSDB April ₂ ... n-th VSDB 4 _n, and within each of n BOSP 4, its code input is connected to the code input of BOICS 8, the output of which is the output of BOSP 4 (Fig. 1).

The receiving part 3 (Fig. 1) consists of a digital group signal separation unit (BRTSGS) 17, a first reception signal processing unit (BOSPR) 18 ₁ , a second BOSPR 18 ₂ ... n-th BOSPR 18 _n , and also a unit for combining the output signals ( ACBF) 19. The input of the BRCSG 17 is the input of the receiving part 3, and each of the n outputs of the BRCGS 17 is connected, respectively, to the input of the corresponding BOSPR 18, the output of each of which is connected to the corresponding input of the ACBG 19, the output of which is the output of the device.

Each of n BOSPR 18 (Fig. 1) contains a block for separating individual digital signals (BRICS) 20, the information input of which is the input of BOSPR 18, as well as a first signal recovery block (BBC) 21 ₁ , a block of the second stage of modulation signal recovery (BMSC) 22 and the block of the third stage of modulation signal recovery (BTSMVS) 23.

The first BVS 21 _{1 of} each of n BOSPR 4 (Fig. 1) contains a first digital-to-analog converter (DAC) 24, a second DAC 25, a first adder 26, a second adder 27, a voltage controlled oscillator (VCO) 28, and an amplitude modulator (AM) 29.

The input of the first DAC 24 and the input of the second DAC 25 are, respectively, the first and second digital inputs of the first BVS 21 ₁ , and their outputs are connected, respectively, with the first input of the first adder 26 and with the first input of the second adder 27, the second inputs of which are connected, respectively , with the first and second analog inputs of the first BVS 21 ₁ . The output of the first adder 26 is connected through the VCO 28 to the first input AM 29, and the output of the second adder 27 is connected to the second input AM 29, the output of which is the output of the first BVS 211 and at the same time is the output of BOSPR 4.

The first and second digital inputs of the first BVS 21 _{1 are} connected, respectively, to the first and second outputs of the BRICS 20 (Fig. 1), and the first and second analog inputs of the first BVS 211 are connected, respectively, to the first and second outputs of the BVSMV 22 (Fig. 1 , Fig. 4). The first, second, third and fourth digital inputs of the BVSMVS 22 are connected, respectively, with the third, fourth, fifth and sixth outputs of the BRICS 20, and the first, second, third and fourth analog inputs of the BVSMVS 22 are connected, respectively, with the first, second, third and fourth outputs BTSMVS 23 (Fig. 1, Fig. 5). The first, second, third, fourth, fifth, sixth, seventh and eighth digital inputs of the BTSMVS 23 are connected, respectively, with the seventh, eighth, ninth, tenth, eleventh, twelfth, thirteenth and fourteenth outputs of the BRICS 20.

In this case, the first, second ... n control inputs of the receiving part 3 (U _pr1 , U _pr2 ... U _prn ) are connected to the code inputs, respectively, of the first BOSPR 18 ₁ , the second BOSPR 18 ₂ ... n-th BOSPR 18 _n , and inside each of n BOSPR 18 its code input is connected to the code input BRICS 20 (Fig. 1).

The proposed method is carried out using the proposed device as follows (Fig. 1). The original analog signal is fed to the input of the transmitting part 1, and inside the transmitting part 1 this signal is applied to the parallel inputs, the first BOSP 4 ₁ , the second BOSP 4 ₂ ... n-th BOSP 4 _n . In each of n BOSP 4, an analog signal is input to PF 6, where a limited frequency band is allocated from the original signal. Moreover, in each of the n BOSP 4, PF 6 is tuned to a certain part of the spectrum of the original analog signal, as a result of which the entire original analog signal is divided into n frequency bands. Thus, n strip analog signals are generated.

After that, a strip analog signal in each of n BOSP 4 at the first stage of modulation decomposition is supplied from the output of the PF 6 to the input of the first BRS 7 ₁ , and inside this block the signal is fed to the parallel input of the DPA 11 and the first input of the HMFCO 12 (Fig. 1) . After a half-wave rectification, the signal from the output of the ДПВ 11 is fed to the second input of the HVMCHAO 12. In the HVMCHAO 12, the band signal undergoes modulation decomposition (Fig. 8). For this, as will be shown below, a Hilbert-conjugated signal is formed from a strip analog signal. From the first complex signal obtained in this way, consisting of S (t) and S ₁ (t), the signal of the first instantaneous frequency ω ₁ (t) and the first Hilbert amplitude envelope A ₁ (t) are extracted, which appear, respectively, on the first and second GVMCHAO outputs 12.

Next, the signals from the first and second outputs of the high-frequency filter 12 are fed to the inputs, respectively, of the first low-pass filter 13 and the second low-pass filter 14 (Fig. 1), in which from the signal of the first instantaneous frequency ω ₁ (t) and the signal of the first Hilbert amplitude envelope A ₁ (t ) emit two quasi-constant analog transmission signals. In this case, the first quasi-constant analog signal ω _c1 (t) from the output of the first low-pass filter 13 is a parameter - the average value of the instantaneous frequency (SZMCH) of the strip analog signal, characterizing the weighted average value of the frequency (SZCh) of the spectrum of this strip analog signal. And the second quasi-constant analog signal A _c1 (t) from the output of the second low-pass filter 14 is also a parameter - the average value of the Hilbert amplitude envelope (NWGAO) of the strip analog signal, which characterizes the weighted average value of the amplitude envelope (NWAO) of the same strip analog signal.

Then, each of the pair of quasi-constant transmission signals from the outputs of the first low-pass filter 13 and the second low-pass filter 14 is fed to the inputs of the first ADC 15 and the second ADC 16, respectively (Fig. 1), where they undergo analog-to-digital conversion. Two individual digital transmission signals from the outputs of the first ADC 15 and the second ADC 16 (the first and second digital outputs of the first BRS 7 ₁ ) are fed, respectively, to the first and second information inputs of BOICS 8.

After the strip analog signal at the first stage in the first BRS 7 _{1 of} each of n BOSP 4 underwent modulation decomposition (MP), then the first ω _c1 (t) and the second A _c1 (t) quasi-constant analog signals from the outputs of the first LPF, respectively 13 and the second low-pass filter 14 are fed, respectively, to the first and second analog outputs of the BRS 7 ₁ and then received, respectively, to the first and second analog inputs of the BVSMRS 9 (Fig. 1, Fig. 2). And the signal of the first instantaneous frequency ω ₁ (t) and the signal of the first Hilbert amplitude envelope A ₁ (t) are supplied, respectively, from the first and second outputs of the HVMCHAO 12 to, respectively, the third and fourth analog outputs of the BRS 7 ₁ and then received, respectively, on the third and fourth analog inputs BVSMRS 9 (Fig. 1, Fig. 2).

Next, in each of the n frequency bands in each of the BOSP 4 at the second MP stage in the MSSMRS 9, the first quasi-constant analog transmission signal ω _c1 (t) is subtracted from the signal of the first instantaneous frequency ω ₁ (t) and the first variable analog signal ω _p1 (t ) And from the signal of the first Hilbert amplitude envelope A ₁ (t), the second quasi-constant analog transmission signal A _c2 (t) is subtracted and the second alternating analog signal A _p2 (t) is formed (Fig. 2). After that, in BVMSRS 9 in relation to the first and second variable analog signals ω _p1 (t) and A _p2 (t) carry out the same operations that were carried out at the first stage MP in the BRS 7 ₁ . For this, from the first and second variable analog signals ω _п1 (t) and Α _п2 (t), the corresponding signals conjugated by him according to Hilbert are formed. And from each, from the second and third complex signals generated in this way, respectively, the second and third pairs of parametric signals, respectively, consisting of the signal of the second instantaneous frequency ω ₂ (t) and the signal of the second Hilbert amplitude envelope A ₂ ( t), the signal of the third instantaneous frequency ω ₃ (t) and the signal of the third Hilbert amplitude envelope A ₃ (t). Then, from the second and third pairs of parametric signals (ω ₂ (t) and A ₂ (t), ω ₃ (1) and A ₃ (1)), by low-pass filtering, the second and third pairs of quasi-constant analog transmission signals are isolated consisting, respectively, of the third ω _c3 (t) and fourth A _c4 (t), fifth ω _c5 (t) and sixth A _c6 (t) quasi-constant analog transmission signals.

Then in BVSMRS 9 (Fig. 1, Fig. 2), these third ω _c3 (t) and fourth A _c4 (t), fifth ω _c5 (t) and sixth A _c6 (t) quasi-constant analog transmission signals undergo analog-to-digital conversion in, respectively, the third, fourth, fifth and sixth individual digital transmission signals, which, respectively, from the first, second, third and fourth digital outputs of the BVMSRS 9 are received, respectively, at the third, fourth, fifth and sixth information inputs of the BICTS 8.

In addition, in BVSMRS 9, these third ω _c3 (t) and fourth A _c4 (t), fifth ω _c5 (t) and sixth A _c6 (t) quasi-constant analog transmission signals are fed to the first, second, fifth and sixth analog, respectively outputs BVSMRS 9 and then arrive, respectively, at the first, second, fifth and sixth analog inputs of BTSMP 10 (Fig. 1, Fig 3). And the signal of the second instantaneous frequency ω ₂ (t), the signal of the second Hilbert amplitude envelope A ₂ (t), the signal of the third instantaneous frequency ω ₃ (t) and the signal of the third Hilbert amplitude envelope A ₃ (t) are supplied, respectively, to the third, fourth , the seventh and eighth analog outputs of BVSMRS 9 and then arrive, respectively, at the third, fourth, seventh and eighth analog inputs of BTSMRS 10 (Fig. 1, Fig. 3).

Then, in each of the n frequency bands in each of the BOSP 4 at the third MP stage in the BTSMRS 10, the third ω _c3 (t) is subtracted from the second instantaneous frequency signal ω ₂ (t) and the second Hilbert amplitude envelope signal A ₂ (t), respectively and the fourth A _c4 (t) quasi-constant analog transmission signals, and form, respectively, the third ω _p3 (t) and the fourth A _p4 (t) variable analog signals. And from the signal of the third instantaneous frequency ω _p3 (t) and the signal of the third Hilbert amplitude envelope A ₃ (t), the fifth ω _c5 (t) and sixth A _c6 (t) quasi-constant analog transmission signals are subtracted, respectively. As a result, receive, respectively, the fifth ω _p5 (t) and sixth A _p6 (t) variable analog signals (Fig. 3). After that, from the third ω _p3 (t) and fourth A _p4 (t), fifth ω _p5 (t) and sixth A _p6 (t) variable analog signals, the corresponding signals conjugated by him according to Hilbert are formed and, from each of those thus formed, respectively, the fourth and fifth, sixth and seventh complex signals emit, respectively, the fourth and fifth, sixth and seventh pairs of parametric signals consisting, respectively, of the fourth instantaneous frequency signal ω ₄ (t) and the fourth Hilbert amplitude envelope signal A ₄ (t ), the signal of the fifth mg Ram frequencies ω ₅ (t) signal and the fifth Hilbert amplitude envelope A ₅ (t), the signal sixth instantaneous frequency ω ₆ (t) signal and the sixth Hilbert amplitude envelope A ₆ (t), the seventh instantaneous frequency ω signal ₇ (t) and signal of the seventh Hilbert amplitude envelope A ₇ (t). And then from the fourth and fifth, sixth and seventh pairs of parametric signals by low-pass filtering, respectively, the fourth and fifth, sixth and seventh pairs of quasi-constant analog transmission signals are selected, consisting, respectively, of the seventh ω _c7 (t) and the eighth A _c8 (t ), the ninth ω _c9 (t) and the tenth A _c10 (t), the eleventh ω _c11 (t) and the twelfth A _c12 (t), the thirteenth ω _c13 (t) and the fourteenth A _c14 (t), quasi-constant analog transmission signals.

Then, in BTSMRS 10 (Fig. 1, Fig. 3) these seventh ω _c7 (t), eighth A _c8 (t), ninth ω _c9 (t), tenth A _c10 (t), eleventh ω _c11 (t), twelfth A _c12 (t), thirteenth ω _c13 (t) and fourteenth A _c14 (t), quasi-constant analog transmission signals undergo analog-to-digital conversion into, respectively, the seventh, eighth, ninth, tenth, eleventh, twelfth, thirteenth and fourteenth individual digital transmission signals, which, respectively, from the first, second, third, fourth, fifth, sixth, seventh and eighth digital outputs of BTSMP 10 p tread, respectively, in the seventh, eighth, ninth, tenth, eleventh, twelfth, thirteenth and fourteenth data inputs BOITSS 8 (FIG. 1).

Thus, in each of n BOSP 4, a group of 14 individual digital transmission signals or from B _n pairs of individual digital transmission signals is formed from the corresponding analog bandpass signal.

Further, these B _n pairs of individual digital transmission signals are combined into a BOICS 8 (each of n BOSP 4) and receive at its output a digital group transmission signal (Fig. 1, Fig. 6). Moreover, each of the n digital group transmission signals in the corresponding BICPS 8 (corresponding to BOSP 4), under the action of a control signal (code combination) at the code input of the BICPS 8 (code input of the corresponding BOSIC 4, i.e., to the corresponding control input U _p transmitting parts 1), form independently of other groups and are composed of either individual digital transmission signals related only to the first stage of modulation decomposition, in which B _n is 1, or the first and second steps of modulation decomposition, when of which B _n is equal to 3, or from digital signals related to all three stages of decomposition, for which B _n is 7. A digital group transmission signal from the output of BOICS 8 (Fig. 1) and, accordingly, from the output of each of n n BOSP 4, It is fed to the corresponding input of BOTSGS 5. In BOTSGS 5 n digital group transmission signals are again combined and the generated digital linear signal from the output of BOTSGS 5, which means that the output of the transmitting part 1 is transmitted via communication line 2.

The independent generation of each of the n digital group transmission signals in the corresponding BICTs 8 (corresponding to BOSP 4) allows, in relation to groups associated with the transmission of high-frequency bands of analog signals, in certain cases to be limited to the transmission of individual digital transmission signals related only to the first stage of modulation decomposition, in which B _n is equal to 1, or the first and second steps of modulation decomposition, in which B _n is equal to 3. This is due to the peculiarities of human auditory perception of near-frequency sound components. It is desirable to transmit groups of digital signals associated with the transmission of low and medium frequency bands of analog signals using three stages of modulation decomposition, at which B _n is 7. Such flexible generation of each of n digital group transmission signals allows to reduce the transmission speed of a digital signal over a communication line without a noticeable decrease in the quality of the transmitted information.

And in the receiving part 3 (Fig. 1), a digital linear signal is fed to the input of the BRTSGS 17, in which this linear signal is divided into n digital group reception signals. After that, each of the n digital group reception signals from the corresponding outputs of the BRSPGS 17 is fed to the input of the corresponding BOSPR 18, and inside each BOSPR 18 this signal is fed to the information input of the BRICS 20. In BRICS 20, the digital group reception signal is divided into B _n pairs of individual digital signals receive and form n groups of individual digital reception signals. Moreover, each of the n groups of individual digital reception signals in BRICS 20 (Fig. 1, Fig. 7) of each of the BOSPR 18, under the action of the corresponding control signal (code combination) at the code input of the BRICS 20 (code input of the corresponding BOSPR 18, t. . e on the corresponding control input U _n of the receiving part 3) is formed independently of other groups and comprise either of the individual digital signal pairs reception pertaining only to the first stage of the modulation recovery in which B _n is 1, or the first and second steps of the modulation nnogo recovery in which B _n is equal to 3, either from the individual pairs of receiving digital signals related to the three stages of modulation recovery in which B _n = 7.

Individual digital reception signals from the first and second outputs of BRICS 20 (Fig. 1, Fig. 7) are supplied, respectively, to the first and second digital inputs of the first BVS 21 ₁ . The individual digital reception signals from the third, fourth, fifth and sixth outputs of the BRICS 20 are supplied, respectively, to the first, second, third and fourth digital inputs of the BVMSVS 22. Individual digital reception signals from the seventh, eighth, ninth, tenth, eleventh, twelfth, thirteenth and the fourteenth outputs of the BRICC 20 are fed, respectively, to the first, second, third, fourth, fifth, sixth, seventh and eighth digital inputs of the BTSMVS 23.

Then, in each of n independent groups of individual digital reception signals in each of BOSPR 18 (Fig. 1), digital-to-analog conversion is performed in the first BVS 21 ₁ , BVSMVS 22, BTSMVS 23 and n n independent groups of analog reception signals are generated in n BOSPr 18, each of which contains B _n pairs of quasi-constant analog reception signals. Moreover, in the first BVS 21 ₁ , the first ω _c1 (t) and the second A _c2 (t) form quasi-constant analog reception signals. In BMSMVS 22 (Fig. 1, Fig. 4) form the third ω _c3 (t) and the fourth A _c4 (t), the fifth ω _c5 (t) and the sixth A _c6 (t) quasi-constant analog reception signals. And in BTSMVS 23 (Fig. 1, Fig. 5) form the seventh ω _c7 (t) and the eighth A _c8 (t), the ninth ω _c9 (t) and the tenth A _c10 (t), the eleventh ω _c11 (t) and the twelfth A _c12 (t), thirteenth ω _c13 (t) and fourteenth A _c14 (t) quasi-constant analog receive signals.

After that, in the corresponding independent groups of analog reception signals, in the corresponding BOSPR 18, for the case when B _n = 7 (under the action of the corresponding code combination at the BRICC 20 code input), at the third stage of modulation signal recovery in the BTSMVS 23 (Fig. 1, FIG. 5) in each of the fourth, fifth, sixth and seventh pairs of quasi-analog receiving signals, first using, respectively, the seventh ω _c7 (t), the ninth ω _c9 (t), the eleventh ω _c11 (t) and thirteenth ω _c13 ( t) quasi-constant analog reception signals as controls yayuschih frequency, form, respectively, third, fourth, fifth and sixth quasiharmonic frequency-modulated oscillation (cos phase).

And then, using the eighth A _c8 (t), tenth A _c10 (t), twelfth A _c12 (t) and fourteenth A _c14 (t) quasi-constant analog receive signals modulate in amplitude these, respectively, third, fourth, fifth and sixth quasi-harmonic frequency-modulated oscillations, and form, in BTSMVS 23, respectively, the third ω _p3 (t), fourth A _p4 (t), fifth ω _p5 (t) and sixth A _p6 (t) restored alternating analog signals that are received, respectively, at the first, second, third and fourth outputs of the BTSMVS 23 (Fig. 1, Fig. 5).

These reconstructed variable analog signals from the first, second, third and fourth outputs of the BTSMVS 23 in the corresponding independent groups of analog reception signals, in the corresponding BOSPR 18 (Fig. 1) at the second stage of the modulation signal recovery, respectively, go to the first, second, third and the fourth analog inputs of the MFSS 22 (FIG. 1, FIG. 4), in which these reconstructed variable analog signals are added, respectively, to the third ω _c3 (t), fourth A _c4 (t), fifth ω _c5 (t) and sixth A _c6 (t) analog kvaziostoyannymi bubbled reception signals and form, respectively, the signal of the second reduced instantaneous frequency ω ₂ (t), the signal of the second reduced Hilbert amplitude envelope A ₂ (t), the signal of the third reduced instantaneous frequency ω ₃ (t) signal and a third recovered Hilbert amplitude envelope A ₃ (t). And then, using the signals of the second ω ₂ (t) and third ω ₃ (t) of the restored instantaneous frequencies as frequency control, the first and second quasi-harmonic frequency-modulated oscillations are formed, respectively.

After that, using the signals of the second A ₂ (t) and third A ₃ (t) of the reconstructed Hilbert amplitude envelopes, these first and second quasi-harmonic frequency-modulated oscillations are modulated in amplitude and, accordingly, the first ω _p1 (t) is generated and the second A _p2 (t) reconstructed variable analog signals that are respectively fed to the first and second outputs of the BMSVS 22 (FIG. 1, FIG. 4).

These reconstructed variable analog signals from the first and second outputs of the BVSMVS 22 (Fig. 1) in the corresponding independent groups of analog reception signals, in the corresponding BOSPR 18 at the first stage of the modulation signal recovery, respectively, go to the first and second analog inputs of the first BVS 21 ₁ . In BVS 21 _1, these first ω _p1 (t) and second A _p2 (t) reconstructed analog analog signals are supplied to the second inputs of the first adder 26 and second adder 27, respectively. The first inputs of the first adder 26 and second adder 27 from the outputs respectively, the first DAC 24 and the second DAC 25 receive, respectively, the first ω _c1 (t) and the second A _c2 (t) quasi-constant analog signals. The first ω _c1 (t) quasi-constant analog receive signal is added, in the first adder 26, with the first ω _p1 (t) restored alternating analog signal and the signal of the first restored instantaneous frequency ω ₁ (t) is formed. And the second A _c2 (t) quasi-constant analog reception signal is added, in the second adder 27, with the second A _p2 (t) restored alternating analog signal and the signal of the first restored Hilbert amplitude envelope A ₁ (t) is formed.

The signal of the first restored instantaneous frequency ω ₁ (t) from the output of the first adder 26 is fed to the input of the VCO 28 (Fig. 1), in which it is used as the control frequency. At the output of the VCO 28, an output quasi-harmonic frequency-modulated oscillation is obtained, which is fed to the first input AM 29. The second restored input Hilbert amplitude envelope A ₁ (t), which modulates the amplitude of the output quasiharmonic frequency-modulated oscillation, is fed to the second input AM 29 from the output of the second adder 27. The output AM 29 and, accordingly, the output of the first BVS 211 (output BOSPR 18) receive the output analog signal reception S (t).

Similarly, in the respective independent groups of analog reception signals, in the corresponding BOSPR 18, in which B _n = 7, the analog output signals S (t) are also received (Fig. 1).

In other independent groups of analog reception signals, in the corresponding BOSPR 18, for the case when B _n = 3 (under the action of the corresponding code combination at the BRICC 20 code input) at the second stage of modulation signal recovery in the BMSSV 22 (Fig. 1, Fig. 4 ) in each of the second and third pairs of quasi-analog receiving signals from the first, respectively third ω _c3 (t) and fifth ω _c5 (t) quasi-analog reception signals as the control frequency, form, respectively, first and second quasi-harmonic h otno-modulated oscillations.

And then, using the fourth A _c4 (t) and sixth A _c6 (t) quasi-constant analog receive signals, these first and second quasi-harmonic frequency-modulated oscillations are modulated in amplitude and form in the BMSWS 22, respectively, the first ω _p1 (t) and the second A _p2 (t) reconstructed analog analog signals that are supplied, respectively, to the first and second outputs of the MSS 22 (Fig. 1, Fig. 4).

These recovered variable analog signals from the first and second outputs of the BMSMVS 22 in the corresponding independent groups of analog reception signals, in the corresponding BOSPR 18 (Fig. 1) at the first stage of modulation signal recovery, respectively, go to the first and second analog inputs of the first BVS 21 ₁ , wherein these variables are reconstructed analog signals fold, respectively, with the first ω _c1 (t) and the second a _c2 (t) quasiconstant analog reception signals, and form, respectively, the signal of the first uprising ennoy instantaneous frequency ω ₁ (t) signal and a first reconstructed Hilbert envelope of the amplitude A ₁ (t).

After that, using the signal of the first reconstructed instantaneous frequency ω ₁ (t) as the control frequency, an output quasiharmonic frequency-modulated oscillation is generated, and then, using the signal of the first reconstructed Hilbert amplitude envelope A ₁ (t), this output quasiharmonic frequency is modulated in amplitude -modulated oscillation, and form at the output of the first BVS 21 ₁ (output BOSPR 18) the output analog signal reception S (t) (Fig. 1). The operation of the first BVS 21 _{1 is} described in more detail above for the case when B _n = 7.

Similarly, in the corresponding independent groups of analog reception signals, in the corresponding BOSPR 18, in which B _n = 3, the analog output signals S (t) are also received (Fig. 1).

In the third independent groups of analog reception signals, in the corresponding BOSPR 18 (Fig. 1), for the case when B _n = 1 (under the action of the corresponding code combination at the BRICC 20 code input) at the first stage of modulation signal recovery in the first BVS 211 in each from the first pair of quasi-constant analog receive signals, first using, respectively, the first quasi-constant analog receive signal ω _c1 (t) as the control frequency, an output quasi-harmonic frequency-modulated oscillation is formed, and then, Using the second quasi-constant analog receive signal A _c2 (t), this output quasi-harmonic frequency-modulated oscillation is modulated in amplitude, and the output analog receive signal S (t) is generated at the output of the first BVS 21 ₁ (BOSPR 18 output) (Fig. 1). The operation of the first BVS 21 _{1 is} described in more detail above for the case when B _n = 7

Similarly, in the corresponding independent groups of analog reception signals, in the corresponding BOSPR 18, in which B _n = 1, the analog output signals S (t) are also received (Fig. 1).

After that, n parallel output analog reception signals S (t) from n independent groups of analog reception signals (in which B _n can be equal to 7, 3 or 1) from the outputs of BOSPR 18 ₁ , BOSPR 18 ₂ ... BOSPR 18 _n are received, respectively the first, second ... n inputs of the BACS 19. In the BACS 19 (Fig. 1), these n parallel output analog reception signals S (t) are combined and form the restored analog signal at the output of the BACS 19.

The proposed device for transmitting and receiving signals represented by the parameters of spectral modulation decomposition, in contrast to the prototype, allows for modulation decomposition to use the entire spectrum of each of n strip analog signals at each of the three stages of this modulation decomposition. As a result, the accuracy of the formation of quasi-constant parameters of modulation decomposition, according to which the information analog signal is restored at the receiving side, is increased. As a result, it is possible to improve the quality of transmission of information signals. In addition, improving the quality of transmission of information signals can significantly reduce the speed of a digital signal in a channel in exchange for a slight deterioration in the quality of analog signals.

A feature of the proposed device for transmitting and receiving signals represented by the parameters of spectral modulation decomposition is that it is non-standard in it: a block of the second stage of the modulation signal decomposition, a block of the third stage of the modulation signal decomposition, a block of the second stage of the modulation signal recovery, block of the third stage of the modulation signal recovery , a unit for combining individual digital signals, a unit for separating individual digital signals, a Hilbert circuit High frequency and amplitude envelope separator.

An example of the implementation of the block of the second stage of modulation signal decomposition (MSSMRS) 9 is shown in FIG. 2. This block contains: the first subtraction scheme (CB ₁ ), the second subtraction scheme (CB ₂ ), the second signal decomposition block (BRS ₂ ) and the third signal decomposition block (BRS ₃ ). The first and second inputs CB _{1 are} connected, respectively, with the first and third analog inputs of the BVSMRS 9, and the first and second inputs CB _{1 are} connected, respectively, with the second and fourth analog inputs of the BVSMRS 9. The output CB _{1 is} connected to the input of the BRS ₂ , and the output CB _{2 is} connected to the input of the BRS ₃ . The first and second digital outputs of the BRS _{2 are} connected, respectively, with the first and second digital outputs of the BVSMRS 9, and the first and second digital outputs of the BRS _{3 are} connected, respectively, with the third and fourth digital outputs of the BVSMRS 9. The first, second third and fourth analog outputs of the BRS ₂ are connected respectively to the first, second, third and fourth analog outputs BVSMRS 9, and first, second, third and fourth analog outputs couplings ₃ are connected respectively to the fifth, sixth, seventh and eighth analog outputs 9. It is of BVSMRS tag, the second signal decomposition unit (EB ₂₎ and third signal decomposition unit (EB ₃₎ included in BVSMRS 9 entirely similar to the first signal decomposition unit (EB) 7 ₁ schematically depicted in FIG. one.

The block of the second stage of modulation decomposition of the signal BVSMRS 9 (Fig. 2) works as follows. The first, second, third and fourth analog inputs of the BVSMRS 9 s, respectively, of the first, second, third and fourth analog outputs of the BRS 7 ₁ (Fig. 1) respectively receive the first quasi-constant analog signal ω _c1 (t), the second quasi-constant analog the signal Ad (t), the signal of the first instantaneous frequency ω ₁ (t), and the signal of the first Hilbert amplitude envelope A ₁ (t). Inside BVSMRS 9 (FIG. 2), these signals are supplied respectively to a first input CB _1, CB to a first input _2, a second input of CB ₁ and CB ₂ the second input. In CB _{1, the} first quasi-constant analog transmission signal ω _c1 (t) is subtracted from the signal of the first instantaneous frequency ω ₁ (t) and the first alternating analog signal ω _p1 (t) is output. And in CB _{2, the} second quasi-constant analog transmission signal A _c2 (t) is subtracted from the signal of the first Hilbert amplitude envelope A ₁ (t) and the second variable analog signal A _p2 (t) is output. These first alternating analog signal ω _p1 (t) and the second alternating analog signal A _p2 (t) from the outputs, respectively, CB ₁ and CB ₂ are fed to the inputs, respectively, BRS ₂ and BRS ₃ , in which, in relation, respectively, of the first and the second variable analog signals ω _p1 (t) and A _p2 (t) perform the same operations that were carried out at the first stage MP in the BRS 7 ₁ (in Fig. 1). For this, from the first and second variable analog signals ω _p1 (t) and A _p2 (t) in, respectively, BRS ₂ and BRS ₃ form the corresponding signals conjugated by him according to Hilbert.

And from each of the second (in BRS ₂ ) and third (in BRS ₃ ) complex signals formed in this way, respectively, the second and third pairs of parametric signals, respectively, consisting of the second instantaneous frequency signal ω ₃ (t ) and the signal of the second Hilbert amplitude envelope A ₂ (t) in the BRS ₂ , as well as the signal of the third instantaneous frequency ω ₃ (t) and the signal of the third Hilbert amplitude envelope A ₃ (t) in the BRS ₃ (Fig. 2). Then, from the second and third pairs of parametric signals (ω ₂ (t) and A ₂ (t), ω ₃ (t) and A ₃ (t)), by low-pass filtering, the second and third pairs of quasi-constant analog transmission signals are isolated consisting, respectively, of the third ω _c3 (t) and fourth A _c4 (t) in BRS ₂ , the fifth ω _c5 (t) and sixth A _c6 (t) in BRS ₃ quasi-constant analog transmission signals.

Then, in BRS _2, these third ω _c3 (t) and fourth A _c4 (t), and in BRS ₃ , the fifth ω _c5 (t) and sixth A _c6 (t) quasi-constant analog transmission signals undergo analog-to-digital conversion into, respectively, the third and fourth - in the BRS ₂ , the fifth and sixth - in the BRS ₃ individual digital transmission signals, which, respectively, from the first and second digital outputs of the BRS ₂ are received, respectively, on the first and second digital outputs BVSMRS 9. And from the first and second digital outputs BRS ₃ individual digital transmission signals are supplied respectively to t second and fourth digital outputs BVSMRS 9 (FIG. 2).

In addition, the third ω _c3 (t) and fourth A _c4 (t) quasi-constant analogue transmission signals from, respectively, the first and second analogue outputs of the BRS ₂ are supplied, respectively, to the first and second analogue outputs of the BCMRS 9. And the fifth ω _c5 (t) and the sixth A _c6 (t) quasi-constant analogue transmission signals from, respectively, the first and second analogue outputs of the BRS ₃ are supplied, respectively, to the fifth and sixth analog outputs of the BMSRS 9. The second instantaneous frequency signal is ω ₂ (t), and the second Hilbert envelope of the amplitude a ₂ (t) with, respective but, the third and fourth analog outputs RBS ₂ are fed respectively to the third and fourth analog outputs BVSMRS 9 (FIG. 2). And the signal of the third instantaneous frequency ω ₃ (t) and the signal of the third Hilbert amplitude envelope A ₃ (t) with, respectively, of the third and fourth analog outputs of the BRS ₃ are supplied, respectively, to the seventh and eighth analog outputs of the BVSMRS 9.

An example of implementation of the block of the third stage of modulation signal decomposition (BTSMP) 10 is shown in FIG. 3. This block contains: the second block of the second stage of modulation signal decomposition (BVSMRS ₂ ) and the third block of the second stage of modulation signal decomposition (BVSMRS ₃ ). The first, second, third and fourth analog inputs of the BTSMRS 10 are connected, respectively, with the first, second, third and fourth analog inputs of the BVSMRS ₂ , and the fifth, sixth, seventh and eighth analog inputs of the BTSMRS 10 are connected, respectively, with the first, second, third and the fourth analog inputs BVSMRS ₃ . The first, second, third and fourth digital outputs of the BVSMRS _{2 are} connected, respectively, with the first, second, third and fourth digital outputs of the BTSMRS 10, and the first, second, third and fourth digital outputs of BVSMRS _{3 are} connected, respectively, with the fifth, sixth, seventh and the eighth digital outputs of BTSMP 10.

It should be noted that the second block of the second stage of modulation signal decomposition (BVSMRS ₂ ) and the third block of the second stage of modulation signal decomposition (BVSMRS ₃ ) included in the BTSMRS 10 are completely similar to the block of the second stage of modulation signal decomposition (BVSMRS 9), the diagram of which is shown in FIG. 2.

The block of the third stage of modulation decomposition of the signal BTSMP 10 (Fig. 3) works as follows. The first, second, third and fourth analog inputs of the BTSMRS 10 s, respectively, of the first, second, third and fourth analog outputs of the BVSMRS 9 (Fig. 1) receive, respectively, the third quasi-constant analog transmission signal ω _c3 (t), the fourth quasi-constant analog the transmission signal A _c4 (t), the second instantaneous frequency signal ω ₂ (t) and the second Hilbert amplitude envelope signal A ₂ O), which are fed inside the BTSMP 10 (Fig. 3), respectively, to the first, second, third and fourth analog BVSMRS inputs ₂ . And the fifth, sixth, seventh and eighth analog inputs of the BTSMRS 10 s, respectively, of the fifth, sixth, seventh and eighth analog outputs of the BVSMRS 9 (Fig. 1) receive, respectively, the fifth quasi-constant analog transmission signal ω _c5 (t), sixth quasi-constant the analog transmission signal A _c6 (t), the signal of the third instantaneous frequency ω ₃ (t) and the signal of the third Hilbert amplitude envelope A ₃ (t), which are supplied inside the BTSMP 10 (Fig. 3), respectively, to the first, second, third and fourth analog inputs BVSMRS ₃ .

In BVMSRS ₂ from the signal of the second instantaneous frequency ω ₂ (t) and the signal of the second Hilbert amplitude envelope A ₂ (t), the third ω _c3 (t) and fourth A _c4 (t) quasi-constant analog transmission signals are subtracted, and form, respectively , the third ω _p3 (t) and the fourth A _p4 (t) variable analog signals. And in BVMSRS ₃ from the signal of the third instantaneous frequency ω ₃ (t) and the signal of the third Hilbert amplitude envelope A ₃ (t), the fifth ω _c5 (t) and sixth A _c6 (t) quasi-constant analog transmission signals are subtracted, respectively. As a result, the fifth ω _p5 (t) and the sixth A _p6 (t) respectively receive analog signals.

After that, from the third ω _p3 (t) and the fourth A _p4 (t) variable analog signals - in BVSMRS ₂ , as well as from the fifth ω _p5 (t) and sixth _{п p6} (t) variable analog signals - in BVSMRS ₃ (Fig. 3) form the corresponding signals conjugated by him according to Hilbert. From each of the fourth and fifth (in BVSMRS ₂ ), sixth and seventh (in BVSMRS ₃ ) complex signals generated in this way, respectively, the fourth and fifth, sixth and seventh pairs of parametric signals, respectively, consisting of the signal the fourth instantaneous frequency ω ₄ (t) and the signal of the fourth Hilbert amplitude envelope A ₄ (t), the signal of the fifth instantaneous frequency ω ₅ (t) and the signal of the fifth Hilbert amplitude envelope A ₅ (t) - in the MFSR ₂ , and also from the sixth signal instantaneous frequency ω ₆ (t) and signal the sixth Hilbert amplitude envelope Α ₆ (t), the signal of the seventh instantaneous frequency ω ₇ (t), and the signal of the seventh Hilbert amplitude envelope A ₇ (t) - in the MFSR ₃ . And then from the fourth and fifth (in BVSMRS ₂ ), sixth and seventh (in BVSMRS ₃ ) pairs of parametric signals by low-pass filtering, respectively, the fourth and fifth (in BVSMRS ₂ ), the sixth and seventh (in BVSMRS ₃ ) pairs of quasi-constant analog transmission signals, respectively, consisting of the seventh ω _c7 (t) and the eighth A _c8 (t), the ninth ω _c9 (t) and the tenth A _c10 (t) - in the BCMRS ₂ , the eleventh ω _c11 (t) and the twelfth Ac ₁₂ (t), the thirteenth ω _c13 (t), and the fourteenth A _c14 (t) are in BMSRS ₃ , quasi-constant analog transmission signals.

Then, in BVSMRS ₂ (Fig. 3), these seventh ω _c7 (t), eighth A _c8 (t), ninth ω _c9 (t) and tenth A _c10 (t), quasi-constant analog transmission signals undergo analog-to-digital conversion to, respectively , seventh, eighth, ninth and tenth individual digital transmission signals, which, respectively, from the first, second, third and fourth digital outputs of the BVSMRS ₂ are received, respectively, to the first, second, third and fourth digital outputs of the BTSMRS 10. And in BVSMRS ₃ eleventh ω _c11 (t), twelfth A _c12 (t), thirteenth ω _c13 (t) and fourteenth A _c14 ( t), quasi-constant analog transmission signals are subjected to analog-to-digital conversion into, respectively, the eleventh, twelfth, thirteenth and fourteenth individual digital transmission signals, which, respectively, from the first, second, third and fourth digital outputs of the BCMRS ₃ are received, respectively, on the fifth , sixth, seventh and eighth digital outputs BTSMP 10.

An example of the implementation of the block of the second stage of modulation signal recovery (BMSVS) 22 is shown in FIG. 4 This block contains:

a second signal recovery unit (BVS ₂ ) and a third signal recovery unit (BVS ₃ ). The first and second analog inputs of BVSMVS 22 are connected, respectively, with the first and second analog inputs of BVS ₂ , and the third and fourth analog inputs of BVSMVS 22 are connected, respectively, with the first and second analog inputs of BVSM ₃ . The first and second digital inputs of the BMSMVS 22 are connected, respectively, with the first and second digital inputs of the BVS ₂ , and the third and fourth digital inputs of the BVSMVS 22 are connected, respectively, with the first and second digital inputs of the BVS ₃ . The output of BVS _{2 is} connected to the first output of BVSMVS 22, and the output of BVS _{3 is} connected to the second output of BVSMVS 22.

It should be noted that the second signal recovery unit (BVS ₂ ) and the third signal recovery block (BVS ₃ ) included in the BVSMVS 22 are completely similar to the first signal recovery block BVS 21 ₁ , the circuit of which is shown in FIG. one.

The block of the second stage of modulation signal recovery (BMSVS) 22 operates as follows (Fig. 4). The individual digital reception signals from the third, fourth, fifth and sixth outputs of the BRICC 20 are supplied, respectively, to the first, second, third and fourth digital inputs of the BMSVS 22 (Fig. 1), and inside the BVMSVS 22 (Fig. 4) these signals are received, respectively, to the first and second digital inputs of the BVS ₂ and to the first and second digital inputs of the BVS ₃ . In BVS ₂ , digital-to-analog conversion of these individual digital reception signals is carried out and a third ω _c3 (t) and a fourth A _c4 (t) quasi-constant analog reception signals are obtained. And in BVS _{3, they} also perform digital-to-analog conversion of individual digital reception signals and obtain the fifth ω _c5 (t) and sixth A _c6 (t) quasi-constant analog reception signals.

On the first, second, third and fourth analog inputs of the BVSMVS 22, respectively, from the first, second, third and fourth outputs of the BTSMVS 23 (Fig. 1), respectively, the third ω _p3 (t), the fourth A _p4 (t), fifth ω _p5 (t) and sixth A _p6 (t) reconstructed variable analog signals. Moreover, the third ω _p3 (t) and fourth A _p4 (t) reconstructed variable analog signals inside the BVMSVS 22 (Fig. 4) are fed to the first and second analog inputs of the BVS ₂ , respectively, and the fifth ω _p5 (t) and the sixth A _n6 (t) restored alternating analog signals are fed to, respectively, the first and second analog inputs of the BVS ₃ .

In BVS _{2, the} third ω _p3 (t) and fourth A _p4 (t) reconstructed analog signals are added, respectively, with the third ω _c3 (t) and fourth A _c4 (t) quasi-constant analog reception signals and form, respectively, the signal of the second reconstructed instantaneous frequency ω ₂ (t) and the signal of the second restored Hilbert amplitude envelope A ₂ (t). And in BVS _{3, the} fifth ω _p5 (t) and sixth A _p6 (t) reconstructed analogue signals are added, respectively, with the fifth ω _c5 (t) and sixth A _c6 (t) quasi-constant analog reception signals and form, respectively, the third the reconstructed instantaneous frequency ω ₃ (t) and the signal of the third reconstructed Hilbert amplitude envelope A ₃ (t).

And then in BVS ₂ (Fig. 4), using the signal of the second ω ₂ (t) of the restored instantaneous frequency as the control frequency, the first quasi-harmonic frequency-modulated oscillation is formed, which is modulated in amplitude, using the second A ₂ (t) signal reconstructed Hilbert amplitude envelope and receive the first ωp ₁ (t) reconstructed alternating analog signal. And in BVS ₃ , using the signal of the third ω ₃ (t) reconstructed instantaneous frequency as the control frequency, a second quasi-harmonic frequency-modulated oscillation is generated, which is modulated in amplitude, using the signal of the third A ₃ (t) reconstructed Hilbert amplitude envelope and get the second A _p2 (t) restored alternating analog signal. These first ω _p1 (t) and second A _p2 (t) restored alternating analog signals, respectively, from the output of the BVS ₂ and the output of the BVS ₃ are received, respectively, at the first and second outputs of the BVSMVS 22.

An example of the implementation of the block of the third stage of modulation signal recovery (BTSMVS) 23 is shown in FIG. 5. This block contains: the second block of the second stage of modulation signal recovery (BVSMVS ₂ ) and the third block of the second stage of modulation signal recovery (BVSMVS ₃ ). The first, second, third and fourth digital inputs of BTSMVS 23 are connected, respectively, with the first, second, third and fourth digital inputs of BVSMVS ₂ , and the fifth, sixth, seventh and eighth digital inputs of BTSMVS 23 are connected, respectively, with the first, second, third and the fourth digital inputs BVSMVS ₃ . The first and second outputs of BVSMVS _{2 are} connected, respectively, with the first and second outputs of BTSMVS 23, and the first and second outputs of BVSMVS _{3 are} connected, respectively, with the third and fourth outputs of BTSMVS 23.

It should be noted that the second block of the second stage of modulation signal recovery (BVSMVS ₂ ) and the third block of the second stage of modulation signal recovery (BVSMVS ₃ ) included in the BTSMVS 23 are completely similar to the block of the second stage of modulation signal recovery (BVSMVS 22), the diagram of which is shown in FIG. four.

The block of the third stage of modulation signal recovery (BTSMVS) 23 (Fig. 5) works as follows. Individual digital reception signals from the seventh, eighth, ninth, tenth, eleventh, twelfth, thirteenth and fourteenth outputs of the BRICS 20 are supplied, respectively, to the first, second, third, fourth, fifth, sixth, seventh and eighth digital inputs of the BTSMVS 23 (Fig. 1), and inside the BTSMVS 23 (Fig. 5), these signals are supplied, respectively, to the first, second, third and fourth digital inputs of the BVSMVS ₂ and to the first, second, third and fourth digital inputs of the BVSMVS ₃ .

In BMSMVS ₂ , digital-to-analog conversion of these individual digital reception signals is carried out and pairs of the seventh ω _c7 (t) and eighth A _c8 (t), ninth ω _c9 (t) and tenth A _c10 (t) quasi-constant analog receive signals are _obtained . And in BVMSVS ₃ also carry out digital-to-analog conversion of individual digital reception signals and get pairs of the eleventh ω _c11 (t) and the twelfth A _c12 (t), the thirteenth ω _c13 (t) and the fourteenth A _c14 (t) quasi-constant analog reception signals.

Further, in the BMSMVS ₂ (Fig. 5), using the seventh ω _c7 (t) and the ninth ω _c9 (t), the quasi-constant analog receive signals as frequency control, respectively, form the third and fourth, quasi-harmonic frequency-modulated oscillations (cosine phase), and then using the eighth A _c8 (t) and tenth A _c10 (t) quasi-constant analog receive signals modulate in amplitude these third and fourth, respectively, quasi-harmonic frequency-modulated oscillations and receive, respectively, the third ω _p3 (t ), and the fourth A _p4 (t) restored p Alternating analog signals. And in BMSMVS ₃ , using the eleventh ω _c11 (t) and thirteenth ω _c13 (t) quasi-constant analog reception signals as frequency control, the fifth and sixth quasi-harmonic frequency-modulated oscillations, respectively, are formed, and then, using the twelfth A _c12 (t ) and A fourteenth _c14 (t) quasi-analog reception signals modulate the amplitude, respectively, the fifth and sixth quasiharmonic frequency-modulated oscillation, yielding respectively the fifth _n5 ω (t) and sixth _n6 A (t) reconstructed analog variables stems signals.

Then, the third ω _p3 (t) and the fourth A _p4 (t) reconstructed analog analog signals, respectively, from the first and second outputs of the BVMSVS ₂ arrive, respectively, at the first and second outputs of the BTSMVS 23. And the fifth ω _p5 (t) and the sixth A _p6 ( t) reconstructed variable analog signals, respectively, from the first and second outputs of the BMSMVS ₃ , respectively, to the third and fourth outputs of the BTSMVS 23.

An example implementation of a unit for combining individual digital signals (BOICS) 8 is shown in FIG. 6. This block contains: the first converter of parallel digital signals into serial (PPSSP ₁ ), the second PPSSP ₂ , the third PPSSP ₃ , the decoder (desh), the first circuit OR ₁ , the second circuit OR ₂ , the first circuit AND ₁ , the second circuit And ₂ , the third scheme And ₃ , the fourth scheme And ₄ and the fifth scheme And ₆ .

The first, second and third PCSPs are performed in the form of multiplexers or shift registers with parallel input and serial output of information (for example, K155IR1, K555IR11, K155IR13). The first PPSSP1 (for example, when executed on the basis of shift registers) has two parallel information inputs, which are, respectively, the first and second information inputs of BOICS 8. The second PPSSP2 ₂ has four parallel information inputs, which are, respectively, the third, fourth, fifth and sixth information inputs of BOICS 8. The third PPSSP ₃ has eight parallel information inputs, which are, respectively, from the seventh to fourteenth information inputs of the BICPS 8. The output of the first PPSSP _{1 is} connected to the first inputs Dams of the first and second schemes And ₁ , And ₂ . The output of the second PPSSP _{2 is} connected to the first inputs of the third and fourth circuits And ₃ , And ₄ , and the output of the third PPSSP _{3 is} connected to the first input of the fifth circuit And ₅ .

The code input of the decoder is the code input of BOITS 8 (one of the n control inputs of the transmitting part 1). The first output of the decoder is connected to the second input of the first circuit And ₁ . The second output of the decoder is connected to the first input of the first circuit OR ₁ and to the second input of the fourth circuit And ₄ . The third output of the decoder is connected to the second input of the first circuit OR ₁ , to the second input of the third circuit And ₃ and to the second input of the fifth circuit And ₅ (Fig. 6).

The output of the first circuit OR _{1 is} connected to the second input of the second circuit And ₂ . The outputs from the first to fifth circuits And ₁ , And ₂ , And ₃ , And ₄ , And ₅ , are connected, respectively, to the first input of the second circuit OR ₂ , to the serial input of the second PPSSP ₂ , to the serial input of the third PPSSP ₃ , to the second input the second circuit OR ₂ and to the third input of the second circuit OR ₂ , the output of which is the output of BOICS 8. The supply circuits of the clock pulses to the first second and third PPSSP in the diagram are not shown.

BOICS 8 (Fig. 6) allows you to convert into a digital group signal two individual digital signals (at the first MP stage) supplied to its first and second information inputs, or six similar signals (at the first and second MP stages) supplied to it with the first through sixth information inputs, as well as fourteen similar signals (at the first, second and third steps of MP) supplied to it from the first to fourteenth information inputs. In total, there are three options for connecting to the information inputs of BOICS 8 and, in accordance with these options, the first, second and third PPSSP are involved in different combinations. These options are implemented using code combinations supplied to the control input of BOICS 8 (table 1):

The control code combination 01, which allows only the first PPPSP ₁ to be activated, is used only when implementing the first MP stage, code combination 10 when implementing the first and second MP stages, and code combination 11 when implementing the first, second and third MP stages.

Block combining individual digital signals (BOITS) 8 (Fig. 6) works as follows. Suppose, for example, that code combination 01, corresponding to the operation of only the first stage of the modulation decomposition (MP) of the signal, is supplied to the code input of the decoder (code input BOICS 8) from external control circuits (not shown in the diagram). Under the influence of this code combination, at the first output of the decoder appears the level of a logical unit (log. 1). This level is applied to the second input of the first circuit And ₁ , to the first input of which a digital signal is supplied from the serial output of the first PCPS ₁ . All other schemes And at this time are closed by log levels. 0 from the rest of the outputs of the decoder.

On the first and second parallel information inputs of the first PPSSP ₁ (the first and second information inputs BOICS 8) are two individual digital transmission signals, respectively, from the first and second digital outputs of the first BRS 7 ₁ (Fig. 1). In PPTSSP ₁ (Fig. 6) there is a conversion of these two parallel individual digital signals into a digital group transmission signal corresponding to the first stage MP. This group signal from the output of the first PPSSP ₁ passes through the first circuit And ₁ and the second circuit OR ₂ to the output of BICTS 8.

When applying to the decoder input from external control circuits a code combination of 10, the log level appears on its second output. 1, which passes (through the first circuit OR ₁ ) to the second input of the second circuit And ₂ and to the second input of the fourth And ₄ . As a result of this, the digital group transmission signal corresponding to the first stage MP, from the output of the first PPSSP ₁ passes through the second circuit And ₂ and enters the serial input of the second PPSSP ₂ . Then, the digital group signal corresponding to the first and second steps of the MP, from the serial output of the PPSSP ₂ passes through the fourth circuit AND ₄ and the second circuit OR ₂ to the output of BOICS 8 (Fig. 6).

When a code combination 11 is supplied to the decoder input, the log level appears on the third output of the decoder. 1, which is applied through the first circuit OR ₁ to the second input of the second circuit And ₂ . In addition, the same level is the log. 1 is applied to the second inputs of the third circuit And ₃ and the fifth circuit And ₅ . As a result, the digital group transmission signal corresponding to the first stage MP, from the output of the first PPSSP ₁ passes through the second circuit And ₂ and enters the serial input of the second PPSSP ₂ . And from the serial output of PPSSP _{2, the} digital group signal corresponding to the first and second steps of MP passes through the third And ₃ circuit and enters the serial input of the third PPSSP ₃ . Then, the digital group signal corresponding to the first, second, and third MP stages, from the serial output of the PCSP ₃ passes through the fifth AND ₅ circuit and the second OR ₂ circuit to the output of the BICPS 8 (Fig. 6).

An example implementation of an individual digital signal separation unit (BRICS) 20 is shown in FIG. 7. This block contains: the first converter of the serial signal into parallel signals (CPPS ₁ ), the second CPPS ₂ , the third CPPS ₃ , the decoder (des), the first circuit OR ₁ , the second circuit OR ₂ , the first circuit And ₁ , the second circuit And ₂ and the third scheme And ₃ . PPPSPS are performed in the form of demultiplexers or shift registers with parallel output of information (for example, K555IR16, K531IR24, K533IR25). The first PPPSPS ₁ (for example, when executed on the basis of shift registers) has two parallel outputs, which are, respectively, the first and second outputs of BRICS 20. The second PPPSS ₂ has four parallel outputs, which are, respectively, the third, fourth, fifth and sixth outputs of BRICS 20. third PPSPS ₃ has eight parallel outputs, which are, respectively, the seventh to fourteenth outputs BRITSS 20. The serial output of the first PPSPS ₁ is connected to a first input of the second aND gate _2, and the serial output of the second subkey PPSPS ₂ to the first input of the third AND circuit ₃ (FIG. 7).

Information input BRICC 20 inside this unit is connected to the first input of the first circuit And ₁ . The code input of the decoder is the code input of BRICS 20 (one of the n control inputs of the receiving part 3). The first output of the decoder is connected to the first input of the first circuit OR ₁ . The second output of the decoder is connected to the second input of the first circuit OR ₁ and to the first input of the second circuit OR ₂ . The third output of the decoder is connected to the third input of the first circuit OR ₁ , to the second input of the second circuit OR ₂ and to the second input of the third circuit And ₃ . The output of the first circuit OR _{1 is} connected to the second input of the first circuit And ₁ , and the output of the second circuit OR _{2 is} connected to the second input of the second circuit And ₂ . The outputs of the first And ₁ , the second And ₂ and the third Of the circuits And are connected, respectively, to the serial input of the first PPPS ₁ , to the serial input of the second PPPS ₂ and to the serial input of the third PPPS ₃ . The timing circuits for the first second and third PSPS are not shown in the diagram.

BRITS 20 (Fig. 7) allows you to divide a digital group signal into two individual digital signals (when using the first MB stage), or into six similar signals (when using the first and second MB stages), removed from it from the first to sixth outputs, and there are also fourteen individual digital signals (when using the first, second, and third MB stages), taken from it from the first to fourteenth outputs. In total, there are three options for removing individual digital signals from the outputs of the BRICS 20 and, in accordance with these options, the first, second and third PPPSS are involved in different combinations. These options are implemented using code combinations supplied to the control input of BRICS 20 (table 2):

The control code combination 01, which allows only the first PSPS ₁ to be activated, is used only when the first MB stage is implemented, the 10 code code is used for the first and second MB stages, and the code combination 11 is used for the first, second and third MB stages.

Block separation of individual digital signals (BRITS) 20 (Fig. 7) works as follows. Let, for example, code combination 01, corresponding to the operation of only the first stage of modulation recovery (MB) of the signal, is fed to the code input of the decoder (code input BRICC 20) from external control circuits (not shown in the diagram). Under the influence of this code combination, at the first output of the decoder appears the level of a logical unit (log. 1). This level through the first circuit OR ₁ goes to the second input of the first circuit And ₁ , the first input of which is fed a digital group signal from the information input of BRICS 20. All other AND circuits (except the first) at this time are closed by the log levels. 0 from the rest of the outputs of the decoder.

The digital group reception signal from the information input of BRICS 20 (Fig. 7) passes through the first circuit And ₁ to the serial input of the first PPPS ₁ . In CPSPS ₁ , the conversion (separation) of this group signal into the first and second individual digital reception signals is carried out, which appear, respectively, at the first and second parallel outputs of CPSPS ₁ (the first and second outputs of BRICS 20).

When a code combination 10, corresponding to the operation of the first and second stages of the modulation recovery (MB) signal, is supplied to the decoder input from external control circuits, the log level appears on its second output. 1, which is applied to the second input of the first OR ₁ circuit and to the first input of the second OR ₂ circuit. Log level 1 from the output of OR ₁ and from the output of OR ₂ goes to the second inputs, respectively, of the first circuit And ₁ and the second circuit And ₂ . As a result of this, the digital group reception signal from the information input of BRICC 20 passes through the first circuit And ₁ to the serial input of the first CPSPS ₁ , and from its serial output the digital signal enters through the second circuit And ₂ to the serial input of the second CPSPS ₂ . In PPPSPS ₁ and PPPSPS ₂ is the conversion (separation) of this group signal into the first and second (in PPPSPS ₁ ), the third, fourth, fifth and sixth (in PPPSPS ₂ ) individual digital reception signals. These individual digital reception signals appear, respectively, at the first and second parallel outputs of the CPSPS ₁ and at the first, second, third and fourth parallel outputs of the CPSPS ₂ (from the first to the sixth outputs of BRICS 20).

When applying to the input of the decoder (Fig. 7) from the external control circuits a code combination 11 corresponding to the operation of the first, second and third stages of modulation recovery (MB) of the signal, the log level appears on its third output. 1, which is applied to the third input of the first circuit OR ₁ , to the second input of the second circuit OR ₂ and to the second input of the third circuit From. Log level 1 from the output of OR ₁ and from the output of OR ₂ goes to the second inputs, respectively, of the first circuit And ₁ and the second circuit And ₂ . As a result, the digital group reception signal from the information input of BRICC 20 passes through the first circuit And ₁ to the serial input of the first PCPS ₁ , and from its serial output the digital signal goes through the second circuit And ₂ to the serial input of the second PCPS ₂ , and from its serial output digital the signal enters through the third circuit From to the serial input of the third PPPS ₃ . In PPPSPS ₁ , PPPSPS ₂ and PPPSPS ₃ conversion (separation) of this group signal into the first and second (in PPPSPS ₁ ), the third, fourth, fifth and sixth (in PPPSPS ₂ ), seventh, eighth, ninth, tenth, eleventh, the twelfth, thirteenth and fourteenth (in PPPSPS ₃ ) individual digital reception signals. These individual digital reception signals appear, respectively, at the first and second parallel outputs of the CPSPS ₁ , at the first, second, third and fourth parallel outputs of the CPSPS ₂ and at the first to eighth parallel outputs of the CPSPS ₃ (from the first to the fourteenth outputs of BRICS 20).

An example of the implementation of the Hilbert isolator of instantaneous frequency and amplitude envelope (GVMCHAO) included in the BRS 7 ₁ is shown in FIG. 8. This unit contains: a phase shifter (PV), a half-wave rectifier (DPV), a first differentiating circuit (DS ₁ ), a second DS ₂ , a first squaring circuit (CBK ₁ ), a second ICS ₂ , a first multiplication scheme (SU ₁ ) , the second SU ₂ , an adder, a subtraction scheme (SV), a square root extraction scheme (SICC), and a division scheme (SD).

The first input GVMCHAO (Fig. 8) are parallel connected input PV, the input of the first DS ₁ and the first input of the second SU ₂ . The second input GVMCHAO is the input of the second ICS ₂ . The output of the PV is connected to the input of the second DS ₂ , to the first input of the first SU ₁ , and through the DPV is connected to the input of the first CBK ₁ . The outputs of the first and second DS are connected to the second inputs, respectively, of the first control system ₁ and second control system ₂ , the outputs of which are connected, respectively, to the first and second inputs of CB. The CB output is connected to the first input of the LED, the output of which is the first output of the HVMCO. The outputs of the first and second ICS are connected, respectively, to the first and second inputs of the adder, the output of which is connected to the second input of the LED and to the input of the SICC, the output of which is the second output of the HVMCO.

The Hilbert isolator of the instantaneous frequency and amplitude envelope (GVMCHAO) (Fig. 8), included in the first BRS 7 ₁ , works as follows. The analog band-pass signal S (t) from the first input of the HVMCO is fed to the PV input, in which the phase shift of the spectral components of this signal is performed by 90 °. Thus, a Hilbert-conjugated signal S ₁ (t) from a strip analog signal S (t) is formed. The phase rotation of the spectral components by 90 ° can be carried out by a phase shifter both in the low-frequency region based on analog or digital methods (for example, using FFT transformations with the change of sign of the conversion coefficients for Sin components and IFFT) so based on the transfer of the spectrum to the high-frequency region with subsequent rotation 90 ° phase and return to the low frequency region.

Next, from the first complex signal obtained in this way, consisting of S (t) and S ₁ (t), the signal of the first instantaneous frequency ω (t) and the first Hilbert amplitude envelope A (t) is isolated according to [2] and [3] .

To isolate ω (t), the signal S (t) from the first input of the HVMCO is fed to the input of the first DS ₁ and to the first input of the second SU ₂ , and the signal S ₁ (t) from the output of the PV comes to the input of the second DS ₂ and to the first input of the first SU ₁ (Fig. 8). The signal corresponding to the derivative of S (t) from the output of the first DS _{1 is} applied to the second input of the first SU ₁ , where it is multiplied with S ₁ (t), and the signal corresponding to the derivative of S ₁ (t) from the output of the second DS _{2 is} applied to the second input of the second SU ₂ , where it is multiplied with S (t). The results of multiplication from the output of the first SU ₁ and the output of the second SU ₂ are then fed, respectively, to the first and second inputs of CB. The signal corresponding to the result of the subtraction goes further to the first input of the LED.

The signal at the second input GVMCHAO is an oscillation after two-half-wave rectification (without filtering) of the analog bandpass signal in DPA 11 (Fig. 1). This rectified signal is fed to the input of the second ICS ₂ (Fig. 8). And the signal from the output of the PV after two-half-wave rectification (without filtering) in the DPA is fed to the input of the first CBK ₁ . These rectified signals S (t) and S ₁ (t), after squaring, respectively, in the second ICS ₂ and the first CBK ₁ , from the outputs of these circuits, respectively, go to the second and first inputs of the adder. After that, the signal corresponding [5]:

from the output of the adder is fed to the second input of the LED. As a result of the fission operation, the instantaneous frequency signal ω (t) appears at the output of the LED (the first output of the GVMCHAO).

To isolate the Hilbert amplitude envelope A (t), the signal from the adder output is fed to the input of the SICC, where, after extracting the square root, the signal corresponding to A (t) appears at the output of this circuit (the second output of the HMCO).

Schemes that perform operations similar to the GVMCHAO are given, for example, in the book: Mikhailov V.G., Zlatoustova L.V. "Measurement of speech parameters" M. Radio and communication, 1987, p. 15, fig. 1.4., As well as in the book Dvoryashin B.V., Kuznetsov L.I. "Radio engineering measurements." M. Sov. Radio, 1978, p. 171, fig. 8.7.

The unit for combining digital group signals (BOTSGS) 5 (Fig. 1) is performed on the basis of shift registers with parallel-serial inputs and serial outputs or a multiplexer and can be implemented, among other things, on the basis of a circuit similar to BICGS 10. Circuits for supplying clock pulses to BOCGS 5 not shown in the diagram.

Block separation of digital group signals (BRTSGS) 17 (Fig. 1) is based on shift registers with serial input and parallel-serial outputs or demultiplexers and can be implemented including on the basis of a circuit similar to BRITS 20. Circuits for supplying clock pulses to BRTSGS 17 not shown in the diagram.

The voltage-controlled oscillator (VCO) 28 (Fig. 1), included in the first BVS 211, is a low-frequency FM generator, the output frequency of which corresponds to the signal voltage at its input (see, for example, under the editorship of A. Pirogov “ Vocoder telephony ”M. Svyaz, 1974, p. 187, Fig. 3.50).

Using the proposed method and device for its implementation can improve the quality of the transmission of information signals through the use of the entire spectrum of each of n strip analog signals, into which the input information analog signal is divided. Such use of the entire spectrum of each of the n-band analog signals at each of the three steps of the modulation decomposition makes it possible to increase the accuracy of the formation of quasi-constant modulation decomposition parameters by which the information analog signal is restored on the receiving side. In addition, improving the quality of transmission of information signals allows you to reduce the speed of the digital signal in the channel.

The quality of information signal transmission when using the entire spectrum of each of the n strip analog signals in the proposed method is ensured by the fact that in this case the fine structure of the audio signals is transmitted more qualitatively: period and rate of change of the fundamental tone, width and shape of the spectrum, dynamic range, formant signal structure, etc. In this case, an increase or decrease in the quality of signal transmission is ensured by an increase or decrease in the number of bands n into which the original analog signal is divided, as well as by an increase or decrease in the number of modulation decomposition stages. For example, if the number of bands is reduced to n = 2 and only the first and second stages of modulation decomposition are used, the digital signal transmission speed in the channel will be no more than 1200 bit / s.

Using the proposed method and device, both voice signals and audio broadcasting signals can be transmitted, as well as any analog signals (service, data transmission via modems, etc.).

The proposed method and device may find application in digital transmission systems. Their use will improve the transmission quality of any information messages and reduce the transmission speed in the communication channel.

The economic effect of the use of the present invention is expected to be obtained by ensuring high quality transmission and reception of information analog signals at relatively low transmission speeds or a limited allocated frequency band. The economic effect can also be obtained by reducing the transmission speed of the digital signal and thereby increasing the number of digital channels.

Claims (2)

1. A method for transmitting and receiving signals represented by the parameters of a step modulation decomposition, including on the transmitting side in the first step of modulation decomposition — dividing by filtering the original analog signal into n frequency bands and generating n band analog signals, half-wave rectifying each band analog signal, generating each band analog signal coupled to it according to Hilbert signal and thus obtaining the first complex signal from the first complex signal of the first pair of parametric signals containing the signal of the first instantaneous frequency and the signal of the first Hilbert amplitude envelope, separation from the first pair of parametric signals by low-pass filtering of the first pair of quasi-constant analog transmission signals, consisting of the first and second quasi-constant analog transmission signals respectively, with a signal of the first instantaneous frequency and a signal of the first Hilbert amplitude envelope, analog-to-digital conversion the formation of each pair of quasi-constant analog transmission signals related to the first stage of modulation decomposition of each of the n strip analog signals, and the formation of n groups of individual digital transmission signals, each of which consists of a pair of individual digital transmission signals, combining a pair of individual digital transmission signals and the formation of digital a group transmission signal in each of n groups of individual digital transmission signals, combining n digital group transmission signals and forming a digital linear signal, transmitting a digital linear signal via a communication line, and on the receiving side, dividing the digital linear signal into n digital group reception signals, dividing each of the digital group reception signals into pairs of individual digital reception signals, and generating n groups of individual digital reception signals , at the first stage of modulation recovery - digital-to-analog conversion in each of n groups of individual digital reception signals and the formation of n groups of analog receive signals, each of which contains a pair of quasi-constant analog receive signals, consisting of the first and second quasi-constant analog receive signals, the formation in each of the n groups of analog receive signals of the first quasi-harmonic frequency-modulated oscillation (cosine phase) based on the use of the first quasi-constant analog signal reception as a frequency control, amplitude modulation of the first quasi-harmonic frequency-modulated oscillation based on the use of second th quasi-constant analog signal as a modulating one and generating n output group analog reception signals, combining n group analog reception signals and generating a reconstructed analog signal,
characterized in that on the transmitting side after the first stage of modulation decomposition, in each of the n frequency bands in the second stage of modulation decomposition, the first alternating analog signal is formed from the signal of the first instantaneous frequency and the first quasi-constant analog transmission signal, and from the signal of the first Hilbert amplitude envelope and the second a second alternating analog signal is generated from the quasi-constant analog transmission signal, and then, from the first and second variable analog signals, respectively, the second and third complex signals, from which the second and third pairs of parametric signals are separated, respectively, consisting of a second instantaneous frequency signal and a second Hilbert amplitude envelope signal, a third instantaneous frequency signal and a third Hilbert amplitude envelope signal, and then from the second and the third pair of parametric signals, respectively, allocate the second and third pairs of quasi-constant analog transmission signals, respectively, consisting of the third and even the third, fifth, and sixth quasi-constant analog transmission signals, and in each of the n frequency bands in the third step of the modulation decomposition of the second instantaneous frequency signal and the third quasi-constant analog transmission signal, the second Hilbert amplitude envelope signal and the fourth quasi-constant analog transmission signal, respectively, form the third and the fourth variable analog signals, and from the signal of the third instantaneous frequency and the fifth quasi-constant analog transmission signal, The third Hilbert amplitude envelope and the sixth quasi-constant analog transmission signal form the fifth and sixth variable analog signals, respectively, and then the pairs of the third and fourth, fifth and sixth variable analog signals form pairs of the fourth and fifth, sixth and seventh complex signals, respectively which emit, respectively, the fourth and fifth, sixth and seventh pairs of parametric signals, consisting respectively of a fourth instantaneous frequency signal and a signal the fourth Hilbert amplitude envelope, the fifth instantaneous frequency signal and the fifth Hilbert amplitude envelope signal, the sixth instantaneous frequency signal and the sixth Hilbert amplitude envelope signal, the seventh instantaneous frequency signal and the seventh Hilbert amplitude envelope signal, and then from the fourth and fifth, sixth and seventh parametric pairs signals, respectively, allocate the fourth and fifth, sixth and seventh pairs of quasi-constant analog transmission signals, consisting respectively of seven and the eighth, ninth and tenth, eleventh and twelfth, thirteenth and fourteenth quasi-constant analog transmission signals, after which the pairs of quasi-constant analog transmission signals related to the first, second and third steps of the modulation decomposition of each of the n strip analog signals are subjected to analog-to-digital conversion and forming n groups of individual digital transmission signals, each of which consists of B _n pairs of individual digital transmission signals which are then combined and n Luciano digital baseband signal, wherein each of the n digital baseband transmission signals are formed independently of other groups and comprise either of the individual digital transmit signals relating only to the first stage of the modulation decomposition, where B _n is 1, or the first and second steps of modulating the expansion, in which B _n is 3, any of the digital signals relating to the three stages of modulation decomposition, in which B _n is 7, then n group digital transmission signals again Combine nyayut and generated digital line signal transmitted on a communication line, and at the receiving side a digital line signal is divided into n digital baseband reception signal, after which each of the n digital baseband reception, in turn, is separated into B _n individual digital signals steam admission and n groups of individual digital reception signals are formed, wherein each of n groups of individual digital reception signals are formed independently of other groups and comprise: either pairs of individual digital reception signals, relating REGARD only to the first stage of the modulation recovery in which B _n is 1, or the first and second stages of modulation recovery in which B _n is equal to 3 or of the individual digital signal pairs reception pertaining to all three stages of modulation recovery in which B _n equal to 7, then in each of n independent groups of individual digital reception signals, digital-to-analog conversion is performed and n independent groups of analog reception signals are generated, each of which contains B _n pairs of quasi-constant a tax reception signals, after which, in the corresponding independent groups of analog reception signals, in which B _n = 7, at the third stage of modulation signal recovery in each of the fourth, fifth, sixth and seventh pairs of quasi-constant analog reception signals, using pairs of the seventh and eighth, respectively , the ninth and tenth, eleventh and twelfth, thirteenth and fourteenth quasi-constant analog reception signals, respectively form the third, fourth, fifth and sixth restored variables a analog signals, moreover, in the corresponding independent groups of analog reception signals at the second stage of the modulation recovery of the signal from the third restored alternating analog signal and the third quasi-constant analog receiving signal, the fourth restored alternating analog signal and the fourth quasi-constant analog receiving signal, the fifth restored alternating analog signal and the fifth quasi-constant analog receive signal, sixth reconstituted variable the analog signal and the sixth quasi-constant analog reception signal, respectively, form the second restored instantaneous frequency signal, the second restored Hilbert amplitude envelope signal, the third restored instantaneous frequency signal and the third restored Hilbert amplitude envelope signal, and then using the second restored instantaneous frequency signal and the second restored signal Hilbert amplitude envelope, signal of the third reconstructed instantaneous frequency and with the ignal of the third reconstructed Hilbert amplitude envelope, respectively, the first and second reconstructed variable analog signals are generated, moreover, in the corresponding independent groups of analog reception signals at the first stage of the modulation signal reconstruction from the first reconstructed analog signal and the first quasi-constant analog reception signal, the second reconstructed analog signal and the second quasi-constant analog receive signal is formed respectively The signal of the first reconstructed instantaneous frequency and the signal of the first reconstructed Hilbert amplitude envelope, and then, using the signal of the first reconstructed instantaneous frequency and the signal of the first reconstructed Hilbert amplitude envelope, are formed in the corresponding independent groups of analog reception signals in which B _n = 7, the output analog signal reception, while in the corresponding independent groups of analog reception signals, in which B _n = 3, at the second stage of modulation recovery signal and in each of the second and third pairs of quasi-constant analog receive signals, using the pairs of the third quasi-constant receive analog signal and the fourth quasi-constant receive analog signal, the fifth quasi-constant receive analog signal and the sixth quasi-constant receive analog signal, respectively, the first and second restored alternating analog signals are generated, moreover, in the corresponding independent groups of analog reception signals in the first stage of the modulation restored The signal from the first restored alternating analog signal and the first quasi-constant analog receiving signal, the second restored alternating analog signal and the second quasi-constant analog receiving signal form the signal of the first restored instantaneous frequency and the signal of the first restored Hilbert amplitude envelope, respectively, and then using the signal of the first restored instantaneous frequency and signal of the first reconstructed Hilbert amplitude envelope, forming into the corresponding independent groups of analog reception signals in which B _n = 3, the output of the analog reception signal, while in the corresponding independent groups of analog reception signals in which B _n = 1, the first stage of the modulation signal recovery in each of the first pair of quasi- analog reception signals, using, respectively, the first quasi-constant analog reception signal and the second quasi-constant analog reception signal, are formed in the corresponding independent groups of analog reception signals, in of which B _n = 1, the output analog reception signal, after which n parallel output analog reception signals from n independent groups of analog reception signals are combined and a restored analog signal is formed. 2. A device for implementing a method for transmitting and receiving signals represented by stepwise modulation decomposition parameters, comprising a transmitting part, a communication line and a receiving part, the transmitting part consisting of n transmission signal processing units connected in parallel to the input of the device, the output of each of which is connected to the corresponding the input of the unit for combining digital group signals, the output of which is the output of the transmitting part of the device, with each of the n blocks of processing signal transmission with holds a band-pass filter, the input of which is the input of the processing signal processing unit, as well as the first signal decomposition unit and the individual digital signal combining unit, the output of which is the output of the transmission signal processing unit, while the first and second information inputs of the individual digital signal combining unit are connected respectively to the first and second digital outputs of the first signal decomposition unit containing the Hilbert isolator of instantaneous frequency and amplitude connected in series envelope, the first low-pass filter and the first analog-to-digital converter, the output of which is the first digital output of the first signal decomposition unit, while the first input of the Hilbert isolator of instantaneous frequency and amplitude envelope is connected to the input of a half-wave rectifier and is the input of the first signal decomposition unit, and the output of a half-wave rectifier is connected to the second input of the Hilbert isolator of instantaneous frequency and the amplitude envelope, the second output of which is connected Through the second low-pass filter to the input of the second analog-to-digital converter, the output of which is the second digital output of the first signal decomposition unit, and the receiving part consists of a digital group signal separation unit, the input of which is the input of the receiving part of the device, and each of its n outputs is connected , respectively, to the input of the corresponding unit for processing reception signals, the output of each of which is connected to the corresponding input of the unit for combining output signals, the output of which is the output m of the device, each of n receiving signal processing units containing an individual digital signal separation unit, the information input of which is an input of the receiving signal processing unit, while the first and second outputs of the individual digital signal separation unit are connected, respectively, to the first and second digital inputs of the first a signal recovery unit containing a first digital-to-analog converter, a voltage-controlled generator, and an amplitude modulator, a cat output, connected in series which is the output of the first signal recovery unit, and the second input of the amplitude modulator is connected to the output of the second digital-to-analog converter, the input of the first digital-to-analog converter and the input of the second digital-to-analog converter are, respectively, the first and second digital inputs of the first signal recovery unit,
characterized in that the block of the second stage of the modulation signal decomposition and the block of the third stage of the modulation signal decomposition are additionally introduced in the transmitting part to each of the n signal processing blocks, and the first, second, third and fourth analog outputs are added to the first signal decomposition block, which are inside the first signal decomposition unit is connected respectively to the output of the first low-pass filter, with the output of the second low-pass filter, the first output of the Hilbert isolator of instantaneous frequency and the amplitude envelope and the second output of the Hilbert isolator of instantaneous frequency and the amplitude envelope, while the first, second, third and fourth analog outputs of the first signal decomposition unit are connected respectively to the first, second, third and fourth analog inputs of the second stage modulation decomposition block of the signal, the first, the second, third and fourth digital outputs of which are connected respectively to the third, fourth, fifth and sixth information inputs of the unit for combining individual digital systems nalov, and the first, second, third, fourth, fifth, sixth, seventh and eighth analog outputs of the block of the second stage of modulation decomposition of the signal are connected respectively to the first, second, third, fourth, fifth, sixth, seventh and eighth analog inputs of the block of the third stage of modulation signal decomposition, the first, second, third, fourth, fifth, sixth, seventh and eighth digital outputs of which are connected respectively with the seventh, eighth, ninth, tenth, eleventh, twelfth, thirteenth and fourteenth information the input inputs of the unit for combining individual digital signals, the first, second ... .n control inputs of the transmitting part of the device are connected to the code inputs of the first transmission signal processing unit, the second transmission signal processing unit ... ..n the transmission signal processing unit, and inside each of n transmit signal processing blocks, its code input is connected to the code input of the individual digital signal combining unit, and in the receiving part of the device, in addition to each of n signal processing blocks A block of the second stage of the modulation signal recovery and a block of the third stage of the modulation signal recovery are inputted, and the first and second adders are introduced into the first signal recovery unit, the first inputs of the first and second adders connected, respectively, to the output of the first digital-to-analog converter and the output of the second digital-to-analog converter , and the outputs of the first and second adders are connected, respectively, to the input of the generator controlled by voltage and the second input of the amplitude a regulator, wherein the second inputs of the first and second adders are connected respectively to the first and second analog inputs of the first signal recovery unit, which are connected respectively to the first and second outputs of the second stage block of the modulation signal recovery, the first, second, third and fourth digital inputs of which are connected respectively with the third, fourth, fifth and sixth outputs of the individual digital signal separation unit, and the first, second, third and fourth analog inputs of the second stage unit modulation signal recovery are connected respectively to the first, second, third and fourth outputs of the block of the third stage of the modulation signal recovery, the first, second, third, fourth, fifth, sixth, seventh and eighth digital inputs of which are connected respectively to the seventh, eighth, ninth, tenth, the eleventh, twelfth, thirteenth and fourteenth outputs of the individual digital signal separation unit, while the first, second ... .n control inputs of the receiving part of the device are connected to the code inputs respective first signal processing unit receiving the second signal processing unit receiving ... ..n reception signal processing unit, and inside of each of the n signal processing units receiving coded its input connected to the input of a code division individual digital signals.

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