RU2487443C1 - Method of matching complex impedances and apparatus for realising said method - Google Patents

Abstract

FIELD: radio engineering, communication.

SUBSTANCE: four-terminal element is complex and consists of reactive and resistive elements; a two-terminal nonlinear element is connected between a high-frequency signal source and the input of the four-terminal element, connected to a low-frequency control signal source; the output of the complex four-terminal element is connected to a load; conditions for ensuring a minimum reflected signal are met successively at the given number of frequencies while simultaneously varying amplitude of the control signal.

EFFECT: wider field of physical implementation as regions of variation of real and imaginary components of resistances of the signal source and the load, within which full matching of the complex impedance of the signal source and complex impedance of the load can be carried out successively for the given number of frequencies.

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Description

The invention relates to the field of radio communications and radar and can be used for frequency tunable coordination of arbitrary complex resistances in a given frequency band.

There is a method of matching complex resistances, consisting in the fact that using a matching device made in the form of a resistive four-terminal connected between a high-frequency signal source and a load, at a given frequency, the conditions for minimizing the reflected signal or maximizing the transmission of signal source power to the load are achieved [A. Golovkov A., Devyatkov A.G. Synthesis of matching filtering and phase devices on resistive elements with lumped parameters. Telecommunications, 2006, No. 6, pp. 36-38; Golovkov A.A. Integrated electronic devices. M .: Radio and communications, 1996. - 128 p.].

Known matching devices that implement this method, made in the form of typical circuits of resistive four-terminal devices (L-shaped connection of two resistive two-terminal devices, T-shaped connection of three resistive two-terminal devices, etc.), the resistance values of which are determined from the condition of minimizing the reflected signal or maximizing transmission signal source power to the load [ibid.].

The principle of operation of this method and device is that, thanks to a special choice of the values of the parameters of the resistive quadripole at a given frequency, full coordination of the complex resistance of the signal source and complex resistance of the load is ensured, and in a given frequency band - matching with a given tolerance.

The closest in technical essence and the achieved result (prototype) is a method for matching complex resistances, which consists in the fact that using a matching device made in the form of a reactive four-terminal connected between the high-frequency signal source and the load, the conditions for minimizing the reflected signal are achieved at a given number of frequencies or maximizing the transmission of power of the signal source to the load [A. Golovkov Integrated electronic devices. M .: Radio and communications, 1996. - 128 p.].

The closest in technical essence and the achieved result (prototype) is a matching device that implements this method, made in the form of a typical reactive four-terminal circuit from an L-shaped connection of two reactive two-terminal devices, each of which is made in the form of an oscillatory circuit, the values of which are determined from the condition minimizing the reflected signal or maximizing the transmission of power of the signal source to the load at two frequencies [A. Golovkov Integrated electronic devices. M .: Radio and communications, 1996. - 128 p.].

The principle of operation of this method and device is that, thanks to a special choice of the values of the parameters of the reactive four-terminal network at a given number of frequencies, full coordination of the complex resistance of the signal source and complex resistance of the load is ensured, and coordination with the specified tolerance in a given frequency band.

The main disadvantage of all the above methods and devices is that all the elements of the four-terminal devices (matching devices) are made either only resistive or only reactive. When using only reactive or only resistive elements in matching devices, it is not always possible to provide matching conditions for the criterion of ensuring the minimum of the reflected signal or the maximum transfer of the power of the signal source to the load, since such matching devices have certain areas of physical realizability (areas of variation of the real and imaginary components of the source resistances signal and load) within which these matching conditions are realized (A. Golovkov. Complexer Baths radio electronic device M .: Radio and communication, 1996 -. 128)..

All of the above methods and devices have another important drawback, which is the impossibility of ensuring tuning in frequency of matching arbitrary complex resistances in a given frequency band, since there are no controllable nonlinear elements in the matching device circuit and conditions for such tuning are not created.

The technical result of the invention is the expansion of areas of physical feasibility as areas of change of the real and imaginary components of the resistance of the signal source and load, within which successively at a given number of frequencies full coordination of the complex resistance of the signal source and complex load resistance is ensured, and in a given frequency band - matching with a given tolerance while increasing the frequency band in which frequency tuning is possible arbitrary complex resistances of the signal source and load (for example, the antenna) due to the optimization of the circuit and the parameters of the complex four-terminal network and control of the nonlinear element. The possibility of changing the option of including a nonlinear element relative to the matching complex quadrupole further expands the field of physical feasibility.

1. This result is achieved by the fact that in the known method of matching complex resistances, consisting in the fact that between the source of the high-frequency signal and the load include a matching device made of a four-terminal device, the parameters of which are selected from the condition of ensuring the minimum of the reflected signal, an additional four-terminal device is made complex of reactive and resistive elements, introduce a bipolar nonlinear element and include it in the longitudinal circuit between the high-frequency signal source and the input a four-terminal house, a non-linear element is connected to a source of a low-frequency control signal, a load is connected to the output of a complex four-terminal, the conditions for ensuring the minimum of the reflected signal are performed sequentially at a given number of frequencies while changing the amplitude of the control signal due to the fact that, in the interests of ensuring frequency-tunable coordination of arbitrary complex resistances of a source of a high-frequency signal and load in a given frequency band element z _{22 of} the resistance matrix of a complex quadrupole versus frequency is selected using the following mathematical expression:

, $$z_{22}=z_n+\frac{z_{2\mathrm{one}}^2}{z_0-z-z_{\mathrm{one}\mathrm{one}}}$$

,

where z ₁₁ , z ₂₁ are the given dependences of the corresponding elements of the resistance matrix of a complex quadripole on frequency; z ₀ is the given dependence of the complex resistance of the source of the high-frequency signal on the frequency; z _n is the given dependence of the complex load resistance on frequency; z is the given dependence of the complex resistance of a bipolar nonlinear element on frequency with a corresponding change in the amplitude of the low-frequency control signal.

2. This result is achieved by the fact that in the device for matching complex resistances connected between the high-frequency signal source and the load and consisting of a four-terminal device, the parameters of which are selected from the condition for ensuring the minimum of the reflected signal, an additional four-terminal device is made complex in the form of a U-shaped connection of three two-terminal devices with complex resistance Z _1n , Z _2n , Z _3n , the second complex two-terminal complex four-terminal is formed from series-connected first a resistive bipolar with a resistance R ₁ , a capacitor with a capacitance C, an arbitrary reactive bipolar with a resistance X ₀₁ , X ₀₂ at two frequencies and connected in parallel to each other a second resistive bipolar with a resistance R ₂ and a coil with inductance L, a bipolar nonlinear element connected to the input source of the low-frequency control signal, is connected between the source of the high-frequency signal and the input of the complex four-terminal in the longitudinal circuit, the load is connected to the output quadrupole, the values of the parameters of the second complex two-terminal are determined in accordance with the following mathematical expressions:

; - оптимальные значения сопротивления второго комплексного двухполюсника комплексного четырехполюсника на двух частотах; Z_1n, Z_3n - заданные значения сопротивления первого и третьего комплексных двухполюсников комплексного четырехполюсника на двух частотах; z_0n - заданные значения комплексных сопротивлений источника высокочастотного сигнала на двух частотах; z_нn - заданные значения комплексных сопротивлений нагрузки на двух частотах; z_n - заданные значения комплексных сопротивлений двухполюсного нелинейного элемента на двух частотах, соответствующих двум значениям амплитуды управляющего сигнала; ω_1,2=2πf_1,2; n=1, 2 - номера заданных двух частот f_1,2.r ₁ , r ₂ , x ₁ , x ₂ - the optimal values of the real and imaginary components of the resistance of the second complex two-terminal complex four-terminal at two frequencies; $$Z_{2n}=r_n+j{x}_n=z_{0n}\frac{\left(z_{0n}-z_n\right)\left[z_{nn}\left(Z_{\mathrm{one}n}+Z_{3n}\right)+Z_{\mathrm{one}n}{Z}_{3n}\right]-z_{nn}{Z}_{\mathrm{one}n}{Z}_{3n}}{\left(Z_{\mathrm{one}n}+z_n-z_{0n}\right)\left(Z_{3n}+z_{nn}\right)}$$

; - the optimal resistance values of the second complex two-terminal complex four-terminal at two frequencies; Z _1n , Z _3n - set resistance values of the first and third complex two-terminal complex four-terminal on two frequencies; z _0n - set values of the complex resistances of the source of the high-frequency signal at two frequencies; z _нn - set values of the complex load resistances at two frequencies; z _n - set values of the complex resistances of a bipolar nonlinear element at two frequencies corresponding to two values of the amplitude of the control signal; ω _1,2 = 2πf _1,2 ; n = 1, 2 - numbers of the given two frequencies f _1,2 .

Figure 1 shows a diagram of a matching device of complex resistances (prototype) that implements the prototype method.

Figure 2 shows the structural diagram of the proposed device according to claim 2., Which implements the proposed method according to claim 1.

Figure 3 shows a diagram of a complex quadrupole included in the proposed device, a diagram of which is presented in figure 2.

Figure 4 shows a diagram of a second complex two-terminal, included in the four-terminal, a diagram of which is presented in figure 3.

Matching device prototype (Fig. 1), which implements the prototype method, contains a high-frequency signal source (not shown in Fig. 1) with a complex resistance of 1, a reactive four-terminal, 2 in the form of a L-shaped connection of two reactive two-terminal, 3, 4 each of which is made in the form of a parallel oscillatory circuit on the elements L ₁ - 5, C ₁ - 6 and L ₂ - 7, C ₂ - 8, and the load with complex resistance - 9. The values of the parameters of the circuits are selected from the condition of simultaneous coordination of complex source resistances you co-frequency signal - 1 and load - 9 at two frequencies according to the criterion of ensuring the minimum of the reflected signal. The principle of operation of this device for matching the complex resistances of a source of high-frequency signals and a load (prototype) that implements the prototype method is as follows.

By choosing the values of the parameters of the circuits from the condition of simultaneously matching the complex resistances of the source of the high-frequency signal - 1 and load - 9 at two frequencies according to the criterion for achieving the minimum of the reflected signal at these frequencies, full coordination is achieved, the standing wave coefficient turns out to be unity. With a reasonable choice of the specified two frequencies near their surroundings in a certain frequency band, agreement will be achieved with a given tolerance - the standing wave coefficient does not exceed the specified value.

The disadvantages of the prototype method and device for its implementation are described above.

The proposed device according to claim 2 (figure 2), which implements the proposed method according to claim 1, contains a cascade-connected source of a high-frequency signal (not shown in figure 2) with a complex resistance of 1, a bipolar non-linear element of 19 (included in the longitudinal circuit) connected to the source of the low-frequency control signal - 20, a complex four-terminal - 10 in the form of a U-shaped connection of three complex two-terminal - 11, 12, 13 (Fig.3), the second of which is formed from a series of connected first resistive two-terminal with resistance line R ₁ - 14, a capacitor with a capacitance of C - 15, an arbitrary reactive bipolar - 16 with a frequency dependence of resistance X ₀ and in parallel connected to each other a second resistive bipolar with a resistance of R ₂ - 17 and a coil with inductance L - 18, and the load with complex resistance - 9. The values of the parameters R ₁ , R ₂ , C, L of the second complex two-terminal - 12 complex four-terminal - 10 are selected from the condition of sequentially ensuring coordination of the complex resistances of the high-frequency signal source - 1 and load ki - 9 at two frequencies according to the criterion of ensuring the minimum of the reflected signal with a corresponding change in the amplitude of the low-frequency control signal.

The principle of operation of this device for matching the complex resistances of a source of high-frequency signals and a load that implements the proposed method is as follows.

By choosing the values of the parameters R ₁ , R ₂ , C, L of the second complex two-terminal device, 12 complex four-terminal devices, 10 from the condition of sequentially ensuring coordination of the complex resistances of the high-frequency signal source - 1 and the load - 9 at two frequencies according to the criterion of ensuring the minimum of the reflected signal at two values the amplitudes of the low-frequency control signal at these frequencies are fully consistent, the standing wave coefficient is equal to unity. With a reasonable choice of two frequencies to be set near their surroundings in a certain frequency band, frequency-tunable matching with a given tolerance will be achieved - the standing wave coefficient does not exceed the specified value with a continuous change in the amplitude of the low-frequency control signal. These two frequencies are selected from a given frequency band in accordance with the specified condition. In the particular case corresponding to the constancy of the amplitude of the low-frequency control signal, simultaneous matching with a given tolerance will be achieved in a certain frequency band - the standing wave coefficient does not exceed the specified value, and at the two given frequencies, full matching is carried out simultaneously. The frequency band within which tunable matching is observed is always wider than the frequency band within which simultaneous matching is observed.

Let us prove the feasibility of implementing these properties.

Let the dependences of the resistance z ₀ = r ₀ + jx _{0 of the} source of the high-frequency signal and the load z _n = r _n + jx _n on frequency be known. The dependences of the resistance of the nonlinear element z = r + jx on the frequency and amplitude of the low-frequency control signal are also known. For simplicity of writing, the arguments ω = 2πf (circular frequency) and U, I (amplitudes of the low-frequency control signal) are omitted.

The nonlinear element and the complex four-terminal network (CN) are characterized by the following transfer matrices:

$$A_{n\mathrm{uh}}=\left[\begin{array}{cc}\mathrm{one}& z\\ 0& \mathrm{one}\end{array}\right];A_{\mathrm{to}h}=\left[\begin{array}{cc}\frac{z_{\mathrm{one}\mathrm{one}}}{z_{2\mathrm{one}}}& -\frac{\left|z\right|}{z_{2\mathrm{one}}}\\ \frac{\mathrm{one}}{z_{2\mathrm{one}}}& \frac{-{\mathrm{<figure-callout\; id="2"\; label="z"\; filenames="00000024.png"\; state="\{\{state\}\}">z</figure-callout>}}_{22}}{z_{2\mathrm{one}}}\end{array}\right],\left(\mathrm{one}\right)$$

; z₁₁, z₂₁, z₂₂ - определитель и элементы матрицы сопротивлений КЧ с учетом условия взаимности z₁₂=-z₂₁.Where $$\left|z\right|=z_{\mathrm{one}\mathrm{one}}{\mathrm{<figure-callout\; id="2"\; label="z"\; filenames="00000024.png"\; state="\{\{state\}\}">z</figure-callout>}}_{22}+{\mathrm{<figure-callout\; id="2"\; label="z"\; filenames="00000024.png"\; state="\{\{state\}\}">z</figure-callout>}}_{2\mathrm{one}}^2$$

; z ₁₁ , z ₂₁ , z ₂₂ - determinant and elements of the matrix of impedances of the CN, taking into account the reciprocity condition z ₁₂ = -z ₂₁ .

Multiply the transfer matrix of the nonlinear element by the transfer matrix of the complex four-terminal network. Taking into account z ₀ , z _n (: Feldstein A.L., Yavich L.R. Synthesis of four-terminal and eight-terminal devices on a microwave. M .: Communication, 1971, p. 34-36) we obtain the expression for the normalized classical transfer matrix of a matching device:

$$A=\left[\begin{array}{cc}\frac{z_{\mathrm{one}\mathrm{one}}+z}{z_{2\mathrm{one}}}\sqrt{\frac{z_n}{z_0}}& \frac{-\left(z_{22}z+\left|z\right|\right)}{z_{2\mathrm{one}}}\frac{\mathrm{one}}{\sqrt{z_0{z}_n}}\\ \frac{\mathrm{one}}{z_{2\mathrm{one}}}\sqrt{z_0{z}_n}& -\frac{{\mathrm{<figure-callout\; id="2"\; label="z"\; filenames="00000024.png"\; state="\{\{state\}\}">z</figure-callout>}}_{22}}{z_{2\mathrm{one}}}\sqrt{\frac{z_0}{z_n}}\end{array}\right].\left(2\right)$$

Using the known relations between the elements of the classical transfer matrix and the elements of the scattering matrix (ibid.), Taking into account (2), we obtain the expression for the reflection coefficient:

$$S_{\mathrm{one}\mathrm{one}}=\frac{\left(-z_0+z\right)\left(z_n-{\mathrm{<figure-callout\; id="2"\; label="z"\; filenames="00000024.png"\; state="\{\{state\}\}">z</figure-callout>}}_{22}\right)+z_{\mathrm{one}\mathrm{one}}{z}_n-\left|z\right|}{\left(z_0+z\right)\left(z_n-{\mathrm{<figure-callout\; id="2"\; label="z"\; filenames="00000024.png"\; state="\{\{state\}\}">z</figure-callout>}}_{22}\right)+z_{\mathrm{one}\mathrm{one}}{z}_n-\left|z\right|}.\left(3\right)$$

The solution of the complex equation formed from the equality of the reflection coefficient to zero (3):

$$z_{22}=z_n+\frac{z_{2\mathrm{one}}^2}{z_0-z-z_{\mathrm{one}\mathrm{one}}}.\left(\mathrm{four}\right)$$

The obtained relationship of the elements of the CN resistance matrix (4), taking into account the given frequency dependences z ₁₁ , z ₂₁ , z ₀ , z, z _n, is an optimal approximating function of the frequency dependence of the corresponding element (z ₂₂ ) of the CN resistance matrix. If this approximating function is realized within any frequency band or at separate frequencies, then matching conditions on the criterion of achieving the minimum of the reflected signal will be provided in this frequency band or at these frequencies. To do this, you need to take any typical RF circuit, find the resistance matrix of this circuit and the elements of this matrix found in this way, expressed in terms of the circuit parameters, substitute it in (4) and solve the complex equation for the resistance of the selected one two-terminal network. The frequency characteristics of the remaining parameters r ₀ , x ₀ , r _n , x _n , r, x and the remaining two-terminal CNs can be selected arbitrarily or based on any other physical considerations, for example, from the condition of increasing the frequency band within which tunable frequency matching with a given tolerance - the standing wave coefficient does not exceed a given value with a continuous change in the amplitude of the low-frequency control signal.

In accordance with the above algorithm, expressions are obtained for finding the optimal approximation of the frequency dependence of the complex resistance of the second two-terminal KP in the form of a U-shaped connection of three complex two-terminal (Fig. 3):

$$Z_{2n}=r_n+j{x}_n=z_{0n}\frac{\left(z_{0n}-z_n\right)\left[z_{nn}\left(Z_{\mathrm{one}n}+Z_{3n}\right)+Z_{\mathrm{one}n}{Z}_{3n}\right]-z_{nn}{Z}_{\mathrm{one}n}{Z}_{3n}}{\left(Z_{\mathrm{one}n}+z_n-z_{0n}\right)\left(Z_{3n}+z_{nn}\right)},\left(5\right)$$

where n = 1, 2 ... are the numbers of the interpolation frequencies. Resistances Z _1n , Z _3n can be chosen arbitrarily or on the basis of any other physical considerations. The index n must also be introduced in other notation of physical quantities that explicitly depend on the frequency. The physical meaning of solution (5) lies in the fact that the frequency dependence of the complex resistance of the second two-terminal KCH ensures equality of the frequency dependence of the resistance of the source of the high-frequency signal and the frequency dependence of the input resistance of the rest of the matching device (in section 1-1 ^I (Fig. 2)). In this case, full agreement would be ensured over the entire frequency spectrum. However, the implementation of (5) in a continuous even very narrow frequency band with a constant amplitude of the voltage across a nonlinear element is impossible.

To implement the optimal approximation (5) sequentially at all frequencies of a given frequency band corresponding to a given range of variation of the amplitude of the control signal on a nonlinear element, using a interpolation method, it is necessary to form a two-terminal network with a resistance Z _2n of at least 2N (N is the number of interpolation frequencies) of elements of the type R, L, C, find the expressions for their resistances, equate them to the optimal values of the two-terminal resistances at the given frequencies corresponding to the given amplitudes of the control signal, op defined by formulas (5), and solve the system of 2N equations thus formed with respect to 2N selected parameters R, L, C. The values of the parameters of the remaining elements can be chosen arbitrarily or based on any other physical considerations, for example, from the condition of physical realizability. Let the second KP double-terminal with resistance Z _{2n be} formed from a series-connected first resistive two-terminal with resistance R ₁ , a capacitor with capacitance C, an arbitrary reactive two-terminal with resistors X ₀₁ , X ₀₂ and parallel to each other, a second resistive two-terminal with resistance R ₂ and coils with inductance L (figure 4). The complex resistance of the second two-terminal KCH:

$$Z_{2n}=R_{\mathrm{one}}+\frac{\mathrm{one}}{j{\omega }_{n}C}+j{X}_{0n}+\frac{R_{2}j{\omega }_{n}L}{j{\omega }_{n}L+{\mathrm{<figure-callout\; id="2"\; label="R"\; filenames="00000024.png"\; state="\{\{state\}\}">R</figure-callout>}}_2}.\left(6\right)$$

In (6), we divide the real and imaginary parts together and for N = 2 we compose a system of four equations:

r ₁ , r ₂ , x ₁ , x ₂ are the optimal values of the real and imaginary components of the resistance of the second complex two-terminal complex four-terminal at two frequencies and two amplitudes of the control signal on a nonlinear element (resistance Z _2n (5) depends on z _n ).

The implementation of optimal approximations of the frequency characteristics of the four-terminal network (4) using the U-shaped link (5) and the second two-terminal network of this link using (6), (8) ensures that the matching condition with the given tolerance is achieved sequentially at all given frequencies of the required frequency band corresponding to the range changes in the amplitude of the control signal on a nonlinear element. A reasonable choice of the positions of the frequencies ω ₁ , ω ₂ relative to each other and additional variation of the values of parameter-free types (4) - (6), (8) further increase the frequency band within which frequency-tunable matching with a given tolerance will be achieved - the standing wave coefficient does not exceed a given value with a continuous change in the amplitude of the low-frequency control signal.

The proposed technical solutions are new, because the method and device for matching complex resistances in a given frequency band are unknown due to a special choice of the frequency dependence of element z _{22 of} the resistance matrix of a complex four-terminal network, which is implemented by performing this four-terminal network in the form of a U-shaped connection of three complex two-terminal networks, the second complex bipolar U-shaped connection from the series-connected first resistive a two-terminal with resistance R ₁ , a capacitor with a capacitance C, an arbitrary reactive two-terminal with resistances X ₀₁ , X ₀₂ at two frequencies and in parallel connected to each other a second resistive two-terminal with resistance R ₂ and a coil with inductance L and the choice of these parameters according to the corresponding mathematical expressions in The interests of achieving a minimum of the reflected signal sequentially at all frequencies of this frequency band with a corresponding change in the amplitude of the low-frequency control signal.

The proposed technical solutions have an inventive step, since it does not explicitly follow from the published scientific data and the known technical solutions that the claimed sequence of operations (execution of a matching device for implementing the proposed method in the form shown in Fig. 2, execution of a four-terminal complex in the form of interconnected the above method of three two-terminal networks (Fig.3), the formation of the second two-terminal network from the series-connected first resistive two-terminal network with resistance R _1, a capacitor with capacitance C, an arbitrary reactance two-terminal network with resistances X _01, X ₀₂ at two frequencies and connected in parallel between a second two-terminal resistive with a resistance R ₂ and coil with inductance L (4), the selection of element values z ₂₂ complex matrix resistances quadripole, the choice of values of parameters of the second two-terminal network CN of conditions ensuring sequential consistency conditions at all given frequencies when the state of the nonlinear bipolar ale coagulant under the influence of low-frequency control signal amplitude) provides a tunable matching criterion of the minimum of the reflected signal in a predetermined frequency band by low-frequency law of change of the control signal amplitude.

The proposed technical solutions are practically applicable, since semiconductor diodes (parametric diodes, pin diodes, Gunn diodes, tunnel diodes, avalanche-span diodes, etc.), inductors, resistors and capacitors can be used for their implementation formed in the claimed circuit of a complex four-terminal network. The values of the parameters of the inductances, resistive elements and capacitances included in the circuit of the second two-terminal KCH, can be uniquely determined using mathematical expressions given in the claims.

The technical and economic efficiency of the proposed method and device consists in sequentially providing matching conditions for the complex resistances of the high-frequency signal source and the load at all frequencies in a given continuous frequency band corresponding to a given range of variation in the amplitude of the low-frequency control signal, due to the choice of the circuit and the values of the parameters of the elements R, L , C of a complex four-terminal system according to the criterion of ensuring the minimum of the reflected signal at these frequencies with a variable state the use of a nonlinear bipolar element under the influence of a low-frequency control signal, which allows us to expand the field of physical realizability as a region of change in the real and imaginary components of the resistance of the signal source and load, within which successively at a given number of frequencies full coordination of the complex resistance of the signal source and the complex load resistance is ensured, and in a given frequency band - matching with a given tolerance while increasing the bands s frequencies, in which it is possible to adjust according to the frequency of matching arbitrary complex resistances of the signal source and load (for example, an antenna), due to the optimization of the circuit and the parameters of the complex four-terminal network and control of a nonlinear element.

Claims (2)

1. The method of coordination of complex resistances, consisting in the fact that between the source of the high-frequency signal and the load include a matching device made of a four-terminal network, the parameters of which are selected from the condition of ensuring the minimum of the reflected signal, characterized in that the four-terminal network is made complex of reactive and resistive elements, enter bipolar nonlinear element, include it in a longitudinal circuit between the high-frequency signal source and the input of the four-terminal network and connect to the source of the high-frequency control signal, the load is connected to the output of the complex four-terminal network, the conditions for ensuring the minimum of the reflected signal are satisfied sequentially at a given number of frequencies while changing the amplitude of the control signal due to the fact that in the interests of ensuring frequency-tunable coordination of arbitrary complex resistances of the source of the high-frequency signal and load at a given band element dependency matrix ₂₂ z integrated resistances quadripole the frequency is selected by the following mathematical expression:
$$z_{22}=z_n+\frac{z_{21}^2}{z_0-z-z_{\mathrm{eleven}}},$$

where z ₁₁ , z ₂₂ are the given dependences of the corresponding elements of the resistance matrix of the complex quadripole on frequency; z ₀ is the given dependence of the complex resistance of the source of the high-frequency signal on the frequency; z _n is the given dependence of the complex load resistance on frequency; z is the given dependence of the complex resistance of a bipolar nonlinear element on frequency with a corresponding change in the amplitude of the low-frequency control signal. 2. A device for matching complex resistances, included between the source of the high-frequency signal and the load and consisting of a four-terminal device, the parameters of which are selected from the condition for ensuring the minimum of the reflected signal, characterized in that the four-terminal device is complex in the form of a U-shaped connection of three two-terminal devices with complex resistances Z _1n , Z _2n, Z _3n, a second complex two-terminal integrated quadripole formed of series-connected two-terminal network with a first resistive accompanied ivleniem R _1, a capacitor with capacitance C, an arbitrary reactance two-terminal network with resistances X _01, X ₀₂ at two frequencies and connected in parallel between a second resistive two-terminal resistance R ₂ and coil with inductance L, the entered two-pole non-linear element connected to the entered source baseband control signal, connected between the source of the high-frequency signal and the input of the complex four-terminal into the longitudinal circuit, the load is connected to the output of the four-terminal, the parameter values s second integrated two-terminal network are determined in accordance with the following mathematical expression:
$$R_{\mathrm{one}}=\frac{{\omega }_2^3{r}_{\mathrm{one}}\left(x_2-X_{02}\right)\left[{\omega }_2\left(x_2-X_{02}\right)-2{\omega }_{\mathrm{one}}\left(x_{\mathrm{one}}-X_{0\mathrm{one}}\right)\right]-{\omega }_{\mathrm{one}}^3\left(x_{\mathrm{one}}-X_{0\mathrm{one}}\right)r_2\left[{\omega }_{\mathrm{one}}\left(x_{\mathrm{one}}-X_{0\mathrm{one}}\right)-2{\omega }_2\left(x_2-X_{02}\right)\right]+{\omega }_{\mathrm{one}}^2{\omega }_2^2{\left(r_{\mathrm{one}}-r_2\right)}^3}{\left({\omega }_2^2-{\omega }_{\mathrm{one}}^2\right){\left[{\omega }_2\left(x_2-X_{02}\right)-{\omega }_{\mathrm{one}}\left(x_{\mathrm{one}}-X_{0\mathrm{one}}\right)\right]}^2};$$

$$R_2=\frac{{\omega }_{\mathrm{one}}^{\mathrm{four}}A+{\omega }_2{\omega }_{\mathrm{one}}^{3}B+{\omega }_{\mathrm{one}}^2{\omega }_2^2{C}_{\mathrm{one}}+{\omega }_{\mathrm{one}}{\omega }_2^{3}D+{\omega }_2^{\mathrm{four}}E}{\left(r_2-r_{\mathrm{one}}\right)\left({\omega }_2^2-{\omega }_{\mathrm{one}}^2\right){\left[\left(x_{\mathrm{one}}-X_{0\mathrm{one}}\right){\omega }_{\mathrm{one}}-\left(x_2-X_{02}\right){\omega }_2\right]}^2};$$

$$C=\frac{\left({\omega }_{\mathrm{one}}^2-{\omega }_2^2\right)\left[{\omega }_{\mathrm{one}}\left(x_{\mathrm{one}}-X_{0\mathrm{one}}\right)-{\omega }_2\left(x_2-X_{02}\right)\right]}{{\omega }_{\mathrm{one}}{\omega }_2\left\{{\omega }_{\mathrm{one}}{\omega }_2\left[{\left(r_{\mathrm{one}}-r_2\right)}^2+{\left(x_{\mathrm{one}}-X_{0\mathrm{one}}\right)}^2+{\left(x_2-X_{02}\right)}^2\right]-\left(x_{\mathrm{one}}-X_{0\mathrm{one}}\right)\left(x_2-X_{02}\right)\left({\omega }_{\mathrm{one}}^2+{\omega }_2^2\right)\right\}};$$

$$L=\frac{{\omega }_{\mathrm{one}}^{\mathrm{four}}A+{\omega }_2{\omega }_{\mathrm{one}}^{3}B+{\omega }_{\mathrm{one}}^2{\omega }_2^2{C}_{\mathrm{one}}+{\omega }_{\mathrm{one}}{\omega }_2^{3}D+{\omega }_2^{\mathrm{four}}E}{\left({\omega }_{\mathrm{one}}^2-{\omega }_2^2\right){\left[{\omega }_{\mathrm{one}}\left(x_{\mathrm{one}}-X_{0\mathrm{one}}\right)-{\omega }_2\left(x_2-X_{02}\right)\right]}^3},$$

Where $$A={\left(x_{\mathrm{one}}-X_{0\mathrm{one}}\right)}^2\left[{\left(r_{\mathrm{one}}-r_2\right)}^2+{\left(x_{\mathrm{one}}-X_{0\mathrm{one}}\right)}^2\right];$$

$$B=-2\left(x_{\mathrm{one}}-X_{0\mathrm{one}}\right)\left(x_2-X_{02}\right)\left[{\left(r_{\mathrm{one}}-r_2\right)}^2+2{\left(x_{\mathrm{one}}-X_{0\mathrm{one}}\right)}^2\right];$$

$$C_{\mathrm{one}}=\left[{\left(x_{\mathrm{one}}-X_{0\mathrm{one}}\right)}^2+{\left(x_2-X_{02}\right)}^2\right]{\left(r_{\mathrm{one}}-r_2\right)}^2+6\left(r_{\mathrm{one}}^2{r}_2^2+{\left(x_{\mathrm{one}}-X_{0\mathrm{one}}\right)}^2{\left(x_2-X_{02}\right)}^2\right)+r_{\mathrm{one}}^{\mathrm{four}}+r_2^{\mathrm{four}}-\mathrm{four}{r}_{\mathrm{one}}{r}_2\left(r_{\mathrm{one}}^2+r_2^2\right);$$

$$D=-2\left(x_{\mathrm{one}}-X_{0\mathrm{one}}\right)\left(x_2-X_{02}\right)\left[{\left(r_{\mathrm{one}}-r_2\right)}^2+2{\left(x_2-X_{02}\right)}^2\right];$$

$$E={\left(x_2-X_{02}\right)}^2\left[{\left(r_{\mathrm{one}}-r_2\right)}^2+{\left(x_2-X_{02}\right)}^2\right];$$

r ₁ , r ₂ , x ₁ , x ₂ - the optimal values of the real and imaginary components of the resistance of the second complex two-terminal complex four-terminal at two frequencies; $$Z_{2n}=r_n+j{x}_n=z_{0n}\frac{\left(z_{0n}-z_n\right)\left[z_{nn}\left(Z_{\mathrm{one}n}+Z_{3n}\right)+Z_{\mathrm{one}n}{Z}_{3n}\right]-z_{nn}{Z}_{\mathrm{one}n}{Z}_{3n}}{\left(Z_{\mathrm{one}n}+z_n-z_{0n}\right)\left(Z_{3n}+z_{nn}\right)}$$

- the optimal resistance values of the second complex two-terminal complex four-terminal at two frequencies; Z _1n , Z _3n - set resistance values of the first and third complex two-terminal complex four-terminal on two frequencies; Z _0n - set values of the complex resistances of the source of the high-frequency signal at two frequencies; z _нn - set values of the complex load resistances at two frequencies; z _n - set values of the complex resistances of a bipolar nonlinear element at two frequencies corresponding to two values of the amplitude of the control signal; ω _1,2 = 2πf _1,2 ; n = 1, 2 - numbers of the given two frequencies f _1,2 .

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