RU2486638C1 - Method of generating high-frequency signals and apparatus for realising said method - Google Patents

Abstract

FIELD: radio engineering, communication.

SUBSTANCE: forward transmission circuit is made from a three-terminal nonlinear element. The external feedback circuit used is an arbitrary four-terminal device which is connected to the three-terminal nonlinear element on a series-parallel scheme; the load is in form of a first two-terminal device with complex impedance; the control electrode of the three-terminal nonlinear element is connected in crosswise circuit to a second two-terminal device with complex impedance which imitates the resistance of the generator signal source in amplification mode.

EFFECT: wider range of generated oscillations, generating complex signals, creating efficient compact generation devices for radio communication equipment with a given number of radio channels.

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Description

The invention relates to the field of radio communications and can be used to create devices for generating high-frequency signals at a given number of frequencies, which allows you to generate complex signals and create effective compact radio communications with a given number of radio channels.

A known method of generating a high-frequency signal, based on the conversion of the energy of a constant voltage source into the energy of a high-frequency signal, organizing internal feedback in a non-linear element by using a bipolar non-linear element with negative differential resistance, fulfilling the excitation conditions in the form of amplitude balance and phase balance, which determine respectively, the amplitude and frequency of the generated high-frequency signal, and non-linear matching conditions an element with a load (see IS Gonorovsky. Radio engineering circuits and signals. - M.: “Bustard”, - 2006, p. 414-417).

A device for generating a high-frequency signal, consisting of a constant voltage source that sets the operating point in the middle of the falling section of the current-voltage characteristics of a bipolar nonlinear element with negative differential resistance, a four-terminal reactive load in the form of a parallel oscillatory circuit, while the parameters of the circuit, bipolar nonlinear element and varicap are selected from the condition of providing the given amplitude and frequency of the generated high-frequency signal ala (. cm Gonorovsky IS Radio circuits and signals -. M .: "Bustard" - 2006, s.414-417). The principle of operation of this device is as follows. When a constant voltage (current) source is turned on, due to an abrupt change in the amplitude, oscillations arise in the entire circuit, the spectrum of which occupies the entire frequency radio range. The amplitudes of these oscillations decay quickly. However, due to the presence of internal feedback in a bipolar nonlinear element, a negative differential resistance arises in a section with a falling current-voltage characteristic, which, by matching with a reactive four-terminal, compensates for losses in the circuit. Due to this, the oscillation with a frequency equal to the resonant frequency of the oscillatory circuit is amplified until the amplitude of this oscillation increases to a level at which the amplitude goes beyond the falling section of the current-voltage characteristic. There is a stationary mode.

The closest in technical essence and the achieved result (prototype) is a method of generating a high-frequency signal based on converting the energy of a constant voltage source into the energy of a high-frequency signal, organizing external positive feedback between the load and the control electrode of a three-pole nonlinear element, and fulfilling the excitation conditions in the form of an amplitude balance and phase balance, respectively determining the amplitude and frequency of the generated high-frequency signal, and conditions oglasovaniya nonlinear element to the load (. cm Gonorovsky IS Radio circuits and signals -. M .: "Bustard" - 2006, s.383-401).

The closest in technical essence and the achieved result (prototype) is a device for generating a high-frequency signal, consisting of a constant voltage source that sets an operating point in the middle of the quasilinear section of the current-voltage characteristic of the transistor, reactive four-terminal, load in the form of a parallel oscillatory circuit, external positive RC-circuit feedback between the load and the control electrode of the transistor, while the parameters of the circuit, transistor and varicap selected to provide predetermined amplitude and frequency of the generated high-frequency signal (see Gonorovsky IS Radio circuits and signals -.. M .: "Bustard" - 2006, s.383-401).

The principle of operation of this device is as follows. When a constant voltage (current) source is turned on, due to an abrupt change in the amplitude, oscillations arise in the entire circuit, the spectrum of which occupies the entire frequency radio range. The amplitudes of these oscillations decay quickly. However, due to the presence of a positive feedback circuit, the oscillation with a frequency equal to the resonant frequency of the oscillatory circuit is supplied to the control electrode of the transistor, which, by matching with the reactive four-terminal device, starts to operate in the amplification mode until the amplitude of this oscillation increases to the level at which the saturation mode occurs (amplitude limits). There is a stationary mode.

The disadvantage of these methods and devices is the generation of a high-frequency signal at only one frequency. In addition, it does not indicate how it is necessary to choose the values of the parameters of the reactive four-port network at which the excitation mode and the stationary mode occur. This question arises especially sharply when designing generation devices in the HF and UHF bands, on which the reactive components of the parameters of nonlinear elements must be taken into account. Currently, the classical theory of radio circuits does not take this into account. On the other hand, the generation conditions can be provided without a reactive four-terminal network, which reduces the size and weight of the device by reducing the number of reactive elements.

The technical result of the invention is to increase the range of generated oscillations, generate high-frequency signals at a given number of frequencies and reduce the number of reactive elements, which allows you to generate complex signals and create efficient compact generation devices for radio communications with a given number of radio channels. The use of various types of feedback expands the possibilities of physical feasibility of the specified result.

1. The specified result is achieved by the fact that in the known method of generating high-frequency signals, based on the conversion of the energy of a constant voltage source into the energy of a high-frequency signal, the interaction of a high-frequency signal with a direct transmission circuit, a three-pole nonlinear element and an external feedback circuit, the fulfillment of the excitation conditions in the form of a balance amplitudes and phase balance, respectively determining the amplitude and frequency of the generated high-frequency signals, matching conditions of the output electrode a three-pole non-linear element with a load and conditions for matching the load with a control electrode of a three-pole non-linear element, in addition, the direct transfer circuit is made of a three-pole non-linear element, an arbitrary four-terminal connected to the three-pole non-linear element in a serial-parallel circuit is used as an external feedback circuit, the load is performed in in the form of the first two-terminal with complex resistance, to the control electrode of a three-pole nonlinear element a second two-terminal device with a complex resistance that simulates the resistance of the generator signal source in the amplification mode is connected to the transverse circuit, the excitation conditions in the form of a balance of amplitudes and phase balance and matching conditions are simultaneously fulfilled at a given number of frequencies by choosing the values of the imaginary components of the resistances of the first X _nm and second X _{0m of} two-poles from the condition of providing a stationary generation mode in the form of equality to zero of the denominator of the gain in gain mode simultaneously at all the given frequencies of the generated high-frequency signals at a constant amplitude of the constant voltage source in accordance with the following mathematical expressions:

; $$X_{нm}=\frac{-Y\pm \sqrt{Y^2-4XZ}}{2X},$$

$$X_{0m}=\frac{A{X}_{nm}+B}{C{X}_{nm}+D}$$

; $$X_{nm}=\frac{-Y\pm \sqrt{Y^2-\mathrm{four}XZ}}{2X},$$

where A = - (x _22m r _0m + B ₁ ); B = r _nm (A ₁ + r _0m r _22m ) -r _0m -r _11m ; C = r _22m ; D = x _22m r _nm ; X = -r _22m (r _22m r _0m + A ₁ ); Y = r _22m x _11m -B ₁ -x _22m (r _22m r _0m r _nm + A ₁ r _nm ); A ₁ = r _11m r _22m -x _11m x _22m -r _12m r _21m + x _12m x _21m ; B ₁ = x _11m r _22m + r _11m x _22m -x _12m r _21m -r _12m x _21m ; $$Z=r_{nm}(r_{\mathrm{eleven}m}{r}_{22m}+x_{\mathrm{eleven}m}{x}_{22m})-r_{0m}{r}_{nm}^2(r_{22\mathrm{<figure-callout\; id="2"\; label="m"\; filenames="00000046.png"\; state="\{\{state\}\}">m</figure-callout>}}^2+x_{22m}^2)-r_{nm}^2(A_{\mathrm{one}}{r}_{22m}+B_{\mathrm{one}}{x}_{22m})-r_{\mathrm{eleven}m}-r_{0m}+2r_{0m}{r}_{nm}{r}_{22m}+A_{\mathrm{one}}{r}_{nm};$$

r _0m , X _0m - set values of the real component and optimal values of the imaginary component of the resistance of the source of the input high-frequency signal of the generator in the amplification mode at a given number of frequencies; r _nm , X _nm - the specified values of the real component and the optimal values of the imaginary component of the load resistance at a given number of frequencies; r _11m , x _11m , r _12m , x _12m , r _21m , x _21m , r _22m , x _22m are the given total values of the real and imaginary components of the mixed matrix H of the three-pole nonlinear element for a given amplitude of the constant voltage and the corresponding real and imaginary components mixed matrix H of the external feedback circuit at predetermined frequencies; m = 1, 2 ... N - numbers of frequencies.

2. This result is achieved by the fact that in the device for generating high-frequency signals, consisting of a constant voltage source, a three-pole non-linear element, an external feedback circuit and a load, additionally, the external feedback circuit is made in the form of an arbitrary four-terminal connected in series with a three-pole non-linear element included between the introduced two-terminal with complex resistance, which simulates the resistance of the source of the input high-frequency signal of the generator in gain mode and load, the imaginary components of the resistance of the source of the input high-frequency signal of the generator in the gain and load mode are implemented in the form of successive oscillatory circuits of elements with parameters L _k , C _k parallel connected to arbitrary reactive two-terminal devices with resistances x _k , and the parameter values are determined from the condition of providing a stationary mode of generation at two frequencies using the following mathematical expressions:

$$L_k=\frac{{\omega }_{\mathrm{one}}{X}_{k\mathrm{one}}{x}_{k\mathrm{one}}\left(X_{k2}-x_{k2}\right)+{\omega }_2{X}_{k2}{x}_{k2}\left(x_{k\mathrm{one}}-X_{k\mathrm{one}}\right)}{\left(X_{k2}-x_{k2}\right)\left(x_{k\mathrm{one}}-X_{k\mathrm{one}}\right)\left({\omega }_{\mathrm{one}}^2-{\mathrm{<figure-callout\; id="2"\; label="\omega "\; filenames="00000046.png"\; state="\{\{state\}\}">\omega </figure-callout>}}_2^2\right)};$$

$$C_k=\frac{\left({\omega }_{\mathrm{one}}^2-{\mathrm{<figure-callout\; id="2"\; label="\omega "\; filenames="00000046.png"\; state="\{\{state\}\}">\omega </figure-callout>}}_2^2\right)\left(x_{k\mathrm{one}}-X_{k\mathrm{one}}\right)\left(X_{k2}-x_{k2}\right)}{{\omega }_{\mathrm{one}}{\omega }_2\left[{\omega }_{\mathrm{one}}{X}_{k2}{x}_{k2}\left(x_{k\mathrm{one}}-X_{k\mathrm{one}}\right)+{\omega }_2{X}_{k\mathrm{one}}{x}_{k\mathrm{one}}\left(X_{k2}-x_{k2}\right)\right]};$$

$$X_{0m}=\frac{A{X}_{nm}+B}{C{X}_{nm}+D};$$

$$X_{nm}=\frac{-Y\pm \sqrt{Y^2-\mathrm{four}XZ}}{2X},$$

where A = - (x _22m r _0m + B ₁ ); B = r _nm (A ₁ + r _0m r _22m ) -r _0m -r _11m ; C = r _22m ; D = x _22m r _nm ; X = -r _22m (r _22m r _0m + A ₁ ); Y = r _22m x _11m -B ₁ -x _22m (r _22m r _0m r _nm + A ₁ r _nm ); A ₁ = r _11m r _22m -x _11m x _22m -r _12m r _21m + x _12m x _21m ; B ₁ = x _11m r _22m + r _11m x _22m -x _12m r _21m -r _12m x _21m ; $$Z=r_{nm}(r_{\mathrm{eleven}m}{r}_{22m}+x_{\mathrm{eleven}m}{x}_{22m})-r_{0m}{r}_{nm}^2(r_{22\mathrm{<figure-callout\; id="2"\; label="m"\; filenames="00000046.png"\; state="\{\{state\}\}">m</figure-callout>}}^2+x_{22m}^2)-r_{nm}^2(A_{\mathrm{one}}{r}_{22m}+B_{\mathrm{one}}{x}_{22m})-r_{\mathrm{eleven}m}-r_{0m}+2r_{0m}{r}_{nm}{r}_{22m}+A_{\mathrm{one}}{r}_{nm};$$

X _0m ; X _nm - the optimal values of the imaginary components of the resistances of the source of the input high-frequency signal of the generator in the amplification and load conditions for the given two frequencies ω _m = 2πf _m ; m = 1, 2 - frequency number; r _0m - set values of the real component of the resistance of the source of the input high-frequency signal of the generator in the amplification mode at two frequencies; r _nm - set values of the real component of the load resistance at two frequencies; r _11m , x _11m , r _12m , x _12m , r _21m , x _21m , r _22m , x _22m are the given total values of the real and imaginary components of the mixed matrix H of the three-pole nonlinear element for a given amplitude of the constant voltage and the corresponding real and imaginary components mixed matrix H of the external feedback circuit at predetermined frequencies; x _0m , x _nm - the set values of the resistances of arbitrary bipolar, which are part of the imaginary components X _0m , X _{nm of the} complex resistances of the signal source in the amplification and load modes, at two frequencies; k = 0, n is the index characterizing the imaginary components of the resistance of the signal source in the amplification and load conditions.

Figure 1 shows a diagram of a device for generating high-frequency signals (prototype) that implements the prototype method.

Figure 2 shows the structural diagram of the proposed device according to claim 2, which implements the proposed method of generation according to claim 1 in amplification mode.

Figure 3 shows a diagram of reactive two-terminal devices that implement the imaginary components of the complex resistances of the generator signal source in the amplification and load conditions.

The prototype device (Figure 1), which implements the prototype method, contains a direct transmission circuit in the form of a three-pole non-linear element VT 1 connected to a constant voltage source 2, the first matching filtering device (SFU) 3 (first reactive four-terminal or first matching four-terminal ) and an oscillatory circuit on the elements L 4, R 5, C 6, which is the load 7. The first SFU 3 is connected between the output electrode of the three-pole nonlinear element and the load. Between the load and the control electrode of a three-pole non-linear element, a second SFU 9 (second reactive four-terminal or second matching four-terminal) is connected with the first two-terminal 8 connected to its input and to the output of the second two-terminal 10 with complex resistances in the transverse circuits. All this together forms an external feedback circuit. The first two-terminal 8 is connected to the load. The second two-terminal 10 is connected to the control electrode of a three-pole nonlinear element.

The principle of operation of a device for generating high-frequency signals (prototype) that implements the prototype method is as follows.

When you turn on the constant voltage source 2 due to the abrupt change in the amplitude throughout the circuit, oscillations occur, the spectrum of which occupies the entire frequency radio frequency range. The amplitudes of these oscillations decay quickly. However, due to the presence of external feedback, matching with the first reactive four-terminal 3 of the output electrode of the three-pole nonlinear element and load (direct transmission circuit), matching with the feedback circuit (the first two-terminal 8 with complex resistance, the second reactive four-terminal 9 and the second two-terminal 10 with complex resistance) of the load and the control electrode of a three-pole nonlinear element compensates for losses in the circuit L 4, R 5, C 6. Due to this, the feedback novitsya positive balance conditions are realized, and the phases and amplitudes - the conditions of excitation of electromagnetic waves. As a result, the oscillation with a frequency equal to the resonant frequency of the oscillatory circuit is supplied to the control electrode of a three-pole nonlinear element, which at the initial stage operates in amplification mode. The amplitude of this oscillation is amplified until it increases to a level at which the limiting state of a three-pole nonlinear element occurs. The stationary mode of generation sets in.

The disadvantages of the prototype method and device for its implementation are described above.

$$h_{12m}^{VT}=r_{12m}^{VT}+j{x}_{12m}^{VT},$$

$$h_{21m}^{VT}=r_{21m}^{VT}+j{x}_{21m}^{VT},$$

$$h_{22m}^{VT}=r_{22m}^{VT}+j{x}_{22m}^{VT}$$

на заданных частотах генерируемых сигналов, подключенный к источнику постоянного напряжения 2 (на фиг.2 не показан) и включенный по высокой частоте между источником входного высокочастотного сигнала в режиме усиления с сопротивлением z_0m=r_0m+jx_0m 11 на заданных частотах, имитирующим сопротивление источника высокочастотных колебаний, возникающих при включении источника постоянного напряжения 2 в момент скачкообразного изменения амплитуды его напряжения в режиме генерации, и нагрузкой 12 с сопротивлениями z_нm=r_нm+jx_нm на заданных частотах. К нелинейному элементу как к четырехполюснику по последовательно-параллельной схеме (входы соединены последовательно, а выходы - параллельно) подключена цепь внешней обратной связи, выполненная в виде произвольного четырехполюсника 13, сформированного в общем случае на двухполюсниках с комплексными сопротивлениями. Четырехполюсник 13 тоже характеризуется известными значениями элементов смешанной матрицы Н $$h_{11m}^{OC}=r_{11m}^{OC}+j{x}_{11m}^{OC}$$

, $$h_{12m}^{OC}=r_{12m}^{OC}+j{x}_{12m}^{OC}$$

, $$h_{21m}^{OC}=r_{21m}^{OC}+j{x}_{21m}^{OC}$$

, $$h_{22m}^{OC}=r_{22m}^{OC}+j{x}_{22m}^{OC}$$

на заданных частотах. Синтез генератора (выбор значений мнимых составляющих сопротивлений источника входного высокочастотного сигнала генератора в режиме усиления и нагрузки на двух заданных частотах (m=1, 2 - номер частоты), схем формирования этих двухполюсников (фиг.3) осуществлен по критерию обеспечения баланса амплитуд и баланса фаз путем реализации равенства нулю знаменателя коэффициента передачи устройства генерации в режиме усиления одновременно на заданных частотах генерируемых сигналов при постоянной амплитуде постоянного напряжения. Выбор сопротивлений четырехполюсника 13 можно осуществлять произвольно или исходя из каких-либо других физических соображений. В данном изобретении значения сопротивлений комплексных двухполюсников четырехполюсника 13 выбираются из условий физической реализуемости. В режиме генерации источник входного высокочастотного сигнала отключается, и вместо него устанавливается короткозамыкающая перемычка.The proposed device according to claim 2 (figure 2), which implements the proposed method according to claim 1, contains a three-pole nonlinear element 1 with known elements of a mixed matrix H $$h_{\mathrm{eleven}m}^{VT}=r_{\mathrm{eleven}m}^{VT}+j{x}_{\mathrm{eleven}m}^{VT},$$

$$h_{12m}^{VT}=r_{12m}^{VT}+j{x}_{12m}^{VT},$$

$$h_{21m}^{VT}=r_{21m}^{VT}+j{x}_{21m}^{VT},$$

$$h_{22m}^{VT}=r_{22m}^{VT}+j{x}_{22m}^{VT}$$

at given frequencies of the generated signals, connected to a constant voltage source 2 (not shown in FIG. 2) and turned on at a high frequency between a high-frequency input signal source in gain mode with resistance z _0m = r _0m + jx _0m 11 at given frequencies simulating resistance the source of high-frequency oscillations that occur when the DC voltage source 2 is turned on at the moment of an abrupt change in the amplitude of its voltage in the generation mode, and by a load of 12 with resistances z _nm = r _nm + jx _nm at given frequencies. An external feedback circuit, made in the form of an arbitrary four-terminal 13 formed in the general case on two-terminal with complex resistances, is connected to a nonlinear element as a four-terminal in a series-parallel circuit (inputs are connected in series and outputs are parallel). The four-terminal 13 is also characterized by known values of the elements of the mixed matrix H $$h_{\mathrm{eleven}m}^{OC}=r_{\mathrm{eleven}m}^{OC}+j{x}_{\mathrm{eleven}m}^{OC}$$

, $$h_{12m}^{OC}=r_{12m}^{OC}+j{x}_{12m}^{OC}$$

, $$h_{21m}^{OC}=r_{21m}^{OC}+j{x}_{21m}^{OC}$$

, $$h_{22m}^{OC}=r_{22m}^{OC}+j{x}_{22m}^{OC}$$

at given frequencies. The synthesis of the generator (the choice of the values of the imaginary components of the resistance of the source of the input high-frequency signal of the generator in the gain and load mode at two preset frequencies (m = 1, 2 is the frequency number), the circuits for the formation of these two-terminal circuits (Fig. 3) are carried out according to the criterion of ensuring the balance of amplitudes and phases by implementing the vanishing of the denominator of the transmission coefficient of the generation device in the amplification mode simultaneously at the given frequencies of the generated signals at a constant amplitude of a constant voltage. occurrences quadrupole 13 can be carried out arbitrarily or based on any other physical considerations. In the present invention, the resistance values of complex two-terminal quadripole 13 are selected from the conditions of physical realizability. In a generation mode input high-frequency signal source is disabled, and instead the shorting jumper is installed.

The proposed device operates as follows.

When you turn on the constant voltage source 2 due to the abrupt change in the amplitude in the entire circuit oscillations occur, the spectrum of which occupies the entire frequency radio frequency range. The amplitudes of these oscillations decay quickly. However, due to the presence of external feedback in the circuit, a negative resistance arises, which, due to the indicated choice of the values of the imaginary components of the resistance of the source of the input high-frequency signal of the generator in the amplification mode 11 and load 12, compensates for losses in the entire circuit simultaneously at two given frequencies. The oscillation amplitudes with given frequencies are amplified to certain levels and then limited. Due to this, the oscillations with the given two frequencies are amplified until the amplitudes of these oscillations increase to a level at which the amplitude goes beyond the quasilinear section of the through-current voltage characteristic. There is a stationary mode. Finally, as a result of the interaction of signals at two frequencies with a nonlinear element in the generation mode, products of nonlinear interaction with combination frequencies ω _n = Iω ₁ ± Kω ₂ , I, K = 0, 1, 2 ... arise.

Let us prove the feasibility of implementing these properties.

, $$h_{12}^{VT}=r_{12}^{VT}+j{x}_{12}^{VT}$$

, $$h_{21}^{VT}=r_{21}^{VT}+j{x}_{21}^{VT}$$

, $$h_{22}^{VT}=r_{22}^{VT}+j{x}_{22}^{VT}$$

и цепи обратной связи $$h_{11}^{OC}=r_{11}^{OC}+j{x}_{11}^{OC},$$

$$h_{12}^{OC}=r_{12}^{OC}+j{x}_{12}^{OC},$$

$$h_{21}^{OC}=r_{21}^{OC}+j{x}_{21}^{OC},$$

$$h_{22}^{OC}=r_{22}^{OC}+j{x}_{22}^{OC}$$

от частоты, которые можно определить по известным (например, измеренным или рассчитанным) элементам матриц сопротивлений, проводимостей или передачи. При последовательно-параллельном соединении четырехполюсников элементы их смешанных матриц Н складываются. Суммарные зависимости элементов матриц H цепи прямой передачи в виде нелинейного элемента и цепи обратной связи от частоты: h₁₁=r₁₁+jx₁₁, h₁₂=r₁₂+jx₁₂, h₂₁=r₂₁+jx₂₁, h₂₂=r₂₂+jx₂₂. Размерности элементов матрицы Н: h₁₁ (сопротивление), h₁₂ (безразмерный), h₂₁ (безразмерный), h₂₂ (проводимость).Let us introduce the designations of the given dependences of the resistance of the signal source in the amplification mode z ₀ = r ₀ + jx ₀ and the load z _n = r _n + jx _n on frequency. The initial ones are also the dependences of the elements of the mixed matrix H of a three-pole nonlinear element $$h_{\mathrm{eleven}}^{VT}=r_{\mathrm{eleven}}^{VT}+j{x}_{\mathrm{eleven}}^{VT}$$

, $$h_{12}^{VT}=r_{12}^{VT}+j{x}_{12}^{VT}$$

, $$h_{21}^{VT}=r_{21}^{VT}+j{x}_{21}^{VT}$$

, $$h_{22}^{VT}=r_{22}^{VT}+j{x}_{22}^{VT}$$

and feedback circuits $$h_{\mathrm{eleven}}^{OC}=r_{\mathrm{eleven}}^{OC}+j{x}_{\mathrm{eleven}}^{OC},$$

$$h_{12}^{OC}=r_{12}^{OC}+j{x}_{12}^{OC},$$

$$h_{21}^{OC}=r_{21}^{OC}+j{x}_{21}^{OC},$$

$$h_{22}^{OC}=r_{22}^{OC}+j{x}_{22}^{OC}$$

on the frequency that can be determined by known (for example, measured or calculated) elements of the matrix of resistance, conductivity or transmission. With a series-parallel connection of the four-terminal network, the elements of their mixed matrices H are added. The total dependences of the matrix elements H of the direct transmission circuit in the form of a nonlinear element and feedback loop on frequency: h ₁₁ = r ₁₁ + jx ₁₁ , h ₁₂ = r ₁₂ + jx ₁₂ , h ₂₁ = r ₂₁ + jx ₂₁ , h ₂₂ = r ₂₂ + jx ₂₂ . The dimensions of the elements of the matrix H: h ₁₁ (resistance), h ₁₂ (dimensionless), h ₂₁ (dimensionless), h ₂₂ (conductivity).

The general mixed matrix H of the nonlinear element (VT) and the four-terminal feedback loop (OS) and the corresponding classical transmission matrix of the entire device, taking into account normalization conditions:

$$H=\left|\begin{array}{cc}{h}_{\mathrm{eleven}}& h_{12}\\ h_{21}& h_{22}\end{array}\right|;\text{A}=\left|\begin{array}{cc}\frac{\text{-}\left|\text{h}\right|}{h_{21}}\sqrt{\frac{z_n}{z_0}}& \frac{h_{\mathrm{eleven}}}{h_{21}}\frac{\mathrm{one}}{\sqrt{z_0{z}_n}}\\ \frac{-h_{22}}{h_{21}}\sqrt{z_0{z}_n}& \frac{\mathrm{one}}{h_{21}}\sqrt{\frac{z_0}{z_n}}\end{array}\right|,\text{(one)}$$

where | h | = h ₁₁ h ₂₂ -h ₁₂ h ₂₁ .

Using the well-known connection between the elements of the scattering matrix and the elements of the classical transmission matrix (Feldstein A.L., Yavich L.R. Synthesis of four-terminal and eight-terminal devices on microwave. M: Communication, 1971, p. 34-36) and the transmission matrix from (1) , we obtain the expression for the gain of the generator in amplification mode:

$$S_{21}=\frac{2h_{21}\sqrt{z_0{z}_n}}{z_0+h_{\mathrm{eleven}}-z_n\left(z_0{h}_{22}+\left|h\right|\right)}.\text{(2)}$$

или условию баланса амплитуд и баланса фаз 1-KB=0 (Гоноровский И.С. Радиотехнические цепи и сигналы. - М.: «Дрофа», - 2006, с.383) для цепи с внешней положительной обратной связью. Для данного вида генератора и частотного модулятора $$K=\frac{z_{н}{h}_{21}}{\left(1-h_{22}{z}_{н}\right)z_0}$$

- коэффициент передачи цепи прямой передачи; $$B=\frac{z_{н}\left|h\right|-h_{11}}{\left(1-h_{22}{z}_{н}\right)z_0}$$

- коэффициент усиления цепи обратной связи. Возможны и другие варианты представления величин K и В. Это различие для изобретения не имеет принципиального значения. В любом случае условия баланса амплитуд и баланса фаз соответствуют равенству нулю знаменателя коэффициента передачи.We transform the denominator of the transmission coefficient and write it in the form corresponding to the condition for the emergence of a stationary generation mode $$\mathrm{one}-\frac{z_n\left|h\right|-h_{\mathrm{eleven}}}{\left(\mathrm{one}-h_{22}{z}_n\right)z_0}=0$$

or the condition for the balance of amplitudes and phase balance 1-KB = 0 (Gonorovsky IS Radio engineering circuits and signals. - M .: "Bustard", - 2006, p. 383) for a circuit with external positive feedback. For this type of generator and frequency modulator $$K=\frac{z_n{h}_{21}}{\left(\mathrm{one}-h_{22}{z}_n\right)z_0}$$

- gear ratio of the direct transmission circuit; $$B=\frac{z_n\left|h\right|-h_{\mathrm{eleven}}}{\left(\mathrm{one}-h_{22}{z}_n\right)z_0}$$

- feedback loop gain. There are other possible representations of the values of K and B. This difference for the invention is not of fundamental importance. In any case, the conditions for the balance of amplitudes and phase balance correspond to the equality to zero of the denominator of the transfer coefficient.

We equate the denominator of the transmission coefficient to zero and divide the real and imaginary parts. We get a system of two algebraic equations:

$$\begin{array}{l}{r}_{\mathrm{eleven}}+r_0-r_n(r_{22}{r}_0-A_{\mathrm{one}})+x_n(r_{22}{x}_0+x_{22}{r}_0-B_{\mathrm{one}})+x_{22}{x}_0{r}_n=0;\\ x_{\mathrm{eleven}}+x_0-x_n(r_{22}{r}_0-A_{\mathrm{one}})-r_n(r_{22}{x}_0+x_{22}{r}_0-B_{\mathrm{one}})+x_n{x}_{22}{x}_0=0.\text{(3)}\end{array}$$

Solution of the system of equations (3):

$$x_0=\frac{A{x}_n+B}{C{x}_n+D};$$

$$x_n=\frac{-Y\pm \sqrt{Y^2-\mathrm{four}XZ}}{2X},\text{(four)}$$

A₁=r₁₁r₁₂-x₁₁x₂₂-r₁₂r₂₁+x₁₂x₂₁; B₁=x₁₁r₂₂+r₁₁x₂₂-x₁₂r₂₁-r₁₂x₂₁.where A = - (x ₂₂ r ₀ + B ₁ ); B = r _n (A ₁ + r ₀ r ₂₂ ) -r ₀ -r ₁₁ ; C = r ₂₂ ; D = x ₂₂ r _n ; X = -r ₂₂ (r ₂₂ r ₀ + A ₁ ); Y = r ₂₂ x ₁₁ -B ₁ -x ₂₂ (r ₂₂ r ₀ r _n + r ₀ + A ₁ r _n ); $$Z=r_n(r_{\mathrm{eleven}}{r}_{22}+x_{\mathrm{eleven}}{x}_{22})-r_0{r}_n^2(r_{22}^2+x_{22}^2)-r_n^2(A_{\mathrm{one}}{r}_{22}+B_{\mathrm{one}}{x}_{22})-r_{\mathrm{eleven}}-r_0+2r_0{r}_n{r}_{22}+A_{\mathrm{one}}{r}_n;$$

A ₁ = r ₁₁ r ₁₂ -x ₁₁ x ₂₂ -r ₁₂ r ₂₁ + x ₁₂ x ₂₁ ; B ₁ = x ₁₁ r ₂₂ + r ₁₁ x ₂₂ -x ₁₂ r ₂₁ -r ₁₂ x ₂₁ .

The implementation of the optimal approximating functions (4) can be carried out in various ways, for example, using the interpolation method by finding the values of the parameters of the selected reactive two-terminal networks at which their resistances at the given frequencies coincide with the optimal ones. Here are two examples of the construction of two-terminal networks for two interpolation frequencies, which were used to synthesize the considered version of the generators.

Serial oscillatory circuit connected in parallel with an arbitrary reactive bipolar (Fig.3):

$$\frac{x_{km}\left({\omega }_m^2{L}_k{C}_k-\mathrm{one}\right)}{\left({\omega }_m{L}_k+x_{km}\right){\omega }_m{C}_k-\mathrm{one}}=X_{km},\text{m}=\text{one}\text{, 2;}{\omega }_{\text{m}}=2\pi f_m\text{(5)}$$

$$L_k=\frac{{\omega }_{\mathrm{one}}{X}_{k\mathrm{one}}{x}_{k\mathrm{one}}\left(X_{k2}-x_{k2}\right)+{\omega }_2{X}_{k2}{x}_{k2}\left(x_{k\mathrm{one}}-X_{k\mathrm{one}}\right)}{\left(X_{k2}-x_{k2}\right)\left(x_{k\mathrm{one}}-X_{k\mathrm{one}}\right)\left({\omega }_{\mathrm{one}}^2-{\mathrm{<figure-callout\; id="2"\; label="\omega "\; filenames="00000046.png"\; state="\{\{state\}\}">\omega </figure-callout>}}_2^2\right)};$$

$$C_k=\frac{\left({\omega }_{\mathrm{one}}^2-{\mathrm{<figure-callout\; id="2"\; label="\omega "\; filenames="00000046.png"\; state="\{\{state\}\}">\omega </figure-callout>}}_2^2\right)\left(x_{k\mathrm{one}}-X_{k\mathrm{one}}\right)\left(X_{k2}-x_{k2}\right)}{{\omega }_{\mathrm{one}}{\omega }_2\left[{\omega }_{\mathrm{one}}{X}_{k2}{x}_{k2}\left(x_{k\mathrm{one}}-X_{k\mathrm{one}}\right)+{\omega }_2{X}_{k\mathrm{one}}{x}_{k\mathrm{one}}\left(X_{k2}-x_{k2}\right)\right]},$$

where m = 1, 2 ... is the frequency number; k = 0, n is the index characterizing the imaginary components of the resistance of the signal source in the amplification and load conditions.

The implementation of optimal approximations of the frequency characteristics of the imaginary component of the resistance of the additional two-terminal device and the imaginary component of the load resistance (4) using (5) ensures the implementation of the matching condition, amplitude balance and phase balance simultaneously at two given frequencies. As a result of the interaction of signals at two frequencies with a nonlinear element, additional products of nonlinear interaction arise with Raman frequencies ω _n = Iω ₁ ± Kω ₂ , I, K = 0, 1, 2 ....

The proposed technical solutions have an inventive step, since it does not explicitly follow from the published scientific data and the known technical solutions that the claimed sequence of operations (execution of an external feedback circuit in the form of an arbitrary four-terminal on complex resistances, connected in series-parallel circuit with a three-pole non-linear element ( figure 2), the choice of frequency characteristics of the imaginary component of the resistance of the source of the high-frequency signal of the generator in the mode the gain and the imaginary component of the load resistance, the formation of their circuits in the indicated form (Fig. 3), the choice of the values of their parameters from the condition of providing a stationary mode of generation at two frequencies with the unchanged state of a nonlinear three-pole element connected between the source of the high-frequency signal of the generator in the amplification mode and the load ) provides at the same time the formation of high-frequency signals at given frequencies.

The proposed technical solutions are practically applicable, since for their implementation three-pole non-linear elements (transistors or lamps) commercially available by the industry, reactive elements formed in the declared schemes of reactive two-pole can be used (FIG. 3). The values of the parameters of the inductances and capacitances of these circuits can be uniquely determined using mathematical expressions given in the claims.

The technical and economic efficiency of the proposed device is to simultaneously ensure the generation of a high-frequency signal at two given frequencies due to the choice of the circuit and the values of the parameters of the reactive elements according to the criterion of ensuring the conditions of the balance of phases and amplitudes at these frequencies with the non-linear state of the three-pole element unchanged, which, taking into account non-linear interaction generate complex signals and create radio communications that operate on a given number of radio channels.

Claims (2)

1. A method of generating high-frequency signals based on the conversion of the energy of a constant voltage source into the energy of a high-frequency signal, the interaction of a high-frequency signal with a direct transmission circuit, a three-pole nonlinear element and an external feedback circuit, the fulfillment of the excitation conditions in the form of a balance of amplitudes and phase balance, respectively determining the amplitude and frequency of the generated high-frequency signals, matching conditions of the output electrode of a three-pole nonlinear element with a load and condition coordination of the load with the control electrode of a three-pole non-linear element, characterized in that the forward circuit is made of a three-pole non-linear element, an arbitrary four-terminal connected to the three-pole non-linear element in a series-parallel circuit is used as the external feedback circuit, the load is performed in the form of the first two-pole with complex resistance, to the control electrode of a three-pole nonlinear element, a second two-pole is connected to the transverse circuit IR with a complex impedance simulating a source signal generator resistance under amplification conditions, the conditions of excitation of the balance of the amplitude and phase balance and matching conditions simultaneously operate for a predetermined number of frequencies by choosing the values of imaginary components of impedance of the first X _nm and the second X _0m two-terminal of conditions to ensure stationary generation mode in the form of equality to zero of the denominator of the gain in gain mode simultaneously at all given frequencies of the generated high-frequency signals at a constant amplitude of the DC voltage source in accordance with the following mathematical expressions:
$$X_{0m}=\frac{A{X}_{nm}+B}{C{X}_{nm}+D};$$

$$X_{nm}=\frac{-Y\pm \sqrt{Y^2-\mathrm{four}XZ}}{2X},$$

where A = - (x _22m r _0m + B ₁ ); B = r _nm (A ₁ + r _0m r _22m ) -r _0m -r _11m ; C = r _22m ; D = x _22m r _nm ; X = -r _22m (r _22m r _0m + A ₁ ); Y = r _22m x _11m -B ₁ -x _22m (r _22m r _0m r _nm + A ₁ r _nm ); A ₁ = r _11m r _22m -x _11m x _22m -r _12m r _21m + x _12m x _21m ; B ₁ = x _11m r _22m + r _11m x _22m -x _12m r _21m -r _12m x _21m ; $$Z=r_{nm}(r_{\mathrm{eleven}m}{r}_{22m}+x_{\mathrm{eleven}m}{x}_{22m})-r_{0m}{r}_{nm}^2(r_{22m}^2+x_{22m}^2)-r_{nm}^2(A_{\mathrm{one}}{r}_{22m}+B_{\mathrm{one}}{x}_{22m})-r_{\mathrm{eleven}m}-r_{0m}+2r_{0m}{r}_{nm}{r}_{22m}+A_{\mathrm{one}}{r}_{nm};$$

r _0m , X _0m - set values of the real component and optimal values of the imaginary component of the resistance of the source of the input high-frequency signal of the generator in the amplification mode at a given number of frequencies; r _nm , X _nm - the specified values of the real component and the optimal values of the imaginary component of the load resistance at a given number of frequencies; r _11m , x _11m , r _12m , x _12m , r _21m , x _21m , r _22m , x _22m are the given total values of the real and imaginary components of the mixed matrix H of the three-pole nonlinear element for a given amplitude of the constant voltage and the corresponding real and imaginary components mixed matrix H of the external feedback circuit at predetermined frequencies; m = 1, 2 ... N - numbers of frequencies. 2. A device for generating high-frequency signals, consisting of a constant voltage source, a three-pole nonlinear element, an external feedback circuit and a load, characterized in that the external feedback circuit is made in the form of an arbitrary four-terminal, connected in series with a three-pole non-linear element connected between the introduced two-terminal with complex resistance, which simulates the resistance of the source of the input high-frequency signal of the generator in the amplification mode, and the load, are imaginary constituting the source impedance of the input high-frequency signal generator in a mode of amplification and load implemented as a series resonant circuit element with the parameters L _k, C _k, connected in parallel with arbitrary reactive two-terminal network with x _k resistances, the values of the parameters determined from the condition of providing a stationary lasing at two frequencies using the following mathematical expressions:
$$L_k=\frac{{\omega }_{\mathrm{one}}{X}_{k\mathrm{one}}{x}_{k\mathrm{one}}\left(X_{k2}-x_{k2}\right)+{\omega }_2{X}_{k2}{x}_{k2}\left(x_{k\mathrm{one}}-X_{k\mathrm{one}}\right)}{\left(X_{k2}-x_{k2}\right)\left(x_{k\mathrm{one}}-X_{k\mathrm{one}}\right)\left({\omega }_{\mathrm{one}}^2-{\omega }_2^2\right)};$$

$$C_k=\frac{\left({\omega }_{\mathrm{one}}^2-{\omega }_2^2\right)\left(x_{k\mathrm{one}}-X_{k\mathrm{one}}\right)\left(X_{k2}-x_{k2}\right)}{{\omega }_{\mathrm{one}}{\omega }_2\left[{\omega }_{\mathrm{one}}{X}_{k2}{x}_{k2}\left(x_{k\mathrm{one}}-X_{k\mathrm{one}}\right)+{\omega }_2{X}_{k\mathrm{one}}{x}_{k\mathrm{one}}\left(X_{k2}-x_{k2}\right)\right]}$$

; $$X_{0m}=\frac{A{X}_{nm}+B}{C{X}_{nm}+D}$$

; $$X_{nm}=\frac{-Y\pm \sqrt{Y^2-\mathrm{four}XZ}}{2X},$$

where A = - (x _22m r _0m + B ₁ ); B = r _nm (A ₁ + r _0m r _22m ) -r _0m -r _11m ; C = r _22m ; D = x _22m r _nm ; X = -r _22m (r _22m r _0m + A ₁ ); Y = r _22m x _11m -B ₁ -x _22m (r _22m r _0m r _nm + A ₁ r _nm ); A ₁ = r _11m r _22m -x _11m x _22m -r _12m r _21m + x _12m x _21m ; B ₁ = x _11m r _22m + r _11m x _22m -x _12m r _21m -r _12m x _21m ; $$Z=r_{nm}(r_{\mathrm{eleven}m}{r}_{22m}+x_{\mathrm{eleven}m}{x}_{22m})-r_{0m}{r}_{nm}^2(r_{22m}^2+x_{22m}^2)-r_{nm}^2(A_{\mathrm{one}}{r}_{22m}+B_{\mathrm{one}}{x}_{22m})-r_{\mathrm{eleven}m}-r_{0m}+2r_{0m}{r}_{nm}{r}_{22m}+A_{\mathrm{one}}{r}_{nm};$$

X _0m ; X _nm - the optimal values of the imaginary components of the resistances of the source of the input high-frequency signal of the generator in the amplification and load conditions for the given two frequencies ω _m = 2πf _m ; m = 1, 2 - frequency number;
r _0m - set values of the real component of the resistance of the source of the input high-frequency signal of the generator in the amplification mode at two frequencies; r _nm - set values of the real component of the load resistance at two frequencies; r _11m , x _11m , r _12m , x _12m , r _21m , x _21m , r _22m , x _22m are the given total values of the real and imaginary components of the mixed matrix H of the three-pole nonlinear element for a given amplitude of the constant voltage and the corresponding real and imaginary components mixed matrix H of the external feedback circuit at predetermined frequencies; x _0m ; x _nm - the given values of the resistances of arbitrary two-terminal _circuits that are part of the imaginary components of X _0m ; X _{nm of the} complex resistances of the signal source in the amplification and load modes, at two frequencies; k = 0, n is the index characterizing the imaginary components of the resistance of the signal source in the amplification and load conditions.

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