RU2470323C1 - Method of adjusting output parameters of superregenerative transceiver of radiosonde - Google Patents

Abstract

FIELD: physics, radio.

SUBSTANCE: invention relates to radio engineering and can be used to adjust sensitivity and relative position of the receiving and transmitting frequency of superregenerative transceivers of aerologic radiosondes operating as part of atmospheric radiosounding systems. Disclosed is a method of adjusting output parameters of a superregenerative transceiver of a radiosonde based on optimum selection of the feedback factor of the self-oscillator of the superregenerative transceiver, load resistor, resonance frequency of the oscillatory system, characterised by that when launching the self-oscillator of the superregenerative transceiver, a mode for self-excitation with a hard character of the transient process of establishing self-oscillations is provided, average current and supply voltage of the active device of the self-oscillator of the superregenerative transceiver are stabilised, pulsed current of the control electrode - base of the transistor of the active device of the self-oscillator is controlled, thereby establishing reception frequency relative the carrier frequency of the self-oscillations of the superregenerative transceiver; by adjusting the slope of the exponentially rising leading edge and pulse duration, the required level of sensitivity of the superregenerative transceiver is set.

EFFECT: providing separate adjustment of receiving and transmitting frequency and achieving maximum sensitivity of a superregenerative transceiver of an aerologic radiosonde to the request signal of a surface radar station.

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Description

The invention relates to radio engineering and can be used in aerological radiosondes (ARZ) of atmospheric radio sounding systems for measuring the distance to a radiosonde using a pulsed method, direction finding by angular coordinates and transmitting telemetric information on a single carrier frequency, can also be used to build highly stable and economical super-regenerative reception transmitting devices of radar and communication systems.

Domestic atmospheric radiosounding (SR) systems are constructed using the goniometer-range measuring method for measuring coordinates, velocity and direction of radiosonde movement in a free atmosphere. Measurement of angular coordinates azimuth (β), the elevation angle (ε), and the slant range (R _H) is carried out by radiopulse with active response. Especially effective was the use of super-regenerative transceiver-transponders (SPP) in the composition of radiosondes. Intensive SPP radiation provides reliable transmission of telemetric information and tracking along angular coordinates. The high sensitivity of the SPP to the radio pulse interrogation signal makes it possible to generate a range response signal in the form of a short pause in the radiation of the interferometer with a reduced transmitter power of the interrogation radar pulses. Ultimately, it turns out to be very important that the coordinate determination system and the telemetry information transmission channel of the radio sounding system operate at the same carrier frequency (see V.I. Ermakov et al. "Atmospheric Sensing Systems", Gidrometeoizdat, 1977, p. 247-249).

A common problem in modern ARZs is the difficulty in adjusting the output parameters of super-regenerative transceivers (SPP) due to their mutual influence, which complicates the tuning process during production, and the inability to achieve optimal ratios of sensitivity and radiated power, the mutual position of the frequency of reception and transmission of the SPP.

Another problem of the production and operation of ARZs is the creation of low-cost designs of transceivers that are stable in terms of radio engineering under changing pressure, ambient temperature, supply voltage, and parameters of the ARZ antenna system.

There is a method of adjusting the ARZ tube super-regenerative transceiver with a separate auxiliary oscillator by adjusting the carrier frequency, adjusting the time constant of the inertial auto-bias circuit of the microwave oscillator and communicating with the antenna, which serves to receive request pulses and transmit response and telemetry signals (see V.I. Ermakov and others. "Atmospheric sounding systems" ;; Hydrometeoizdat, 1977, p.240-259). The disadvantage is the inability to use it to configure semiconductor SPP.

There is a method of adjusting the SPP of a radiosonde, which consists in setting the resonant frequency of the oscillating system to the nominal value of the carrier frequency of the SPP, selecting the value of the active load of the microwave oscillator by changing the connection with the transmitting and receiving antenna ARZ, adjusting the time constant of the inertial auto-bias circuit of the microwave oscillator by changing the output the resistance of the super-voltage generator included in the base circuit of the transistor of the microwave oscillator (see RF patents No. 2172965, No. 2214614).

There is a method of adjusting the SPP of a radiosonde, which consists in setting the resonant frequency of the oscillating system to the nominal value of the carrier frequency of the SPP, adjusting the feedback coefficient in the microwave oscillator SPP, selecting the active load of the microwave oscillator by changing the connection with the transceiver antenna ARZ, adjusting the time constant the inertial auto-bias circuit of the microwave oscillator by changing the output resistance of the super-voltage generator, included in the base transistor circuit and microwave togeneratora (see RF patent №2291467 -. PROTOTYPE).

A disadvantage of the known solutions of the tuning methods and the PROTOTYPE is the significant interdependence of the carrier frequency of the SPP on the sensitivity adjustment by changing the output resistance of the generator of the supervoltage voltage included in the base circuit of the microwave transistor transistor.

An object of the invention is to increase the accuracy of tuning the reception and transmission frequencies, as well as the sensitivity of the SPP by eliminating their mutual influence when setting up the ARZ in the production environment by:

- creating a schematic, technical and constructive solution that allows eliminating the influence of sensitivity adjustment on the mutual shift of the receive frequency and the carrier frequency of the SPP when tuning in serial production, thereby increasing the sensitivity, radiation power and stability of the super-regenerative transceiver;

- improving the adaptability of NGN tuning and reducing the cost of production of radiosondes.

To solve this problem, a method is proposed for adjusting the output parameters of a super-regenerative radiosonde transceiver, based on the optimal choice of the feedback coefficient of a super-regenerative transceiver autogenerator, load resistance, resonant frequency of an oscillating system, when a super-regenerative transceiver oscillator is started, they provide a self-excitation mode with a rigid nature of the transition process of establishing auto-oscillations, stabilize the average current and voltage the power supply of the active device of the self-generator of the super-regenerative transceiver, regulate the pulse current of the control electrode - the base of the transistor of the active device of the auto-generator, thereby establish the frequency of reception relative to the carrier frequency of the oscillations of the super-regenerative transceiver, by adjusting the slope of the exponentially rising leading edge and the pulse duration of the generator of the supervising voltage (desired) sensitivity of super-regenerative transceiver ka.

To clarify the essence of the invention, the following structural and electrical circuits and graphs are given:

figure 1 is a structural diagram of a super-regenerative transceiver aerological radiosonde;

figure 2 - Dependence of the attenuation of the circuit of the microwave oscillator from the amplitude of the oscillations;

figure 3 - Waveforms of signals explaining the principle of operation of the SPP with the rigid nature of the establishment of self-oscillations operating at different points of the SPP;

figure 4 - Graphs explaining the principle of shockless start of the microwave oscillator SPP;

5 - a) a Graph of changes in the frequency of self-oscillations in the process of establishing self-oscillations; b) a graph of the change in the pulse current of the emitter of the microwave transistor in the process of establishing self-oscillations;

6 - a) The shape of the superimposing pulses at the output of the GSP SPP when adjusting the time constant of the low-pass filter at the input of the emitter follower; b) the form of superimposing pulses at the output of the SHG when adjusting their duration;

Fig.7 is a Functional diagram of the SPP, including a generator of a supervising voltage, an inertial circuit of auto-bias, a current stabilizer and microwave-AG superregenerative transceiver ARZ;

Fig - Schematic diagram of the microwave oscillator SPP.

The block diagram of the SPP shown in figure 1, contains: a power source - 1; the average current stabilizer of the microwave oscillator - 2; microwave power supply voltage stabilizer - 3; generator of supervising voltage (GSP) - 4; inertial auto-bias circuit - 5; Microwave oscillator - 6; Microwave bandpass filter - 7; ARZ transceiver antenna - 8.

The block diagram of the SPP (Fig. 1) has the following connections: a power source - 1 is connected to a voltage regulator - 3, the first output of the latter is connected to a medium current regulator of a self-oscillator - 2, and a second output is connected to a power input of a super-voltage generator - 4, whose output connected to the input of the inertial circuit of auto-bias - 5; the first output of the current stabilizer - 2 is connected to the power input of the microwave oscillator - 6, and the second output of the current stabilizer - 2 is connected to the output of the inertial auto-bias circuit - 5 and the input of the microwave oscillator - 6, the output / input of which is connected through a microwave bandpass filter 7 with transceiver antenna 8; the modulation input is connected to a super-voltage generator.

The fundamental features of the functioning of the SPP can be explained by analyzing its operation during one period of the supervising frequency T _c (Fig. 3). Figure 3 shows: U _rad - envelope of radio pulses emitted by SPP, duration τ _and ; U _c - superiruyuschey frequency voltage, characterized by _a period T and a duration τ _c; δ _(t) is the law of variation of the attenuation decrement of the circuit of the microwave oscillator; I _eo - video pulses of a direct current emitter of a microwave transistor.

The microwave oscillator (microwave AG) periodically turns on at the moment t _{1 of the} appearance of the super-impulse U _c and turns off at the moment t ₃ after it ends on the damping interval τ _d . The operating frequency of the microwave AG is about 1680 MHz. The pulse frequency of the supervising voltage is 800 kHz (period T _s = 1.25 μs). The oscillation system in the off state of the SPP is characterized by its own attenuation δ ₀ . Changing damping circuit for pulse superizatsii τ _c defines the development process and establishing oscillations in the microwave oscillator CPR.

The superregenerative amplification effect reduces to a decrease in the delay time τ _{s of the} leading edge of microwave pulses of the microwave AG by Δτ _s when an external signal U _{ss appears} during the reception interval of operation τ _pr adjacent to the time of the start of the SPP. Accordingly, the duration of the radio pulse and its energy increase. The level of the output signal of the NGN depending on the level of the request signal in the primary response mode can be estimated using the expression [1]

;

;

;Where

;

;

;

A _∑ is the effective amplitude of the noise in the NGN circuit at the time of startup;

A _c is the amplitude of the external signal.

The above expressions (1) show that the amplification effect ∆τ _s is mainly determined by the value of the starting attenuation δ _p . The occurrence of self-oscillations occurs during start-up attenuation δ _p ≥0, when the emitter current of the active device exceeds the boundary value I _eo ≥I _gr . The development of self-oscillations occurs when δ _p > 0, which is determined by the starting current of the oscillator I _p > I _g at the time of launch. Therefore, a change in the value of I _p leads to the adjustment of the delay time τ _s and the amplification effect — the increment of the delay time ∆τ _s .

The measurement of the slant range to the radiosonde equipped with NGN is carried out by measuring the delay time between the moment of sending short request radio pulses and receiving the response radio pulses of the NGN, increased in duration by the increment of the delay time ∆τ _s . Thus, in essence, the SPP is a transceiver with a temporary separation of the receiving and transmitting operating modes for one period of the superspeeding frequency T _s .

To ensure high sensitivity and amplification in the receiving mode, it is necessary to turn on the microwave oscillator with a minimum value of the starting negative attenuation δ _p . To achieve the maximum output power proportional to A _st , in the SPP it is necessary to increase the negative attenuation in the medium and large amplitudes for this type of active device of the oscillator (see figure 2). To implement these conflicting requirements, it turned out to be necessary to implement a regime of rigid oscillation establishment in the NPS loop [1]. This result can be obtained by analyzing a simplified version of the nonlinear equation of the oscillator

A qualitative analysis of equation (2) allows you to find out the features of the behavior of the function δ (t, A) depending on the amplitude of vibrations A (figure 2) and in the time domain (figure 3). The study of various options for the implementation of the function δ (t, A) shows that, in contrast to the soft mode recommended for the oscillation establishment in the classical superregenerator (with δ (A) = δ _p1 ) [2], it is necessary to implement a transition process with the tough nature of the establishment of oscillations [1]. In this case, the triggering of the SPP can occur with a minimum negative attenuation value at δ (A) = δ _p3 , which ensures a minimum reception bandwidth and high sensitivity. In this case, the establishment of a stationary mode occurs in the region of maximum amplitudes A _st , therefore, at a high level of output power. It must be emphasized that the change in starting attenuation δ _p practically does not affect And _Art . This allows, ultimately, separately and effectively adjust the parameters of the receiving and transmitting operating modes of the SPP by adjusting the starting current of the microwave-AG at the time of switching on. It should be emphasized that in order to ensure a transient process with a rigid nature of the establishment of oscillations, it is necessary to control the base circuit of the microwave oscillator transistor to control the voltage pulses generated by the super-voltage generator (GOS) with a low output resistance. In practice, GOS pulses are generated using an emitter follower providing a low differential output resistance of the GOS (see RF patent No. 93546). The regeneration coefficient (feedback coefficient) in the microwave oscillator should be optimal. The maximum negative attenuation δ (t) = δ _max in the range of average amplitudes provides a quick transition from the receiving to the transmitting mode of operation of the SPP. This contributes to the formation of almost rectangular radio pulses and a symmetric spectrum of SPP radiation, characteristic of a sequence of radio pulses of classical pulsed self-oscillators.

It must be emphasized that in the transistor microwave oscillator SPP, the starting current I _p during the receiving interval exceeds the boundary value of I _{g by} almost only tens to hundreds of μA. Therefore, to reduce the effect of shock excitation of the microwave-AG circuit and ensure high sensitivity, the shape of the emitter current pulses during the receiving interval should be gradually increasing from zero to the starting value I _p = 5-10 mA (see figure 3). Further, the constant component of the emitter current I _eo (and the collector current I _ko = I _eo ) changes synchronously with the amplitude of self-oscillations due to the hard nature of the transient process to the maximum values for this active device until the stationary mode I _ko = 180-250 mA is established. It should be emphasized that the stationary amplitudes A _st and I _emax do not depend on the value of the starting current I _p . It should be noted that the average value of the collector direct current I _{to cf} for the period of superization is determined by the ratio of τ _s and τ _s . Since the value of τ _{s is} regulated by the starting current I _p , it turns out that adjusting the average current I _{to cp} causes a corresponding change in the starting current of the microwave oscillator. For example, under the influence of destabilizing factors by increasing the average current I increases _{to cf.} inrush current I _n, which leads to a reduction _of the delay time τ, τ radio pulse duration increase _and decrease and the sensitivity. As the average current I _{k c} decreases, the process goes in the opposite direction. Thus, the stabilization of the current I _{to sr} allows you to stabilize τ _s sensitivity and bandwidth in the receiving mode, as well as the duration and power of the emitted radio pulses SPP τ _and . Accordingly, the choice of the duration of superimposing pulses τ _s allows us to optimize the ratio of sensitivity and radiated average power of the SPP [1]. Thus, the average current stabilizer I _{to sr} - 2 of the microwave oscillator - 6 is an important node of the SPP.

Introduction to the structure of the SPP voltage stabilizer - 3 power sources - 1 is associated with the need to ensure stability of the carrier frequency of the microwave oscillator SPP in the range f ₀ = 1680 ± 5 MHz.

As noted above, the super-voltage generator - 4 generates video pulses with a frequency of the order of F _c = 800 kHz, which directly control the operation of the microwave oscillator (Fig. 3). In practice, these pulses are generated using an emitter follower connected at the output of the GOS (see RF patent No. 93546), providing its low differential output impedance. GOS parameters are of fundamental importance for optimizing the operation of NGN.

The inertial auto-bias circuit - 5 is necessary to increase the stability of the microwave oscillator - 6 and to ensure the mode of operation with a “response pause” when measuring range as part of a radio sounding system (see RF patent No. 2214614). The response pause is formed due to the reaction of the inertial auto-bias circuit - 5 receiving an additional charge during the increment of the delay time ∆τ _s , which leads to the locking of the microwave oscillator during the generation of the next radio pulse.

Figure 7 shows a simplified version of the functional diagram of the SPP containing GOS, the emitter follower of which is made on the transistor VT1. Microwave AG implemented on the transistor VT2. The inertial self-bias circuit of the microwave-AG is formed by resistor R2 and capacitor C4. Adjustment R2 allows you to change the time constant of the inertial auto-bias circuit and ensures the formation of the response of the SPP to the radar interrogation signal, as suggested in RF patents No. 2172965, No. 2214614. However, when adjusting R2, a shift of the carrier frequency occurs due to a change in the operating mode of the microwave-AG, which does not allow you to simultaneously adjust the sensitivity, combine the receive frequency and the carrier frequency of the SPP.

On Fig for information shows a schematic diagram of a microwave oscillator - 6 (microwave-AG) SPP. Technical characteristics and tuning features of the microwave-AG are discussed in detail in the patent of the Russian Federation No. 104326, therefore, are not considered here.

Next, it is necessary to explain the principle of ensuring the shock-free start of the SPP microwave oscillator, which ensures its maximum sensitivity. Figure 4 shows the oscillations U _∑ in the circuit of the microwave oscillator during startup. In the time interval from 0 to t _{1, the} active microwave-AG device (microwave transistor) is turned off. There are thermal fluctuation oscillations in the circuit. At time t _1, the start-up voltage generator turns on the start-up current of the self-oscillator I _E0 , which increases exponentially. In this time interval, the current I _E0 in the circuit is excited by shock oscillations U _beats . Since the attenuation of the circuit until t ₂ remains positive over the decrementing interval, the shock oscillations decay exponentially up to fluctuation noises U _f , which in this interval are determined by the total effect of thermal fluctuations and fluctuations of the shot current of the active device. At time t _{2, the} current reaches the boundary value I _E0 = I _gr . At this point, the average value of the loop attenuation d _cp is zero. However, the effective value of the damping is determined by the effective value of the fluctuation component of the damping d _eff , which in principle cannot be equal to zero. Therefore, the passband of the NGN circuit at this moment has a minimal but finite value. If the time interval Δt = t ₂ -t _{1 is} sufficient for shock vibrations to decay to the fluctuation level U _f , then the development of self-oscillations U _ak , starting from time t ₂ , in the incremental section occurs from the fluctuation level U _f . The current of the active device then rises to the level of the starting value I _E0 = I _p . It is important to emphasize that in a transistor microwave oscillator SPP with an output average power of not more than 0.5 W, the boundary current is of the order of I _E0 = 5-8 mA, and I _{p the} starting current I _p during the receiving interval exceeds the boundary value of I _gr only tens of microamps. This mode of triggering the NGN is shock-free and fundamentally provides maximum sensitivity of the NGN to the request signal. Since the phase and amplitude of the fluctuations that determine the initial triggering conditions are random processes, the radiation spectrum of the SPP radio pulses in this case will be continuous. If the time interval ∆t = t ₂ -t _{1 is} insufficient for the damping of shock oscillations, then the development of self-oscillations U _ak SPP will be determined by shock oscillations U _beats . Therefore, the phase of the SPP radio pulses will be synchronized by shock oscillations, and the sensitivity of the SPP to an external signal will decrease sharply. The radiation spectrum of the SPP radio pulses in this case will be discrete, ruled. This trigger mode is typical for classic pulsed oscillators. It must be emphasized that further the constant component of the emitter current I _eo (and the collector current I _ko = I _eo ) changes synchronously with the amplitude of self-oscillations due to the hard nature of the transition process to maximum values, up to the establishment of a stationary mode (see Figs. 3, 4) . It should be emphasized that the stationary amplitudes A _st and I _{eomax are} practically independent of the value of the starting current I _p .

The required law of changing the shape of the pulsed current of the microwave oscillator at the time of start-up is provided by pulses of the super-voltage generated by the GSN emitter follower (see figa, b).

To explain the features of adjusting the radiation frequency relative to the reception frequency, Fig. 5 (a) shows the dependence of the frequency change of the microwave oscillator in the process of establishing the amplitude of self-oscillations A for different operating modes of the SPP. The reception frequency f _pr corresponds to the frequency of self-oscillations at the time of starting the SPP with an amplitude of A = 0. In figure 3, this mode corresponds to the moment t ₂ . The carrier emission frequency f _rad CPR steady oscillations corresponds to the frequency at A = _v. Under the condition f _CR = f out of _{2, the} reception frequency and the transmission frequency of the NGN coincide. Under the conditions f ≤f _{straight rad rad 2} and f ₃ ≤f _straight carrier frequency will be higher or lower than the reception frequency CPR. Essentially, the reception frequency f _pr is determined by the resonant frequency of the oscillatory system of the microwave-AG at the time of starting the SPP. Further, the process of establishing the frequency of self-oscillations is determined by the dependence of the integrated reactive parameters of the active device on the amplitude of the currents and voltages in the microwave-AG circuit. As noted earlier, in the SPD, the direct current of the microwave transistor I _eo changes synchronously with the amplitude of the high-frequency oscillations of Fig. 5 (b). Therefore, the adjustment of its stationary value I _{eo st} allows you to effectively control the frequency of steady-state oscillations relative to the reception frequency f _pr The simplest way is to control the pulse value of the current I _{eo st} by adjusting the pulse current of the control electrode of the active device (base current of the microwave transistor) by changing the output resistance of the generator of the super-voltage. In Fig.7, the output resistance of the generator of the supervising voltage (the output of the emitter follower VT1) is adjusted by the resistor R2. An increase in the resistance R2 leads to a decrease in the pulse current I _{eo st1} and a corresponding increase in the carrier frequency of the SPP radio pulses to the position f _pr <f ₁ . The decrease in resistance R2 allows you to combine the frequency of reception and radiation f _CR = f ₂ when I _{eo st2} or to set the frequency of radiation below the frequency of reception f _pr > f ₃ when I _{eo st3} . The reception frequency f _pr is determined by tuning the resonant frequency of the oscillatory system of the microwave-AG at the time of starting the SPP. Thus, by adjusting the amplitude of the video pulses of the current of the active device (microwave transistor) by changing the output impedance of the super-voltage generator R2, it is possible to control the relative position of the receive and transmit frequencies of the SPP with the necessary accuracy. In this case, the radiation power of the SPP practically does not change. However, to maintain the optimal value of the time constant of the auto-bias circuit - 5, which is necessary for the formation of a response signal in range - a "response pause", it is necessary to carry out an appropriate selection of the capacitor C4.

As shown above, to achieve maximum sensitivity, it is necessary to ensure shock-free start-up of a microwave SPP self-oscillator. In practice, this is achieved by adjusting the time constant τ = R1C1 - low-pass filter formed by the resistor R1 and capacitor C1 at the input of the emitter follower VT1 GOS (Fig.7). An increase in the resistance of the resistor R1 leads to a decrease in the steepness of the voltage increase at the input of the microwave oscillator (see Figs. 4 and 6) and a decrease in the level of shock vibrations. However, in this case, the effective duration of the superimposing pulses decreases and the amplification of the SPP decreases, which is proportional to the average delay time τ _s , see relation (2). To restore the necessary level of amplification of the SPP, it is necessary to increase the duration of superimposing pulses accordingly. A decrease in the resistance of the resistor R1 leads to an inverse change in the parameters of the SPP. With the optimal value of the time constant τ = R1C1, the maximum sensitivity and amplification of the SPP are achieved, including in the “response pause” mode. Another option for adjusting the sensitivity and amplification of the SPP can be implemented in principle by changing the duration of the superimposing pulses, as shown in Fig.6 (b). It should be emphasized that the frequency of the SPP radiation does not change when adjusting the sensitivity of the receiving mode.

Actually the work of the NGN as part of the radio system is described in detail in the above patents of the Russian Federation and the works of the same author, and therefore is not repeated in the description of this application.

The proposed method of setting the parameters of the SPP allows you to guarantee the production of SPP radiosondes on modern microwave transistors with a sensitivity of minus 95 ÷ 100 dB / W with an average radiation power of 250 ÷ 350 mW and efficiency not less than 35%. This ARZ transceiver provides accurate measurement of the slant range of a ground radar up to 250-300 km with an accuracy of at least ± 15 m, with a low level of request power of the ground radar. So, the radar transmitter pulse power is 200 W, the average is 0.2 W. ARZ telemetry signals are transmitted by frequency or phase modulation of superimposing pulses, i.e. at one carrier frequency all ARZ coordinates are measured: elevation, azimuth, slant range - and meteorological values are transmitted telemetric signals. Ultimately, the use of NGN as part of the ARZ can significantly reduce the cost of obtaining aerological information on the Roshydromet network of the Russian Federation.

Literature

1. Ivanov V.E., Fridzon M.B., Yesyak S.P. “Radiosounding of the atmosphere, Technical and metrological aspects of the development and application of radiosonde measuring instruments”, ed. V.E. Ivanova. Yekaterinburg. UrB RAS. 2004.596 s. ISBN 5-7691-1513-0.

2. Superregenerators. M.K. Belkin, G.I. Kravchenko, Yu.G. Skorobutov, B.A. Stryukov; Edited by M.K.Belkin. - M .: Radio and communications, 1983 .-- 248 p., Ill.

Claims (1)

A method for adjusting the output parameters of a super-regenerative radiosonde transceiver, based on the optimal choice of the feedback coefficient of the super-regenerative transceiver auto-generator, load resistance, resonant frequency of the oscillating system, characterized in that when the super-regenerative transceiver auto-generator is started, they provide a self-excitation mode with a rigid nature of the transition process of establishing self-oscillations, stabilize the average current and active supply voltage Ora of the self-oscillator of the super-regenerative transceiver, regulate the pulse current of the control electrode - the base of the transistor of the active device of the self-generator, thereby establish the frequency of reception relative to the carrier frequency of self-oscillations of the super-regenerative transceiver, by adjusting the slope of the exponentially rising leading edge and the duration of the super-generating pulse, set the required sensitivity level of the super-regenerative receiver.

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