RU2129746C1 - Plane collapsible double-input antenna - Google Patents

Abstract

FIELD: transceiving equipment of radio-communication systems including space communication and television systems. SUBSTANCE: antenna has two antenna panels with alternating rectangular and U-shaped radiating waveguides for transmitting and receiving channels, respectively, provided with transverse and longitudinal slots, respectively. Dumbbell-shaped transverse slots are fed in traveling- wave mode by pairs of asymmetric capacitive diaphragms placed on opposite wide walls of rectangular radiating waveguide. Changing magnetic field position every half-wave is effected by reversing shift sign of capacitive-diaphragm pairs which provides for in-phase excitation of all dumbbell-shaped radiating slots. Changing diaphragm size ensures single-ended matching of each slot and distribution of slot excitation intensity decaying to ends, as well as desired level of directivity pattern side lobes of antenna. Rectangular radiating waveguides are fed in their center through longitudinal dumbbell- shaped slots coupled with rectangular waveguide feeds of same width which are combined by E-adders placed on second tier of antenna panel. Longitudinal radiating slots are alternately shifted towards two side walls of U-shaped radiating waveguide. Single-ended matching of each longitudinal slot is provided by asymmetric capacitive and inductive diaphragms as well as by slot on partition edge. U-shaped radiating waveguide is fed from rectangular waveguide feed through transverse dumbbell slot and partition slot. Waveguide feeds and transverse feeding slots are combined by E-adders placed on second tier of antenna panel. E-adders of transmitting and receiving channels are combined by series T-junctions. When collapsed, antenna panels are arranged one on top of other. In working position, they are placed on same plane immediately adjacent to each other. EFFECT: improved level of directivity pattern side lobes. 17 dwg

Description

 The invention relates to antenna technology and can be used in transceiver radio communication systems for various purposes, including navy communication.

For transceiver communication systems (VSAT), flat antennas (PA) must have two inputs and receive signals of the f ₁ range in one polarization, linear or circular, and emit signals in the f ₂ range in another polarization orthogonal to the first. Communication systems with pairs of frequency ranges (F ₁ / f ₂ ) 4/6 GHz (C-band) and 12/14 (Ku-band) have been mastered, and the high-frequency range for terrestrial antennas is transmitting.

For the transmission channel, the PA radiation pattern should be characterized by a rapid decrease in the level of the side lobes with an increase in the angle θ, measured along the normal. For PAs, international standards (for example, GSS 25209a) establish the requirement that the antenna gain G (θ) not exceed at least 90% of the side lobes 52 - 10lg D / λ - 25lg θ in a wide range of angles (usually 3 ^o <θ <48 ^o ), where D is the size of the PA, λ is the working wavelength.

 In mirrored antennas (ZA) with round parabolic mirrors, the requirements for side lobes are fulfilled for D / λ> 30. For Ku-band this corresponds to D> 60 mm. In ZA with D / λ <30, these requirements usually cannot be fulfilled due to the influence of the irradiator and the absence of a mechanism in parabolic antennas for regulating the amplitude distribution of fields over the opening of a parabolic mirror.

 In PA, in contrast to ZA, a decrease in the level of side lobes at any D / λ can be achieved by introducing an amplitude field distribution that decreases to the antenna aperture. The operating frequency band required for satellite communication systems when receiving and transmitting Δ f ≈ 500 MHz is realized for any D / λ in a PA with parallel emitters and for D / λ <10 - 15 for a PA with sequential emitters.

Known multi-layer two-input PAs with parallel emitters (BAS-50 antennas made in Germany, a similar solution: EP 0345454, H 01 Q 21/00), designed to receive television signals of arbitrary polarization. In PA there are 6-7 metal printed layers separated by dielectric layers. Two layers contain binary strip dividers and strip emitters. The layers are rotated by 90 ^o and emitters with orthogonal polarization are in the area of the holes in other metal layers. The system forms emitting channels with orthogonal field polarizations in the PA. The disadvantages of printed PAs include significant losses in strip lines, which reduces the gain G and the parameter G / T of the antenna, where T is the noise temperature. PA BAS-50 (the area of the emitting cloth 500 x 500 mm ² ) has a value of G / T = 11 dB / K, which is significantly lower than the values of G / T ≈ 12 - 14 dB / K achieved for single-input PAs of the same area. Multilayer PAs have significant weight (6.5 kg for the BAS-50 antenna) and are of great value.

 The best values of the G / T parameter and the lower weight are for two-input PAs with sequential powering of emitters based on a plane multimode waveguide filled with an insulator with ε = 14 - 25, with two systems of orthogonal radiating slots on the upper metal board of the multimode waveguide, fed in series with two orthogonal plane waves . The waves are excited by horn-parabolic pathogens of the “pilbox” type. A known variant of such a PA with two pathogens "pilbox" and identical transverse resonant slots (application WO 91/17586, H 01 Q 13/20, 13/22). Such a PA has insufficient broadband (Δf <500 MHz at D> 400 - 500 mm) and does not have constructive tools for introducing a decreasing amplitude distribution and reducing the SWR due to the in-phase addition of reflections from transverse resonance slots (the "normal" effect). A known version of the PA with four pathogens "pilbox" and a pair of non-resonant slots, which allows to double the broadband and weaken the effect of the "normal" (patent RU 2099832 C1, H 01 Q 13/20). In PA with D / λ> 15 for geometry violations, a decrease in the antenna gain G is observed due to the instability of the amplitude-phase distribution of the fields. A known option is the construction of a two-input PA (application WO 95/15592, H 01 Q 21/00), in which the instability effect is eliminated based on the layout of the aperture of the PA from parallel waveguides of two types, rectangular and U-shaped sections containing respectively transverse and longitudinal resonant radiating cracks. The excitation of each transverse gap located on the narrow wall of the rectangular waveguide and partially on the adjacent wide walls of the rectangular waveguide is carried out by two thin wires having different inclination on both sides of the gap, which creates a transverse component of the magnetic field along the gap. The alternating change in the orientation of the tilt of the pairs of wires in adjacent slots makes it possible to excite in phase all the transverse slots of the PA line at a distance between adjacent transverse slots approximately equal to half the wavelength in a rectangular waveguide.

 The in-phase excitation of the longitudinal slits in the U-shaped waveguide is achieved by the transverse displacement of the slots on both sides of the neutral of the P-waveguide at a distance between adjacent longitudinal slots equal to half the length in the U-shaped waveguide. The above application can be considered as a prototype of the proposed technical solution. The prototype, however, does not solve the most important tasks that make it possible to use it for the design of satellite communications satellite. There are no tools in the prototype: for one-sided matching of slits, for implementing a decaying amplitude distribution in the traveling wave mode, for expanding the operating frequency band, for constructing folding (case) PAs, for realizing PAs in Ku- and shorter wavelength ranges.

In FIG. 1 shows the proposed construction option of a folding two-input PA, in which the disadvantages of the prototype are eliminated. PA with dimensions L x L x H consists of two antenna panels with dimensions L x L / 2 x H, articulated in the S plane (see Fig. 1a, b). The panels can rotate around an axis 7 lying in the plane S. In the intermediate state, the PA is shown in FIG. 1c, when folded, in FIG. 1d. Each PA panel consists of a layer of radiating waveguides (IV) 1 and a layer of exciting waveguides (BB) 2. Layer 2 (see Fig. 1a) contains a channel input flange 3 λ ₂ , channel input flange 4 λ ₁ , connecting waveguides 11 and 12 (channel λ ₂ ), 13 and 14 (channel λ ₁ ), flanges 5, 6 of the joint of the waveguides, E-adders 8, 9 of the explosive channels λ ₁ and λ ₂ , the overlap section of the explosive 10. The length of the waveguides 11, 12 and 13, 14 up to E-tees 15 and 16 are chosen equal. In FIG. 2 shows a device layer IW 1. For channel λ ₂ used a rectangular cross section IV ₂ • b ₂ to the orientation of the electric field E ₂ along axis X. For channel λ ₁ using U-shaped cross section IV a ₁ • h _2, containing a metal baffle 17 height h ₁ . The electric field E ₁ in the U-shaped ИВ is oriented out of phase with respect to the partition 17, which provides in-phase feeding of the longitudinal radiating slits (IS) 18 displaced relative to the axis of the П-shaped ИВ through the interval d ₁ equal to half the wavelength in this waveguide. On the upper wall of a rectangular IV, there are transverse ISh 19 of a dumbbell shape. The upper metal walls of a rectangular and U-shaped ИВ form a flat radiating surface of PA 20 (see Figs. 2 and 3). The distance d between the axes is less than the minimum wavelength λ ₂ , the Electric fields E ₂ and E ₁ in the transverse 19 and longitudinal 18 ISCH, respectively, are orthogonal, which provide weak cross-polarization along the channels λ ₁ and λ ₂ .
Layer BB 2 is composed of rectangular waveguides with a cross section a ₃ • b ₂ (see Fig. 3) parallel to the waveguide and located under them. In FIG. Figure 8 shows the overlapping section of BB 10, in the center of which are located longitudinal dumbbell communication slots (AH) of channel 22 λ ₁ and channel 21 λ ₂ , exciting U-shaped and rectangular IVs in the central section of PA, respectively. All exciting rectangular waveguides 2 are closed at one end in a section that is offset from the center of the dumbbell transverse and longitudinal exciting slots along the axis of these waveguides: one way for exciting waveguides with a transverse slit 21 and the other side for waveguides with a longitudinal slit 22, all open the outputs are combined by E-adders 8, 9, the outputs of which are offset by a distance equal to the distance between the axes of a rectangular and U-shaped emitting waveguides. In FIG. 4 is a diagram of a cascade of a PA line with sequential switching on of resonant slots for the case of running in a traveling wave mode. In the circuit of FIG. 4 designations are used: W ₀ , θ - wave impedance and electric length of the transmission line between the ISH; r _i - active resistance of the i-th ISCH; N _i - transformation coefficient of an ideal transformer, providing one-way matching of the unit; U _i , I _i , U ' _i = U _i , N _i , I' _i / N _i - voltages and currents at the input and output of an ideal transformer; P _i , P _{i + 1} - power supplied to the input of the i-th and (i + 1) -th cascades of the line.

α_i = 1-P_i+1/P_i = Q_i/P_i, (2)
где α_i - коэффициент, определяющий долю мощности Q_i, выделяемую на сопротивлении r_i, отнесенную к подводимой к каскаду мощности P_i. Приближенно

где ε_i - напряженность электрического поля на i-й щели, A - константа для идентичных щелей в линейке.Switching the output ends of the windings of an ideal transformer makes it possible to ensure that the radiated electric field is in phase in all line arrays for the angle θ = 180 ^o . The transformation coefficient N _i is selected from the matching condition of the cascade at the input:
N $\genfrac{}{}{0ex}{}{\text{2}}{\text{i}}$ = 1 + r _i / W ₀ . (1)
The resistance r _i is determined from the relations

α _i = 1-P _{i + 1} / P _i = Q _i / P _i , (2)
where α _i is a coefficient that determines the share of power Q _i allocated to the resistance r _i , referred to the power P _i supplied to the cascade. Approximately

where ε _i is the electric field strength at the ith slot, A is the constant for identical slots in the ruler.

В (5) предполагается, что отсчет i ведется от центра линейки. Значения α_i на фиг. 6 получены для двух случаев возбуждения линейки: из центра (график П₁) и из концов линейки (график П₂). Компоновка линейки из двух частей позволяет примерно вдвое увеличить широкополосность ПА. При запитке из центра значения коэффициента α_i изменяются значительно меньше, чем для случая запитки линейки с концов ( α_i=0.02 - 1.0). Фиг. 6 иллюстрирует диаграмму направленности линейки ПА, запитываемой из центра для трех длин линейки 400, 600, 800 мм и значений параметров a₂ = 16.0 мм, d = 10.0 мм, d₂ = 14.5 мм, f_2max =145 ГГц и огибающей ε_i в соответствии с (5). Огибающая допустимого уровня боковых лепестков диаграммы направленности F ( θ ,L)=-G+52-10lg L/ λ - 25lg θ определялась для значений G=37 дБ, L=400, 600, 800 мм, λ = 21 мм. Из фиг. 6 следует, что диаграмма направленности ПА не заходит за кривую F ( θ, L) при L=400 - 800 мм. Дальние боковые лепестки существенно ниже кривой F( θ, L) и требования к спаду боковых лепестков выполняются. На фиг. 7 показана зависимость от частоты коэффициента использования поверхности ПА η с линейками вида фиг. 2 с центральной запиткой (см. фиг.5) при длине L= 600 мм, λ₂ = 21 мм для случаев распределения интенсивности электрического поля по щелям ε_i = const и c ε_i в соответствии с (5). Величина η определяется из соотношения
η = |∑ $\genfrac{}{}{0ex}{}{\text{n}}{\text{i=1}}$ ε_i|²/n∑ $\genfrac{}{}{0ex}{}{\text{n}}{\text{i=1}}$ |ε_i|² (6)
Введение косинусоидального распределения ε_i приводит к снижению η до значения 0.93 для средней частоты и до значения η = 0.64 для крайних частот f₂ = 14.25 ± 0.25 ГГц. При равномерном возбуждении щелей в режиме бегущей волны ( ε_i = const) снижение η к краям диапазона оказывается аналогичным. Таким образом, в рассмотренном варианте ПА с центральной запиткой реализуется практически одинаковое снижение η к краям полосы частот канала λ₂ как при равномерном, так и при косинусоидальной распределении ε_i в соответствии с соотношением (5). Для линеек канала λ₁ вводить спадающее распределение ε_i обычно не требуется.For a given distribution of ε _i over the gaps and, correspondingly, for a known distribution of gaps of radiated power Q, the distribution of the coefficients α _i over n cascades of the line is determined from the recurrence
α _i = Q _i / ∑ $\genfrac{}{}{0ex}{}{\text{p = n}}{\text{p = i}}$ Q _p ; α _n = 1. (4)
In (4), it is assumed that the terminal gap of the line completely radiates the power P _n supplied to it. In FIG. Figure 5 shows the dependence of the parameter α _i on i for half of the PA line with the number of slots n = 21 and the distribution of the electric field strength ε _{i / of the} form

In (5), it is assumed that the reference i is from the center of the ruler. The values of α _i in FIG. 6 are obtained for two cases of excitation of the line: from the center (schedule P ₁ ) and from the ends of the line (schedule P ₂ ). The layout of the two-part ruler allows you to approximately double the broadband PA. When washing from the center, the values of the coefficient α _i change much less than for the case of feeding the ruler from the ends (α _i = 0.02 - 1.0). FIG. 6 illustrates the directivity pattern of a PA line powered from the center for three line lengths of 400, 600, 800 mm and parameter values a ₂ = 16.0 mm, d = 10.0 mm, d ₂ = 14.5 mm, f _2max = 145 GHz and the envelope ε _i in in accordance with (5). The envelope of the permissible level of the side lobes of the radiation pattern F (θ, L) = - G + 52-10lg L / λ - 25lg θ was determined for the values G = 37 dB, L = 400, 600, 800 mm, λ = 21 mm. From FIG. 6 it follows that the PA radiation pattern does not go beyond the F (θ, L) curve at L = 400 - 800 mm. The far side lobes are significantly lower than the curve F (θ, L) and the requirements for the decline of the side lobes are fulfilled. In FIG. 7 shows the frequency dependence of the surface utilization coefficient ПА η with rulers of the form of FIG. 2 with central washing (see FIG. 5) with a length L = 600 mm, λ ₂ = 21 mm for cases of distribution of the electric field intensity over the gaps ε _i = const and c ε _i in accordance with (5). The quantity η is determined from the relation
η = | ∑ $\genfrac{}{}{0ex}{}{\text{n}}{\text{i = 1}}$ ε _i | ² / n∑ $\genfrac{}{}{0ex}{}{\text{n}}{\text{i = 1}}$ | ε _i | ² (6)
The introduction of the cosine distribution ε _i leads to a decrease in η to 0.93 for the average frequency and to η = 0.64 for the extreme frequencies f ₂ = 14.25 ± 0.25 GHz. With uniform excitation of the gaps in the traveling wave mode (ε _i = const), the decrease in η to the edges of the range is similar. Thus, in the considered version of the PA with central power supply, almost the same decrease in η to the edges of the frequency band of the channel λ ₂ is realized both with a uniform and cosine distribution ε _i in accordance with relation (5). For the rulers of channel λ ₁ , it is usually not necessary to introduce a decreasing distribution ε _i .

A constructive implementation of the central excitation of the PA line arrays of channels λ ₁ and λ _{2 is} illustrated in FIG. 8. The arrows with indices λ ₁ and λ ₂ show the exciting waveguides (BB), mated to the E-adders 8 and 9 (see Fig. 1) and forming the section 10, where the transverse dumbbell feeding slots (ZP) are located in the plane of symmetry of the PA 22, providing excitation of rectangular IW channel λ ₁ , and longitudinal dumbbell ZP 21, providing excitation of U-shaped IW channel λ ₂ . PA from IV 1 and BB 2 (see Fig. 1) is composed of three boards joined to each other in the planes S ₁ and S ₂ (see Fig. 3), which coincide with the neutrals of rectangular waveguides of width a ₂ and a ₃ .

In FIG. 9 shows the design of half the ruler of the IV channel λ ₂ with n transverse ISH. All transverse ISh 19 have a dumbbell shape with the same dimensions, except for the terminal n-th gap, the dimensions of which are slightly changed (see Fig. 9a). Index λ ₂ indicates the direction of the exciting wave supplied to the ruler from the longitudinal dumbbell ZP 21 (see Fig. 8). In FIG. 9b shows the location of the capacitive diagrams 26 and 27 near each transverse ISH in a rectangular IW of width b ₂ . In FIG. 10c shows inductive diaphragms 28 and 29 located under the IS in a rectangular IW of width a ₂ . FIG. 10a illustrates the location of pairs of capacitive 26, 27 and inductive 28, 29 diaphragms near the transverse dumbbell ISHS 19. Capacitive diaphragms 26, 27 of a height A ₁ and A ₂ are located on opposite wide walls of a rectangular VI with a width a ₂ and height b ₂ . Inductive diagrams 28, 29 with a height of h ₁ and h ₂ are located on the lower wall b _{2 of a} rectangular IW in the plane of capacitive diaphragms 26, 27. The sizes A ₁ , A _{2 of} capacitive and h ₁ , h ₂ inductive diaphragms for all transverse diaphragms are chosen different, providing distribution ε _i in accordance with (5) and with ensuring one-sided matching of each slot at the entrance in accordance with (1). The mirror shift of the capacitive diaphragms in the IW leads to the alternate rotation of the magnetic field vector of the H ₁₀ wave relative to the Z axis (see Fig. 2) in neighboring ISHs with the common-mode excitation of all transverse ISHs (field E ' ₂ in Fig. 2). In FIG. 10b shows the excitation unit in the center of the ruler with transverse dumbbell ISHs through a longitudinal dumbbell slot 21 located in the wall 30 between the rectangular IV 25 and the rectangular BB 23 (see Fig. 3). To match the device of FIG. 10b from the side of the explosive (arrow λ ₂ in Fig. 10b), inductive plane diaphragms 31 and 32 are inserted in the plane of the ZP 21. The explosive behind the dumb bar ZP 21 has a closing wall 33. All angles at the joints of the diaphragms with the walls of the waveguides are rounded (radius r = 2 mm in Fig. 10), taking into account the possibility of manufacturing PA on milling machines with program control. In FIG. 11a, b shows the construction of a ruler with longitudinal IS 18 based on a U-shaped ИВ and the excitation unit of a П-shaped ИВ through a transverse dumbbell slit 22 connecting a rectangular BB a ₃ • b ₂ (see Fig. 3) through a wall 24 with П- figurative IV channel λ ₁ with dimensions a ₁ , h ₁ and h ₂ (see Fig. 2). The arrow with the index λ ₁ in FIG. 11a shows the direction of the exciting wave supplied to the ruler. Approximation elements are introduced near each longitudinal ISh 18: asymmetric capacitive diagram 34 placed on the side surface of the metal partition directly below the longitudinal ISh 18, asymmetric inductive diaphragm 35 in the plane of the asymmetric capacitive diaphragm 34 at the bottom of the U-shaped ИВ, transverse groove 36, placed on the upper the edge of the dividing wall at a certain distance from the longitudinal ISCH 18. The sizes of the diaphragms 34, 35 and the groove 36 are chosen different for different longitudinal ISH so as to ensure the required the available distribution ε _i = const and was ensured in accordance with (1) and (4) the one-sided matching of each IS. To match the node of FIG. 11a, two pairs of asymmetric capacitive diaphragms 37 and 38 placed in pairs on opposite wide walls of the explosive are inserted into a rectangular explosive with a transverse dumbbell ЗЩ 22 from two sides of this gap. Behind the dumbbell diaphragm 22, a closing wall 39 is inserted into the BB. A groove 41 is inserted into the dividing wall of the U-shaped IV above the dumbbell bar ZP 22 along the entire height of the dividing wall 40, the width of which increases in steps from the base of the BB to the upper edge of the dividing wall. In FIG. 12 and 13 show the calculated radiation patterns in the Y plane for the extreme frequencies of the range 13.9 and 14.6 GHz Pa with dimensions of 600 x 600 mm ² formed from 30 rulers of the form of FIG. 10a with a distance between adjacent rulers 2d = 20mm (see figure 2). The influence of the waveguides of the channel λ _{1 /} on the radiation patterns of the channel λ ₂ was negligible. Envelopes F (θ, L) = -G + 52-10lgL / λ - 25lg θ at g = 34 dB do not intersect the side lobes of the radiation pattern, with the exception of individual lobes for the frequency f = 13.9 GHz (see Fig. 12a, b) . The PA radiation pattern in the X plane (Fig. 12c) has a first side lobe at 13 dB. The cross-polarization component (field E _x in Fig. 12d) has side lobes at a level of - 30 dB for angles θ = ± 43 ^o and at a level of 48 dB for angles θ <15 ^o . In FIG. 14 shows the distribution of | ε _i | and arg φ _i along the transverse LH lines for the extreme 14.6 GHz (Fig. 14a) and the average 14.3 GHz (Fig. 14b) channel frequencies λ ₂ . The input coefficient of the standing wave at the input of the PA channel λ ₂ does not exceed 1.8. In FIG. 15, for λ ₁ = 25 mm, the calculated radiation patterns of PAs with dimensions of 600 x 600 mm ² with the number of rulers 30 on the basis of U-shaped ИВ (see Fig. 11) and equal-amplitude longitudinal excitation of the longitudinal IS in the traveling wave mode are shown. The level of the first side lobe of the radiation pattern for the X and Y planes at the level of - (13 - 15) dB (Fig. 15a, b, c). The cross-polarization component (field E _y in Fig. 12d) is at the level of - 42 dB for θ <15 ^o and at the level of 12 dB for θ ≈ 57 ^o . The standing wave coefficient is 1.12. In the frequency range of the channel λ ₁ (λ = 24.5 - 25.5 mm, see Fig. 16.17) in half-length rulers, while maintaining equal-amplitude excitation, a slope of the phase distribution over the slots occurs. Changes in the phase slope leads to a decrease in η to approximately 0.5 for the extreme frequencies of the channel λ _1.

Claims (1)

A flat two-input folding antenna containing alternating parallel rectangular emitting and U-shaped radiating waveguides with transverse and longitudinal radiating slots, respectively, characterized in that the antenna is divided into two antenna panels containing an equal number of rectangular radiating waveguides and U-shaped radiating waveguides, narrow walls rectangular radiating waveguides and the walls of the U-shaped radiating waveguides located above the dividing wall form a flat radiating surface antenna surface, transverse radiating slots are dumbbell-shaped, longitudinal radiating slots are displaced from the dividing wall alternately to the two side walls of the U-shaped radiating waveguide, a pair of asymmetric capacitive diaphragms with different diameters is inserted from both sides of each transverse radiating slit various transverse radiating slits with a width, thickness, and an offset from the center of this gap placed on opposite wide walls of a rectangular radiating waveguide, in the planes of asymmetric capacitive diaphragms, asymmetric inductive diaphragms are introduced into the rectangular radiating waveguide, located
on a narrow wall of a rectangular radiating waveguide that does not contain transverse radiating slits, asymmetric capacitive diaphragms between two adjacent transverse radiating slots are located on the same wide wall of a rectangular radiating waveguide, in the sectional plane of a U-shaped radiating waveguide that coincides with the center of the longitudinal radiating slit, an asymmetric capacitive diaphragm with a width and thickness variable for different longitudinal radiating slots is introduced, located on one of the lateral surfaces of the dividing wall of the U-shaped radiating waveguide, which is located under the longitudinal radiating slot, in the plane of the asymmetric capacitive diaphragm at the bottom of the groove formed by the side wall of the U-shaped radiating waveguide and the lateral surface of the dividing wall of the U-shaped radiating waveguide, on which the asymmetric capacitive diaphragm , an asymmetric inductive diaphragm with a width and a thickness variable for different longitudinal radiating slots is introduced, on the upper edge there is a section The transverse grooves are made of the partition wall of the U-shaped emitting waveguide, the depth and offset of which from the center of the longitudinal emitting slots are selected different for different longitudinal emitting slits of the U-shaped emitting waveguide, each rectangular emitting waveguide is closed at the ends and excited in the center through a dumbbell longitudinal exciting slit, which is located in a narrow wall of a rectangular radiating waveguide that does not contain transverse radiating slits, each U-shaped radiating waveguide behind whip at the ends and in the center is excited via the exciting dumbbell transverse slit which is located in a narrow wall of the U-shaped radiating waveguide that are free of longitudinal radiating slots in each rectangular
an excitation waveguide with a dumbbell transverse excitation gap, two pairs of asymmetric capacitive diaphragms are introduced on two sides of this gap, displaced relative to each other along the axis of this waveguide and located pairwise on opposite wide walls of a rectangular excitation waveguide, in the dividing wall of the U-shaped radiating waveguide above the dumbbell transverse an exciting gap is made along the entire height of the dividing partition groove, the width of which increases in steps from the base to the upper edge On the narrow walls of a rectangular emitting waveguide and a rectangular excitation waveguide that does not contain a dumbbell longitudinal excitation gap, asymmetric inductive diaphragms are introduced in the plane passing through the center of the dumbbell longitudinal excitation gap, all excitation rectangular waveguides are closed from one end in a certain section which is offset from the center of the dumbbell transverse and longitudinal exciting slots along the axis of these waveguides in one direction for exciting straight Golnaya waveguides with a dumbbell transverse excitation gap and the other way for exciting rectangular waveguides with a dumbbell longitudinal excitation gap, all open outputs of the excitation rectangular waveguides with dumbbell transverse excitation slits and all open outputs of the exciting rectangular waveguides with dumbbell longitudinal excitatory excitation the outputs of which are offset by a distance equal to the distance between the axes of a rectangular and U-shaped radiating waveguides, the waveguide outputs of the E-adders of two antenna panels are joined by E-tees located on one of the antenna panels, the output waveguides of which are the antenna inputs, and connecting waveguides of equal length, one of which contains a flat waveguide contact flange, the plane of which coincides with the junction plane antenna panels, at the intersection of the junction plane of the antenna panels and the flat radiating surface of the antenna there is an axis around which the antenna panels rotate relative to each other , providing folding and deployment of the antenna.

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