RU2016494C1 - Television system - Google Patents

Abstract

FIELD: color television. SUBSTANCE: E_m(t) is formed with the use of reflex-modulated signals E₃(t). Quadrature modulation of subcarrier in phase 0 and ± Π/2 is performed with video signals E_1-1(t), E_1-2(t) at transmitting site forming reflex-modulated signals E₃(t) on subcarriers which selection of frequencies f provides for required deferences of phase on subcarriers in adjacent lines of one frame and in lines of contiguous frames identical by numbers. Formed reflex-modulated signals are transmitted within time intervals of full color TV signal assigned for them. During reception elements of reflex-modulated signals E_m(t) are isolated from full color TV signal E₃(t), are delayed by time intervals multiple of duration of television scanning, delayed and undelayed elements are multiplied by harmonic signals U₁(t), U₂(t), video signals E_1-1(t), E_1-2(t) are algebraically summed up and isolated from signals obtained with summing. EFFECT: enhanced volume of information transmitted by full color TV signal, improved noise immunity of transmitted information. 21 cl, 21 dwg

Description

 The invention relates to the field of communications systems, in particular to telecommunications.

 Broadcast television systems use two methods of compressing signals containing information on the brightness and color of images - frequency and time. In frequency division multiplexing, the color signal, which is the product of modulation of the color subcarrier by color difference signals, is transmitted within the frequency spectrum of the luminance signal. This method is used in standard broadcast television systems NTSC, SECAM, PAL (C. C. I.) Report 407-1, 1966-1970). The advantage of the frequency compression of luminance and color signals is the relative simplicity of the decoding device in the TV, which was especially important at the level of technology that existed in the initial period of introduction of color broadcasting (1950-1960). However, with frequency multiplexing, the quality of color images is significantly reduced due to crosstalk between luminance and chrominance signals. Significant suppression of this interference is achieved, as a rule, by reducing the resolution in the spatial and temporal regions. So, for example, the comb filtering method, by summing the signals of adjacent frames, provides complete suppression of crosstalk between luminance and color signals only on fixed portions of images, and in NTSC for this it is necessary to sum the signals of two adjacent frames, in PAL - four, in SECAM - up to six frames. Comb filtering by summing adjacent in time and space signals of the lines leads to a decrease in the horizontal and vertical clarity. The placement of the frequency components of the chroma signal in the high-frequency region of the spectrum of the full color television signal determines the increased sensitivity of the signals of standard rotary television systems to uneven frequency and phase characteristics of the path, to noise interference with a quadratic spectral density, to distortions of the type "differential amplification" and "differential phase" . With this in mind, for high-quality systems, as well as for future high-definition television systems - HDTV, it is proposed to use a temporary method of compressing signals containing information about luminance and color, transmitting these signals in a row interval sequentially.

For a high-quality television system without changing the number of lines Z of decomposition and frame rate f _p, a number of variants of the direct satellite broadcasting system MAC (Multiplexed Analogue Component, CCI R, Report AB / 10-11, 1983-1986) are proposed. In the MAC system signal line, one of the color difference signals with a compression ratio in time of 3: 1 and a luminance signal compressed in time by 1.5 times are transmitted in the active part of the line, and color difference signals are transmitted alternately through the line. To preserve brightness clarity, an extension of the frequency band of the full color television signal by 1.5 times is required. Since such an extension of the frequency band is permissible only in newly organized satellite broadcasting channels, the MAC-D2 option was also proposed, the full color signal frequency band in which corresponds to the standard for terrestrial broadcasting, but the horizontal luminance clarity is 1.5 times lower, respectively.

 In other methods of temporary compaction, the luminance signal without changing its time scale is proposed to transmit in the entire active interval, and color-difference signals compressed in time, in part of the blanking interval. Such proposals include, for example, Japanese patent N 51-48623, cl. 97 (5), H11 (9), 1976, MUSE system (NHK Tech. Report, 1984, Vol. 27, N 7, p. 19; IEEE trans., 1987, Vol. BC-33, N 4, p. 130), an HDTV system with temporary compression of the luminance signal and color-difference signals (Electronics 1983, Vol. 56, No. 14, pp 82-84). In all these systems, the transmission of color difference signals is carried out alternately, for example, the color difference signal "R-Y" is transmitted in one line in the blanking interval, and the color difference signal "B-Y" is transmitted in the blanking interval of the next scan line.

 An important advantage of systems with temporary compaction of luminance and color-difference signals is the complete absence of crosstalk (interference) between these signals, which is less than that of standard broadcast systems, sensitivity to uneven frequency and phase characteristics of the communication channel, and noise interference with quadratic spectral density. At the same time, the sequential transmission of color-difference signals is noticeably inferior to their simultaneous transmission in terms of noise immunity, as well as the visibility of noise on the screen due to the enlargement of their vertical structure, the color-difference signal and noise transmitted in the previous line are repeated in the next line. In alternate transmission, flicker of brightness and color occurs at the horizontal boundaries between the color details of the images. You can completely eliminate these flickers only by stopping the structure of the transmission of color-difference signals, as was done in MAC, the odd-numbered lines always transmit the same color-difference signal by name, for example, "RY", in even-numbered lines - another color-difference signal "BY", so each frame begins with a “RY” transmission. But this leads to a noticeable and irreparable decrease in vertical color clarity, which is especially true when transcoding into signals of standard broadcasting systems. In addition, since “R-Y” and “B-Y” can have significantly different ranges, their nonlinear distortions in the transmission channel lead to irreparable color tone distortions, and the relationship between “R-Y” and “B-Y” is violated. Similar difficulties are encountered in solving problems of reducing the speed of the digital stream when transmitting color-compressed color-difference signals sequentially in the paths of digital communication lines. Due to the differences in the “R-Y” and “B-Y” ranges, encoding of the high-frequency components of color difference signals with a small number of levels can lead to color fringes.

 Until now, acceptable methods for simultaneously transmitting two color difference signals in blanking intervals have not been known.

 The arc circle of issues is related to the need to increase the amount of information for the transmission period of a line, field, frame of a television scan. These tasks arise during the development of new systems - with a change in the frame format to 16: 9, with the transmission of two color images in real time, the transmission of high-definition images. Changing the image format from the existing 4: 3 to 16: 9 while maintaining the same sharpness horizontally and vertically as in existing broadcast systems requires an extension of the frequency band of the full color television signal by one third. The transmission of two color images, for example, in a stereo color television system with the same sharpness and with the same methods of generating a full color television signal as in existing broadcast systems, requires a 2-fold extension of the frequency band while maintaining the 4: 3 format and 2.67 times when switching to 16: 9 format. The transition from existing television standards of 525 lines x 60 fields (30 frames) and 625 lines x 50 fields (25 frames) to high-definition television systems using existing methods for generating a full color television signal requires a significant expansion of the frequency band.

So, in a Japanese HDTV system with temporary compression of the luminance signal and color difference signals with the number of decomposition lines 1125, the number of fields 60 (30 frames), the aspect ratio 16: 9, the full band with an equivalent increase in the horizontal and vertical definition would be 33.75 MHz s taking into account the values of the Kell coefficient adopted in different countries - from 25.8 to 31.1 MHz, i.e. ≈ 5-6 times wider than in existing standard systems. Reducing the frequency band in this system to 20 MHz, as proposed by Japanese experts, provides horizontal clarity taking into account a format change of up to 16: 9 compared to:
- with a 525 x 60 system - 1.56 times higher (vertically 1.96 times higher) with a 4.76-fold extension of the frequency band;
- with a system of 625 lines of standard 4: 2: 2 (analog studio code base) - 1.16 times higher with a frequency band extension of 3.48 times;
- with a system of 625 lines of OIRT - 1.11 times higher, the frequency band - 3.33 times. Vertical clarity is 1.8 times higher than 625-line systems.

 Since there are no dedicated channels for transmitting a full color television signal with a bandwidth of 20 MHz in the frequency ranges mastered for television broadcasting, the time-division HDTV system was modified into the MUSE system, which should be considered as a MUSE method for transmitting time-division HDTV signals. In the MUSE system, the frame rate is 15 Hz at a field frequency of 60 Hz, i.e. each frame consists of four fields, interlaced scanning is used in combination with an interlaced raster. In each field, 562.5 lines are transmitted with a duration of 29.63 μs, the number of lines played on the screen is 1125 (in the active part of the frame, 1035 lines). The bandwidth of the full color signal is 8.1 MHz. In each transmission line, 374 independent brightness elements may be transmitted. To reproduce one line of the image on the screen, the signals of two transmission lines (from two fields) are used, i.e. 748 independent samples of the luminance signal input.

66667 мкс. В этом случае число строк передачи в одном кадре, определяемое (Recomendation N 476 C. C. I. R) как отношение частоты f_н строк к частоте f_р кадров, составляет 2250. При этом, если в исходном изображении при числе строк разложения 1125 и числе кадров 30 в секунду, число независимых отсчетов (элементов) яркости, например, составляет в активной части строки и в активной части кадра, а также в секунду - при полосе частот сигнала яркости 33,75 МГц: в строке - 1560, в кадре - 1,61x 10⁶, в секунду ≈ 48,44 ˙10⁶; при полосе частот сигнала яркости 20 МГц, соответственно, эти цифры ≈ 924, ≈0,957 ˙10⁶, ≈ 28,7 x 10⁶; при сокращении полосы частот до 16,2 МГц: ≈748, ≈ 0,775 ˙10⁶,≈ 23,25˙ 10⁶. При воспроизведении изображений по системе MUSE число независимых элементов яркости на экране должно восстанавливаться из переданных в двух строках 2 х 374=748, переданных за кадр - 0,774 ˙10⁶, переданных в секунду - 11,61 ˙ 10⁶ отсчетов сигнала яркости.Thus, with the number of lines of decomposition of 1125 in one frame of a frequency of 30 Hz on the transmitting side (frequency of lines of 33,750 Hz), the number of lines of transmission in a full color television signal doubles by reducing the frame rate from 30 to 15 Hz while maintaining the line frequency. Indeed, the frame period, i.e. the time after which information about the same image point is transmitted in the MUSE system is a period of four fields, which corresponds to

66667 μs. In this case, the number of transmission lines in one frame, defined (Recomendation N 476 CCI R) as the ratio of the frequency f _n lines to the frequency f _p frames, is 2250. Moreover, if in the original image with the number of lines of decomposition 1125 and the number of frames 30 in second, the number of independent samples (elements) of brightness, for example, is in the active part of the line and in the active part of the frame, and also per second - with a frequency band of the luminance signal of 33.75 MHz: in the line - 1560, in the frame - 1.61 x 10 ⁶ , per second ≈ 48.44 ˙10 ⁶ ; with a frequency band of a luminance signal of 20 MHz, respectively, these figures are ≈ 924, ≈0.957 ˙10 ⁶ , ≈ 28.7 x 10 ⁶ ; when reducing the frequency band to 16.2 MHz: ≈748, ≈ 0.775 ˙10 ⁶ , ≈ 23.25 ˙ 10 ⁶ . When playing back images by MUSE system, the number of independent elements on the screen brightness should recover from transmitted in two lines 2 x 374 = 748, transmitted per frame - 0,774 ˙10 ⁶ transmitted per second - 11,61 ˙ June ¹⁰ samples the luminance signal.

 The theoretical clarity limit in MUSE is 748 luminance elements per line, but in practice, losses are inevitable with an interdigital raster, it is impossible to synthesize a filter with an infinitely steep drop in frequency response. So, for example, when using the studio's digital code 4: 2: 2, the loss is about 17%. Even if we assume that when playing back the images of the MUSE system, the losses will be 5-10%, then the horizontal clarity, taking into account the change in the aspect ratio from 4: 3 to 16: 9 in MUSE, compared to standard broadcast systems of 625 lines, will be compared to a system of 625 lines, the frequency band of the brightness signal Δ F = 5 MHz (standard G CCI R) - 0.97-1.03 (theoretical limit of 1.08); in comparison with the system of 625 lines, Δ F = 5.5 MHz (England) - 0.88-0.93 (theoretical limit of 0.98); in comparison with the system of 625 lines, Δ F = 575 MHz (analog base of studio code 4: 2: 2) -0.84-0.9 (theoretical limit of 0.94); in comparison with the system of 625 lines, Δ F = 6 MHz (O. I. R. T and France) - 0.81-0.85 (theoretical limit of 0.9). Moreover, the indicated values are achieved in the MUSE system only for the motionless plot details, for moving objects the horizontal clarity in MUSE is significantly lower.

It is believed that due to the high correlation of adjacent frame signals, reaching 100% for brightness signals on the motionless plot details, a decrease in frame rate is quite acceptable, it is nothing more than a decrease in the redundancy of a television signal. As for the “smearing of transitions” for moving scenes that occur when the number of frames is reduced from 30 to 15 per second, MUSE uses special measures to compensate for this undesirable effect (the so-called “motion detector” system), which corrects the blurring of the boundaries of moving objects beyond by reducing spatial clarity of images. At the same time, reducing the frame rate from 30 to 15 Hz on the transmitting side and repeating each element on the receiving side to restore the frame frequency of 30 Hz (the requirement of no flickering) increases the visibility of noise on the receiving screen by about 7.7 dB. Taking into account the expansion of the frequency band to 8.1 MHz, the noise immunity in MUSE is much lower compared to existing broadcast television systems, the allowable noise power in the communication channel with frequency modulation (transmission via satellite) is an order of magnitude lower. But even for such an image, it is necessary to transmit a volume of information that cannot be transmitted by the most broadband color television signal of existing broadcast systems. The system signal has 625 lines, 25 frames Δ F = 6 MHz, the active part of the line is 52 μs, the number of active lines in the frame is 575, only 8.97 × 10 ⁶ independent brightness elements per second can be transmitted (625 in the active part of the line , ≈ 0.359 ˙10 ⁶ in the active part of the frame), i.e. about 77.3% of what is required in MUSE and about 3.2 times less than in an HDTV system with 1125 lines with a frame frequency of 30 Hz and a signal frequency band Δ F = 20 MHz.

 Thus, to create high-quality television systems, and even more so to create new broadcast systems (stereo color television, HDTV), it is necessary to increase the amount of information transmitted by a full color television signal. It is practically unrealistic to use for this a proportional extension of the signal frequency band when broadcasting to television receivers in the mastered frequency ranges. In this case, it would be necessary to reduce the number of programs and change the entire frequency plan, since in these ranges all channels are distributed and used, and they are designed to transmit a signal with a maximum frequency band of about 6 MHz (at a high frequency, the channel band of the terrestrial channel is about 8 MHz for the most broadband at the satellite channel FM-27 MHz.

Another way is to transmit additional information by eliminating redundancy in the television signal. Such methods implemented for broadcast systems include:
- transmission of color signals in the frequency band of the luminance signal by frequency multiplexing (NTSC, SECAM, PAL, MAC-60, for example),
- alternating transmission of signals containing color information (SECAM, MAC, MUSE, HDTV 1125 x 60 x 2: 1, for example),
- reduction in frame rate (MUSE, HD-NTSC with an interventional raster, for example).

 A number of aspects of the influence of these technical solutions on the quality and noise immunity of images were considered above.

The third way is to reduce the frequency band of the information signal without reducing redundancy. In television, the possibility of such a technical solution was paid attention to when developing the PAL system. Theoretically, a method for transmitting and decoding a quadrature modulated signal by two definitely formed signal bursts with partial and even complete suppression of one sideband is theoretically possible. the frequency band was exchanged for the transmission time, which was partially used when transmitting color signals to PAL. However, such an exchange is quite effective in practice even in conditions of a high degree of correlation of television signals in adjacent frames, especially when temporarily compressing the luminance and color signals. What is required is not partial, as in PAL color signals, but almost complete suppression of one sideband, since when temporarily compressing quadrature modulated color signals with luminance signals, the subcarrier frequency must be very low. This could be done in practice by using almost perfect filters, since the width of the spectrum of television signals is measured in megahertz and there are “zero” frequencies in them. Therefore, to effectively suppress one sideband, filters would be required with a bandwidth of the order of several megahertz and with a slope of tens of decibels per unit or tens of kilohertz. When restoring the signal from the quadrature modulation on the low frequency subcarrier and suppressed one side - reverse shift it to the RF carrier heterodyning except such nearly ideal filter would be required as almost ideal phase shifters (providing precise rotation 90 ^of, for example, for all spectral components of hertz or kilohertz to several megahertz). Therefore, for example, in cable trunk communication lines where television signals are transmitted by the method of single-band modulation, the carrier frequency must be selected within the order of 25-40% of the width of one side band. Consequently, the efficiency of band exchange for a time reaches only 70-80% and is associated with significant technical difficulties. But if the “packing” of the quadrature-modulated television signal could be implemented in practice without the indicated technical difficulties, moreover, by bringing the band-time exchange efficiency to a value close to 100% (exactly 100% cannot be achieved even theoretically in this case), and most importantly to restore from two packages the original quadrature-modulated television signal from which modulating signals could be extracted, using rather simple technical means for this restoration, then the way to reduce the frequency band t composite color television signal without elimination would represent a very promising therein redundancy.

 It should be noted that simply stretching in time a quadrature modulated television signal with a band of 2 Δ F and placing it in a frequency band from 0 to Δ F (carrier frequency F) is not a suitable method. It is not applicable to color signals, since there are two color-difference signals, and in this way they can transmit half as much per frame. In addition, such a transmission will require a very high linearity of the phase response in the band from 0 to F.

 The basis of the invention is the creation of a television system that provides an increase in the amount of information transmitted by a full color television signal per unit time, without expanding the frequency band of this signal.

 The solution to this problem is possible if, using a high correlation of the signals of adjacent frames, fields and lines of a television image, the video signals containing information about luminance and color are replaced by signals with a larger information capacity that are part of the full color television signal with temporary compression. Such signals, in particular, are the sending of quadrature modulated television signals provided that they are placed in a frequency band approximately equal to the width of one side band. A very simple technical way of “folding” the spectrum of a quadrature-modulated signal to place it in a frequency band approximately equal to the width of one sideband is quadrature modulation of the carrier or subcarrier, the frequency of which is much lower than the upper cutoff frequency of the spectrum of modulating video signals, implemented without full or partial limitation (suppression) of one side strip. Such a voltage with a “wrapped” lower sideband contains all the frequency components of the upper and lower sidebands of the quadrature modulated signal. This gives reason to believe that all the information stored in such a voltage is stored in a quadrature modulated signal with the side signals deployed on a high-frequency carrier. However, it is only possible to consider the information obtained as a result of transferring the quadrature modulated signal to a low-frequency carrier voltage with a “wrapped” lower side frequency band as an information signal when information contained in the modulating signals can be extracted from this voltage on the receiving side. As the studies showed, this is feasible, and quite simple in technical implementation techniques. Since voltage with a “wrapped” sideband can be used to transmit information, it can be qualified as a signal. A characteristic distinguishing feature of such a signal with quadrature modulation, the carrier frequency of which is much lower than the upper cutoff frequency of the spectra of the modulating signals, is the presence of the components of the “wrapped” (“reflected”, “reflex”) lower sideband. To determine the process of generating such a signal, the term “reflex quadrature modulation” can be used in contrast to quadrature modulation with unfolded sidebands, including quadrature modulation with one sideband partially suppressed, as mentioned above. The useful signal itself formed by “reflex quadrature modulation” can be called a “reflex quadrature modulation signal” or abbreviated as “reflex-modulated signal”.

, формируя рефлексно-модулированные сигналы на поднесущих, выбор частот f которых обеспечивает требуемые разности фаз φ немодулированных поднесущих в соседних строках одного кадра φ_н и в одинаковых по номерам строках смежных кадров φ_р. Сформированные рефлексно-модулированные сигналы передают в выделенных для них временных интервалах полного цветового телевизионного сигнала. На приемной стороне из принятого полного цветового телевизионного сигнала выделяют посылки рефлексно-модулированных сигналов и направляют их в каналы обработки информации, содержащейся в этих рефлексно-модулированных сигналах. В каналах обработки осуществляют задержку посылок рефлексно-модулированных сигналов на интервалы времени, кратные длительностям периодов телевизионной развертки, и обрабатывают совместно задержанную и незадержанную посылки этих сигналов путем их умножения на гармонические сигналы в соответствующих фазах. Напряжения, получаемые в результате перемножений задержанной и незадержанной посылок рефлексно-модулированных сигналов с гармоническими сигналами в данном канале обработки, алгебраически суммируют и выделяют из суммированного напряжения модулирующие видеосигналы. Выделенные в соответствующих каналах обработки сигналы яркости и цветоразностные сигналы с выравненными временными масштабами совмещают во времени.This goal is achieved by the fact that in a television system, in a full color television signal which signals containing information about the brightness and color of the images are transmitted with a temporary seal, placing the brightness signals in the entire interval of the active part of the line, and time-compressed color difference signals containing information about color, transmitted in blanking intervals in rows, the full color television signal according to the invention is formed using reflex-modulated signals containing information about tdelnyh image characteristics, including reflex-modulated signals luminance and chrominance signals. In this case, video signals containing information about individual characteristics of the images, i.e. such video signals, which include brightness signals and color difference signals, perform quadrature modulation of subcarriers in the phases "0" and ±

, forming reflex-modulated signals on subcarriers, the choice of frequencies f of which provides the required phase differences φ of unmodulated subcarriers in adjacent rows of one frame φ _n and in identical rows of adjacent frames φ _p . The formed reflex-modulated signals are transmitted in the time intervals allocated to them for the full color television signal. On the receiving side, the packages of reflex-modulated signals are isolated from the received full color television signal and sent to the channels for processing information contained in these reflex-modulated signals. The processing channels delay the sendings of reflex-modulated signals by time intervals that are multiples of the durations of the television scan periods, and process the delayed and unstoppable sendings of these signals by multiplying them by harmonic signals in the corresponding phases. The voltages obtained as a result of multiplication of the delayed and uncontrolled sendings of reflex-modulated signals with harmonic signals in a given processing channel algebraically summarize and extract modulating video signals from the summed voltage. The luminance signals and color-difference signals with equalized time scales extracted in the respective processing channels are combined in time.

According to the invention, it is possible to process the delayed and uncontrolled packets of reflex-modulated signals by multiplying one of them by a harmonic signal of the form U ₁ (t) = 2cosω _x t, and the other sending by a harmonic signal of the form U ₂ (t) = 2cos (ω _x t + π + q φ _n ), where ω _x = 2 π f _x ; f _x is the frequency of the harmonic signal exceeding the cutoff frequency of the spectrum of the reflex modulated signal; φ _n = 2πfτ _n ; f is the frequency of the subcarrier of the reflex modulated signal; τ _n - the length of the line; q is the number of the natural number. The algebraic summation of the voltages obtained by multiplying the bursts of reflex-modulated signals with harmonic signals U ₁ (t) and U ₂ (t) gives a quadrature modulated signal with unfolded side bands on a high-frequency carrier. When detecting this signal, you can select the video signals modulating the carrier on the transmitting side.

The combined processing of delayed and undelayed packets of reflex-modulated signals at the receiving side according to the invention can also be carried out directly at the subcarrier frequency f. In this case, one premise must be multiplied by a harmonic signal of the form U ₁ (t) = 2cos ω t, where ω = 2πf, and the other premise by a harmonic signal of the form U ₂ (t) = 2cos (ωt + π + qφ _н ). During the algebraic summation of the stresses resulting from these multiplications, one of the modulating video signals is directly distinguished. In order to isolate the second modulating signal, one of the packages of reflex-modulated signals must be multiplied by a harmonic signal of the form U ₃ (t) = 2sin ω t, and the other package by a harmonic signal of the form U ₄ (t) = 2sin (ω t + π + q φ _n ). In the algebraic summation of the voltages resulting from these multiplications, the second modulating video signal is directly distinguished.

, где f_н=

частота строк; f_р - частота кадров; m и n - числа натурального ряда, выбор значений которых обеспечивает разность фаз φ_оцветовой поднесущей в соседних строках одного кадра φ_он≈

(2n-1) и в одинаковых по номерам строках смежных кадров φ_ор= π (2i-1), где i - целое число. Для этого в качестве модулирующих цветовую поднесущую видеосигналов надо использовать цветоразностные сигналы и изменить временной масштаб сформированного сигнала цветности с коэффициентом сжатия К, равным отношению верхней граничной частоты номинальной полосы частот полного цветового телевизионного сигнала к выбранному значению верхней граничной частоты спектра, передаваемого в одной строке сигнала цветности до его сжатия во времени. Входящие в состав сигнала цветности сигналы цветовой синхронизации, представляющие собою сжатые во времени в К раз сигналы рефлексно-модулированной поднесущей в "опорной" фазе, могут передаваться в нескольких строках интервала гашения по кадрам, причем время передачи каждой посылки сигналов цветовой синхронизации в строках кадрового интервала гашения должно быть равно времени передачи сигнала цветности в одной строке активной части кадра. Сформированный сигнал цветности, сжатый во времени, должен передаваться в строках полного цветового телевизионного сигнала в интервалах между срезом строчного синхронизирующего импульса и началом активной части строки. На приемной стороне выделенные из принятого полного цветового телевизионного сигнала посылки сигналов цветности целесообразно задерживать на время, равное длительности кадра, и алгебраически суммировать с посылками сигналов цветности, выделенными из одинаковых по номерам строк незадержанного сигнала кадра, поступающего на вход. Посылки алгебраически суммированных сигналов цветности из одинаковых по номерам строк смежных кадров необходимо дополнительно задержать на время T=q τ_н, где τ_н=

, и совместно обрабатывать дополнительно задержанную и незадержанную посылки сигналов цветности путем умножения их на гармонические сигналы в соответствующих фазах. При этом следует учитывать, что разность фаз Δφ_о между фазой φ₀₁ немодулированной цветовой поднесущей в задержанной посылке сигнала цветности и фазой φ₀₂немодулированной цветовой поднесущей в незадержанной посылке сигнала цветности была связана с временем Т задержки соотношением
Δφ_o = φ₀₁ - φ₀₂ = ω_oq τ_н, где ω₀=2 π f₀.It is advisable that in the full color television signal of the proposed television system in the blanking intervals, both color difference signals are simultaneously transmitted along the lines, forming a color signal on the color subcarrier with frequency quadrature reflex
f _o =

where f _n =

line frequency; f _p - frame rate; m and n are the numbers of the natural series, the choice of the values of which ensures the phase difference φ _{about the} color subcarrier in adjacent rows of one frame φ _it ≈

(2n-1) and in identical rows of adjacent frames φ _op = π (2i-1), where i is an integer. For this, color-difference signals must be used as color-modulating video subcarrier signals and the time scale of the generated color signal must be changed with a compression coefficient K equal to the ratio of the upper cutoff frequency of the nominal frequency band of the full color television signal to the selected value of the upper cutoff frequency of the spectrum transmitted in one line of the color signal before its compression in time. The color synchronization signals included in the color signal, which are time-compressed K-times reflex-modulated subcarrier signals in the "reference" phase, can be transmitted in several lines of the blanking interval per frame, with the transmission time of each transmission of color synchronization signals in the frame interval lines the blanking should be equal to the transmission time of the color signal in one line of the active part of the frame. The generated color signal, compressed in time, should be transmitted in the lines of the full color television signal in the intervals between the slice of the horizontal synchronizing pulse and the beginning of the active part of the line. On the receiving side, it is advisable to delay the chroma signal packets extracted from the received full color television signal for a time equal to the frame duration, and algebraically add them to the chroma signal packets isolated from the same line numbers of the undelayed frame signal input. Parcels of algebraically summed color signals from the same row numbers of adjacent frames must be additionally delayed for a time T = q τ _n , where τ _n =

, and jointly process the additionally delayed and uncontrolled sending of color signals by multiplying them by harmonic signals in the corresponding phases. It should be borne in mind that the phase difference Δφ _about between the phase φ _{01 of the} unmodulated color subcarrier in the delayed sending of the color signal and the phase φ _{02 of the} unmodulated color subcarrier in the unattended sending of the color signal was related to the delay time T by the relation
Δφ _o = φ ₀₁ - φ ₀₂ = ω _o q τ _n , where ω ₀ = 2 π f ₀ .

According to the invention, the combined processing of delayed and uncontrolled bursts of summed chroma signals from the same row numbers of adjacent frames can be done by multiplying one of them by a harmonic signal of the form U ₁ (t) = 2cosω _x t, and the other burst by a harmonic signal of the form U ₂ ( t) = 2cos (ω _x t + π + Δφ _o ), where ω _x = 2 π f _x ; f _x is the frequency of the harmonic signal exceeding the cutoff frequency of the spectrum of the color signal. When summing the stresses resulting from these multiplications, a quadrature modulated color signal with unfolded side bands on a high-frequency carrier is obtained. By synchronous detection of this signal, both color difference signals can be distinguished.

(2n + 1).It is also possible to jointly process delayed and uncontrolled bursts of summed chroma signals from the same line numbers of adjacent frames and extract color-difference signals directly at a frequency f _{0 of the} color subcarrier. With this processing, one of the premises should be multiplied by a harmonic signal of the form U ₁ (t) = 2cosω _о t, the second premise should be multiplied by a harmonic signal of the form U ₂ (t) = 2cosω (ω _о t + π + Δφ _o ) and algebraically sum the voltages, resulting from these multiplications. In this way, one of the color difference signals is isolated directly. To select the second color-difference signal, one of the sendings of the color signals summed from the same line numbers of adjacent frames must be multiplied by a harmonic signal of the form U ₃ (t) = 2sinω _o t, the second premise should be multiplied by a harmonic signal of the form U ₄ (t) = 2sin ( ω _o t + π + Δφ _o ) and algebraically sum the stresses resulting from this pair of multiplications. In this case, the second color difference signal is directly distinguished. According to the invention, it is advisable to choose the time of the additional delay of the packets of the summed color signals from the same line numbers of adjacent frames during the joint processing of these packages on the receiving side, equal to the string length τ _n . In this case, the phase difference of the harmonic signals, by which it is necessary to multiply the delayed and uncontrolled packages, should be chosen equal to π + Δφ _o

(2n + 1).

, где Z - число строк разложения. Возможно использование двух вариантов осуществления такой задержки. В первом варианте дополнительную задержку посылок в первом поле осуществляют на время T₁=

τ_н, а во втором поле - на время T₂=

τ_н . При этом разность фаз гармонических сигналов, на которые требуется умножать задержанные и незадержанные посылки сигналов цветности, следует выбирать равными в первом поле Π-

±

(Z+1) , а во втором поле Π-

±

(Z-1) . Во втором варианте дополнительную задержку посылок суммированных сигналов цветности из одинаковых по номерам строк смежных кадров выбирают и в первом и во втором полях идентичной и равной времени T₁=

τ_н. Соответственно разность фаз гармонических сигналов, на которые требуется умножать, задержанные и незадержанные посылки, следует выбирать равной Π-

±

(Z+1) в обоих полях.It is also advisable that in a number of applications of the proposed system, when the delayed and uncontrolled bursts of summed color signals from the same row numbers of adjacent frames are processed together on the receiving side, an additional burst delay of time T, approximately equal to the duration of the television scan field, should be used, T =

where Z is the number of lines of decomposition. It is possible to use two embodiments of such a delay. In the first embodiment, an additional delay in the parcels in the first field is carried out at a time T ₁ =

τ _n , and in the second field - for the time T ₂ =

τ _n In this case, the phase difference of the harmonic signals, by which it is necessary to multiply the delayed and uncontrolled sending of color signals, should be chosen equal in the first field Π-

±

(Z + 1), and in the second field Π-

±

(Z-1). In the second embodiment, the additional delay of the sendings of the summed chroma signals from the identical line numbers of adjacent frames is selected in the first and second fields of identical and equal time T ₁ =

τ _n Accordingly, the phase difference of the harmonic signals by which you want to multiply, the delayed and uncontrolled packages should be chosen equal to Π-

±

(Z + 1) in both fields.

2S-1+

из второго поля, где S - число натурального ряда. Сигналы двух строк записи (2S-1) и 2S первого изображения преобразовывают в сигналы одной строки передачи первого изображения. Сигналы двух строк записи (2S-1) и 2S второго изображения преобразуют в сигналы одной строки передачи второго изображения. Преобразования эти осуществляют для сигналов первого и второго изображений раздельно и идентичными способами. При этом из строк записи (2S-1) и 2S одновременно считывают сигналы цветности и, алгебраически суммируя их, получают общий для строк записи (2S-1) и 2S сигнал цветности на цветовой поднесущей с частотой f₀. Разность фаз немодулированной цветовой поднесущей в строках передачи, сформированных из сигналов строк записи (2S-1) и 2S, и в строках передачи, сформированных из сигналов строк записи (2S+1) и (2S+2) того же самого изображения, составит величину φ_он= 2Πf_oτ_н≈

(2n-1) . Записанные в строках записи (2S-1) и 2S cигналы, содержащие информацию о яркости, также передают одновременно, формируя из этих сигналов рефлексно-модулированный сигнал яркости. Для этого считанными из строк записи (2S-1) и 2S cигналами яркости осуществляют рефлексную квадратурную модуляцию поднесущей яркости, частота которой f_y=

f_н , где d - число натурального ряда. Выбор значения d должен обеспечивать разность фаз немодулированной поднесущей яркости в одинаковых по номерам строках смежных кадров φ_ур =

(2d-1).It is advisable that in a television system with the simultaneous transmission of color-difference signals in the blanking intervals in a full color television signal for a duration of one line, reflex-modulated signals containing information about the brightness and color of two adjacent rows of images in space are transmitted, and simultaneously transmit in real scale time two color television images in a combined frequency band, nominal for the transmission of one such image. To do this, on the transmitting side, it is necessary to memorize the luminance and color signals of two fields of one frame separately of the first and second images, placing sequentially in the recording lines of each image the signals of adjacent in space lines of this image from the first and second fields so that in the recording line (2S-1 ) contained information about the brightness and color of the line (2S-1) from the first field, and the line of record 2S contained information about the brightness and color of the line

2S-1 +

from the second field, where S is the number of the natural number. The signals of the two recording lines (2S-1) and 2S of the first image are converted into signals of one transmission line of the first image. The signals of the two recording lines (2S-1) and 2S of the second image are converted into signals of one transmission line of the second image. These transformations are carried out for signals of the first and second images separately and in identical ways. At the same time, color signals are read from the recording lines (2S-1) and 2S and, algebraically summing them, a common color signal for the recording lines (2S-1) and 2S is obtained on the color subcarrier with a frequency f ₀ . The phase difference of the unmodulated color subcarrier in the transmission lines formed from the signals of the recording lines (2S-1) and 2S, and in the transmission lines formed from the signals of the recording lines (2S + 1) and (2S + 2) of the same image, will be φ _he = 2Πf _o τ _n ≈

(2n-1). The signals recorded in the recording lines (2S-1) and 2S, containing information about the brightness, are also transmitted simultaneously, forming a reflectively modulated brightness signal from these signals. For this, the luminance signals read from the recording lines (2S-1) and 2S carry out reflex quadrature modulation of the luminance subcarrier, the frequency of which is f _y =

f _n , where d is the number of the natural number. The choice of the value of d should provide the phase difference of the unmodulated brightness subcarrier in the same row numbers of adjacent frames φ _ur =

(2d-1).

(2n+1), и выделение цветоразностных сигналов. Полученные на выходе каналов обработки цветоразностные сигналы используют для воспроизведения информации о цветности, содержащейся в строках записи (2S-1) и 2S. В число операций обработки рефлексно-модулированных сигналов яркости входят выделение посылок этих сигналов из задержанных на время кадра и незадержанных сигналов строк, совместная обработка задержанной и незадержанной посылок рефлексно-модулированных сигналов яркости из одинаковых по номерам строк смежных кадров путем умножения этих посылок на гармонические сигналы в соответствующих фазах, алгебраического суммирования напряжений, получаемых в результате перемножений посылок рефлексно-модулированных сигналов яркости с гармоническими сигналами, и выделения сигналов яркости строк записи (2S-1) и 2S. Выделенные сигналы, содержащие информацию о цветности и яркости строки записи 2S, требуется задержать на время T₁=

τ_н, чтобы восстановить полный цветовой телевизионный сигнал чересстрочного разложения исходного изображения.The generated reflex-modulated luminance signals and color signals containing luminance and color information from the recording lines (2S-1) and 2S of the first image are transmitted in line (2S-1) of the full color television signal, reflex-modulated luminance signals and color signals containing luminance and chrominance information from recording lines (2S-1) and 2S of the second image are transmitted in line 2S of the full color television signal. In this case, the color signals of the first and second images are transmitted respectively in the blanking intervals, and reflex-modulated brightness signals of these images are transmitted without changing the time scale in the active intervals of the lines of the full color television signal. In the same line numbers of adjacent frames transmit signals of the same image. On the receiving side, signals from the first and second images extracted from the full color television signal are sent to the processing channels of these signals. In the signal processing channels of each image, identical processing operations are carried out. Such operations include the delay of signals arriving at the channel input for the duration of the frame, the extraction of color signals from signals of the same row numbers of adjacent frames, the algebraic summation of the delayed and unavailable color signals from the same row numbers of adjacent frames, the additional delay of these algebraically summed color signals for a time equal to the duration of two lines, multiplication of additional delayed and undelivered packets of summed color signals from the same x by line numbers of adjacent frames for harmonic signals, the phase difference of which should be Π + Δφ _o ≈

(2n + 1), and the allocation of color difference signals. The color difference signals obtained at the output of the processing channels are used to reproduce the color information contained in the recording lines (2S-1) and 2S. The processing operations of reflex-modulated luminance signals include the extraction of the parcels of these signals from the delayed for the frame time and uncontrolled line signals, the combined processing of the delayed and uncontrolled parcels of reflex-modulated brightness signals from the same line numbers of adjacent frames by multiplying these parcels by harmonic signals in corresponding phases, algebraic summation of the voltages obtained as a result of multiplication of the packages of reflex-modulated brightness signals with harmonious Skim signals and luminance signals of lines allocation record (2S-1) and 2S. The selected signals containing information about the color and brightness of the recording line 2S, you need to delay for a time T ₁ =

τ _n to restore the full color television signal of the interlaced decomposition of the original image.

(2d+1)], где ω_xy=2 π f_xy; f_хy - частота несущей, удовлетворяющая условию f_xy-f_y выше верхней граничной частоты спектра рефлексно-модулированного сигнала яркости. При алгебраическом суммировании напряжений, получаемых в результате этих перемножений, образуется квадратурно-модулированный сигнал с развернутыми боковыми полосами на высокочастотной несущей. При детектировании этого сигнала могут быть выделены яркости строк записи (2S-1) и 2S изображения. Также возможно осуществить совместную обработку задержанной и незадержанной посылок рефлексно-модулированного сигнала яркости и выделение сигналов яркости строк записи (2S-1) и 2S на приемной стороне непосредственно на частоте поднесущей яркости. Для этого требуется произвести умножение одной посылки на гармонический сигнал вида U₁(t)=2cos ω_yt, а другой посылки на гармонический сигнал вида U₂(t)=2cos[ω_yt +

(2d+1)].При алгебраическом суммировании напряжений, получаемых в результате этих перемножений, непосредственно выделяется сигнал яркости строки записи (2S-1) изображения. При умножении одной посылки на гармонический сигнал вида U₃(t)= 2sin ω_yt, а другой посылки на гармонический сигнал вида U₄(t)=2sin [ ω_yt +

(2d +1 )] и алгебраическом суммировании напряжений, получаемых в результате этих перемножений, может быть непосредственно выделен сигнал яркости строки записи 2S изображения.According to the invention, it is possible to carry out joint processing of the delayed and uncontrolled packages of the reflex-modulated brightness signal on the receiving side by multiplying one of them by a harmonic signal of the form U ₁ (t) = 2cos ω _xy t and the other by a harmonic signal of the form U ₂ (t) = 2cos [ω _xy t +

(2d + 1)], where ω _xy = 2 π f _xy ; f _xy is the carrier frequency satisfying the condition f _xy -f _y above the upper cutoff frequency of the spectrum of the reflex-modulated luminance signal. In the algebraic summation of the stresses resulting from these multiplications, a quadrature modulated signal with unfolded side bands on a high-frequency carrier is formed. When detecting this signal, the brightness of the recording lines (2S-1) and 2S of the image can be highlighted. It is also possible to carry out joint processing of the delayed and uncontrolled bursts of the reflex-modulated luminance signal and the allocation of the luminance signals of the recording lines (2S-1) and 2S on the receiving side directly at the luminance subcarrier frequency. For this, it is necessary to multiply one premise by a harmonic signal of the form U ₁ (t) = 2cos ω _y t, and the other premise by a harmonic signal of the form U ₂ (t) = 2cos [ω _y t +

(2d + 1)]. In the algebraic summation of the stresses resulting from these multiplications, the brightness signal of the recording line (2S-1) of the image is directly extracted. When you multiply one premise by a harmonic signal of the form U ₃ (t) = 2sin ω _y t, and another premise by a harmonic signal of the form U ₄ (t) = 2sin [ω _y t +

(2d +1)] and the algebraic summation of the stresses resulting from these multiplications, the luminance signal of the recording line 2S of the image can be directly extracted.

) того же изображения, восстанавливая тем самым исходный полный цветовой телевизионный сигнал соответствующего изображения.It is advisable that in the proposed television system, when transmitting two color images in a combined frequency band on the receiving side, such a processing of the full color television signal is provided, in which color signals are extracted from the signal processing channels of each image from the input signals and repeated by time delays T ₁ = τ _n An undelayed message is placed in the blanking interval of the restored line luminance signal (2S-1) of this image, and a delayed message of color signal is placed in the blanking interval of the restored line luminance signal (2S-1 +

) of the same image, thereby restoring the original full color television signal of the corresponding image.

, и длительностью каждой из этих строк, равной 2 τ_н. Формирование такого полного цветового телевизионного сигнала позволит передать в реальном масштабе времени сигналы телевизионных изображений с исходным числом строк разложения Z₁=

и числом кадров в секунду N =

в полосе частот, равной половине от номинальной полосы частот, необходимой для передачи сигналов таких телевизионных изображений известными способами. Для этого на передающей стороне нужно осуществить запоминание сигналов яркости и цветности двух полей одного кадра изображения, размещая последовательно в строках записи сигналы смежных в пространстве строк изображения, причем в строке записи (2S-1) должна содержаться информация о цветности и яркости из строки (2S-1) первого поля, а в строке записи 2S - информация о яркости и цветности из строки (2S - 1 +

) второго поля. Из строк записи (2S-1) и 2S одновременно считывают сигналы, содержащие информацию о цветности, и, алгебраически суммируя эти сигналы, формируют общий для строк записи (2S-1) и 2S сигнал цветности на поднесущей. Частота цветовой поднесущей f₀, а разность фаз немодулированной поднесущей в сигналах цветности, сформированных из исходных сигналов строк записи (2S-1) и 2S, и в сигналах цветности, сформированных из исходных сигналов в строках записи (2S+1) и (2S+2), составляет Δφ_o≈

(2n-1) .It is advisable that in a television system with the simultaneous transmission of color-difference signals in the blanking intervals in a full color television signal for a duration of two lines transmitted reflex-modulated signals containing information about the brightness and color of two adjacent lines of space in the image. This can be done by stretching twice the transmission time of the luminance and color signals of each image line and forming from the pairs of time-stretched and simultaneously transmitted signals of two adjacent spatial image lines a full color television signal with a transmission frequency of lines equal to

, and with a duration of each of these lines equal to 2 τ _n . The formation of such a full color television signal will allow real-time transmission of television image signals with the original number of lines of decomposition Z ₁ =

and frames per second N =

in a frequency band equal to half of the nominal frequency band necessary for transmitting signals of such television images by known methods. To do this, on the transmitting side, it is necessary to memorize the luminance and color signals of two fields of one image frame, placing sequentially in the recording lines the signals of adjacent image lines in space, and the recording line (2S-1) should contain information about the color and brightness from the line (2S -1) of the first field, and in the recording line 2S - information about the brightness and color from the line (2S - 1 +

) of the second field. From the recording lines (2S-1) and 2S, signals containing chroma information are read at the same time, and by algebraically summing these signals, a common chroma signal for the recording lines (2S-1) and 2S is formed on the subcarrier. The color subcarrier frequency is f ₀ , and the phase difference of the unmodulated subcarrier in the color signals generated from the source signals of the recording lines (2S-1) and 2S, and in the color signals generated from the original signals in the recording lines (2S + 1) and (2S + 2) is Δφ _o ≈

(2n-1).

f_н, что обеспечивает разность фаз немодулированной поднесущей яркости в одинаковых по номерам строках смежных кадров φ_yp=

(2d-1) . При растяжении в два раза по времени сформированных рефлексно-модулированных сигналов яркости и сигналов цветности сужается соответственно вдвое ширина их частотного спектра, а также уменьшаются до величин

и

значения частот цветовой поднесущей и поднесущей яркости. Растянутые во времени рефлексно-модулированные сигналы яркости и сигналы цветности передают соответственно в интервалах активной части строк и в интервалах гашения полного цветового телевизионного сигнала. Поскольку длительность каждой строки передачи равна 2τ_н, то число строк передачи в кадре составляет
Z₂=

=

.The formation of quadrature modulated luminance signals is carried out by reflex quadrature modulation of the luminance subcarrier by luminance signals simultaneously read from the recording lines (2S-1) and 2S. Luminance subcarrier frequency f _y =

f _n , which provides the phase difference of the unmodulated luminance subcarrier in the same row numbers of adjacent frames φ _yp =

(2d-1). When the reflex-modulated luminance and color signals are doubled in time, they are respectively halved by the width of their frequency spectrum, and also reduced to

and

color subcarrier and luminance subcarrier frequencies. The time-stretched reflex-modulated luminance and color signals are transmitted respectively in the intervals of the active part of the lines and in the blanking intervals of the full color television signal. Since the duration of each transmission line is 2τ _n , the number of transmission lines in the frame is
Z ₂ =

=

.

(2n+1) ; полученные в результате цветоразностные сигналы используют для воспроизведения информации о цветности, содержавшейся в строках записи (2S-1) и 2S изображения.On the receiving side, in the received full color television signal, it is necessary to halve the line lengths to restore the original time durations of the color signals in the blanking and reflex-modulated luminance signals in the active parts of the lines and, accordingly, the width of the frequency spectra of these signals, as well as the frequency values f ₀ and f _y subcarriers. The full color television signal with time-squeezed lines up to the length of τ _n should be delayed for the duration of the frame and distinguished from the delayed for the time of the frame and uncontrolled signals of the same number of line frames of adjacent frames of the color signals and reflex-modulated luminance signals, to sum the color signal packets from identical by line numbers of adjacent frames. The summarized bursts of chroma signals are additionally delayed by 2τ _n and the phase difference of the harmonic signals is selected by which the delayed and uncontrolled bursts of chroma signals equal to Π + Δφ _o ≈ are multiplied

(2n + 1); the resulting color difference signals are used to reproduce the color information contained in the recording lines (2S-1) and 2S of the image.

τ_н , восстанавливая сигналы строк (2S-1) (2S - 1 +

)чересстрочной развертки исходного изображения.Isolated from the same line numbers of adjacent frames, delayed for the frame time and uncontrolled sending of reflex-modulated luminance signals are jointly processed by multiplying them by harmonic signals in the corresponding phases, the voltages obtained as a result of these multiplications are algebraically summed, and the luminance signals of recording lines are extracted (2S -1) and 2S. The selected signals containing information about the brightness and color of the lines of the 2S record are delayed by the time T ₁ =

τ _n , restoring the signals of the rows (2S-1) (2S - 1 +

) interlaced scan of the original image.

(2d + 1)], где ω_xy=2 π f_xy; f_xy - частота несущей, удовлетворяющая условию f_xy-f_y - выше верхней граничной частоты спектра рефлексно-модулированного сигнала яркости до его растяжения во времени. Полученные в результате этих перемножений напряжения алгебраически суммируют, формируя сигнал с развернутыми боковыми полосами на высокочастотной несущей, детектируют этот сигнал и выделяют сигналы яркости строк записи (2S-1) и 2S изображения. Также возможно, чтобы совместная обработка задержанной и незадержанной посылок рефлексно-модулированного сигнала яркости на приемной стороне и выделение сигналов яркости строк записи (2S-1) и 2S осуществлялись непосредственно на частоте поднесущей яркости f_y=

. Для этого необходимо произвести умножение одной посылки на гармонический сигнал вида U₁(t)= 2cos ω_yt, а другой посылки на гармонический сигнал вида U₂(t)=2cos[ ω_yt +

(2d +1) ]. При алгебраическом суммировании напряжений, получаемых в результате этих перемножений, непосредственно выделяется сигнал яркости строки записи (2S-1). При умножении одной посылки на гармонический сигнал вида U₃(t)= 2sin ω_yt, а другой посылки на гармонический сигнал вида U₄(t)= 2sin [ω_yt +

(2d + 1)] и алгебраическом суммировании напряжений, получаемых в результате этой пары перемножений, может быть непосредственно выделен сигнал яркости строки записи 2S изображения.According to the invention, it is possible that, on the receiving side, the combined processing of the delayed and uncontrolled packets of reflex-modulated brightness signals is carried out by multiplying one of them by a harmonic signal of the form U ₁ (t) = 2cos ω _xy t and the other by a harmonic signal of the form U ₂ (t ) = 2cos [ω _xy t +

(2d + 1)], where ω _xy = 2 π f _xy ; f _xy is the carrier frequency satisfying the condition f _xy -f _y is higher than the upper cutoff frequency of the spectrum of the reflex-modulated brightness signal until it stretches in time. The voltages obtained as a result of these multiplications are algebraically summed, forming a signal with unfolded sidebands on a high-frequency carrier, this signal is detected and the brightness signals of the recording lines (2S-1) and 2S images are extracted. It is also possible that the combined processing of the delayed and uncontrolled packets of the reflex-modulated luminance signal at the receiving side and the extraction of the luminance signals of the recording lines (2S-1) and 2S are carried out directly at the luminance subcarrier frequency f _y =

. For this, it is necessary to multiply one premise by a harmonic signal of the form U ₁ (t) = 2cos ω _y t, and the other premise by a harmonic signal of the form U ₂ (t) = 2cos [ω _y t +

(2d +1)]. In the algebraic summation of the stresses resulting from these multiplications, the brightness signal of the recording line (2S-1) is directly allocated. When you multiply one premise by a harmonic signal of the form U ₃ (t) = 2sin ω _y t, and another premise by a harmonic signal of the form U ₄ (t) = 2sin [ω _y t +

(2d + 1)] and the algebraic summation of the stresses resulting from this pair of multiplications, the luminance signal of the recording line 2S of the image can be directly extracted.

It is advisable that, on the receiving side, the number of scan lines providing visual perception of a given vertical definition is selected to be Z ₃ exceeding the number Z ₁ of decomposition lines of the luminance signals and color difference signals on the transmitting side. For this, the number of lines Z _{3 of} reproduction of each of the luminance signals and color difference signals can be obtained by interpolation from the number of lines Z ₁ . To interpolate each line displayed on the screen, it is necessary to use the signals of l lines of image decomposition on the transmitting side, with half of these l lines being leading, and the second half subsequent for the interpolated scan line on the screen. In accordance with the characteristics of the method of interpolating the number of lines Z ₃ from the number of lines Z ₁ , the very number of lines Z _{1 of the} decomposition of images on the transmitting side should be selected. It is advisable that on the transmitting side the luminance signals and color difference signals, which, as modulating video signals E _1-1 (t) and E _1-2 (t), respectively modulate the luminance subcarrier and the color subcarrier in the process of generating reflectively modulated luminance and chrominance signals, subjected to preliminary correction. In this case, the corrected modulating video signal must be delayed for a time equal to the duration of two frames 2 τ _p and a difference signal must be generated, which is the difference between the values of the corrected video signal at time t and t-2 τ _p . The generated difference signal can be subjected to the necessary additional processing, including, for example, the operation of the frequency filtering of noise reduction. This difference signal is algebraically summed with a pre-corrected video signal delayed by a time equal to the frame duration τ _p . The video signal corrected in this way is used as the modulating corresponding subcarrier when generating reflex modulated signals of the form E ₃ (t) that are part of the full color television signal.

, где φ₁(t) =

-t

, t изменяется в пределах от 0 до τ_н, τ_н - длительность строки; Δτ_н - длительность интервала гашения по строке, положительное число W₁>2,

- модуль значения φ₁(t) при t =

. Обработанными видеосигналами, прошедшими необходимую частотную коррекцию, можно модулировать соответственно цветовую поднесущую и поднесущую яркости при формировании сигналов цветности и рефлексно-модулированных сигналов яркости, входящих в состав полного цветового телевизионного сигнала. При этом на передающей стороне потребуется, чтобы выделенные сигналы яркости и цветоразностные сигналы записывались построчно с тактовой частотой f_s3 и считывались с переменной вдоль строки тактовой частотой
f_S4(t) =

Кроме того, целесообразно, чтобы при обработке модулирующих видеосигналов на передающей стороне тактовую частоту f_s1(t) записи выбирали изменяющейся в интервале времени t, равном длительности поля τ_v,
f_S1(t) =

, где
φ₂(t) =

- t

, t изменяется в пределах от 0 до τ_v; Δτ_v - длительность интервала гашения по полям, положительное число W₂>2,

- модуль значения φ₂(t) при t =

f_s1(t)=f_s1 при cosφ₂(t) =

cosφ₂(t)dφ . На приемной стороне соответственно требуется, чтобы при обработке выделенных сигналов яркости и цветоразностных сигналов тактовая частота f_s3(t) записи изменялась в интервале τ_v поля по закону
f_S3(t) =

, где f_s3(t)= f_s3 при cosφ₂(t) =

cosφ₂(t)dφ .It is also advisable that, on the transmitting side, when generating chroma signals and reflex-modulated luminance signals, color difference signals and luminance signals used as modulating color and light luminance subcarriers of video signals are subjected to special processing. Such processing should include recording the signals of each line with a clock frequency f _s1 and reading these signals with a clock frequency varying along the line
f _S2 (t) =

where φ ₁ (t) =

-t

, t varies in the range from 0 to τ _n , τ _n is the line duration; Δτ _n - the duration of the blanking interval on the line, a positive number W ₁ > 2,

is the absolute value of φ ₁ (t) at t =

. The processed video signals that have passed the necessary frequency correction can be modulated, respectively, the color subcarrier and the subcarrier of brightness in the formation of color signals and reflex-modulated brightness signals that are part of the full color television signal. At the same time, on the transmitting side, it is required that the selected luminance signals and color difference signals are recorded line by line with a clock frequency f _s3 and read out with a variable clock frequency along the line
f _S4 (t) =

In addition, it is advisable that when processing modulating video signals on the transmitting side, the recording clock frequency f _s1 (t) is selected to vary in the time interval t equal to the field duration τ _v ,
f _S1 (t) =

where
φ ₂ (t) =

- t

, t varies from 0 to τ _v ; Δτ _v is the duration of the blanking interval in the fields, a positive number W ₂ > 2,

is the absolute value of φ ₂ (t) at t =

f _s1 (t) = f _s1 for cosφ ₂ (t) =

cosφ ₂ (t) dφ. On the receiving side, respectively, it is required that, when processing the extracted luminance and color-difference signals, the clock frequency f _s3 (t) of the record changes in the interval τ _{v of the} field according to the law
f _S3 (t) =

, where f _s3 (t) = f _s3 for cosφ ₂ (t) =

cosφ ₂ (t) dφ.

· f_S1·

C₁τ_v+(1-C₁)

+Δτ_v-2t

, где |τ_v+ Δτ_v-2t|- модуль величины (τ_v+ Δτ_v-2t), не равное нулю положительное число C₁ - коэффициент, равный отношению значения f_s1(t) при t =

к значению f_s1(t) при t =

, f_s1 - значение f_s1(t) при t =

+

, тактовую частоту f_s2(t) считывания выбирали бы изменяющейся в интервале τ_н строки в соответствии с выражением
f_S2(t) =

· f_S1(t)

C₂τ_н+(1-C₂)

+Δτ_н-2t

, где |τ_н+ Δτ_н-2t| - модуль величины (τ_н+ Δτ_н-2t), t изменяется в пределах от 0 до τ_н, не равное нулю положительное число С₂ - коэффициент, равный отношению значения f_s2(t) при t =

к значению f_s2(t) при t =

, а на приемной стороне тактовую частоту f_s3(t) записи выбирали бы изменяющейся за время t, равное длительности (τ_v) поля в соответствии с выражением
f_S3(t)= f_S3·

, где f_s3 - значение f_s3(t) при t =

, и тактовую частоту f_s4(t) считывания - изменяющейся в интервале (τ_н) строки в соответствии с выражением
f_S4(t)= f_S3(t)·

, где t изменялось бы в пределах от 0 до τ_н.It is highly advisable that in the television system according to the invention, when processing information signals on the transmitting side, the recording frequency f _s1 is selected to vary in the time interval t equal to the field duration τ _v in accordance with the expression
f _S1 (t) =

F _S1

C ₁ τ _v + (1-C ₁ )

+ Δτ _v -2t

, where | τ _v + Δτ _v -2t | is the modulus of the quantity (τ _v + Δτ _v -2t), a non-zero positive number C ₁ is a coefficient equal to the ratio of the value of f _s1 (t) at t =

to the value of f _s1 (t) at t =

, f _s1 is the value of f _s1 (t) at t =

+

, the clock frequency f _s2 (t) of reading would be chosen varying in the interval τ _{n of the} line in accordance with the expression
f _S2 (t) =

F _S1 (t)

C ₂ τ _n + (1-C ₂ )

+ Δτ _n -2t

where | τ _n + Δτ _n -2t | is the magnitude modulus (τ _n + Δτ _n -2t), t varies from 0 to τ _n , a non-zero positive number C ₂ is a coefficient equal to the ratio of f _s2 (t) at t =

to the value f _s2 (t) at t =

, and on the receiving side, the clock frequency f _s3 (t) of the recording would be chosen to change over time t, equal to the duration (τ _v ) of the field in accordance with the expression
f _S3 (t) = f _S3

where f _s3 is the value of f _s3 (t) at t =

, and the clock frequency f _s4 (t) of reading - changing in the interval (τ _n ) of the line in accordance with the expression
f _S4 (t) = f _S3 (t)

, where t would vary from 0 to τ _n .

In FIG. 1 shows a functional diagram of the formation of a reflex modulated signal; in FIG. 2 is an exemplary view of one line of a full color television signal E _M (t) of a television system with temporary compression of luminance and color signals according to the invention; in FIG. 3 is a functional diagram of a decoder of a full color television signal of the proposed television system; in FIG. 4 is a functional diagram of a processing unit for a reflex-modulated signal with its transfer to a high-frequency carrier and the selection of modulating signals; in FIG. 5 is a functional diagram of a block for processing a reflex-modulated signal and isolating the modulating signals directly at a subcarrier frequency f; in FIG. 6 is a functional diagram of processing a reflex-modulated signal and isolating the modulating signals directly at the subcarrier frequency f with the separation of the modulating signals by additional summing devices; in FIG. 7 is a functional diagram of a device (encoder) for generating a full color television signal of the proposed television system; in FIG. 8 is an exemplary view of one line of the full color television signal of the proposed television system with the simultaneous transmission of color difference signals in the blanking interval; in FIG. 9 is a functional diagram of a color signal processing channel of the proposed television system; in FIG. 10 is a functional block diagram of the formation of a full color television signal, in which during the duration of one line transmit reflex-modulated signals containing information about the brightness and color of two adjacent spatial lines of the image; in FIG. 11 is a functional diagram of a device for generating a full color television signal containing signals of transmission lines of the first and second images; in FIG. 12 is an exemplary view of two lines of a full color television signal containing information about two color images; in FIG. 13 is a functional diagram of a device for processing a full color television signal containing information about two color images; in FIG. 14 is a functional diagram of processing reflex-modulated luminance and chrominance signals extracted from a full color television signal containing information about two color images; in FIG. 15 is a functional diagram of a device for generating from a full color television signal containing information about two color images full color television signals of the first and second programs at an intermediate receiving point; in FIG. 16 is a functional diagram of a device for generating a full color television signal of the proposed television system that provides image transmission in a reduced frequency band; in FIG. 17 is a functional diagram of an apparatus for processing a full color television signal of a television system providing image transmission in a reduced frequency band at a receiving end; in FIG. 18 is an exemplary view of a full color television signal of a television system capable of transmitting images in a reduced frequency band; in FIG. 19 is a functional diagram of generating on the receiving side luminance signals and color difference signals with a number of lines greater than the number of decomposition lines; in FIG. 20 is a functional diagram of a device for pre-correcting luminance signals and color difference signals; in FIG. 21 is a functional diagram of a device for special processing of luminance signals and color difference signals on the transmitting side.

", формируя рефлексно-модулированный сигнал вида E₃(t). Частоты f =

поднесущих выбираются таким образом, чтобы обеспечить требуемые разности фаз φ поднесущих рефлексно-модули- рованных сигналов E₃(t) в соседних строках одного кадра φ_н и в одинаковых по номерам строках смежных кадров φ_p соответственно. О выборе разности фаза φ_н и φ_p подробно будет сказано ниже.The proposed television system with temporary compaction of luminance and color signals, the full color television signal E _M (t) of which is formed using reflex-modulated signals of the form E ₃ (t), containing information about the individual characteristics of the image, is as follows. The luminance signals E _y (t) are placed over the entire interval of the active part of the line, and the time-compressed color difference signals E _RY (t) E _BY (t), which contain color information, are transmitted in line blanking intervals. At the same time, on the transmitting side, the video signals E _1-1 (t), E _1-2 (t) - carry out quadrature modulation of the subcarriers in the phases "0" and "±

", forming a reflex-modulated signal of the form E ₃ (t). Frequencies f =

subcarriers are selected in such a way as to provide the required phase differences φ of the subcarriers of the reflex modulated signals E ₃ (t) in adjacent lines of the same frame φ _n and in the same line numbers of adjacent frames φ _p, respectively. The phase difference φ _n and φ _p will be described in detail below.

The formation of reflex modulated signals E ₃ (t) is carried out in block 1 of the formation of reflex modulated signals. One of the modulating video signals E _1-1 (t) is supplied to one input of the modulator 2 ₁ , the other input of which receives the voltage of the subcarrier 2cosω t. The second modulating video signal E _1-2 (t) is supplied to the first input of modulator 2 ₂ , the other input of which is supplied with voltage 2sin ω t. The signal E _2-1 (t) = 2E _1-1 (t) cos ω t is output from the output of the modulator 2 ₁ . The signal E _2-2 (t) = 2E _1-2 (t) sin ω t is output from the output of modulator 2 ₂ . The signals E _2-1 (t) and E _2-2 (t) are fed to the inputs of the adder 3, from the output of which a reflex quadrature modulated signal E ₃ (t) (abbreviated hereinafter referred to as "reflex modulated signal") is taken. the modulated signal E ₃ (t) can be implemented in both analog and digital forms.In the case of the formation of reflex modulated signals E ₃ (t) in digital form, the video signals E _1-1 (t), E _1-2 (t) voltage subcarriers 2sin ω t, 2cos ω t and _2-1 signals E (t), E _2-2 (t) and E ₃ (t) represent digital streams, modulators February ₁ and ₂ February videosign _1-1 fishing E (t), E _1-2 (t) are diagrams of multipliers in digital form, and an adder 3 - signal adder digitally forming reflex process modulated signal E ₃ (t) at this terminated..

.In cases where it is necessary, this will be discussed below, on the transmitting side, the time scale of the reflex-modulated signal E ₃ (t) can be implemented. For this, a reflex-modulated signal of the form E ₃ (t) is recorded in the storage device 4, recording with a clock frequency f ₁ . Reading the reflex modulated signal E ₃ (t) from the storage device 4 is carried out using the clock frequency f ₂ . From the output of the storage device 4 remove the signal E * ₃ (t) with a modified time scale. The coefficient of change in the time scale K =

.

The formed reflex-modulated signals E ₃ (t) are transmitted in the intervals allocated to them for the full color television signal E _M (t). An exemplary arrangement of signals containing information about individual image characteristics in one line of a full color television signal E _M (t) is shown in FIG. 2. With a total line length from t _0-1 to t _0-2, synchronization signals and, if necessary, additional information signals are placed in the time interval from t _0-1 to t ₁ . The color signal takes an interval from t ₂ to t ₃ , a signal containing information about the brightness, an interval from t ₄ to t ₅ . Sections from t ₁ to t ₂ , from t ₃ to t ₄ , from t ₅ to t _0-2 are guard intervals. Signaling additional information is optional. One of the types of additional information signals can be a sound signal.

At the receiver side in a decoder, an example of an enlarged functional diagram of which is shown in FIG. 3, the full color television signal E _M (t) is processed. The full color television signal E _M (t) is supplied to one input of the signal separation circuit 5, and the control signal U (t) is supplied to the other input. From the outputs of circuit 5, signals E ₄ (t), a color signal, E ₅ (t), a signal containing information about brightness, E ₆ (t), a synchronization signal, and E ₇ (t), an additional information signal, are taken. Each of the signals E ₄ (t) -E ₇ (t) enters its own processing channel. In channel 6, color signals E ₄ (t) are processed; at the output of channel 6, color difference signals E _RY (t) and E _BY (t) are received; in channel 7 - signals E ₅ (t) containing information about the brightness, and at the output of channel 7 receive a signal E _y (t) of brightness; at the output of channel 8, synchronization signals E _s are received; at the output of channel 9, signals E _{d of} additional information. In those cases when the input of channels 6, 7 of the processing of color signals E ₄ (t) and signals E ₅ (t) containing information about the brightness, reflex-modulated signals of the form E * ₃ (t) are received, the time scale of which has been changed on the transmitting side, channels 6, 7 of the signal processing E ₄ (t) and E ₅ (t) should contain memory devices that change the time scale of the input signal, the opposite of that which was produced on the transmitting side by block 4. Highlighted by channel 6 color difference signals E _RY (t) and E _BY (t) and allocated by channel 7 luminance signals E _y (t) with aligned time scales are combined in time.

If the inputs of channels 6, 7 receive reflex-modulated signals of the form E ₃ (t), these channels must contain blocks for processing reflex-modulated signals E ₃ (t) and the selection of modulating video signals E _1-1 (t) and E ₁ from them _-2 (t). Examples of functional circuits of the reflex modulated signal processing unit 10 E ₃ (t) are shown in FIG. 4 and 5. In some cases of processing reflex-modulated signals E ₃ (t) in channel 6 (Fig. 3), some change in the functional diagram of block 10 may be required. Such a circuit is shown in Fig. 6.

In FIG. 4 shows an example of a functional diagram of a block 10 for processing a reflex-modulated signal E ₃ (t) with transferring it to a high-frequency carrier and isolating modulating video signals E _1-1 (t) and E _1-2 (t). In block 10, the undelayed sending of the reflex modulated signal E ₃ (t) is simultaneously fed to the input of the delay device 11 and to one of the multiplication inputs 12 ₁ .

E ₃ (t) = E _1-1 (t) cos ωt + E _1-2 (t) sinω t (1) where ω = 2 π f, f is the subcarrier frequency. The harmonic signal voltage is supplied to the other input of the multiplier 12 ₁
U ₁ (t) = 2cos ω _x t, where ω _x = 2π f _x , f _x is the frequency of the harmonic signal, and f _x > f _lim is the upper cutoff frequency of the spectrum of the reflex-modulated signal E ₃ (t). The signal voltage at the output of the multiplier 12 ₁ is equal to E ₃ (t) 2cos ω _x t = E _1-1 (t) [cos (ω _x - ω) t +
+ cos (ω _x + ω) t] + E _1-2 (t) [sin (ω _x - ω) t +
+ sin (ω _x + ω) t] (2)
The input of the multiplier 12 ₂ from the output of the delay device 11 receives a delayed time T sending a reflex modulated signal E ₃ (tT). The value of the delay time T is a multiple of an integer number of television scan periods, for example, T = q τ _n , where τ _n is the line length, q is the number of the natural number.

q

q

представляющий собой квадратурно-модулированный сигнал с развернутыми боковыми полосами на несущей, частота f_x-f =

которой выше верхней граничной частоты f_lim спектра сигнала E₃(t).E ₃ (t - T) = E _1-1 (t) cos ω (t - T) +
+ E _1-2 (t) sinω (t - T) = E _1-1 (t) cos (ωt -
- q φ _n ) + E _1-2 (t) sin (ωt - q φ _n ), (3)
since ω τ _n = τ _n are the phase differences of the unmodulated subcarrier in adjacent rows of one frame. The harmonic signal voltage U ₂ (t) = 2cos (ω _x t + π + q τ _n ) is supplied to the other input of the multiplier 12 ₂ . The signal voltage at the output of the multiplier 12 ₂ is
E ₃ (t - T) ^. 2 cos (ω _x + π + qφ _н ) = E _1-1 (t) x
x [cos (ω _x t −ω t + π + 2 q φ _n ) -
- cos (ω _x - ω) t] + E _1-2 (t) [-sin (ω _x t -
-ω t + π + 2 q φ _н ) -sin (ω _x + ω) t] (4)
The output voltages of the signals of the multipliers 12 ₁ and 12 ₂ enter the adder 13, from the output of which the signal is taken
2

q

q

representing a quadrature modulated signal with unfolded side bands on the carrier, frequency f _x -f =

which is higher than the upper cutoff frequency f _lim of the signal spectrum E ₃ (t).

cos

(ω_x-ω)t+

+q

и
U_x2(t) =

sin

(ω_x-ω)t+

+q

. С выходов детекторов 14₁ и 14₂ снимают видеосигналы E_1-1(t) и E_1-2(t). Напряжение сигнала на выходе сумматора 13 максимально, когда cos

+q

= ± 1, т.е. когда q qφ_н=

(2x-1), где х - целое число. В случае qφ_н= πх сигнал на выходе сумматора 13 равен нулю. При изменении qφ_н от 0 (или π ) до

(или π +

) размах сигнала на выходе сумматора 13 также будет меняться от 0 до максимального значения. Поэтому при q φ_н=

(2x - 1) достигается максимальная помехозащищеность обработки рефлексно-модулированного сигнала E₃(t) в блоке 10. Как следует из изложенного выше, при любых значениях q φ_н не возникает перекрестных искажений между сигналами E_1-1(t) и E_1-2(t), если правильно выбрать фазы гармонических сигналов U_x1(t) и U_x2(t). Поэтому способ обработки рефлексно-модулированного сигнала E₃(t) с переносом его на высокочастотную несущую является универсальны. Однако такой способ не всегда является удобным, например, при обработке сигнала E₃(t) в цифровой форме. Поэтому предлагается также способ обработки рефлексно-модулированного сигнала E₃(t) и выделения из него модулирующих видеосигналов E_1-1(t) и E_1-2(t) непосредственно на частоте f поднесущей.The signal from the output of the adder 13 is fed to the inputs of synchronous detectors 14 ₁ and 14 ₂ . The other inputs of the detectors 14 ₁ and 14 ₂ respectively receive harmonic signals
U _x1 (t) =

cos

(ω _x -ω) t +

+ q

and
U _x2 (t) =

sin

(ω _x -ω) t +

+ q

. From the outputs of the detectors 14 ₁ and 14 ₂ remove the video signals E _1-1 (t) and E _1-2 (t). The signal voltage at the output of the adder 13 is maximum when cos

+ q

= ± 1, i.e. when q qφ _n =

(2x-1), where x is an integer. In the case of qφ _n = πx, the signal at the output of the adder 13 is equal to zero. When qφ _n changes from 0 (or π) to

(or π +

) the amplitude of the signal at the output of the adder 13 will also vary from 0 to the maximum value. Therefore, for q φ _n =

(2x - 1) the maximum noise immunity of processing the reflex-modulated signal E ₃ (t) in block 10 is achieved. As follows from the above, for any values of q φ _n there is no cross distortion between the signals E _1-1 (t) and E _{1 -2} (t), if the phases of the harmonic signals U _x1 (t) and U _x2 (t) are correctly selected. Therefore, the method of processing a reflex modulated signal E ₃ (t) with transferring it to a high-frequency carrier is universal. However, this method is not always convenient, for example, when processing the signal E ₃ (t) in digital form. Therefore, a method for processing a reflex modulated signal E ₃ (t) and extracting modulating video signals E _1-1 (t) and E _1-2 (t) directly from the subcarrier frequency f thereof is also proposed.

(2x-1) , где х - целое число, cos2qφ_н=-1, sin2qφ_н=0, напряжение сигнала на выходе сумматора 13₁ равно 2E_1-1(t), напряжение сигнала на выходе сумматора 13₂ равно 2E_1-2(t). В этих случаях для обработки рефлексно-модулированного сигнала E₃(t) используют блок 10, представленный на фиг. 5. При q φ_н= π(2х-1), cos2qφ_н=1, sin2qφ_н=0 напряжения сигналов на выходах сумматоров 13₁ и 13₂ равны нулю. При qφ_н=

(2x-1) , cos2qφ_н=0, sin2qφ_н= +1 напряжение сигнала на выходе сумматора 13₁ равно E_1-1(t) + E_1-2(t), напряжение сигнала на выходе сумматора 13₂ равно E_1-1(t)+E_1-2(t).In FIG. 5 and 6 are examples of functional diagrams of a block 10 for processing a reflex-modulated signal E ₃ (t) and for extracting modulating video signals E _1-1 (t) and E _1-2 (t) directly at a subcarrier frequency f. Uncontrolled sending of a reflex modulated signal
E ₃ (t) = E _1-1 (t) cos ωt + E _1-2 (t) sinω t (1)
This package is supplied to the inputs of the delay device 11 and multipliers 12 ₁ and 12 ₃ . The second inputs of the multipliers 12 ₁ and 12 ₃ respectively receive the voltage of the harmonic signals U ₁ (t) = 2cos ω t and U ₃ (t) = 2sin ω t. The voltage at the output of the multiplier 12 ₁ is
E ₃ (t) ^. 2 cosω t = E _1-2 (t) sin 2ω t +
+ E _1-1 (t) + E _1-1 (t) cos 2ω t (6)
The signal voltage at the output of the multiplier 12 ₃ is
E ₃ (t) ^. 2 sinω t = E _1-1 (t) sin 2ω t +
+ E _1-2 (t) + E _1-2 (t) cos 2ω t (7)
C the output of the device 11 delay delayed by the time T sending a reflex modulated signal
E ₃ (t - T) = E _1-1 (t) cos ω (t - q φ _n ) +
+ E _1-2 (t) sin (ωt - q φ _н ), (3) goes to the inputs of multipliers 12 ₂ and 12 ₄ , to the second inputs of which respectively
U ₂ (t) = 2 cos (ωt + π + q φ _н )
and U ₄ (t) = 2 sin (ωt + π + q φ _n )
The signal voltage at the output of the multiplier 12 ₂
E ₃ (tT) ^. 2 cos (ωt + π + q φ _н ) = E _1-1 (t) x
x [cos (π + 2 q φ _n ) - cos 2ω t] - E _1-2 (t) x
x [sin (π + 2 q φ _n ) + cos 2 ωt] (8)
The signal voltage at the output of the multiplier 12 ₄
E ₃ (tT) ^. 2 sin (ωt + π + q φ _n ) = E _1-1 (t) x
x [sin (π + 2 q φ _n ) ^. sin 2 ωt] +
+ E _1-2 (t) [cos (π + 2q φ _н ) + cos 2 ωt] (9)
The signals from the outputs of the multipliers 12 ₁ and 12 ₂ enter the adder 13 ₁ , the output of which receives a signal
E _1-1 (t) (1 - cos 2 q φ _n ) + E _1-2 (t) sin 2 q φ _n (10)
The signals from the outputs of the multipliers 12 ₃ and 12 ₄ enter the adder 13 ₂ , the output of which receives a signal
E _1-1 (t) sin 2 q φ _n ) + E _1-2 (t) (1 - cos 2 q φ _n ) (11)
When qφ _n =

(2x-1), where x is an integer, cos2qφ _n = -1, sin2qφ _n = 0, the signal voltage at the output of the adder 13 ₁ is 2E _1-1 (t), the voltage of the signal at the output of the adder 13 ₂ is 2E _{1- 2} (t). In these cases, to process the reflex modulated signal E ₃ (t), use the block 10 shown in FIG. 5. For q φ _n = π (2x-1), cos2qφ _n = 1, sin2qφ _n = 0, the signal voltages at the outputs of the adders 13 ₁ and 13 ₂ are equal to zero. When qφ _n =

(2x-1), cos2qφ _n = 0, sin2qφ _n = +1 signal voltage at the output of the adder 13 ₁ is equal to E _1-1 (t) + E _1-2 (t), the signal voltage at the output of the adder 13 ₂ is equal to E _{1 -1} (t) + E _1-2 (t).

E_1-1(t)sin2qφ_н+E_1-2(t)(1-cos2qφ_н)

E

В суммирующем устройстве 15₂ алгебраически суммируют сигналы

E_1-1(t)(1-cos2qφ_н)+E_1-2(t)sin2q

и E_1-1(t) sin 2q φ_н + E_1-2(t) (1 -cos 2q φ_н), получая в результате
E_1-2(t)

= 2E_1-2(t)
И в случае обработки рефлексно-модулированного сигнала E₃(t) в блоке 10 (фиг. 4) и в блоке 10 (фиг. 6) максимальная помехозащищенность достигается при q φ_н = -

(2x - 1).To separate the signals E _1-1 (t) and E _1-2 (t) in this case, additional summing devices 15 ₁ and 15 ₂ must be installed in block 10 (Fig. 6), in which signals E ₁ are directly separated by algebraic summation _-1 (t) and E _1-2 (t). It should be noted that, as with the processing of the reflex modulated signal E ₃ (t) with transfer to the high-frequency carrier in block 10 (Fig. 4), the signal E ₃ (t) is processed directly at the frequency f of the subcarrier in block 10 (Fig. 6 ) the separation of the video signals E _1-1 (t) and E _1-2 (t) is feasible without cross-distortion between them for any values of q φ _{n ≠ π} (2х-1). For this, in the adder 15 _{1, the} signals E _1-1 (t) (1-cos2qφ _n ) + E _1-2 (t) sin2q φ _n and

E _1-1 (t) sin2qφ _n + E _1-2 (t) (1-cos2qφ _n )

E

In the adder 15 _{2 the} signals are algebraically summed

E _1-1 (t) (1-cos2qφ _n ) + E _1-2 (t) sin2q

and E _1-1 (t) sin 2q φ _n + E _1-2 (t) (1 -cos 2q φ _n ), resulting in
E _1-2 (t)

= 2E _1-2 (t)
And in the case of processing a reflex-modulated signal E ₃ (t) in block 10 (Fig. 4) and in block 10 (Fig. 6), the maximum noise immunity is achieved when q φ _n = -

(2x - 1).

In the proposed television system with the simultaneous transmission of color-difference signals, the formation of the full color television signal E _M (t) on the transmitting side is carried out by a device, an example of a functional diagram of which is shown in FIG. 7. In this and subsequent sections of the description, the notation “color signal before its compression in time” is used for the designation “color signal E _c (t)”, and for the color signal compressed in time, the designation E * _c (t) is used.

, где f_н - частота строк, f_р - частота кадров, n, m - числа натурального ряда, выбор которых обеспечивает разность фаз φ_o цветовой поднесущей в соседних строках одного кадра φ_он≈

(2n-1) и в одинаковых по номерам строках смежных кадров φ_ор≈ π(2i-1).The matrix 16 (Fig. 7) receives from the image source (not shown in Fig. 7) the initial signals E _R (t), E _B (t), E _G (t) of the primary colors, as well as pulses I _{sc of} color synchronization and sync signal Es. Pulses I _sc color synchronization are several rectangular pulses of a duration equal to the duration of the active part of the line, located at the beginning of the interval blanking. From the outputs of the matrix 16, a luminance signal E _y (t) containing the synchronization signal E _s and color difference signals E _RY (t) and E _BY (t) are taken. The latter in this case are used as modulating video signals E _1-1 (t) and E _1-2 (t) (Fig. 1). The luminance signal E _y (t), previously delayed for a time φ _{n by the} delay device 17 (Fig. 7), is supplied to one of the inputs of the adder 18. One of the color difference signals, for example, the signal E _BY (t), contains impulses I _sc color synchronization. Color difference signals E _RY (t) and E _BY (t) are fed to the inputs of block 1 (Fig. 7), in which a color signal E _c (t) is formed, which is a reflex modulated signal of the form E ₃ (t). The formation of the color signal E _c (t) is carried out by reflex-quadrature modulation of the color subcarrier with a frequency f _o
f _o =

, where f _n is the frequency of the lines, f _p is the frequency of the frames, n, m are the numbers of the natural series, the choice of which ensures the phase difference φ _{o of the} color subcarrier in adjacent rows of one frame φ _it ≈

(2n-1) and in the same row numbers of adjacent frames φ _op ≈ π (2i-1).

From the output of block 1 (Fig. 7), the color signals E _c (t) are fed to the input of the storage device 4, where the time scale of this signal is changed by a factor of K and its placement in time in the line blanking intervals between the slice of the horizontal sync pulse and the beginning of the active parts of the string. The coefficient K is equal to the ratio of the upper cutoff frequency of the nominal frequency band of the full color television signal E _m (t) to the upper cutoff frequency f _{lim of the} spectrum transmitted in one line of the color signal E _c (t) until it is compressed over time. Placing the time-compressed reflex-modulated color signal E * _c (t) in the desired interval of the line blanking interval is carried out when reading from the memory device 4. From the output of the memory device 4, the time-compressed color signal E * _c (t), which includes the color synchronization signal E _{sc is} supplied to another input of the adder 18. The color synchronization signal E _sc has the form of sendings of a K-time compressed signal of a reflex-modulated color subcarrier in the “reference” phase. These packages are placed in several lines of the blanking interval per frame. The duration of each sending of the color synchronization signal E _sc in the lines of the blanking frame interval is equal to the duration of the time-compressed color signal E * _c (t) transmitted in one line of the active part of the frame.

From the output of the adder 18, the full color television signal E _m (t) is taken, an exemplary view of one line of which is shown in FIG. 8. The full color television signal E _m (t) contains the sending of a time-compressed color signal E * ₃ (t). When the total length of one line of the full color television signal E _m (t) is equal to the interval t _0-1 -t _0-2 , in the time interval t _0-1 -t ₁ , horizontal synchronization signals and, if necessary, additional information signals are transmitted , in the interval t ₂ -t ₃ - chroma signals E * ₃ (t), in the interval t ₄ -t ₅ - luminance signal E _y (t). Intervals t ₁ -t ₂ ; t ₃ -t ₄ ; t ₅ -t _0-2 are guard intervals. The color signal E * _c (t) in the full color television signal E _m (t) is located in the time intervals between the slice of the horizontal sync pulse and the beginning of the active part of the line on the pedestal transmitted in the time interval t ₂ -t ₃ , the level of which is equal to half the amplitude of the signal E _y (t) brightness from black to white.

On the receiving side, as mentioned above, the full color television signal E _m (t) is fed to the decoder circuit 5 (FIG. 3), where a time-compressed chroma signal E * _c (t) is extracted, which enters the processing channel 6 . An example of the functional diagram of the channel 6 for processing the time-compressed color signal E * _c (t) in the decoder is shown in FIG. 9. The allocated bursts of the time-compressed color signal E * _c (t) are delayed in the delay device 19 by a time equal to the duration τ _{p of the} frame. Delayed color signals E _c (t) are sent to one of the inputs of the adder 20, where they are algebraically summed with the color signals E * _c (t) in the same-numbered lines of the uncontrolled frame signal fed to the other input of the adder 20 from the output of circuit 5 (Fig. 3). From the output of the adder 20 (Fig. 9), the sending of the summed signals E * _c (t) of the color of the same line numbers of adjacent frames is supplied to the storage device 21, in which the time scale of the signal E * _c (t) is changed by 1 / K times. From the output of the storage device 21, the sending of the summed signals E _c (t) of the color with the restored time scale is supplied to the reflex-modulated signal processing unit 10. Further processing of the color signals E _c (t) in the block 10 described previously with reference to FIG. 4, 5 and 6, can be carried out both with transfer to a high-frequency carrier (Fig. 4), and directly at a frequency f _{0 of the} color subcarrier (Fig. 5, 6). The time of the additional delay of the signal E _c (t) of color T = q τ _n , where q is the number of the natural number, τ _n is the line length. The delay is carried out by the device 11 (Fig. 4) of the delay in block 10.

In block 10 (Fig. 4), the unresolved color signal E _c (t) is multiplied in the multiplier 12 ₁ with a harmonic signal of the form U ₁ (t) = 2cosω _x t, where ω _x = 2 πf _x , f _x > f _lim , and the delayed bursts of the chrominance signal E _c (tT) are multiplied in the multiplier 12 ₂ with a harmonic signal of the form U ₂ (t) = 2sin (ω _x t + π + Δφ _o ), where Δφ _o = φ ₀₁ -φ ₀₂ , φ ₀₁ and φ ₀₂ - color phase phases of the delayed E _c (tT) and undelayed E _c (t) bursts of color signals. In this case, the phase difference Δφ _o = φ ₀₁ -φ ₀₂ is associated with the delay time T = q τ _{n by the} ratio
Δφ _o = φ ₀₁ -φ ₀₂ = ω _o qτ _n , where ω _o = 2πf _o .

The signal at the output of the adder 13 is a quadrature modulated color signal with unfolded side bands on a high-frequency carrier. After detecting this signal, the color difference signals E _RY (t) and E _BY (t), respectively, are removed from the outputs of synchronous detectors 14 ₁ and 14 _2, respectively. In block 10 (Fig. 5 and 6), it is possible to implement another option for the joint processing of delayed and uncontrolled bursts of color signals, for which the uncontrolled summed color signal E _c (t) in multipliers 12 ₁ and 12 ₃ is multiplied by signals of the form U ₁ (t) = 2cos ω ₀ t and U ₃ (t) = 2sin ω ₀ t, respectively. The delayed color signal E _c (tT) in the multipliers 12 ₂ and 12 ₄ is multiplied by signals of the form
U ₂ (t) = 2 cos (ω _o t + π + Δφ _o )
and
U4 (t) = 2 sin (ω _o t + π + Δφ _o )
respectively.

Summing in the adder 13 ₁ voltage obtained at the outputs of the multipliers 12 ₁ and 12 ₂ directly select one of the color difference signals, for example E _RY (t). Summing in the adder 13 ₂ voltage obtained at the outputs of the multipliers 12 ₃ and 12 ₄ , directly emit the second color difference signal E _BY (t).

=

=

±

=

±

=
В случае рефлексной модуляции частота f_o цветовой поднесущей мала и значение n и m не превышает практически нескольких единиц. Напротив, величина Z >> 1, например, в стандартных вещательных системах Z=525 и Z=625, в планируемых системах телевидения высокой четкости предполагается Z>1000. Поэтому с малой ошибкой, не превышающей долей процента, можно пренебречь членом ±

(2m - 1) и записать
Δφ_o=φ_он=2Πf_oτ_н=

(2n-1).The following are options for the joint processing of undelayed and delayed at different times sending color signals E _c (t). The processing options are presented both with transfer to a high frequency f _x and color signals E _c (t) processing directly at a color subcarrier frequency f _o . For example, with an additional delay at the receiving side of the sending of algebraically summed signals E _c (t) of color from the same row numbers of adjacent frames for a time T equal to the duration τ _{n of the} scan line, the phase difference φ _{is the} unmodulated color subcarrier frequency f _o in the delayed packet E _c (t- τ _n ) and in the undelivered package E _c (t) is

=

=

±

=

±

=
In the case of reflex modulation, the frequency f _{o of the} color subcarrier is small and the value of n and m does not exceed practically several units. On the contrary, the value Z >> 1, for example, in standard broadcast systems Z = 525 and Z = 625, in the planned high-definition television systems it is assumed Z> 1000. Therefore, with a small error not exceeding a fraction of a percent, we can neglect the term ±

(2m - 1) and write
Δφ _o = φ _he = 2Πf _o τ _n =

(2n-1).

(2n-1), T= τ_н. Тогда сигнал, поступающий на вход устройства 11 задержки и на один из входов перемножителя 12₁ (математическое выражение 1) - E₃(t)=E_c(t)=E_R-Y(t)cos ω_o t+E_B-Y(t)sin ω_o t. Напряжение гармонического сигнала U₁(t), поступающего на другой вход перемножителя 12₁ U₁(t)= 2cos ω_xt, где ω_х=2 π f_x, f_x>f_lim - верхней граничной частоты спектра сигнала E_c(t). Напряжение, поступающее с выхода устройства 11 задержки на один из входов перемножителя 12₂, математическое выражение (3)
E

t

t-

(2n-1)

+
Напряжение гармонического сигнала U₂(t), поступающего на другой вход перемножителя 12₂
U₂(t) = 2cos

t+Π+

(2n-1)

=2cos

t+

(2n+1)

Напряжения сигналов, поступающих на входы сумматора 13 с выходов перемножителей 12₁ и 12₂, математические выражения (2) и (4)
E₃(t) ^. U₁(t) = E_c(t) ^. 2 cos ω_xt = E_R-Y (t) x
x [cos (ω_x - ω_o)t + cos (ω_x + ω_o) t] + E_B-Y (t) x
x [ -sin (ω_x - ω_o) t + sin (ω_x + ω_o) t]
E

)

=
Напряжение на выходе сумматора 13, математическое выражение (5),
E₃(t) ^. U₁ (t) - E₃ (t-T) ^. U₂(t) =
= 2E_R-Y (t) cos (ω_x - ω_o) t + 2 E_B-Y (t) x
x sin (ω_x - ω_o) t, где ω_x- ω_o =2 π (f_x-f_o), f_x-f_o>f_lim - верхней граничной частоты спектра сигнала E_c(t). Напряжения гармонических сигналов, поступающих на синхронные детекторы 14₁ и 14₂, U_x1(t)=cos(ω_x- ω_o)t, U_x2(t)= -sin( ω_x- ω_o )t. С выходов синхронных детекторов 14₁ и 14₂ снимают цветоразностные сигналы E_R-Y(t) и E_B-Y(t).When processing the signal E _c (t) in block 10 (Fig. 4) to describe the signal processing processes E _c (t), you can use mathematical expressions (1) - (5) to describe the processing processes of the reflex modulated signal E ₃ (t), introducing the following substitutions into these expressions: E ₃ (t), E _c (t), E _1-1 (t) = E _RY (t), E _1-2 (t) = E _BY (t), ω = ω _o = 2πf _o , q = 1, qφ _n =

(2n-1), T = τ _n . Then the signal supplied to the input of the delay device 11 and to one of the inputs of the multiplier 12 ₁ (mathematical expression 1) - E ₃ (t) = E _c (t) = E _RY (t) cos ω _o t + E _BY (t) sin ω _o t. The voltage of the harmonic signal U ₁ (t) supplied to the other input of the multiplier 12 ₁ U ₁ (t) = 2cos ω _x t, where ω _x = 2 π f _x , f _x > f _lim is the upper cutoff frequency of the signal spectrum E _c ( t). The voltage supplied from the output of the delay device 11 to one of the inputs of the multiplier 12 ₂ , mathematical expression (3)
E

t

t-

(2n-1)

+
The voltage of the harmonic signal U ₂ (t) supplied to the other input of the multiplier 12 ₂
U ₂ (t) = 2cos

t + Π +

(2n-1)

= 2cos

t +

(2n + 1)

The voltage of the signals supplied to the inputs of the adder 13 from the outputs of the multipliers 12 ₁ and 12 ₂ , mathematical expressions (2) and (4)
E ₃ (t) ^. U ₁ (t) = E _c (t) ^. 2 cos ω _x t = E _RY (t) x
x [cos (ω _x - ω _o ) t + cos (ω _x + ω _o ) t] + E _BY (t) x
x [-sin (ω _x - ω _o ) t + sin (ω _x + ω _o ) t]
E

)

=
The voltage at the output of the adder 13, a mathematical expression (5),
E ₃ (t) ^. U ₁ (t) - E ₃ (tT) ^. U ₂ (t) =
= 2E _RY (t) cos (ω _x - ω _o ) t + 2 E _BY (t) x
x sin (ω _x - ω _o ) t, where ω _x - ω _o = 2 π (f _x -f _o ), f _x -f _o > f _lim is the upper cutoff frequency of the signal spectrum E _c (t). The voltages of the harmonic signals supplied to the synchronous detectors 14 ₁ and 14 ₂ , U _x1 (t) = cos (ω _x - ω _o ) t, U _x2 (t) = -sin (ω _x - ω _o ) t. Color-difference signals E _RY (t) and E _BY (t) are taken from the outputs of synchronous detectors 14 ₁ and 14 ₂ .

(2n-1)+E_B-Y(t)sin[ω_o t-

(2n-1)] и соответственно на другие входы перемножителей 12₂ и 12₄поступают гармонические сигналы вида
U₂(t)=2cos

t+

(2n+1)

и U₄(t)=2sin

t+

(2n+1)

Напряжения сигналов, поступающих в сумматор 13₁ с выходов перемножителей 12₁ и 12₂, математические выражения (6) и (8)
E₃(t) ^. U₁(t) = E_c(t) ^. 2 cos ω_xt = E_R-Y (t) +
+ E_R-Y (t) cos 2 ω_ot + E_B-Y (t) sin 2 ω_o t и

(t

Напряжение сигнала на выходе сумматора 13₁ равно 2E_R-Y(t). Напряжение сигналов, поступающих в сумматор 13₂ с выходов перемножителей 12₃ и 12₄, математические выражения (7) и (9)
E₃(t) ^. U₃(t) = E_c(t) ^. 2 sin ω_o t = E_R-Y (t) x
x sin 2 ω_ot + E_B-Y (t) - E_B-Y (t) cos 2 ω_o t и

(t

Напряжение сигнала на выходе сумматора 13₂ равно 2E_B-Y(t).In block 10 (Fig. 5) of processing the reflex modulated signal E ₃ (t), the inputs E ₃ (t) = E _c (t) = E _RY (t) cos are received at the inputs of the delay device 11 and multipliers 12 ₁ and 12 ₃ ω _o t + E _BY (t) sin ω _o t in accordance with the mathematical expression (1). The voltage of the harmonic signals supplied respectively to the second inputs of the multipliers 12 ₁ and 12 ₃ U ₁ (t) = 2cos ω _o t and U ₃ (t) = 2 sin ω _o t. The inputs of the multipliers 12 ₂ and 12 ₄ receives after the device 11 delay signal E ₃ (tT) = E _c (t- τ _n ) = E _RY (t) cos [ω _o t-

(2n-1) + E _BY (t) sin [ω _o t-

(2n-1)] and accordingly to the other inputs of the multipliers 12 ₂ and 12 ₄ receive harmonic signals of the form
U ₂ (t) = 2cos

t +

(2n + 1)

and U ₄ (t) = 2sin

t +

(2n + 1)

The voltage of the signals entering the adder 13 ₁ from the outputs of the multipliers 12 ₁ and 12 ₂ , mathematical expressions (6) and (8)
E ₃ (t) ^. U ₁ (t) = E _c (t) ^. 2 cos ω _x t = E _RY (t) +
+ E _RY (t) cos 2 ω _o t + E _BY (t) sin 2 ω _o t and

(t

The signal voltage at the output of the adder 13 ₁ is equal to 2E _RY (t). The voltage of the signals entering the adder 13 ₂ from the outputs of the multipliers 12 ₃ and 12 ₄ , mathematical expressions (7) and (9)
E ₃ (t) ^. U ₃ (t) = E _c (t) ^. 2 sin ω _o t = E _RY (t) x
x sin 2 ω _o t + E _BY (t) - E _BY (t) cos 2 ω _o t and

(t

The voltage of the signal at the output of the adder 13 ₂ is 2E _BY (t).

или q₂=

. Разность Δφ_o фаз немодулированной поднесущей в задержанной и незадержанной посылках сигнала E_c(t) цветности при этом составит

или где T₁=

, T₂=

При этом задержка может быть как неодинаковой в первом и втором полях одного кадра, например в первом поле на Т₁, а во втором на Т₂, так и одинаковой для обоих полей, например на Т₁. И вариант с одинаковой задержкой в каждом поле, и вариант с неодинаковой задержкой в каждом поле дают вертикальную четкость цветности, примерно равную половину от яркостей, но пространственно частотные характеристики в первом и втором случае могут несколько отличаться. Записав в общем случае выражение для разностей фаз при задержках на Т₁ и Т₂ в виде
Δφ₀=2Πf₀T=2Πf

τ_н=

±

(Z ± 1), можно несколько упростить это выражение. Поскольку Z >> 1 (например, в стандартных вещательных системах Z= 525 и Z=625, в планируемых системах телевидения высокой четкости Z>1000), то

= 1 с точностью не хуже 0,998 (ошибка меньше 0,2%), и выражение для Δφ_o можно записать в виде Δφ₀=

(Z ± 1) ±

(2m-1). При обработке сигнала E_c(t) цветности в блоке 10 (фиг. 4) для описания процессов обработки можно использовать математические выражения (1)-(5) процессов обработки рефлексно-модулированного сигнала E₃(t), введя в эти выражения следующие подстановки E₃(t)=E_c(t), E_1-1(t)=E_R-Y(t), E_1-2(t)=E_B-Y(t), ω = ω_o =2πf_o (эти подстановки аналогичны тем, которые были сделаны выше для случая задержки сигнала E_c(t) на τ_н) и
q =

, T =

, qφ_н= Δφ₀.In a number of technological processes for the production of television programs, for example, with some methods of forming combined images, it may be necessary that the vertical color clarity is half the vertical clarity of the brightness image. In this case, the additional delay in the sending of the summed color signals E _c (t) from the same row numbers of adjacent frames should be approximately equal to the duration of one field. Since, as indicated above, the delay should be carried out only by an integer number of lines (otherwise, there will be a spatial horizontal shift of the delayed and uncontrolled images), then in this case q ₁ =

or q ₂ =

. The phase difference Δφ _o of the unmodulated subcarrier in the delayed and uncontrolled transmission of the color signal E _c (t) in this case will be

or where T ₁ =

, T ₂ =

Moreover, the delay can be either unequal in the first and second fields of one frame, for example, in the first field at T ₁ , and in the second at T ₂ , or the same for both fields, for example at T ₁ . Both the variant with the same delay in each field and the variant with the unequal delay in each field give a vertical color sharpness approximately equal to half of the brightness, but the spatial-frequency characteristics in the first and second cases may differ slightly. Having written in the general case the expression for the phase differences at delays at T ₁ and T ₂ in the form
Δφ ₀ = 2Πf ₀ T = 2Πf

τ _n =

±

(Z ± 1), this expression can be simplified somewhat. Since Z >> 1 (for example, in standard broadcast systems Z = 525 and Z = 625, in the planned high-definition television systems Z> 1000), then

= 1 with an accuracy not worse than 0.998 (error less than 0.2%), and the expression for Δφ _o can be written in the form Δφ ₀ =

(Z ± 1) ±

(2m-1). When processing the color signal E _c (t) in block 10 (Fig. 4), mathematical expressions (1) - (5) of the processes for processing the reflex-modulated signal E ₃ (t) can be used to describe the processing processes by introducing the following substitutions into these expressions E ₃ (t) = E _c (t), E _1-1 (t) = E _RY (t), E _1-2 (t) = E _BY (t), ω = ω _o = 2πf _o (these substitutions similar to those that were done above for the case of signal delay E _c (t) by τ _n ) and
q =

, T =

, qφ _n = Δφ ₀ .

Then the signal supplied to the input of the delay device 11 and to one of the inputs of the multiplier 12 ₁ , mathematical expression (1), E ₃ (t) = E _c (t) = E _RY (t) cos ω _o t + + E _BY ( t) sin ω _o t. The voltage of the harmonic signal U ₁ (t) supplied to the other input of the multiplier 12 ₁ , U ₁ (t) = 2cos ω _x t, where ω _x = 2 π f _x , f _x > f _lim is the upper cutoff frequency of the signal spectrum E _c (t).

t

= E_R-Y(t)cos(ω₀t-Δφ_o)+ .The voltage supplied from the delay device 11 to one of the inputs of the multiplier 12 ₂ , mathematical expression (3),
E

t

= E _RY (t) cos (ω ₀ t-Δφ _o ) +.

t

=

=
Напряжение сигнала на выходе сумматора 13, математическое выражение (5),
E₃(t) ^. U₁(t) + E₃(t-T) U₂(t) = E_R-Y (t) x
x cos (ω_x - ω_o) t + E_R-Y (t) cos [(ω_x - ω_o) t +
+ π+ 2 Δφ_o] - E_B-Y (t) cos (ω_x - ω_o) t -
- E_B-Y (t)x sin [(ω_x - ω_o) t + π+ 2 Δφ_o].The voltage of the harmonic signal U ₂ (t) supplied to the second input of the multiplier 12 ₂ , U ₂ (t) = 2cos (ω _x t + π + Δφ _o ). The voltage of the signals coming from the outputs of the multipliers 12 ₁ and 12 ₂ to the adder 13, mathematical expressions (2) and (4)
E ₃ (t) ^. U ₁ (t) = E _c (t) ^. 2 cos ω _x t = E _RY (t) x
x [cos (ω _x - ω _o ) t + cos (ω _x + ω _o ) t] + E _BY (t) x
x [-sin (ω _x - ω _o ) t + sin (ω _x + ω _o ) t]
E

t

=

=
The signal voltage at the output of the adder 13, a mathematical expression (5),
E ₃ (t) ^. U ₁ (t) + E ₃ (tT) U ₂ (t) = E _RY (t) x
x cos (ω _x - ω _o ) t + E _RY (t) cos [(ω _x - ω _o) t +
+ π + 2 Δφ _o ] - E _BY (t) cos (ω _x - ω _o ) t -
- E _BY (t) x sin [(ω _x - ω _o ) t + π + 2 Δφ _o ].

)

2

-

(2m-1)

=
Поскольку при чересстрочной развертки число Z всегда нечетное (например, как указывалось выше, Z=625, Z=525),

всегда число целое, и составляющую 2Π·n

из скобок выражения аргумента для cos можно исключить как целое число периодов.co

)

2

-

(2m-1)

=
Since in interlacing, the number Z is always odd (for example, as mentioned above, Z = 625, Z = 525),

always integer, and component 2Π · n

from the brackets of the argument expression for cos can be excluded as an integer number of periods.

можно представить суммой двух величин 2

= 2

= 2

+ 2

, где Δ Z - число строк, отняв которое от числа строк Z, обеспечивают равенство значения

числу натурального ряда. В этом случае 2

будет представлять собой целое число периодов, и выражение для
cos [ (ω_x - ω_o) t + π - 2 Δφ_o] принимает вид
cos

(ω_x-ω_o)t+Π+2

=cos

(ω_x-ω_o)t+Π+2

±

(2m-1)

.Component 2

can be represented by the sum of two quantities 2

= 2

= 2

+ 2

, where Δ Z is the number of rows, subtracting which from the number of rows Z, ensure the equality of the value

the number of natural numbers. In this case 2

will be an integer number of periods, and the expression for
cos [(ω _x - ω _o ) t + π - 2 Δφ _o ] takes the form
cos

(ω _x -ω _o ) t + Π + 2

= cos

(ω _x -ω _o ) t + Π + 2

±

(2m-1)

.

Тогда cos

(ω_x-ω_o)t+Π-2

=cos

(ω_x-ω_o)t+Π-2

±

(2m-1)

.For specific values of Z, for example Z = 525 and Z = 625,

Then cos

(ω _x -ω _o ) t + Π-2

= cos

(ω _x -ω _o ) t + Π-2

±

(2m-1)

.

co

-ω_o)t+Π-2

±

(2m-1)

=
При задержке на T=T₂=

cos[(ω_x-ω_o)t+π+2Δφ₀₂]=cos[(ω_x-ω_o)t+π±

(2m-1)
Напряжение сигнала на выходе сумматора 13 будет равно: при задержке на время T₁ =

При задержке на время T₂=

E

С выходов синхронных детекторов 14₁ и 14₂, на вторые входы которых подают гармонические сигналы частоты f_x-f_o=

в соответствующей фазе, снимают цветоразностные сигналы E_R-Y(t) и E_B-Y(t). Обработка сигнала E_c(t) цветности и выделение цветоразностных сигналов E_R-Y(t) и E_B-Y(t) непосредственно на частоте f_o цветовой поднесущей осуществляется блоком 10 обработки рефлексно-модулированного сигнала E₃(t), функциональная схема которого приведена на фиг. 6.With a delay of T = T ₁ =

co

-ω _o ) t + Π-2

±

(2m-1)

=
With a delay of T = T ₂ =

cos [(ω _x -ω _o ) t + π + 2Δφ ₀₂ ] = cos [(ω _x -ω _o ) t + π ±

(2m-1)
The voltage of the signal at the output of the adder 13 will be equal to: with a time delay T ₁ =

With a time delay T ₂ =

E

From the outputs of synchronous detectors 14 ₁ and 14 ₂ , to the second inputs of which they feed harmonic signals of frequency f _x -f _o =

in the corresponding phase, color difference signals E _RY (t) and E _BY (t) are recorded. The color signal E _c (t) is processed and the color difference signals E _RY (t) and E _BY (t) are extracted directly at the color subcarrier frequency f _o by the block 10 for processing the reflex-modulated signal E ₃ (t), the functional diagram of which is shown in FIG. . 6.

Substitutions in mathematical expressions (1), (3) and (6) - (11) used to describe the processing of the reflex modulated signal E ₃ (t) directly at the frequency f of the subcarrier in block 10 (Fig. 6) are the same as indicated above when processing the signal E _c (t) in block 10 of FIG. 4.

;

;

=

=

;
Такими же, как при описании обработки сигнала E_c(t) цветности в блоке 10 фиг. 4, являются напряжения незадержанной и задержанной посылок сигнала E_c(t), поступающих в блоке 10 фиг. 6, на входы устройства 11 задержки и на входы перемножителей 12₁ и 12₃, незадержанная посылка сигнала E_c(t), сформированная в соответствии с математическим выражением (1), и на входы перемножителей 12₂ и 12₄, задержанная посылка, математическое выражение (3).E ₃ (t) = E _c (t); E _1-1 (t) = E _RY (t);
E _1-2 (t) = E _BY (t); ω = ω _o = 2 πf _o ;

;

;

=

=

;
The same as in the description of the color processing E _c (t) in block 10 of FIG. 4 are the voltages of the delayed and delayed signal bursts E _c (t) received in block 10 of FIG. 6, to the inputs of the delay device 11 and to the inputs of the multipliers 12 ₁ and 12 ₃ , the undelayed signal package E _c (t), formed in accordance with the mathematical expression (1), and to the inputs of the multipliers 12 ₂ and 12 ₄ , the delayed package, mathematical expression (3).

E ₃ (t) = Ec (t) = E _RY (t) cos ω _o t + E _BY (t) x
x sin ω _o t,
E ₃ (tT) = E _c (tT) = E _RY (t) cos (ω _o t - Δφ _o ) +
+ E _BY (t) sin (ω _o t - Δφ _o ).

The harmonic signals U ₁ (t) -U ₄ (t) supplied to the second inputs of the multipliers 12 ₁ -12 ₄ are as follows:
by the multiplier 12 ₁ - U ₁ (t) = 2cos ω _o t,
by the multiplier 12 ₃ - U ₃ (t) = 2sin ω _o t,
by the multiplier 12 ₂ - U ₂ (t) = 2cos (ω _o t + π + Δφ _o ),
by the multiplier 12 ₄ - U ₄ (t) = 2sin (ω _o t + π + Δφ _o ).

The voltage of the signal from the output of the multiplier 12 ₁ to the adder 13, mathematical expression (6)
E ₃ (t) ^. U ₁ (t) = E _c (t) ^. 2 cos ω _o t = E _RY (t) +
+ E _RY (t) cos 2 ω _o t + E _BY (t) sin 2 ω _o t.

The voltage of the signal from the output of the multiplier 12 ₃ to the adder 13 ₂ , mathematical expression (7)
E ₃ (t) ^. U ₃ (t) = E _c (t) ^. 2 sin ω _o t = E _RY (t) x
x sin 2 ω _o t + E _BY (t) - E _BY (t) cos 2 ω _o t.

t

t+Π+Δφ_c)=
Напряжение сигнала, поступающего с выхода перемножителя 12₄ в сумматор 13₂, математическое выражение (9)
E₃(t-T) ^. U₄ (t) = E_c(t) ^. 2 sin (ω_o t +
+ π+ Δφ_o) = E_R-Y (t) sin (π + 2 Δφ _o) -
-E_R-Y (t) x sin 2 ω_o t + E_B-Y (t) x
xcos ( π+ 2 Δφ_o) + E_B-Y (t) cos 2 ω_o t.The voltage of the signal from the output of the multiplier 12 ₂ in the adder 13 ₁ , mathematical expression (8)
E

t

t + Π + Δφ _c ) =
The voltage of the signal from the output of the multiplier 12 ₄ into the adder 13 ₂ , mathematical expression (9)
E ₃ (tT) ^. U ₄ (t) = E _c (t) ^. 2 sin (ω _o t +
+ π + Δφ _o ) = E _RY (t) sin (π + 2 Δφ _o ) -
-E _RY (t) x sin 2 ω _o t + E _BY (t) x
xcos (π + 2 Δφ _o ) + E _BY (t) cos 2 ω _o t.

The voltage of the signal at the output of the adder 13 ₁ , mathematical expression (10)
E _RY (t) [1 - cos 2 Δφ _o ] + E _BY (t) sin 2Δφ _o .

The voltage of the signal at the output of the adder 13 ₂ , mathematical expression (11)
-E _RY (t) sin 2 Δφ _o + E _BY (t) [1 -
- cos 2 Δφ _o ].

2

)

=
Как указывалось выше, при чересстрочной развертке число Z всегда нечетное, следовательно, Z+1 - число всегда чeтное, тогда

- целое число и
cos

2Πn

-

±

(2m-1)

= cos

-

±

(2m-1)

= 0
Модуль sin

-

±

(2m-1) всегда равен 1, а знак "+" или "-" перед единицей зависит от ряда факторов, в том числе конкретной величины Z, величины задержки T₁=

или T₂=

, знака перед составляющей

(2m - 1), значения числа m. В частных случаях примеров Z=525 и Z=625 при задержке на

,

3Π = 2Π·131+Π
В обоих случаях (Z=525 и Z=625) при задержке на T₁=

si

-

)

i

(2m-1)

=
При Z=525 и Z=625 в случае задержки на время T₂=

3

1

Соответственно напряжение на выходе сумматора 13₁ при времени задержки T₁=

для Z=525 и Z=625 E_R-Y(t) + E_B-Y(t) sin

(2m - 1). Напряжение на выходе сумматора 13₂ при тех же условиях
± E_R-Y(t)sin

(2m-1)+E_B-Y(t). Как указывалось выше, при любом целочисленном значении m модуль sin

(2m - 1) =1, изменение m вызывает лишь изменение знака перед единицей. При значениях m когда sin

(2m - 1) = - 1 напряжения сигналов на выходах сумматоров 13₁ и 13₂ соответственно: E_R-Y(t) +E_B-Y(t) и E_R-y(t)+E_B-Y(t). При значениях m, когда sin

(2m - 1) = 1, напряжения сигналов на выходах сумматоров 13₁ и 13₂ соответственно: E_R-Y(t) +E_B-Y(t) и + E_R-Y(t)+E_B-Y(t), т.е. когда на выходе сумматора 13₁ напряжение сигнала равно E_R-Y(t)-E_B-Y(t), напряжение сигнала на выходе сумматора 13₂ равно E_R-Y(t)+E_B-Y(t). Когда на выходе сумматора 13₁ напряжение сигнала равно E_R-Y(t)+E_B-Y(t), напряжение сигнала на выходе сумматора 13₂ равно -E_R-Y(t)+E_B-Y(t). Следовательно, из этих напряжений путем алгебраического суммирования в устройствах 15₁ и 15₂суммирования можно всегда выделить цветоразностные сигналы E_R-Y(t) и E_B-Y(t).co

2

)

=
As indicated above, when interlaced, the number Z is always odd, therefore, Z + 1 is the number always even, then

is an integer and
cos

2Πn

-

±

(2m-1)

= cos

-

±

(2m-1)

= 0
Sin module

-

±

(2m-1) is always 1, and the sign “+” or “-” in front of the unit depends on a number of factors, including the specific value of Z, the delay value T ₁ =

or T ₂ =

, sign in front of the component

(2m - 1), the values of the number m. In particular cases of examples Z = 525 and Z = 625 with a delay of

,

3Π = 2Π · 131 + Π
In both cases (Z = 525 and Z = 625) with a delay of T ₁ =

si

-

)

i

(2m-1)

=
With Z = 525 and Z = 625 in the case of a time delay T ₂ =

3

1

Accordingly, the voltage at the output of the adder 13 ₁ when the delay time T ₁ =

for Z = 525 and Z = 625 E _RY (t) + E _BY (t) sin

(2m - 1). The voltage at the output of the adder 13 ₂ under the same conditions
± E _RY (t) sin

(2m-1) + E _BY (t). As indicated above, for any integer value m, the modulus sin

(2m - 1) = 1, a change in m causes only a change in sign in front of one. For m when sin

(2m - 1) = - 1 the voltage of the signals at the outputs of the adders 13 ₁ and 13 _2, respectively: E _RY (t) + E _BY (t) and E _Ry (t) + E _BY (t). For m, when sin

(2m - 1) = 1, the voltage of the signals at the outputs of the adders 13 ₁ and 13 _2, respectively: E _RY (t) + E _BY (t) and + E _RY (t) + E _BY (t), i.e. when the output voltage of the adder 13 ₁ the signal voltage is E _RY (t) -E _BY (t), the voltage of the signal at the output of the adder 13 ₂ is E _RY (t) + E _BY (t). When the output voltage of the adder 13 ₁ the signal voltage is E _RY (t) + E _BY (t), the signal voltage at the output of the adder 13 ₂ is -E _RY (t) + E _BY (t). Therefore, from these stresses by algebraic summation in the devices 15 ₁ and 15 ₂ summation, you can always select the color difference signals E _RY (t) and E _BY (t).

In this and subsequent sections of the description, the following notation is used: E _Y (t) - luminance signal (as in the previous sections), for luminance video signals; E _YQ (t) - reflex-modulated luminance signal (as in the previous sections), for signals generated by reflex quadrature modulation of the luminance subcarrier by two luminance video signals; E _M (t) - a hollow color television signal (as in the previous sections), which includes brightness signals E _Y (t); E ¹ _MQ (t) - full color television signal, which includes reflex-modulated signals E _YQ (t) brightness; E _MQ (t) - color television signal, E _MQ (t) not containing a synchronization signal E _sc ; E _MQ1-2 (t) - full color television signal containing information about two television images.

2S-1+

из второго поля, где s - число натурального ряда. Сигналы двух строк записи (2s-1) и 2s первого изображения преобразуются в сигналы одной строки передачи первого изображения. Сигналы двух строк записи (2s-1) и 2s второго изображения преобразуются в сигналы одной строки передачи второго изображения. Преобразования эти осуществляются для сигналов первого и второго изображений раздельно и идентичными способами.A television system with the simultaneous transmission of color difference signals E _RY (t), E _BY (t) in the blanking intervals can be converted in such a way that information about two color television images can be transmitted simultaneously with its full color television signal. In this case, both images are transmitted in real time and in a combined frequency band, nominal for transmitting one such image with the same sharpness vertically and horizontally. In the full color television signal E _MQ1-2 (t) of this television system, the signals of the first and second images are transmitted alternately through the line. During the duration of one line, reflex-modulated signals are transmitted containing information about the brightness and color of two adjacent in space lines of one image. To do this, on the transmitting side, luminance signals E _y (t) and chrominance signals E * _c (t) are stored for two fields of one frame separately of the first and second images, placing sequentially in the recording lines of each image the signals of adjacent in space lines of this image from the first and second fields. In this case, the recording line (2s-1) contains information about the brightness and color of the line (2s-1) from the first field, and the recording line 2s contains information about the brightness and color of the line

2S-1 +

from the second field, where s is the number of the natural number. The signals of the two recording lines (2s-1) and 2s of the first image are converted into signals of one transmission line of the first image. The signals of the two recording lines (2s-1) and 2s of the second image are converted into signals of one transmission line of the second image. These transformations are carried out for the signals of the first and second images separately and in identical ways.

2S-1+

второго поля записываемого кадра размещаются соответственно в строках записи (2s-1) и 2s запоминающего устройства 23. Сжатые во времени сигналы E*_c(2s-1)(t) и E*_c(2s)(t) цветности из строк записи (2s-1) и 2s одновременно считывают из запоминающего устройства 23 и алгебраически суммируют их в сумматоре 24 блока 22. При этом на выходе сумматора 24 получают общий для строк записи (2s-1) и 2s этого изображения сжатый во времени сигнал E*_c(t) цветности на поднесущей, частота которой остается равной f₀. Разность фаз φ_он немодулированной цветовой поднесущей в строках передачи, сформированных из сигналов строк записи (2s-1) и 2s и сформированных из сигналов строк записи (2s+1) и (2s+2) того же самого изображения, составляет φ_он≈

(2n-1) . Считанными одновременно из строк записи (2s-1) и 2s из запоминающего устройства 23 сигналами E_y(2s-1)(t) и E_y2s(t) яркости, как видеосигналами E_1-1(t) и E_1-2(t) в блоке 1 модулируют поднесущую яркости частоты f_y, формируя рефлексно-модулированный сигнал E_YQ(t) яркости, являющийся рефлексно-модулированным сигналом E₃(t). Поднесущая яркости частоты f_yвыбирается равной нечетной гармонике четвертьстрочной частоты f_н, т.е. f_y=

f_н . В сформированном рефлексно-модулированном сигнале E_YQ(t) яркости разность фаз φ_o поднесущих рефлексно-модулированного сигнала E_YQ(t) в одинаковых по номерам строках смежных кадров при этом будет равна φ_yp= +

(2d-1) , где d - число натурального ряда.The _{generation of} signals of transmission lines of one image in the full color television signal E _MQ1-2 (t) can be carried out by block 22, an example of a functional diagram of which is shown in FIG. 10. The full color television signal of one image E _M (t) is input to the storage device 23 of block 22 (Fig. 10). When recording the signals E _y (t), E _c (t) of luminance and color of one frame of this image, signals of adjacent rows in space, i.e. signals of the line (2s-1) of the first field and line

2S-1 +

the second field of the recorded frame are placed respectively in the recording lines (2s-1) and 2s of the storage device 23. The time-compressed signals E * _{c (2s-1)} (t) and E * _{c (2s)} (t) of color from the recording lines ( 2s-1) and 2s are simultaneously read from the storage device 23 and algebraically summed in the adder 24 of the block 22. At the same time, at the output of the adder 24, the time-compressed signal E * _c (for the recording lines (2s-1) and 2s of this image) is obtained t) chrominance on a subcarrier whose frequency remains equal to f ₀ . The phase difference φ _{it of the} unmodulated color subcarrier in the transmission lines formed from the signals of the recording lines (2s-1) and 2s and formed from the signals of the recording lines (2s + 1) and (2s + 2) of the same image is φ _he ≈

(2n-1). Read simultaneously from the recording lines (2s-1) and 2s from the storage device 23 signals E _{y (2s-1)} (t) and E _y2s (t) of brightness, as video signals E _1-1 (t) and E _1-2 ( t) in block 1, a luminance subcarrier of frequency f _{y is} modulated, forming a reflex modulated luminance signal E _YQ (t), which is a reflex modulated signal E ₃ (t). The brightness subcarrier of the frequency f _y is chosen to be equal to the odd harmonic of the quarter-line frequency f _n , i.e. f _y =

f _n In the generated reflex-modulated signal E _YQ (t) of brightness, the phase difference φ _{o of the} subcarriers of the reflex-modulated signal E _YQ (t) in the same row numbers of adjacent frames will be equal to φ _yp = +

(2d-1), where d is the number of the natural number.

From the output of block 1, the reflex-modulated luminance signal E _YQ (t) is fed to the input of the adder 25, the other input of which receives the time-compressed color signal E * _c (t). From the output of the adder 25, the signals of the transmission lines of one image of the color television signal E ¹ _MQ (t), i.e., a signal that does not contain the synchronization signal Esc, are taken. The color television signal E ¹ _MQ1 (t), containing information about the brightness and color of the recording lines (2s-1) and 2s of the first image, is transmitted in line (2s-1) of the full color television signal E _MQ1-2 (t). The color television signal E ¹ _MQ2 (t) containing information about the brightness and color of the recording lines (2s-1) and 2s of the second image is transmitted in line 2s of the full color television signal E _MQ1-2 (t), i.e. signals E ¹ _MQ1 (t) and E ¹ _MQ2 (t) are transmitted through the line. In this case, the color signals of the first and second images are transmitted respectively in the blanking intervals, and the reflex-modulated brightness signals of the first and second images are transmitted without changing their time scale in the active intervals of the lines of the full color television signal E _MQ1-2 (t). Moreover, in the same line numbers of adjacent frames transmit signals of the same of two images.

The full color television signal E _MQ1-2 (t), containing the signals of the transmission lines of the first and second images, is generated by the device, an example of the circuit of which is shown in FIG. 11. In this device, the signals E ¹ _MQ1 (t) and E ¹ _MQ2 (t) of the transmission lines of the first and second images generated in blocks 22 ₁ and 22 ₂ , similar to block 22, are summed in the adder 26 (Fig. 11). The adder 26 also receives the synchronization signals E _sd and additional information, which are mixed into the full color television signal E _MQ1-2 (t). An exemplary view of two lines of the full color television signal E _MQ1-2 (t) is shown in FIG. 12.

When the length of the transmission line of the signals of the first image from t _0-1 to t _0-2 and the transmission line of signals of the second image from t _0-2 to t _0-3 (intervals t _0-1 -t _0-2 and t _0-2 - t _{0-3 are the} same) in the time intervals t _0-1 -t _1-1 and t _0-2 -t _1-2 - synchronization signals are transmitted, in the intervals t _2-1 -t _3-1 and t _2-2 - t _3-2 - chroma signals E * _c (t), in the intervals t _4-1 -t _5-1 and t _4-2 -t _5-2 - reflex-modulated luminance signals E _YQ (t), t _{1- 1} -t _2-1 and t _1-2 -t _2-2 , t _3-1 -t _4-1 and t _3-2 -t _4-2 , t _5-1 -t _0-2 , t _{5- 2} -t _0-3 - guard intervals. On the receiving side, full color television signal E _MQ1 - ₂ (t) is used to extract chroma signals E * _c (t) and luminance reflex modulated signals E _YQ (t) of the first and second images. The processing of these signals is carried out in the same way in devices 27 ₁ and 27 ₂ . An example of a functional processing circuit for the full color television signal E _MQ1-2 (t) is shown in FIG. 13. Separation of the full color television signals of the first and second images and the isolation of the color signal E * _c1 (t) and the reflex modulated signal E _YQ1 (t) of the brightness of the first image, the signal E * _c2 (t) and the reflex modulated signal E _YQ2 (t) of the brightness of the second image is produced by the signal separation circuit 5. In the same scheme 5 is the selection of signals E _s , E _d synchronization and additional information.

Devices 27 ₁ and 27 _{2 for} processing signals of the first and second images, the outputs of which are taken respectively signals E _y1 (t) brightness and color-difference signals E _{(BY) 1} (t), E _{(RY) 1} (t) of the first image, and the signal E _y2 (t) and color difference signals E _{(RY) 2} (t), E _{(BY) 2} (t) of the second image are identical. Therefore, in FIG. 14 is an example of a functional diagram of a first image signal processing apparatus 27.

(2n+1) . Полученные на выходах канала 6 цветоразностные сигналы E_R-Y(t) и E_B-Y(t) используют для воспроизведения информации о цветности, содержащейся в строках записи (2s-1) и 2s данного изображения. Снимаемые с выхода канала 6 цветоразностные сигналы E_R-Y(t) и E_B-Y(t) записываются в блоки 28₁ и 28₂(фиг. 14) памяти соответственно. Считывание цветоразностного сигнала E_R-Y(t) из строки записи (2s-1) производится в первом поле при воспроизведении строки (2s-1) изображения. Считывание цветоразностного сигнала E_R-Y(t) из строки записи 2s производится через время T₁=

при воспроизведении строки

2S-1+

изображения во втором поле. Идентичным способом производится запись и считывание цветоразностного сигнала E_B-Y(t) из соответствующих строк записи (2s-1) и 2s блока 28₂памяти. Обработка рефлексно-модулированного сигнала E_YQ(t) яркости, выделенного схемой 5 (фиг. 13) из строк передачи одного изображения полного цветового телевизионного сигнала E_MQ1-2(t), производится в предназначенном для этого блока 29 (фиг. 14). Рефлексно-модулированный сигнал E_YQ(t) яркости одного изображения подается на вход блока 10 обработки рефлексно-модулированного сигнала вида E₃(t). Дальнейшая обработка рефлексно-модулированного сигнала E_YQ(t) яркости в блоке 10 может осуществляться как с переносом на высокочастотную несущую (фиг. 4), так и непосредственно на частоте f_y поднесущей яркости. Время задержки рефлексно-модулированного сигнала E_YQ(t) яркости равно длительности кадра τ_p = Z τ_н, где τ_н - длительность строки, τ_н=

.Isolated from the full color television signal by the circuit 5 (Fig. 13), the color signals E * _c (t) of the transmission lines of one image are fed to the input of the color signal processing channel 6. The difference Δφ _{o of the} phases of the harmonic signals, by which the delayed and uncontrolled sending of the chrominance signals E * _c (t) are multiplied, in block 10 of the color signal processing channel 6, is selected to be Π + Δφ _o ≈

(2n + 1). The color difference signals E _RY (t) and E _BY (t) obtained at the outputs of channel 6 are used to reproduce the color information contained in the recording lines (2s-1) and 2s of this image. The color difference signals E _RY (t) and E _BY (t) taken from the output of channel 6 are recorded in the memory blocks 28 ₁ and 28 ₂ (Fig. 14), respectively. The color difference signal E _RY (t) is read from the recording line (2s-1) in the first field when playing the image line (2s-1). The color difference signal E _RY (t) is read from the recording line 2s after time T ₁ =

when playing a string

2S-1 +

images in the second field. In an identical way, the color difference signal E _BY (t) is recorded and read from the corresponding recording lines (2s-1) and 2s of the memory block 28 ₂ . The processing of the reflex modulated brightness signal E _YQ (t) highlighted by circuit 5 (Fig. 13) from the transmission lines of one image of the full color television signal E _MQ1-2 (t) is performed in the unit 29 intended for this purpose (Fig. 14). The reflex modulated signal E _YQ (t) of the brightness of one image is fed to the input of the reflex modulated signal processing unit 10 of the form E ₃ (t). Further processing of the reflex-modulated brightness signal E _YQ (t) in block 10 can be carried out both with transfer to a high-frequency carrier (Fig. 4), and directly at a frequency f _{y of the} brightness subcarrier. The delay time of the reflex-modulated signal E _YQ (t) of brightness is equal to the frame duration τ _p = Z τ _n , where τ _n is the line length, τ _n =

.

(2n +1)] . Напряжения, полученные в результате первого и второго перемножений, суммируют в сумматоре 13, формируя сигнал с развернутыми боковыми полосами на несущей, частота которой f_xy+ f_y выше граничной верхней частоты f_max спектра рефлексно-модулированного сигнала E_YQ(t) яркости. После детектирования этого сигнала с выходов синхронных детекторов 14₁ и 14₂ снимают сигналы E_y(2s-10)(t) яркости строки (2s-1) первого поля и E_y(2s)(t) яркости строки

2S-1+

из второго поля одного и того же изображения. Обработка рефлексно-модулированного сигнала E_YQ(t) яркости непосредственно на частоте f_y поднесущей яркости можeт осуществляться в блоке 10 (фиг. 5). Незадержанный сигнал E_YQ(t) умножается в перемножителе 12₁ на гармонический сигнал вида U₁(t)=2cosω_yt. Задержанный сигнал E_YQ(t- τ_р) умножается в перемножителе 12₂ на гармонический сигнал вида U₂(t) = 2 sin [ω_yt +

(2d +1)].In block 10 (Fig. 4), the delayed sending of the signal E _YQ (t) is supplied to the inputs of the delay device 11 and the multiplier 12 ₁ . In the multiplier 12 ₁ , the signal E _YQ (t) is multiplied by a harmonic signal of the form U ₁ (t) = 2cosω _xy (t), where ω _xy = 2πf _xy , f _xy is the frequency of the harmonic signal exceeding the upper cutoff frequency f _{max of the} spectrum reflectively -modulated signal E _YQ (t) brightness. The delayed signal E _YQ (t- τ _p ) is multiplied in the multiplier 12 ₂ by a harmonic signal of the form U ₂ (t) = 2 cos [ω _xy t +

(2n +1)]. The voltages obtained as a result of the first and second multiplications are summed in the adder 13, forming a signal with unfolded side bands on the carrier, whose frequency f _xy + f _{y is} higher than the boundary upper frequency f _{max of the} spectrum of the reflex-modulated signal of brightness E _YQ (t). After detecting this signal from the outputs of synchronous detectors 14 ₁ and 14 _{2, the} signals E _{y (2s-10) (} t) of the line brightness (2s-1) of the first field and E _{y (2s)} (t) of the line brightness are removed

2S-1 +

from the second field of the same image. The processing of the reflex modulated brightness signal E _YQ (t) directly at the frequency f _{y of the} brightness subcarrier can be carried out in block 10 (Fig. 5). The uncontrolled signal E _YQ (t) is multiplied in the multiplier 12 ₁ by a harmonic signal of the form U ₁ (t) = 2cosω _y t. The delayed signal E _YQ (t- τ _p ) is multiplied in the multiplier 12 ₂ by a harmonic signal of the form U ₂ (t) = 2 sin [ω _y t +

(2d +1)].

(2d +1)]. После алгебраического суммирования в сумматоре 13₂ напряжений, полученных в результате этих перемножений, на его выходе непосредственно выделяют сигнал E_y(2s)(t) яркости строки

2S-1+

из второго поля. Сигналы E_y(2s-1)(t) и E_y(2s)(t) яркости записываются соответственно в строки записи (2s-1) и 2s устройства 30 памяти (фиг. 14).After algebraic summation in the adder 13 _{1 of the} voltages obtained as a result of the first and second multiplications, the signal E _{y (2s-1)} (t) of the line brightness (2s-1) of the first field is directly isolated at the output of the adder 13 ₁ . The uncontrolled signal E _YQ (t) also enters the multiplier 12 ₃ , where it is multiplied by a harmonic signal of the form U ₃ (t) = 2sin ω _y t. The delayed signal E _YQ (t- τ _p ) is also fed to the multiplier 12 ₄ , where it is multiplied by a harmonic signal of the form U ₄ (t) = 2 sin [ω _y t +

(2d +1)]. After algebraic summing in the adder 13 ₂ voltages obtained as a result of these multiplications, the signal E _{y (2s)} (t) of line brightness is directly extracted at its output

2S-1 +

from the second field. The luminance signals E _{y (2s-1)} (t) and E _{y (2s)} (t) are recorded respectively in the recording lines (2s-1) and 2s of the memory device 30 (Fig. 14).

при воспроизведении строки

2S-1+

изображения во втором поле. Таким образом на выходе устройства 27 обработки сигналов одного изображения восстанавливаются сигналы чересстрочной развертки.The read signals E _y (t) from the recording line (2s-1) is carried out in the first field when playing the image line (2s-1). Reading the signal E _y (t) brightness from the recording line 2s is carried out through T ₁ =

when playing a string

2S-1 +

images in the second field. Thus, at the output of the signal processing device 27 of an image, interlaced signals are restored.

The above processing of the full color television signal E _MQ1-2 (t) of two images can be used when reproducing stereo-color images, as well as transmitting two independent programs with subsequent transcoding at the receiving side into signals of standard broadcasting or other systems.

и помещают незадержанную посылку в интервал гашения восстановленного сигнала E_y(2s-1)(t) яркости строки (2s-1) данного изображения, а задержанную посылку сигнала E*_c(t) цветности помещают в интервал гашения восстановленного сигнала E_y2s(t) яркости строки

2S-1+

этого же изображения. Формирование из полного цветового телевизионного сигнала E_MQ1-2(t) двух программ полных цветовых телевизионных сигналов E_M1(t) и E_M2(t) первой и второй программ может быть осуществлено устройством, пример функциональной схемы которого показан на фиг. 15.When transmitting images of two independent programs, it may be necessary to separate them at an intermediate receiving point and transmit further the image of each program with the full color television signal E _m (t) (Fig. 8) of the proposed television system. In this case, the processing of the full color television signal E _MQ1-2 (t) and separation of the reflex-modulated signal E _YQ (t) of brightness is performed at an intermediate receiving point. At the intermediate point, decoding of the color signals E * _c (t) is not required. The decoding of these signals is carried out at the receiving side, for example, directly in televisions, identical to that described above with reference to FIG. 9. At the intermediate receiving point, the chrominance signals E * _c (t) of the first and second images are extracted from their signal lines of the corresponding image of the full color television signal E _MQ1-2 (t). The selected color signals E * _c (t) in the processing channel of each image are repeated by a delay of time T ₁ =

and the undelayed packet is placed in the blanking interval of the restored signal E _{y (2s-1)} (t) of the line brightness (2s-1) of the given image, and the delayed sending of the chroma signal E * _c (t) is placed in the blanking interval of the restored signal E _y2s (t ) line brightness

2S-1 +

of the same image. The formation from the full color television signal E _MQ1-2 (t) of two programs of the full color television signals E _M1 (t) and E _M2 (t) of the first and second programs can be carried out by a device, an example of a functional diagram of which is shown in FIG. fifteen.

Selected by the circuit 5 from the incoming signal E _MQ1-2 (t), the reflection-modulated luminance signals E _YQ (t) and the color signals E * _c (t) of each image are fed to their processing channel 31 ₁ , 31 ₂ . Signal processing of the first and second images is carried out in channels 31 ₁ , 31 ₂ completely identically. Therefore, we can confine ourselves to the description of one channel 31. Reflex-modulated luminance signals E _YQ (t) are processed in block 29.

, помещая этот сигнал в интервале гашения строки

2S-1+

сигнала E_y(t) яркости в сумматоре 32. На выходах каналов 31₁, 31₂ получают цветовые телевизионные сигналы E_M1(t) и E_M2(t) чересстрочной развертки изображений первой и второй программ соответственно.The color signal E * _c (t) is recorded simultaneously in the recording lines (2s-1) and 2s of the memory unit 28 (Fig. 15). The read color signal E * _c (t) from the recording lines (2s-1) is placed in the blanking interval of the line (2s-1) of the brightness signal E _y (t) in the adder 32. Reading the color signal E * _c (t) from the recording line 2s produce after time T ₁ =

by placing this signal in the line blanking interval

2S-1 +

signal E _y (t) of brightness in the adder 32. At the outputs of channels 31 ₁ , 31 ₂ receive color television signals E _M1 (t) and E _M2 (t) interlaced images of the first and second programs, respectively.

 Below are descriptions of options for generating signals of one image on the transmitting side and processing them on the receiving side.

t+

цветности этого же изображения из строки

2S-1+

второго поля.The signal voltage E * _{c (2s-1)} (t) of the color of one of the images in the row (2s-1) of the first field is
E * _RY (t) cos K ω _o [t + (2 s-1) τ _n ] +
+ E * _BY (t) sin K ω _o [t + (2s-1) τ _n ], where K is the compression coefficient of the color signal E * _c (t) in time, ω _o = 2πf _o . This voltage is recorded in the recording line of the storage device 23 (Fig. 10). In the recording line 2s of the storage device 23, the voltage of the signal E is written

t +

colors of the same image from a string

2S-1 +

second field.

t+

2S-1+

+E $\genfrac{}{}{0ex}{}{\text{*}}{\text{B}}$ _-Y(t)sinK

t+

2S-1+

При суммировании этих напряжений в сумматоре 24 фаза немодулированной цветовой поднесущей в суммированном сигнале цветности E*_c(t) будет равна K ω_o

2S-1+

. При суммировании сигнала E*_c(2s)(t) из строки 2s первого поля этого же изображения и сигнала E*

t+

цветности из строки

2S+

второго поля на выходе сумматора 24 фаза немодулированной поднесущей в суммированном сигнале E_c(t+2 τ_н) будет равна K

2S+

) , так как эти сигналы записывались соответственно в строки записи (2s-1) и (2s+1), в строки (2s) и (2s+2) запоминающегося устройства 23 через время τ_н в первом поле и через время τ_н во втором поле, а считываются из устройства 23 через время 2 τ_н. Разность фаз немодулированной поднесущей в сигналах одного и того же изображения через время 2 τ_н в сигналах E*_c(t) и E*_c(t+2 τ_н) равна К ω_о τ_н=К φ_он, а после растяжки во времени на приемной стороне в

раз Δφ_o= φ_oн= 2Πf_oτ_н ≈

(2n-1) . Обработка сигнала E_c(t) цветности с такой разностью фаз между задержанной и незадержанной посылками этого сигнала в блоках 10 обработки рефлексно-модулированного сигнала E₃(t) (фиг. 4 и 5) детально рассмотрены при описании телевизионной системы с одновременной передачей цветоразностных сигналов в интервале гашения. Единственное отличие в том, что задержка сигнала E_c(t) в устройстве 11 задержки в блоке 10 должна осуществляться в этом случае на время 2 τ_н, как это объяснено выше. При этом поскольку фаза поднесущей величина относительная, можно принять

2S-1+

= 0) (опорная фаза), тогда

2S+

=φ_oн=

(2n-1) Результаты также останутся идентичными, если в математические выражения (1) и (3) ввести

2S-1+

=φ_OH1) , введя также φ_он1 в выражения для U₁(t) и U₂(t) при описании работы блока 10, представленного на фиг. 4, и в выражения для U₁(t), U₂(t), U₃(t), U₄(t) при описании работы блока 10, изображенного на фиг. 5. Тогда для обозначения фазы поднесущей задержанной посылки сигнала E_c(t)

2S+

следует ввести обозначение
φ_он1+φ_он=φ_он1+

(2n-1)
Обработка рефлексно-модулированных сигналов E_YQ(t) яркости в канале 7 (фиг. 3) также осуществляется в блоке 10 обработки рефлексно-модулированных сигналов E₃(t), примеры функциональных схем которого приведены на фиг. 4 и 5. При формировании рефлексно-модулированного сигнала E_YQ(t) яркости одного из изображений считанные из строк записи (2s-1) и 2s запоминающего устройства 23 (фиг. 10) сигнал E_y(2s-1)(t) яркости строки (2s-1) из первого поля и сигнал E_y(2s)(t) яркости строки

2S-1+

из второго поля модулируют поднесущую яркости, частота которой f_y
E_YQ (t) = E_Y(2s-1) (t) cos ω_y t + E_y(2s) (t) x
x sin ω_yt, где ω_y = 2π f_y.E $\genfrac{}{}{0ex}{}{\text{*}}{\text{R}}$ _-Y (t) cosK

t +

2S-1 +

+ E $\genfrac{}{}{0ex}{}{\text{*}}{\text{B}}$ _-Y (t) sinK

t +

2S-1 +

When summing these voltages in the adder 24, the phase of the unmodulated color subcarrier in the summed color signal E * _c (t) will be equal to K ω _o

2S-1 +

. When summing the signal E * _{c (2s)} (t) from line 2s of the first field of the same image and signal E *

t +

color from a string

2S +

the second field at the output of the adder 24 phase unmodulated subcarrier in the summed signal E _c (t + 2 τ _n ) will be equal to K

2S +

), since these signals were recorded respectively in the recording lines (2s-1) and (2s + 1), in the lines (2s) and (2s + 2) of the memory device 23 after a time τ _n in the first field and after a time τ _n in the second field, and are read from the device 23 after 2 τ _n . The phase difference of the unmodulated subcarrier in the signals of the same image after 2 τ _n in the signals E * _c (t) and E * _c (t + 2 τ _n ) is equal to K ω _о τ _n = K φ _it , and after stretching time on the receiving side in

time Δφ _o = φ _OH = 2Πf _o τ _n ≈

(2n-1). The processing of the color signal E _c (t) with such a phase difference between the delayed and uncontrolled bursts of this signal in the blocks 10 for processing the reflex-modulated signal E ₃ (t) (Figs. 4 and 5) are considered in detail when describing a television system with simultaneous transmission of color-difference signals in the blanking interval. The only difference is that the delay of the signal E _c (t) in the delay device 11 in block 10 should be carried out in this case for a time of 2 τ _n , as explained above. Moreover, since the phase of the subcarrier is relative, we can take

2S-1 +

= 0) (reference phase), then

2S +

cp = _OH =

(2n-1) The results will also remain identical if we introduce into mathematical expressions (1) and (3)

2S-1 +

= φ _OH1 ), also introducing φ _on1 in the expressions for U ₁ (t) and U ₂ (t) when describing the operation of unit 10 shown in FIG. 4, and in expressions for U ₁ (t), U ₂ (t), U ₃ (t), U ₄ (t) when describing the operation of block 10 shown in FIG. 5. Then, to indicate the phase of the subcarrier of the delayed signal transmission, E _c (t)

2S +

the designation should be entered
φ _he1 + φ _he = φ _he1 +

(2n-1)
Processing of reflex modulated signals E _YQ (t) of brightness in channel 7 (FIG. 3) is also carried out in block 10 for processing reflex modulated signals E ₃ (t), examples of functional circuits of which are shown in FIG. 4 and 5. When generating a reflex modulated brightness signal E _YQ (t) of one of the images, read from the recording lines (2s-1) and 2s of the storage device 23 (Fig. 10), the brightness signal E _{y (2s-1)} (t) line (2s-1) from the first field and the signal E _{y (2s)} (t) the brightness of the line

2S-1 +

from the second field, a brightness subcarrier is modulated whose frequency f _y
E _YQ (t) = E _{Y (2s-1)} (t) cos ω _y t + E _{y (2s)} (t) x
x sin ω _y t, where ω _y = 2π f _y .

f_н, то разность фаз φ_yр немодулированной поднесущей яркости в одинаковых по номерам строках смежных кадров составляет
φ_yp=2Πf_yZτ_н= 2P

Z=2Π(2d-1)

Поскольку разность фаз немодулированной поднесущей яркости через каждые четыре строки равна 2 π (2d-1), т.е. целому числу периодов, то выражение для φ_yр можно записать в виде
φ_yp= 2Π(2d-1)

= 2π(2d-1)

+ 2π(2d-1)

, где Δ Z - число строк, которое минимально нужно алгебраически вычесть из числа строк Z в кадре, чтобы частное от деления

было числом натурального ряда. Тогда
cos

t+2Π(2d-1)

+2Π(2d-1)

= cos

t+

(2d-1)ΔZ

При чересстрочной развертке число Z всегда нечетное, напротив, число Z-ΔZ, как дающее при делении на четыре целочисленное значение, всегда четное, следовательно, число ΔZ всегда нечетное, причем можно показать, что для любого нечетного Z >> 1 величина Δ Z всегда будет равна либо +1, либо -1. В этом случае cos(ω_yt+φ_yp) = cos

t ±

(2d-1)

. . При обработке рефлексно-модулированного сигнала E_YQ(t) яркости в блоке 10 (фиг. 4) обработки рефлексно-модулированного сигнала E₃(t), пример функциональной схемы которого приведен на фиг. 4, для описания процессов обработки рефлексно-модулированного сигнала E_YQ(t) яркости можно использовать математические выражения (1-5) описания процессов обработки рефлексно-модулированного сигнала E₃(t), введя в эти выражения следующие подстановки:
E₃(t) = E_YQ(t) , E_1-1 (t) = E_y(2s-1) (t),
E_1-2(t) = E_Y(2s) (t), ω = ω _y = 2π f_y, q = Z,
qφ_н= ±

(2d-1), T = Z τ_н. Тогда сигнал, поступающий на вход устройства 11 задержки и на один из входов перемножителя 12₁, математическое выражение (1), E₃(t)=E_YQ(t)=E_y(2s-1)(t)cos ω_yt+E_y(2s)(t)sin ω_yt. Напряжение гармонического сигнала U₁(t), поступающего на другой вход перемножителя 12₁, U₁(t)= 2cos ω_xy(t), где ω_xy= 2πf_xy, f_xy>f_max - верхней граничной частоты спектра рефлексно-модулированного сигнала E_YQ(t) яркости.Since the frequency f _{y of the} brightness subcarrier is

f _n , then the phase difference φ _{yр of the} unmodulated brightness subcarrier in the same row numbers of adjacent frames is
φ _yp = 2Πf _y Zτ _n = 2P

Z = 2Π (2d-1)

Since the phase difference of the unmodulated luminance subcarrier is equal to 2 π (2d-1) every four lines, i.e. integer number of periods, then the expression for φ _yр can be written as
φ _yp = 2Π (2d-1)

= 2π (2d-1)

+ 2π (2d-1)

, where Δ Z is the number of lines that minimally need to be algebraically subtracted from the number of lines Z in the frame so that the quotient from division

was a natural number. Then
cos

t + 2Π (2d-1)

+ 2Π (2d-1)

= cos

t +

(2d-1) ΔZ

When interlaced, the number Z is always odd, on the contrary, the number Z-ΔZ, which gives an integer value when divided by four, is always even, therefore, the number ΔZ is always odd, and it can be shown that for any odd Z >> 1 the value Δ Z is always will be equal to +1 or -1. In this case, cos (ω _y t + φ _yp ) = cos

t ±

(2d-1)

. . When processing the reflex modulated signal E _YQ (t) of brightness in block 10 (FIG. 4), the processing of the reflex modulated signal E ₃ (t), an example of a functional diagram of which is shown in FIG. 4, to describe the processes of processing a reflex modulated signal E _YQ (t) of brightness, one can use mathematical expressions (1-5) to describe the processes of processing a reflex modulated signal E ₃ (t) by introducing the following substitutions into these expressions:
E ₃ (t) = E _YQ (t), E _1-1 (t) = E _{y (2s-1)} (t),
E _1-2 (t) = E _{Y (2s)} (t), ω = ω _y = 2π f _y , q = Z,
qφ _n = ±

(2d-1), T = Z τ _n Then the signal supplied to the input of the delay device 11 and to one of the inputs of the multiplier 12 ₁ , mathematical expression (1), E ₃ (t) = E _YQ (t) = E _{y (2s-1)} (t) cos ω _y t + E _{y (2s)} (t) sin ω _y t. The voltage of the harmonic signal U ₁ (t) supplied to the other input of the multiplier 12 ₁ , U ₁ (t) = 2cos ω _xy (t), where ω _xy = 2πf _xy , f _xy > f _max is the upper cutoff frequency of the spectrum of reflex-modulated signal E _YQ (t) brightness.

t

os

t ±

(2d-1)

+ На второй вход перемножителя 12₂ поступает напряжение гармонического сигнала U₂(t) = 2cos

t+Π ∓

(2d-1)

. Напряжения сигналов, поступающих с выходов перемножителей 12₁ и 12₂ в сумматор 13, математические выражения (2) и (4),
E₃(t) ^. U₁(t) = E_YQ(t) ^. 2 cos ω_xy t =
= E_Y(2s-1) (t) [cos (ω_xy -ω _y) t + cos (ω_xy +
+ ω_y)t ] + E_Y(2s) (t) [-sin (ω_xy - ω_y) t +
+ sin (ω_xy + ω_y) t]
и

так как Π+2

= 2Πd, Π-2

= -2Π(d-2).The voltage supplied from the output of the delay device 11 to one of the inputs of the multiplier 12 ₂ , mathematical expression (3)
E

t

os

t ±

(2d-1)

+ The second input of the multiplier 12 ₂ receives the voltage of the harmonic signal U ₂ (t) = 2cos

t + Π ∓

(2d-1)

. The voltage of the signals coming from the outputs of the multipliers 12 ₁ and 12 ₂ to the adder 13, mathematical expressions (2) and (4),
E ₃ (t) ^. U ₁ (t) = E _YQ (t) ^. 2 cos ω _xy t =
= E _{Y (2s-1)} (t) [cos (ω _xy- ω _y ) t + cos (ω _xy +
+ ω _y ) t] + E _{Y (2s)} (t) [-sin (ω _xy - ω _y ) t +
+ sin (ω _xy + ω _y ) t]
and

since Π + 2

= 2Πd, Π-2

= -2Π (d-2).

The voltage at the output of the adder 13, mathematical expression (5)
E ₃ (t) ^. U ₁ (t) + E ₃ (tT) ^. U ₂ (t) = 2 E _{y (2s-1)} (t) x
x cos (ω _xy - ω _y ) t - 2 E _{y (2s)} (t) sin (ω _xy - ω _y ) t, where ω _xy - ω _y = 2 π (f _xy - f _y ), f _xy - f _o > f _max .

2S-1+

из второго поля одного из изображений.The voltages of the harmonic signals supplied to the synchronous detectors 14 ₁ and 14 _2, respectively, are U _x1 (t) = cos (ω _xy - ω _y ) t and U _x2 (t) = - sin (ω _xy - ω _y ) t. From the outputs of synchronous detectors 14 ₁ and 14 _{2, the} signals of the line brightness E _{y (2s-1)} (t) of the first field and the line brightness signal E _{y (2s)} (t) are taken

2S-1 +

from the second field of one of the images.

(2d-1), T = Z τ_н.Processing the reflex modulated signal E _YQ (t) of luminance can be carried out directly at the frequency f _{y of the} luminance subcarrier in block 10 for processing the reflex modulated signal E ₃ (t), the functional diagram of which is shown in FIG. 5. To describe the signal processing processes E _YQ (t) in block 10, mathematical expressions (1) and (3) and (6-9) are used with the corresponding substitutions
E ₃ (t) = E _YQ (t), E _1-1 (t) = E _{Y (2s-1)} (t),
E _1-2 (t) = E _{Y (2s)} (t), ω = ω _y = 2 π f _y , q = Z,
qφ _n = ±

(2d-1), T = Z τ _n

Uncontrolled sending of a signal to the inputs of the delay device 11 and multipliers 12 ₁ , 12 ₃ , mathematical expression (1), E ₃ (t) = E _YQ (t) = E _{y (2s-1)} (t) cos ω _y t + E _{y (2s)} (t) sin ω _y (t). The voltage of the harmonic signals U ₁ (t) and U ₃ (t), respectively, supplied to the other inputs of the multipliers 12 ₁ and 12 ₃ ,
U ₁ (t) = 2 cos ω _y t and U ₃ (t) = 2 sin ω _y t.

Напряжение гармонических сигналов U₂(t) и U₄(t), поступающих соответственно на вторые входы перемножителей 12₂ и 12₄,

,
Напряжения сигналов, поступающих в сумматор 13₁ с выходов перемножителей 12₁ и 12₂, математические выражения (6) и (8)
E₃(t) ^. U₁(t) = E_YQ ^. 2 cos ω_y t =
E_Y(2s-1) (t) + E_Y(2s) (t) cos 2 ω_y t +
+ E_Y(2s) (t) sin 2 ω_yt,

t

так как cos [ π

π(2d-1) ] = 1, sin [π

π (2d-1)] = 0 С выхода сумматора 13₁ снимается сигнал E_y(2s-1)(t) яркости строки (2s-1) первого поля.The inputs of the multipliers 12 ₂ and 12 ₄ comes from the output of the device 11 delay, mathematical expression (3), voltage

The voltage of the harmonic signals U ₂ (t) and U ₄ (t) supplied respectively to the second inputs of the multipliers 12 ₂ and 12 ₄ ,

,
The voltage of the signals entering the adder 13 ₁ from the outputs of the multipliers 12 ₁ and 12 ₂ , mathematical expressions (6) and (8)
E ₃ (t) ^. U ₁ (t) = E _YQ ^. 2 cos ω _y t =
E _{Y (2s-1)} (t) + E _{Y (2s)} (t) cos 2 ω _y t +
+ E _{Y (2s)} (t) sin 2 ω _y t,

t

since cos [π

π (2d-1)] = 1, sin [π

π (2d-1)] = 0 From the output of the adder 13 _{1 the} signal E _{y (2s-1)} (t) of the brightness of the line (2s-1) of the first field is taken.

С выхода сумматора 13₂ снимается сигнал E_y(2s)(t) яркости строки

2S-1+

из второго поля.The voltage of the signals entering the adder 13 ₂ from the outputs of the multipliers 12 ₂ and 12 ₄ , mathematical expressions (7) and (9),
E ₃ (t) ^. U ₃ (t) = E _QY (t) ^. 2 sin ω _y t =
= E _{Y (2s-1)} (t) sin 2 ω _y t + E _{Y (2s)} (t) -
- E _{Y (2s)} (t) cos 2 ω _y t,
E

The output of the adder 13 ₂ is removed signal E _{y (2s)} (t) the brightness of the line

2S-1 +

from the second field.

In this and subsequent sections of the description, the notation E _MQexp (t) is introduced to indicate the full color television signal.

The proposed television system with the simultaneous transmission of color-difference signals in the blanking intervals can be converted in such a way that its full color television signal can transmit a television image with a given vertical and horizontal clarity and with a given frame frequency in a frequency band equal to half of the nominal frequency band, required for transmission by known methods of television images with the same clarity vertically and horizontally and with the same frame rate. The full color television signal E _MQexp (t) of this television system transmits time-stretched reflex-modulated signals containing information about the brightness and color of two adjacent spatial lines of the image. For this, the reflex-modulated signals E _YQ (t), E * _c (t) of brightness and color of each image line are stretched twice in time and form one transmission line (2 τ _n long) of the full color television signal E _MQexp (t) from simultaneously transmitted signals of two adjacent rows in space.

2S-1+

второго поля. Из строк записи (2s-1) и 2s одновременно считывают сигналы E*_c(2s-1)(t) и E*_c(2s)(t) цветности и, алгебраически суммируя их в сумматоре 24, получают общий для строк записи (2s-1) и 2s сигнал E*_c(t) цветности на поднесущей с частотой f_o. Разность фаз немодулированной цветовой поднесущей в сигналах цветности, сформированных из сигналов строк записи (2s-1) и 2s и сформированных из сигналов строк записи (2s+1) и (2s+2), составляет φ_он≈

(2n-1), как и в случае, описанном со ссылкой на фиг. 10.Thus, luminance and color information from one line of the original image is transmitted over a time of about 2 τ _n , and luminance and color information of two lines is also transmitted during the same time. In this case, rows adjacent in space are combined in pairs, for example, the first and second, third and fourth, fifth and sixth, and so on. Therefore, the number of transmission lines is halved compared to the number of lines in the original full color television signal E _m (t), and the frame transmission time remains the same. Therefore, despite the _{halving of the} frequency band of the full color television signal E _MQexp (t), which is achieved by increasing the transmission time of the signal of each line while transmitting the signals of two lines in a time of 2 τ _n , the number of independent elements, for example, brightness, each frame and in one second is stored the same as in the original full color television signal E _M (t) of this image. On the transmitting side, the formation of the full color television signal E _MQexp (t) can be carried out by a device, an example of a functional diagram of which is shown in FIG. 16. From the signal separation circuit 5, the color television signal E ¹ _m (t) is supplied to the device 22. The process of generating the signal E ¹ _MQ (t) in the device 22 is identical to that described previously with reference to FIG. 10. The signals E _y (t) of fury and E * _c (t) of the color of two fields of one image frame are recorded in the storage device 23 (Fig. 10), placed sequentially in the recording lines 23 (Fig. 10), placed sequentially in the recording lines signals of adjacent spatial rows of images from the first and second fields. Moreover, the recording line (2s-1) contains information about the brightness and color from the line (2s-1) of the first field, and the recording line 2s contains information about the brightness and color from the line

2S-1 +

second field. From the recording lines (2s-1) and 2s, the chroma signals E * _{c (2s-1)} (t) and E * _{c (2s)} (t) are read at the same time and, algebraically summing them in the adder 24, we obtain a common recording line ( 2s-1) and 2s, a color signal E * _c (t) on a subcarrier with a frequency f _o . The phase difference of the unmodulated color subcarrier in the color signals generated from the signals of the recording lines (2s-1) and 2s and formed from the signals of the recording lines (2s + 1) and (2s + 2) is φ _he ≈

(2n-1), as in the case described with reference to FIG. 10.

f_н . В рефлексно-модулированном сигнале E_YQ(t) яркости разность фаз немодулированной поднесущей яркости в одинаковых по номерам строках смежных кадров при этом будет равна φ_yp≈

(2d-1) . На входы сумматора 25 поступают сигналы E*_c(t) и E_YQ(t), а с его выхода снимается цветовой телевизионный сигнал E¹ _MQ(t).The luminance signals E _{y (2s-1)} (t) and E _y2s (t) from the recording lines (2s-1) and 2s simultaneously read from the storage device 23 modulate the luminance subcarrier in block 1 in quadrature, from the output of which the signal is taken E _YQ (t), as in the case described with reference to FIG. 10. The odd harmonic of the quarter-line frequency f _y = is selected as the brightness subcarrier

f _n In a reflex-modulated signal E _YQ (t) of brightness, the phase difference of the unmodulated brightness subcarrier in the same row numbers of adjacent frames will be equal to φ _yp ≈

(2d-1). The inputs of the adder 25 receives the signals E * _c (t) and E _YQ (t), and a color television signal E ¹ _MQ (t) is taken from its output.

. Эти растянутые во времени сигналы E*_c(t) цветности передают в интервалах гашения, а рефлексно-модулированные сигналы E_YQ(t) яркости - в интервале активной части строки полного цветового телевизионного сигнала E_MQexp(t). При этом длительность каждой строки полного цветового телевизионного сигнала E_MQexp(t) равна 2 τ_н, частота строк

, а число строк в кадре Z₂=

=

=

, где Z₁ - число строк исходного сигнала E¹ _MQ(t).Formed in block 22 (Fig. 16), the color television signal E ¹ _MQ (t) with the help of the storage device 33 is stretched twice in time, thereby narrowing the width of its frequency spectrum by half, and also reducing the values of the frequencies of the subcarriers stretched in time chrominance signal E * _c (t) and luminance reflex modulated signal E _YQ (t) up to values

. These stretched in time signals E * _c (t) chrominance are transmitted in blanking intervals, and reflex-modulated signals E _YQ (t) brightness - in the active line interval of the composite color television signal E _MQexp (t). Moreover, the duration of each line of the full color television signal E _MQexp (t) is 2 τ _n , the frequency of the lines

, and the number of lines in the frame Z ₂ =

=

=

where Z ₁ is the number of lines of the original signal E ¹ _MQ (t).

. В этот же блок 34 могут, например, поступать и сигналы E_d дополнительной информации, которые, смешиваясь с сигналом E_s синхронизации, образуют на выходе блока 34 сигнал E_sd. В сумматоре 35 растянутый во времени цветовой телевизионный сигнал E¹ _MQexp(t), смешиваясь с сигналом E_sd, образует на выходе полный цветовой телевизионный сигнал E_MQexp(t). Примерный вид сигнала E_MQexp(t) соответствует виду сигнала E_м(t), приведенному на фиг. 2. В данному случае интервал времени от t_0-1 до t_0-2 равен 2 τ_н.The synchronization signal, allocated by the circuit 5, is supplied to the conversion unit 34, from the output of which the synchronization signals E _s are removed, which are followed with a frequency

. For example, additional information signals E _d may also enter this block 34, which, when mixed with the synchronization signal E _s , form the signal E _sd at the output of the block 34. In the adder 35, the time-stretched color television signal E ¹ _MQexp (t), mixing with the signal E _sd , forms the output color television signal E _MQexp (t). An exemplary view of the signal E _MQexp (t) corresponds to the type of signal E _m (t) shown in FIG. 2. In this case, the time interval from t _0-1 to t _0-2 is 2 τ _n .

At the receiving side, in the received full color television signal E _MQexp (t), the line length is halved, i.e. to τ _n while maintaining the duration of τ _p frame. In this case, the initial time durations of the color signals E * _c (t) in the blanking intervals and reflex-modulated signals E _YQ (t) of brightness in the intervals of the active parts of the lines are restored. And accordingly, the width of the frequency spectra of these signals and the nominal values of the frequencies f _o and f _y subcarriers are restored.

An example of a functional diagram of a device for processing a full color television signal E _MQexp (t) is shown in FIG. 17.

The storage device 36 reduces the length of the lines arriving at its input of the full color television signal E _MQexp (t) by half while maintaining the duration τ _p frame. This is achieved by choosing a ratio of 1: 2 for the clock frequencies of writing and reading signals in the storage device 36. Reading is carried out in cycles. The reading cycle consists of two intervals of duration τ _n each. In the first interval for a time equal to τ _n , the signal is read from the storage device 36. The beginning of the reading intervals is tied to the values of the input signal corresponding to time t _0-1 , t _0-2 (Fig. 18) and so on. Then the reading stops also for the time τ _n . As a result, the full color television signal E _MQ (t) is removed from the output of the storage device 36, an exemplary view of which is shown in FIG. eighteen.

The signal E _MQ (t) is input to the circuit 5 (Fig. 17) signal separation. The chrominance signal E * _c (t) and the luminance reflex modulated signal E _YQ (t) isolated by the circuit 5 are supplied from its output to the signal processing device 27 E _YQ (t) and E * _c (t). The signal processing process E _YQ (t) and E * _c (t) and the functional diagram of the device 27 are described previously with reference to FIG. 14. From the output of the device 27, a luminance signal E _y (t) and color difference signals E _RY (t) and E _BY (t) are taken with a horizontal frequency f _n and a string duration τ _n . Highlighted by the circuit 5, the synchronization signals E _s (their selection can also be carried out directly at the input of the storage device 36 before the signal is compressed) are sent to the conversion unit 37, where the synchronization signals are generated from them, following with a frequency f _n . From another output of the circuit 5, a signal E _{d of} additional information is removed. The selected luminance signals E _y (t) and the color difference signals E _RY (t) and E _BY (t) of the rows of the first and second fields are used when reproducing the image.

The proposed television system with the simultaneous transmission of color-difference signals E _RY (t) and E _BY (t) in the full color television signal E _MQ (t) can be converted so that on the receiving side the number of scan lines of the signals E _y (t) of brightness and color difference signals E _BY (t) and E _RY (t) to ensure visual perception of a given vertical definition is chosen equal to Z ₃ . Moreover, the number Z ₃ scan lines exceeds the number Z ₁ lines of decomposition of luminance signals E _y (t) and color difference signals E _RY (t) and E _BY (t), which modulate respectively the luminance subcarrier of frequency f _y and the color subcarrier of frequency f _o in the process the formation on the transmitting side of the full color television signal E _MQ (t). The formation of luminance signals E _y (t) and color difference signals E _BY (t) and E _RY (t), the number of scan lines of which is chosen equal to Z ₃ , can be carried out by devices 38 ₁ , 38 ₂ , 38 ₃ . Functional diagram with devices 38 ₁ , 38 ₂ , 38 _{3 is} shown in FIG. 19. The full color television signal E _MQ (t) is supplied to the signal separation circuit 5. From the output of circuit 5, the color signals E * _c (t) are respectively supplied to the device 27 (Fig. 14) for processing these signals. From the outputs of device 27 (Fig. 19), the luminance signal E _y (t) and color difference signals E _RY (t) and E _BY (t) are received respectively at the inputs of devices 38 ₁ , 38 ₂ , 38 ₃ , where the method of interpolation from the number of lines Z ₁ decomposition of the signal E _y (t) and color difference signals E _RY (t) and E _BY (t) receive the number of lines Z ₃ playback of each of the signals. To interpolate each scan line of the image on the receiving side, the signals l of the decomposition lines on the transmitting side are used. Moreover, of the l lines, half are leading, the second half are subsequent for the interpolated image line displayed on the screen. To perform the interpolation operation, digital filters are used, which are the devices 38 ₁ , 38 ₂ , 38 ₃ . On the transmitting side, the number Z ₁ of decomposition lines is selected in accordance with the characteristics of the interpolation method of the number Z ₃ lines from the number Z ₁ lines.

The proposed television system with the simultaneous transmission of color-difference signals in the blanking intervals can be converted in such a way that on the transmitting side, when generating color signals E _c (t) and reflex-modulated luminance signals E _YQ (t), the color-difference signals E _RY (t) and E _BY (t) and luminance signals E _y (t), which, as video signals E _1-1 (t), E _1-2 (t), modulate the luminance subcarrier of frequency f _y and the color subcarrier of frequency f _o , respectively, are subjected to preliminary correction.

 The functional diagram of the correction device is shown in FIG. twenty.

Since the correction devices 39 ₁ and 39 _{2 of the} video signals E _1-1 (t) and E _1-2 (t) are identical, a description is made of one correction device 39 ₁ . At the input of the device 39 ₁ correction receives pre-corrected video signal E _1-1 (t). The corrected video signal E _1-1 (t) is input to the delay unit 40 ₁ , where it is delayed for a time τ _p equal to the duration of one frame. From the output of the delay unit 40 _{1, the} video signal E _1-1 (t) is supplied to the input of the delay unit 40 ₂ , where it is also delayed by a time τ _p equal to the duration of one frame, and simultaneously enters one of the inputs of the algebraic adder 41 ₁ . The predicted video signal E _1-1 (t) is also fed to one of the inputs of the algebraic adder 41 ₂ , the second input of which receives a signal from the output of the storage device 40 ₂ . At the output of the algebraic adder 41 ₂ , a difference signal Δ E _1-1 (t) is formed, which is the difference between the values of the pre-corrected video signal E _1-1 (t) at time t and t-2 τ _p . From the output of the algebraic adder 41 _{2 the} difference signal Δ E _1-1 (t) is fed to the input of the difference signal processing device 42, in which the necessary operations of frequency filtering and noise reduction are carried out. From the output of the device 42, the difference signal ΔE _1-1 (t) is supplied to the second input of the algebraic adder 41 ₁ , where it is summed with the corrected video signal E _1-1 (t), delayed by the time τ _p frame. Then, the corrected video signal E _1-1 (t) from the output of the algebraic adder 41 _{1 is} fed to the input of the block 1 for generating a reflex-modulated signal E ₃ (t).

A television system with the simultaneous transmission of color-difference signals in the blanking intervals can be converted in such a way that, on the transmitting side, when generating chrominance signals E _c (t) and reflectively modulated luminance signals E _YQ (t), color-difference signals E _RY (t) and E _BY (t) and luminance signals E _y (t), which, as the video signals E _1-1 (t) and E _1-2 (t), modulate the luminance subcarrier of frequency fy and the color subcarrier, respectively, are subjected to special processing.

The functional diagram of the video signal processing device E _1-1 (t) and E _1-2 (t) is shown in FIG. 21.

The methods for processing information signals E _1-1 (t) and E _1-2 (t) are identical. The following is a description of the video signal processing method E _1-1 (t).

Each line of the video signal E _1-1 (t) is recorded with a clock frequency f _s1 in the device 43 ₁ memory. Reading each line of the signal from the device 43 ₁ memory is produced with a changing along the line clock frequency f _s2 (t).

где φ₁(t) =

-t

, t изменяется в пределах от 0 до τ_н, τ_н - длительность строки, Δτ_н - длительность интервала гашения по строкам, положительное число W₁>2,

- модуль значения φ₁ (t) при t =

.f _S2 (t) =

where φ ₁ (t) =

-t

, t varies in the range from 0 to τ _n , τ _n is the length of the string, Δτ _n is the duration of the blanking interval in rows, a positive number W ₁ > 2,

is the absolute value of φ ₁ (t) at t =

.

Телевизионная система с одновременной передачей цветоразностных сигналов E_R-Y(t) и E_B-Y(t) в интервалах гашения может быть преобразована таким образом, что при обработке видеосигналов E_1-1(t) и E_1-2(t) на передающей стороне тактовую частоту f_s1(t) записи выбирают изменяющейся в интервале времени t, равном длительности τ_v поля.From the output of the device 43 ₁ memory video signal E _1-1 (t) is input to the block 44 ₁ , where they carry out its frequency correction. From the output of block 44 _{1, the} processed video signal E _1-1 (t) is fed to the input of block 1 for generating a reflex-modulated signal of the form E ₃ (t), which is part of the full color television signal E _MQ (t). On the receiving side, the extracted luminance video signals E _y (t) and the color difference signals E _BY (t) and E _RY (t) are recorded line by line with a clock frequency f _s3 to the memory devices 28 ₁ , 28 ₂ and 30, respectively, of the signal processing device 27 E _YQ ( t) and E _c (t) described with reference to FIG. 14, and read with a variable along the line clock frequency
f _S4 (t) =

A television system with the simultaneous transmission of color difference signals E _RY (t) and E _BY (t) in the blanking intervals can be converted in such a way that when processing video signals E _1-1 (t) and E _1-2 (t) on the transmitting side, the clock the recording frequency f _s1 (t) is selected varying in the time interval t equal to the duration τ _{v of the} field.

где φ₂(t) =

-t

, t изменяется в пределах от 0 до τ_v, τ_v - длительность интервала гашения по полям, положительное число W₂>2,

- модуль значения φ₂(t) при t =

, f_s1(t)=f_s1 при cosφ₂(t) =

cosφ(t)dφ , а считывают с частотой f_s2(t).f _S1 (t) =

where φ ₂ (t) =

-t

, t varies from 0 to τ _v , τ _v is the duration of the field blanking interval, a positive number W ₂ > 2,

is the absolute value of φ ₂ (t) at t =

, f _s1 (t) = f _s1 for cosφ ₂ (t) =

cosφ (t) dφ, and read with a frequency f _s2 (t).

где f_s3=f_s3(t) при cosφ₂(t) =

cosφ₂(t)dt, а считывают с частотой f_s4(t).On the receiving side, when processing luminance signals E _y (t) and color difference signals E _RY (t) and E _BY (t), the recording clock frequency f _s2 (t) is selected as a variable in the interval equal to the field duration τ _v ,
f _S3 (t) =

where f _s3 = f _s3 (t) for cosφ ₂ (t) =

cosφ ₂ (t) dt, and read with a frequency f _s4 (t).

· f

C₁τ_v+(1-C₁)

+Δτ_v-2t

где |τ_v + Δτ_v - 2t| - модуль величины (τ_v+ τ_v-2t), С₁ - коэффициент, равный отношению значения f_s1(t) при t =

к значению f_s1(t) при t =

С₁ 0, f_s1 - значение f_s1(t) при t =

+

.A television system with the simultaneous transmission of color-difference signals in the blanking intervals can be transformed so that when processing the video signals E _1-1 (t) and E _1-2 (t) on the transmitting side, the recording clock frequency f _s1 is selected to vary in the time interval t, equal to the field duration τ _v , in accordance with the expression
f _S1 (t) =

F

C ₁ τ _v + (1-C ₁ )

+ Δτ _v -2t

where | τ _v + Δτ _v - 2t | is the magnitude modulus (τ _v + τ _v -2t), C ₁ is a coefficient equal to the ratio of the value of f _s1 (t) at t =

to the value of f _s1 (t) at t =

C ₁ 0, f _s1 is the value of f _s1 (t) at t =

+

.

· f_S1(t)

C₂τ_н+(1-C₂)

+Δτ_н-2t

где |τ_н + τ_н - 2t| - модуль выражения (τ_н+Δτ_н-2t), t - изменяется в интервале от 0 до τ_н, положительное число С₂ - коэффициент, равный отношению значения f_s2(t) t =

к значению f_s2(t) при t =

.The read clock frequency f _s2 (t) is chosen to vary in the interval τ _{n of the} line in accordance with the expression
f _S2 (t) =

F _S1 (t)

C ₂ τ _n + (1-C ₂ )

+ Δτ _n -2t

where | τ _n + τ _n - 2t | is the expression modulus (τ _n + Δτ _n -2t), t - varies in the range from 0 to τ _n , a positive number C ₂ is a coefficient equal to the ratio of the value of f _s2 (t) t =

to the value f _s2 (t) at t =

.

где f_s3 - значение f_s3(t) при t =

+

.On the receiving side, when processing the luminance signals Ey (t) and color difference signals ER-Y (t) and EB-Y (t), the recording clock frequency fs3 (t) is selected to change over a time equal to the field duration v, in accordance with the expression
f _S3 (t) = f _S3

where f _s3 is the value of f _s3 (t) at t =

+

.

, где t изменяется в пределах от 0 до τ_н.The read clock frequency f _s4 (t) is selected in accordance with the expression
f _S4 (t) = f _S3

, where t varies from 0 to τ _n .

Broadcast television signals in a narrow frequency band. The proposed television system, the full color television signal E _MQ (t) of which consists of transmission line signals with a duration of 2 τ _n , can be used to transmit television, for example, in special paths when recording television programs on household video recorders. Unlike a system for transmitting two color images in a combined frequency band, a television system with transmission lines of 2 τ _n duration can, for example, be used to transmit two television programs with different decomposition standards - European via satellite link (with division of the high-frequency channel frequency band) (625 lines, 25 frames) and American (525 lines, 30 frames). Moreover, due to the reduction of the frequency band of the full color television signal of the European system from 5-6 MHz to 2.5-3 MHz, the American standard - from 4.2 to 2.1 MHz, the deviation indices and noise immunity of the transmission of each program will practically not differ from noise immunity of transmission of one standard broadcasting system through this satellite communication channel. Another example of the use of this system is the transmission of high-definition television images without proportionally expanding the frequency band of the full color television signal.

EXAMPLE 1. Image transmission of the original system 625 lines, 25 frames (50 fields) in a channel with a frequency band of about 3 MHz. Input signal E _m (t) - the number of decomposition lines is 625, the line length is τ _n = 64 μs, the length of the active part of the line is 52 μs, the duration of the color signal transmission is 10.4 μs (compression ratio of the color signal 5: 1), frequency band the full color television signal Δf = 6 MHz, the magnitude of the signal E _y (t) brightness from "black level" to "white level" 0.7, the magnitude of the "pedestal" - 0.35 (Fig. 8).

f_н, где f_н - частота строк входного сигнала Е_м(t). Рефлексно-модулированный сигнал E_YQ(t) яркости имеет размах +0,5 от уровня привязки (постоянной составляющей), так же, как и сигнал E*_c(t) цветности. Сигналы E_YQ(t) и E_c(t) суммируются (они не совпадают во времени), образуя полный цветовой телевизионный сигнал E_MQ(t), который растягивается во времени в два раза. В растянутый сигнал замешиваются сигналы E_s синхронизации. Примерный вид осциллограммы полного цветового телевизионного сигнала E_MQexp(t), состоящего из строк передачи длительностью 2 τ_н, соответствует показанному на фиг. 2. В данном случае время от t_0-1 до t_0-2 (между началами сигналов E_s синхронизации) составляет 128 мкс. В интервале от t_0-1 до t₁ длительностью 2 мкс передается сигнал E_sсинхронизации, интервалы t₁÷t₂, t₃÷t₄, и t₅÷t₆ длительностью по 0,4 мкс каждый - защитные интервалы между сигналами. В интервале t₂÷t₃длительностью 20,8 мкс передается сигнал E*_c(t) цветности, в интервале t₄÷t₅ длительностью 104 мкс передается растянутый во времени рефлексно-модулированный сигнал E_YQexp(t) яркости. Таким образом входной сигнал E_MQ(t) преобразуется в сигнал E_MQexp(t) со следующими характеристиками:
частота строк 7812,5 Гц, число строк в кадре 312,5, частота кадров 25 Гц, полоса частот полного цветового телевизионного сигнала 3 МГц.Signal conditioning E _MQ exp (t). Because signal E _{m (2s-1) (t)} lines of the first field stands signal E * _{c (2s-1) (t)} color together with "pedestal" of the signal E _{m (2s) (t)} line of the second field is also highlighted color signal E * _{c (2s)} (t) with its “pedestal". During the algebraic summation of these stresses (in this case, subtraction), a color signal E * _c (t) is formed, the difference of the "pedestals" will give zero. Isolated from the signals E _{m (2s-1)} (t) and E _{m (2s)} (t) the signals E _{y (2s-1)} (t) and E _{y (2s)} (t) of brightness in the damping intervals, of which earlier the color signals are removed, the “pedestals” are introduced with a span of 0.35 (half the brightness range from the “black level” to the “white level”, and the level is assigned to the flat part (top) of the pedestal pulses. As a result, the signals are E _{y (2s-1 )} (t) and E _{y (2s)} (t) of brightness become bipolar with a maximum swing of + 0.35. The bipolar signals E _{y (2s-1)} (t) and E _{y (2s)} (t) of brightness modulate the brightness subcarrier, whose frequency
f _y =

f _n , where f _n - line frequency of the input signal E _m (t). The reflex modulated luminance signal E _YQ (t) has a magnitude of +0.5 of the reference level (DC component), as well as the chrominance signal E * _c (t). The signals E _YQ (t) and E _c (t) are summed (they do not coincide in time), forming a full color television signal E _MQ (t), which is doubled in time. The synchronized signals E _{s are} mixed into the stretched signal. An exemplary waveform of the full color television signal E _MQexp (t), consisting of transmission lines of 2 τ _n duration, corresponds to that shown in FIG. 2. In this case, the time from t _0-1 to t _0-2 (between the beginning of the synchronization signals E _s ) is 128 μs. In the interval from t _0-1 to t _{1 with a} duration of 2 μs, a synchronization signal E _s is transmitted, the intervals t ₁ ÷ t ₂ , t ₃ ÷ t ₄ , and t ₅ ÷ t _{6 with a} duration of 0.4 μs each are protective intervals between signals . In the interval t ₂ ÷ t _{3 with a} duration of 20.8 μs, a color signal E * _c (t) is transmitted, in the interval t ₄ ÷ t _{5 with a} duration of 104 μs, a time-stretched reflex-modulated brightness signal E _YQexp (t) is transmitted. Thus, the input signal E _MQ (t) is converted into a signal E _MQexp (t) with the following characteristics:
the line frequency is 7812.5 Hz, the number of lines in the frame is 312.5, the frame rate is 25 Hz, the frequency band of the full color television signal is 3 MHz.

t+E_Y(2S)exp(t)cos

t, где ω_у=2πf_у
Число независимых элементов сигнала E_y(2s-1)exp(t) ^. sin

tравно 2 ˙3 ˙10⁶ ˙104x10^-6= 624, число независимых элементов сигнала E_y(2s)exp(t) cos

t в той же строке передачи равно 2 ˙3˙ 10⁶ ˙104 ˙10^-6=624. Таким образом, общее число независимых элементов яркости в одной строке передачи 624x x2=1248, в кадре - 39˙ 10⁴, в активной части кадра - 358800, в секунду - 897 ˙10⁴, т.е. столько же, сколько и в исходном сигнале E_м(t).E _YQexp (t) = E _{Y (2S-1) exp} (t) sin

t + E _{Y (2S) exp} (t) cos

t, where ω _y = 2πf _y
The number of independent signal elements E _{y (2s-1) exp} (t) ^. sin

equals 2 ˙3 ˙10 ⁶ ˙104x10 ^-6 = 624, the number of independent signal elements E _{y (2s) exp} (t) cos

t in the same transmission line is 2 ˙3˙ 10 ⁶ ˙104 ˙10 ^-6 = 624. Thus, the total number of independent brightness elements in one transmission line is 624x x2 = 1248, in the frame - 39˙ 10 ⁴ , in the active part of the frame - 358800, per second - 897 ˙ 10 ⁴ , i.e. as much as in the original signal E _m (t).

2S-1+

изображения способом, описанным выше со ссылкой на фиг. 17. Параметры восстановленных сигналов яркости и цветности соответствуют параметрам исходных сигналов, использовавшихся при формировании полного цветового телевизионного сигнала на передающей стороне.On the receiving side, operations are performed for processing the full color television signal E _MQexp (t) and extracting from it the signals E _{y (2s-1)} (t) and E _{y (2s)} (t) of brightness and the color signal E * _c (t), common to strings (2s-1) and 2s, to play strings (2s-1) and

2S-1 +

images in the manner described above with reference to FIG. 17. The parameters of the restored luminance and chrominance signals correspond to the parameters of the original signals used in the formation of the full color television signal on the transmitting side.

=

= 2,25 раза где 16:9 - формат кадра предлагаемой системы ТВЧ, число элементов в активной части строки ТВЧ - 1560. Эквивалентная четкость по горизонтали системы ТВЧ 1560 x

= 877,5, 4: 3 - формат кадра системы 625 строк, 52 мкс - длительность активной части строки в системе 625 строк 50 полей;
- с системой 625 строк Δ F=5,5 МГц (стандарт I C.C.I.R) - в 2,05 раза;
- с системой 625 строк Δ F=5,75 МГц (аналоговая база цифрового кода студии 4:2:2) - 1,96 раза;
- с системой 625 строк Δ F=6 МГц (стандарты D, K, KI и L C.C.I.R) - в 1,875 раза.PRI me R 2. Implementation of a high definition television system (HDTV). Initial data: the number of independent brightness elements in a row of 2000, which corresponds to the number of independent brightness elements in a row of an HDTV 1125/60/2: 1 system with a full frequency band of 33.75 MHz. The duration of the active interval τ _per line is 78% of τ _n . The ratio between the brightness and color definition horizontally is 4: 1. These data are taken the same as in the HDTV 1125 system for easy comparison of the two systems. The number of independent elements in the active line interval τ _on is 2000 x x0,78 = 1560, that given the differences in the formats 16: 9 and 4: 3 will exceed the brightness definition in comparison with systems 625 lines 50 fields, namely:
- with a system of 625 lines Δ F = 5 MHz (G CCIR standard) -
1560

=

= 2.25 times where 16: 9 is the frame format of the proposed HDTV system, the number of elements in the active part of the HDTV line is 1560. Equivalent horizontal definition of the HDTV system 1560 x

= 877.5, 4: 3 — the frame format of the system of 625 lines, 52 μs — the duration of the active part of the line in the system of 625 lines of 50 fields;
- with a system of 625 lines Δ F = 5.5 MHz (standard I CCIR) - 2.05 times;
- with a system of 625 lines Δ F = 5.75 MHz (analog base of digital studio code 4: 2: 2) - 1.96 times;
- with a system of 625 lines Δ F = 6 MHz (standards D, K, KI and L CCIR) - 1.875 times.

 Compared with the 525-line system, 60 fields, Δ F = 4.2 MHz (standard M C. C. I.R. used in the USA, Canada, Japan and some other countries) - ≈ 2.68 times. Compared with the HDTV system, 1125 lines ΔF = 20 MHz - 1.69 times. Compared to potential theoretical clarity in the MUSE system (748 samples per line) - 2.1 times.

It should be noted that the horizontal clarity value calculated as the ratio of the number of independent brightness elements in the active interval τ _by to the frame format of 877.5 lines (or pixel) corresponds to the horizontal clarity of 1125 lines (pixel). At viewing distances equal to three and four screen heights (respectively ≈ 1.69 and 2.25 screen widths), this amounts to 41.7 Hz and 32 Hz / ^o , for the number of lines 877.5 clarity (taking into account elements in the active part of the line ) at the same angles of view, respectively 32.5 Hz / ^o and 25.6 Hz / ^o . For comparison, visual acuity at 1 arcminute, accepted as nominal when observing field objects, corresponds to a spatial frequency of 30 Hz / ^o .

 The requirements for vertical clarity are determined by the anisotropy of the vertical and horizontal resolution of the eyes when observing widescreen images, when the horizontal resolution is determined by binocular vision, and vertically by monocular. According to physiological data, this anisotropy is 0.7-0.8. Thus, with a horizontal clarity of 877.5 pixels (television lines), the vertical clarity in the active part of the frame should be 614-702 pixels, taking into account the frame reverse (8%), respectively, 667-763 pixels. For comparison, in systems with 625 lines of decomposition, in the active part of the frame - 575 lines, the vertical clarity for interlaced scanning is 364 pixels, for progressive scanning is about 405 pixels, and in terms of the frame reverse movement - 395 and 440 pixels. In the HDTV system, 1125 lines with an active part of the frame of 1035 lines, vertical clarity for interlacing is 655 pixels (taking into account the reverse movement of the frame 712 pixels), in the case of progressive scanning - about 729 pixels (taking into account the reverse movement in the frame - 792 pixels).

 When using on the receiving side of the interpolator in the form of a digital filter with a slope of the frequency response of the order of 11-15% of the passband, you can limit yourself to the number Z = 875 lines of decomposition with the number of active lines of the order of 805-810, which ensures vertical clarity of reproduced images of the order of 725-729 a pixel in the active part of the frame (787.5 pixels, taking into account the reverse stroke) with a slope slope of the filter amplitude-frequency characteristic of 11% and a vertical clarity of about 702-706 pixels in the active part of the frame (763 pixels with of inverse motion) when the steepness of the cutoff frequency response filter approximately 15% of the bandwidth.

 Thus, the vertical clarity achieved by transmitting 875 lines of decomposition of the original image and applying interpolation exceeds the clarity achieved by interlacing in 625 lines by 1.9-2 times, the clarity achieved by progressive scanning by 625 lines by 1.74 -1.8 times. Compared to the HDTV 1125 system, in the case of interlaced scanning of images of this system, it is 1.07-1.11 times. With progressive scan of images in HDTV - 0.996-1 times, i.e. the clarity is almost the same.

, где частота кадров f_р=25 Гц, число строк Z=875, частота строк f_н=875x25=21875 Гц, τ_н=45,714 10^-6 с, ΔF =

= 21,875·10⁶Гц.To transmit system signals with the number of independent elements for a time τ _n lines equal to 2000, with the number of lines of decomposition 875, with a field frequency of 50 Hz (25 frames), the required frequency band Δ F is 21.875 MHz line length τ _n =

where the frame rate f _p = 25 Hz, the number of lines Z = 875, the line frequency f _n = 875x25 = 21875 Hz, τ _n = 45.714 10 ^-6 s, ΔF =

= 21.875 · 10 ⁶ Hz.

2S-1+

второго поля выделяют соответственно сигналы E*_c(2s-1)(t) и E*_c(2s)(t) цветности вместе с "пьедесталами". При алгебраическом суммировании выделенных напряжений (в данном случае вычитании) образуется общий для строк (2s-1) и

2S-1+

сигнал E*_c(t) цветности, разность "пьедесталов" дает ноль. В выделенные из полного цветового телевизионного сигнала Е_м(t) в строках (2s-1) и

2S-1+

сигналы E_y(2s-1)(t) и E_y(2s)(t) яркости в гасящие интервалы, свободные после выделения из них сигналов E*_c(t) цветности, вводят "пьедесталы" размахом 0,35 (половина размаха сигнала яркости от "уровня черного" до "уровня белого" на фиг. 8) и осуществляют привязку уровня по плоской части (вершине) импульсов "пьедесталов". В результате сигналы E_y(2s-1)(t) и E_y(2s)(t) становятся биполярными с размахом + 0,35. Биополярными сигналами E_y(2s-1)(t) и E_y(2s)(t) модулируют поднесущую яркости, частота f_y которой равна f_y=

f_н , где f_н - частота строк входного сигнала Е_м(t), f_н=21875 Гц. Приняв d=3, например, получаем для частоты f_y поднесущей яркости значение f_y=27343,75 Гц. Рефлексно-модулированный сигнал E_YQ(t) яркости имеет размах + 0,5 от уровня привязки, являющегося "нулевым". Такой же размах имеет сигнал E*_c(t) цветности. Растянутые во времени в два раза сигналы E*_c(t) цветности и рефлексно-модулированный сигнал E_YQ(t) яркости используют при формировании полного цветового телевизионного сигнала E_MQexp(t). Форма сигнала E_MQexp(t) на выходе соответствует приведенной на фиг. 2. Интервал времени t_0-1÷ t_0-2 - длительность строки преобразованного входного сигнала предлагаемой системы ТВЧ 2000 х 875/50/2:1, τ_н на выходе (длительность строки передачи) равна суммарному времени 4 10³ независимых отсчетов частоты 21,875 МГц (≈ 91,43 ˙10^-6 с). Интервал времени t_0-1÷t₁ - длительность передачи импульсов синхронизации по строкам - равен 61 независимому отсчету тактовой части 21,875 МГц х 2 (≈ 1,386 ˙10^-6 с).The full color television signal E _m (t) of such a system, which can be arbitrarily called the HDTV system 2000 x 875/50/2: 1, is fed to the input of the signal separation circuit 5 (Fig. 16). The input waveform E _m (t) corresponds to the form shown in FIG. 8. The time intervals t _0-1 ÷ t _0-2 = 45.714 ^. 10 ^-6 s - duration τ _n lines; interval t _0-1 ÷ t ₁ ≈ 0.534 ^. 10 ^-6 s (about 23.5 independent samples of the signal) is the transmission interval of the signal E _s horizontal synchronization; the interval t ₂ ÷ t ₃ = 8.914 ^. 10 ^-6 s - transmission interval of the "pedestal" with a span of 0.35 (half the magnitude of the signal E _y (t) brightness from the "black level" to "white level"). On the “pedestal” is a time-compressed color signal E * _c (t) (390 independent samples of the color-difference signal E _RY (t) and 390 independent samples of the color-difference signal E _BY (t), which reflectively modulate the color subcarrier with a frequency f _o ). The interval t ₄ ÷ t ₅ = 35.66 10 ^-6 s (1560 independent samples of the signal E _y (t) brightness) is the active part of the string with a duration of τ _on ; the intervals t ₁ ÷ t ₂ , t ₃ ÷ t ₄ , t ₄ ÷ t _0-2 are protective intervals of duration ≈ 0.2x10 ^-6 s each (of the order of nine independent samples of the signal each). From the input full color television signal E _m (t) lines (2s-1) of the first field and adjacent in space of the line

2S-1 +

the second field, respectively, emit signals E * _{c (2s-1)} (t) and E * _{c (2s)} (t) of color together with the "pedestals". When algebraic summation of the selected stresses (in this case, subtraction) is formed common for the rows (2s-1) and

2S-1 +

the color signal E * _c (t), the difference of the "pedestals" gives zero. In isolated from the full color television signal E _m (t) in lines (2s-1) and

2S-1 +

signals E _{y (2s-1)} (t) and E _{y (2s)} (t) of brightness in the blanking intervals, free after separation of the signals E * _c (t) of color from them, introduce “pedestals” with a span of 0.35 (half the span luminance signal from the "black level" to the "white level" in Fig. 8) and carry out the level binding on the flat part (top) of the pulses of the "pedestals". As a result, the signals E _{y (2s-1)} (t) and E _{y (2s)} (t) become bipolar with a magnitude of + 0.35. The bi-polar signals E _{y (2s-1)} (t) and E _{y (2s)} (t) modulate the brightness subcarrier whose frequency f _y is equal to f _y =

f _n , where f _n - line frequency of the input signal E _m (t), f _n = 21875 Hz. Taking d = 3, for example, we obtain for the frequency f _{y of the} brightness subcarrier the value f _y = 27343.75 Hz. The reflex modulated luminance signal E _YQ (t) has a magnitude of + 0.5 of the reference level, which is “zero”. The signal of the same color has E * _c (t). Time Stretched twice signals E * _c (t) chrominance and reflex modulated signal E _YQ (t) luminance is used when forming the composite color television signal E _MQexp (t). The waveform E _MQexp (t) at the output corresponds to that shown in FIG. 2. The time interval t _0-1 ÷ t _0-2 is the line length of the converted input signal of the proposed HDTV system 2000 x 875/50/2: 1, τ _n at the output (transmission line duration) is equal to the total time 4 10 ³ independent frequency samples 21.875 MHz (≈ 91.43 × 10 ^-6 s). The time interval t _0-1 ÷ t ₁ - the duration of the transmission of synchronization pulses along the lines - is equal to 61 independent samples of the clock part of 21.875 MHz x 2 (≈ 1.386 × 10 ^-6 s).

= 10937,5 Гц . Полоса частот Δ F выходного полного цветового телевизионного сигнала E_MQexp(t) Δ F=10,9375 МГц, что вдвое меньше, чем во входном сигнале системы ТВЧ 2000 х 875/50/2: 1 и в 3,1 раза меньше, чем у сигнала системы HDTV 1125/60/2: 1, Δ F=33,75 МГц при той же воспроизводимой четкости на приемном экране (1560 независимых элементов яркости в строке). По сравнению с системой HDTV 1125/60/2:1, Δ F=20 МГц, четкость по горизонтали выше в ≈ 1,69 раза при более узкой полосе в ≈ 1,83 раза. По сравнению с системой MUSE - в ≈ 2,1 раза выше при расширении полосы частот ΔF примерно на 35%. Такая же горизонтальная четкость, как в системе HDTV 1125/60/2:1, Δ F=20 МГц обеспечивается при полосе частот Δ F полного цветового телевизионного сигнала E_MQexp(t) ΔF=6,48 МГц.The interval t ₂ -t ₃ allocated for the transmission of the color signal E * _c (t) with a duration of 780 independent samples of the clock frequency of 21.875 x 2 MHz is approximately equal to 17.83 10 ^-6 s. The interval of the active course τ _on the line t ₄ ÷ t ₅ , in which a reflex-modulated brightness signal E _YQ (t) is transmitted with a duration of 3120 independent samples of the clock frequency of 21.875 x 2 MHz, is approximately equal to 71.314 × 10 ^-6 s. Guard intervals t ₁ ÷ t ₂ , t ₃ ÷ t ₄ , t ₅ ÷ t _0-2 duration ≈ 0.3≈ 10 ^-6 s each. Transmission Line Frequency -

= 10937.5 Hz. The frequency band Δ F of the output full color television signal E _MQexp (t) Δ F = 10.9375 MHz, which is half that in the input signal of the HDTV system 2000 x 875/50/2: 1 and 3.1 times less than the signal of the HDTV system 1125/60/2: 1, Δ F = 33.75 MHz with the same reproducible clarity on the receiving screen (1560 independent brightness elements per line). Compared with the HDTV 1125/60/2: 1 system, Δ F = 20 MHz, the horizontal clarity is ≈1.69 times higher with a narrower band ≈1.83 times. Compared with the MUSE system, it is ≈ 2.1 times higher with an expansion of the ΔF frequency band by about 35%. The same horizontal definition as in HDTV 1125/60/2: 1, Δ F = 20 MHz is provided for the frequency band Δ F of the full color television signal E _MQexp (t) ΔF = 6.48 MHz.

The introduction of variable definition in line and frame, linearly decreasing from the center to the edge of the raster from 100% to ≈ 93% at the borders of the raster (at the most angular points of the raster to 13%), which is almost imperceptible to the image at the receiving screen on these points of the image, frequency band Δ F up to 6 MHz, which corresponds to the standard frequency bandwidth of communication channels in the European zone - the video bandwidth of the modulating full color television signal E _m (t). Processing the full color television signal at the receiving side and extracting luminance and color signals from it is carried out by the method described above with reference to FIG. 17.

 Further processing of the luminance and color difference signals may be carried out in accordance with the methods described with reference to FIG. 19, 20, 21.

The proposed television system with temporary compression of signals containing information about luminance and color, with transmission in the blanking intervals along the lines of a color signal, which is a color subcarrier, reflex-modulated simultaneously by two color-difference signals, as well as its modifications with transmission in the active part of the line reflex modulated brightness signals transmit more information in the same frequency band than the known broadcast television systems. Since it is necessary to compare with the known broadcasting systems having a different number of lines and decomposition frames, the unequal ratio of the active interval τ _by to the line length τ _n , and also differing in the frequency band of the full color television signal, when comparing these parameters are chosen the same for the proposed system and compared with her famous broadcast system.

Color information per unit time (1 s),
- in comparison with the SECAM (625 lines, τ _on = 81,25% τ _n, Δ F = 7 MHz) is greater than a ≈ 1,4 times for small color saturations in SECAM, in ≈ 2,7 times to color saturation of about 50 % in SECAM (transmission of color information to SECAM due to non-linear distortions in the encoder depends on color saturation), there is no crosstalk from the luminance channel characteristic of SECAM;
- in comparison with PAL - approximately the same, but without crosstalk from the brightness signal;
- in comparison with MAC-S (625 lines, Δ F = 8.4 MHz), approximately 1.5 times more;
- compared to the HDTV system (1125 lines, 30 Hz frame rate, 60 Hz field frequency, τ _78% τ _n, Δ F = 20 MHz) twice more;
- in comparison with MUSE (Δ F = 8.1 MHz) - twice as much.

Information about the brightness transmitted in the active part of the line, all other things being equal, the number of lines and frames, the duration τ _on , the frequency band in comparison with all known broadcast television systems is twice as much, compared with systems with frequency compression of the brightness signals and color without crosstalk from the color signal.

As shown by theoretical and experimental studies, the proposed television system, due to the increase in the amount of color information transmitted in the blanking interval by lines, has the following advantages compared to standard television broadcasting systems (NTSC, SECAM, PAL):
- high quality color and black and white (compatible) images due to the absence of cross-distortion between the luminance and color signals; providing full brightness clarity defined by the broadcast standard; lack of flickering on horizontal color transitions;
- great flexibility of characteristics according to the color signal (change of sharpness horizontally, vertically and along the time axis), which may be required when using the system at various links of the path. For example, horizontal color clarity can be obtained equal to from 1/5 to more than 1/2 of the brightness with corresponding changes in vertical resolution from full to 1/4 and along the time axis from 100% to 50% of the brightness. It is essential that this does not require decoding of the full color signal affecting the luminance component;
- sensitivity to frequency and phase distortions in the communication channel is almost the same as that of black-and-white television signals. Due to the use of reflex-quadrature modulation of the unevenness of the frequency and phase characteristics, as well as distortions of the type "differential phase" and "differential amplification" does not cause color distortion (color tone and saturation) on the screen, there is no cross distortion between color difference signals. By limiting the bandwidth of the communication channel, only the color and brightness clarity of the images change, and approximately the same in percentage terms. In terms of sensitivity to limiting the bandwidth of the channel, there are significant advantages not only in comparison with existing standard color television systems, but also in comparison with the MAC system;
- the absence of quality losses and specific distortions associated with the separation of the luminance and color components in the original full color signal when transcoding into signals of standard color television systems, as well as into signals of digital television systems;
- greater noise immunity of color signals during transmission via terrestrial and space communication channels, as well as during video recording, than in standard color television systems. The noise immunity of the luminance signal is higher than in the MAC.

 The properties of the full color television signal of the proposed television system determine the wide possibilities for its use in various fields of television technology.

1. In program production complexes, as an intermediate coding system, since the proposed television system has in this respect advantages over existing standard systems, namely: when mixing signals, existing mixers can be used in the mode of working with black and white television signals, not neither decoding nor re-encoding is required, which significantly reduces the quality of the images; no special operation is required to align the phases of the subcarriers, since at a low subcarrier frequency (for example, 12 kHz) 5 ^{about the} phase of the subcarrier is substantially more than half the duration of the brightness element (a requirement for mixing black and white television signals); when forming combined images, it does not require remodulation of the full color signal (unlike SECAM); when recording a full color signal, no additional requirements are imposed on the image path of the VCR compared to the norms for recording black and white television signals; when electronic synthesizers and image converters ("Electronic Artist" video effects devices) are working from the full color signal, there are no quality losses associated with the separation of luminance and color components in the input signal; in the joint work of technical means using an analogue full color signal (existing communication lines, VCRs) and devices or complexes that use digital component signals, when it is necessary to perform digital-to-analog and analog-to-digital conversions several times, the image quality can only decrease due to the increase in quantization noise, as in black and white television.

 2. In communication systems for transmissions on terrestrial and space communication channels, as well as through television radio transmitters and repeaters; to ensure high quality images during transmission of color programs (additional requirements related to the transmission of color signals are not imposed on the characteristics of communication lines); to ensure the transmission of color programs through special communication lines whose characteristics are worse than standard or unstable in time; for transmitting color images in special narrow-band (1.5-2 MHz) paths; to ensure high quality images in the international exchange of programs using transcoding; to provide communication between digital telecentres using analogue communication lines; to reduce colorimetric distortions in the transmission of color television signals in digital communication lines with a reduced speed of digital streams; for the possibility of creating a system of two color programs in existing communication lines (the image quality of each of the programs is the same as when transmitting one color television program on this communication line using standard broadcast systems); for the possibility of creating a system for transmitting stereo-color television signals with full vertical and horizontal clarity of the “right” and “left” images (in accordance with the requirements of decomposition standards of 625 lines, 50 fields) in existing communication lines (additional requirements are imposed on the characteristics of the communication channel only with respect to linear amplitude characteristics, as in the transmission of two programs); for the possibility of creating high-definition television signal transmission systems in existing communication lines, as well as through existing television radio transmitters and repeaters (additional requirements to the characteristics of the communication channel are imposed only by the linearity of the amplitude characteristics); for the possibility of creating mass receivers of high-frequency television, the requirements for the characteristics of the radio channel (selector, amplifier) which would not practically differ from the requirements for the parameters of the radio frequency path of modern TVs.

 3. In semi-professional and household video recordings to ensure full brightness clarity, for example, corresponding to the 625 line decomposition standard when recording a signal with a band of 2.6-3 MHz, and also to record high-definition television signals in a band of 6-8 MHz with a two-head video recorder.

Claims (19)

1. A TELEVISION SYSTEM in which a full color television signal (PCTS) of signals transmitted with information about the brightness and color of images is temporarily compressed by placing luminance signals in the entire interval of the active part of the line, and color-compressed color-difference signals containing color information - in line blanking intervals, characterized in that, in order to increase the amount of information transmitted by the PTsTS, and improve the noise immunity of the transmitted information, PTsTs are formed using information On certain characteristics of images, reflex modulated signals (RMS) of the form E ₃ (t), including RMS E _yQ (t) brightness and color signals E _c (t), while transmitting with video signals E _1-1 (t) , E _1-2 (t) containing information about the individual characteristics of the images, i.e. such video signals as luminance signals E _y (t) and color difference signals E _RY (t) and E _BY (t) perform quadrature modulation
subcarriers in phases 0 and

form a PMC of the form E ₃ (t) = E _1-1 (t) cosω t + E _1-2 (t) sinω t on the subcarriers, the choice of frequencies f =

which provides the required phase differences φ of unmodulated subcarriers in adjacent rows of the same frame φ _n and in the same row numbers of adjacent frames φ _p , and transmit the generated RMSs of the form E ₃ (t) in the PTCTS time intervals E _m (t) allocated for them, and when receiving from the received PCTS E _m (t), RMS parcels of the form E ₃ (t) are isolated and sent to the processing channels of the information contained in these signals, in the RMS processing channels of the form E ₃ (t), the parcels of these signals are delayed for time T multiples of the durations of the periods of television th scanning, and treated together delayed and undelayed sending PMC type E ₃ (t) by multiplying them by harmonic signals in the respective phases, algebraically summing the voltage resulting from multiplications of the delayed and undelayed parcels PMC type E ₃ (t) in each channel
processing, and isolated from the signals obtained by summing these voltages in a given processing channel, the corresponding video signals E _1-1 (t), E _1-2 (t) modulating subcarriers during transmission, including brightness signals E _y (t) and color difference signals E _Ry (t), E _By (t) when processing the PMC E _yQ (t) luminance and color signals E _c (t), align the time scales of the signals E _y (t) luminance and color difference signals (E _Ry (t ), E _By (t)) and combine them in time. 2. The system according to claim 1, characterized in that when receiving the combined processing of the delayed and uncontrolled packages of RMS of the form E ₃ (t) is carried out by multiplying one parcel by a harmonic signal of the form U ₁ (t) = 2cosω _x t, the other parcel - harmonic signal of the form U ₂ (t) = 2cos (ω _x t + π + q φ _n ),
where ω _x = 2π f _x , f _x is the frequency of the harmonic signal that exceeds the upper boundary frequency f _lim of the PMC spectrum of the form E ₃ (t), q is the number of the natural series, the algebraic stresses obtained as a result of the first and second multiplications are summarized, and detected the quadrature modulated signal obtained with this summation with the side bands deployed on a high-frequency carrier, highlighting both modulating video signals E _1-1 (t) and E _1-2 (t). 3. The system according to claim 1, characterized in that, when receiving, the combined processing of the delayed and uncontrolled PMC packages of the form E ₃ (t) is carried out directly at the subcarrier frequency f by multiplying one package by a harmonic signal of the form U ₁ (t) = 2cosω t, and another premise - to a harmonic signal of the form U ₂ (t) = 2cos (ω t + π + q φ _н ), where ω = 2π f, q is the number of the natural series, and by algebraic summation of the stresses obtained as a result of the first and second multiplications directly isolated subcarrier modulating video signal e _1-1 (t), multiply simultaneously the delayed and undelayed form parcels PMC E ₃ (t) respectively to harmonic signals of the form U ₃ (t) = 2sinω t and
U ₄ (t) = 2sin (ω t + π + q φ _н ) and by summing the voltages obtained as a result of these two multiplications, the second modulating video subcarrier signal E _1-2 (t) is directly isolated. 4. The system according to claim 1, characterized in that both color difference signals E _Ry (t), E _By (t) are simultaneously transmitted to the PCTS E _m (t) by reflex quadrature modulation of the color subcarrier, while transmitting color difference signals E _Ry (t) and E _By (t), as video signals E _1-1 (t) and E _1-2 (t), modulate the subcarrier voltages in phases 0 and

forming a color signal E _c (t), which is a PMC of the form E ₃ (t), on a color subcarrier of frequency
f _o =

where f _n - line frequency;
f _p is the frame rate;
m and n are natural numbers, the choice of which ensures the phase difference φ _{0 of the} color subcarrier in adjacent rows of one frame φ _it ≈

(2n-1) and in identical rows of adjacent frames φ _0p = π (2i - 1), where i is an integer,
change the time scale of the chrominance signal E _c (t) with a compression coefficient K equal to the ratio of the upper cutoff frequency of the nominal PCTS frequency band E _m (t) to the selected value of the upper cutoff frequency f _{lim of the} spectrum transmitted in one line of the chrominance signal E _c (t) to compress it in time, a part of signal E _c (t) chrominance burst signals in the form of chips compressed in time in the signal K times reflex-modulated color subcarrier in the "reference" phase is transmitted in several lines of blanking interval of frames, wherein while transmitting each transmission signal of the color burst in lines frame interval blanking equal chrominance signal transmit timing in a single active portion of a frame line, compressed in time signal E _c ^* (t) chrominance are transmitted in PTSTS E _m (t) in the intervals between the trailing edge of horizontal sync signal and the beginning of the active part of the line, and when received from the received PCTS, E _m (t) is isolated
sending signals E _c ^* (t) of color, delay them for a time equal to the duration of the frame, algebraically summarizing with sending signals of E _c ^* (t) of color in identical lines of the unstopped signal of the frame entering the input, sending signals E _c (t ) the colors summed from the same line numbers of adjacent frames are additionally delayed for a time T = q τ _n , where τ _n =

- the length of the string, and the delayed and uncontrolled sending of color signals E _c (t) are processed together by multiplying them by harmonic signals in the corresponding phases, the difference Δ φ _{0 of the} phase φ _{01 of the} unmodulated color subcarrier in the delayed sending of the color signal E _c (t) and phase φ _{02 of the} unmodulated color subcarrier in the undelayed color signal E _c (t) is related to the delay time T by the relation
Δ φ ₀ = φ ₀₁ - φ ₀₂ = ω ₀ q τ _n ,
where ω ₀ = 2π f ₀ . 5. The system according to claims 1, 2 and 4, characterized in that the combined processing of the delayed and uncontrolled packages of algebraically summed signals E _c (t) of color from the same line numbers of adjacent frames is carried out by multiplying one of them by a harmonic signal of the form U ₁ (t) = 2cos ω _x t, and the other on a harmonic signal of the form U ₂ (t) = 2cos (ω _x t + π + Δ φ ₀ ), where
ω _x = 2π f _x , f _x is the frequency of the harmonic signal exceeding the cutoff frequency f _{lim of the} spectrum of the color signal E _c (t), summarize the voltages obtained as a result of these multiplications and detect the resulting color signal with the side bands deployed on the high-frequency carrier, highlighting both color difference signals E _Ry (t) and E _By (t). 6. The system according to claims 1, 3 and 4, characterized in that when receiving the combined processing of delayed and uncontrolled packages of algebraically summed signals E _c (t) of color from the same line numbers of adjacent frames, they are performed by multiplying one package by a harmonic signal of the form U ₁ (t) = 2cos ω ₀ t, and the other package - to a harmonic signal of the form U ₂ (t) = 2cos (ω ₀ t + π + Δ φ ₀ ) and by summing the voltages obtained as a result of the first and second multiplications, directly distinguish one of the color-difference signals E _Ry (t), multiplied for simultaneously ERZHAN undelayed and sending these signals E _c (t) chrominance signals respectively to harmonic species
U ₃ (t) = 2sinω t and
U ₄ (t) = 2sin (ω ₀ t + π + Δ φ ₀ )
and by summing the voltages resulting from these two multiplications, the second color difference signal E _By (t) is directly extracted. 7. The system according to claims 4, 5 and 6, characterized in that when receiving the sending of algebraically summed signals E _c (t), the colors from the same row numbers of adjacent frames are additionally delayed for a time T equal to the length τ _{n of the} row, and the difference phases of harmonic signals, which multiply the delayed and uncontrolled sending signals E _c (t) color, choose equal
Π + Δφ _o ≈

(2n + 1)
8. The system of claims. 4, 5 and 6, characterized in that when receiving the sending of algebraically summed signals E _c (t), the colors from the same line numbers of adjacent frames are additionally delayed by an unequal number of lines in the first and second fields, namely: in the first field, the delay is time
T ₁ =

τ _n
where Z is the number of lines of decomposition,
and in the second field - for a while
T ₂ =

τ _n
wherein the phase difference of the harmonic signals, which multiply the delayed and uncontrolled sending signals E _c (t) color, in the first field is chosen equal
Π-

±

(Z + 1),
and in the second field - equal
Π-

±

(Z-1). 9. The system according to claims 4, 5 and 6, characterized in that when receiving the sending of algebraically summed signals E _c (t), colors from the same row numbers of adjacent frames are additionally delayed equally in the first and second fields for a while
T ₁ =

τ _n
at the same time, the phase difference of the harmonic signals is selected, by which the delayed and uncontrolled sending of signals E _c (t) of the color equal to
Π-

±

(Z + 1). 10. The system of claims. 1, 4 and 5 or 6, characterized in that in its PCTS E _mQ (t) for the duration of the duration of one line transmit RMS
E _c (t) and E _yQ (t),
containing information about the colors and luminances of two adjacent spatial lines of the image, and simultaneously transmit in real time two color television images in the combined frequency band, nominal for the transmission of one such image, while the signals E _y (t), E _{c are} stored during transmission ^* (t) luminance and chrominance of two fields of one frame separately of the first and second images by placing successively in rows each recording image signals in the adjacent space of the image lines of the first and vtorog fields, wherein in the string 2s - 1 entry contains information about the luminance and chrominance lines 2s - 1 of the first field and line 2s record contains information about the luminance and chrominance lines 2S-1 +

from the second field, where s is the number of the natural number, the signal of two recording lines 2s - 1 and 2s of the first image is converted into a signal of one transmission line of the first image, the signals of two recording lines 2s - 1 and 2s of the second image are converted to a signal of one
the transmission lines of the second image, these conversions are carried out separately and in the same way for the signals of the first and second images, for which the color signals E _c ^* (t) are read simultaneously from the lines 2s - 1 and 2s of the corresponding image and, algebraically summing them, they get the same for lines 2s - 1 and 2s of the recording of this image signal E $\genfrac{}{}{0ex}{}{\text{*}}{\text{c}}$ (t) chromaticity on a color subcarrier whose frequency remains equal to f ₀ , and the phase difference φ _{0n of the} unmodulated subcarrier in transmission lines generated from signals of recording lines 2s - 1 and 2s and generated from signals of lines 2s + 1 and 2s + 2 of recording of the same image, is φ _it ≈

(2n-1), the signals containing information about the brightness recorded in lines 2s - 1 and 2s of the recording are also transmitted simultaneously by reflex quadrature modulation of the brightness subcarrier, while the signals E _{y (2s-1)} read from the recording lines 2s - 1 and 2s ₎ (t), E _y2s (t) of brightness, as the video signals E _1-1 (t), E _1-2 (t), modulate the voltage of the subcarrier in phases "0" and

forming a brightness RMS E _yQ (t), which is a RMS of the form E ₃ (t) on the brightness subcarrier, for which an odd harmonic of a quarter-line frequency f _y =

f _n , where d is the number of the natural number, the choice of the value of which provides the phase difference φ _{уp of the} brightness subcarrier in the same row numbers of adjacent frames φ _ur =

(2d-1), the generated RMS E _yQ1 (t) luminance and chrominance signals E _c ^* (t) containing information about the luminance and color of the recording lines 2s - 1 and 2s of the first image are transmitted in line 2s - 1 of the _PCTC E _{MQ1- 2} (t), PMC E _yQ2 (t) luminance and chrominance signals E _c2 ^* (t) containing information about the luminance and chrominance of recording lines 2s - 1 and 2s of the second image, are transmitted in line 2s of the _PCTC E _MQ1-2 (t) , wherein signals E _c ^* (t) chrominance first and second pictures transmitted, respectively, in the blanking intervals in rows and PMC E _yQ (t) of brightness of the first and second pictures transmitted without change belt scale intervals active lines PTSTS E _MQ1-2 (t), and in identical numbers of rows of adjacent frames transmitted signals of the same of the two images, thus from PTSTS E _MQ1-2 (t) emit signals E _MQ1 (t ) and E _MQ2 (t) of the first and second images, direct them to the signal processing channels of each of these images, where they carry out identical signal processing operations E _MQ1 (t) and E _MQ2 (t), i.e. delay these signals for the duration of the frame, extract from the delayed and uncontrolled signals E _mQ (t) lines identical in numbers in adjacent frames, the color signals E _c (t), sum these signals algebraically, delay the algebraically summed color signals from the same line numbers adjacent frames additionally for a time equal to the duration of two lines, choose the phase difference of the harmonic signals, which multiply the delayed and uncontrolled sending of the summed color signals equal to Π + Δφ _o ≈

(2n + 1), the resulting color-difference signals E _Ry (t) and E _By (t) obtained at the outputs of the processing channels are used to reproduce the color information contained in lines 2s - 1 and 2s of the recording of this image from time delayed τ _{p of the} frame and the unreserved signals of the rows of the same image, isolate the PMC packages E _yQ (t) of brightness from the same frames by the row numbers, process them by multiplying them by the harmonic signals in the corresponding phases, and the stresses resulting from such multiplications are algebraically summed signals, and emit the signals E _{yQ (2s-1)} (t) and E _yQ2s (t) of the brightness of the recording lines 2s - 1 and 2s, the extracted signals containing information about the brightness and color of the recording lines 2s of the image are delayed by T ₁ =

and restore the signals of lines 2s - 1 and 2S-1 +

interlaced source image. 11. The system of claim 10, characterized in that when receiving joint processing of the delayed and uncontrolled packages of the PMC E _yQ (t) brightness is carried out by multiplying one of them by a harmonic signal of the form U ₁ (t) = 2cosω _xy t, and the other of the package - on a harmonic signal of the form U ₂ (t) = 2cos

t + Π +

(2d + 1)

= 2cos

t +

(2d + 1)

,, where ω _xy = 2π f _xy , f _xy is the carrier frequency satisfying the condition f _xy - f _y above the upper cutoff frequency of the PMC spectrum E _yQ (t) of brightness, the stresses obtained as a result of both multiplications are algebraically summed, forming a signal with unfolded side bands on the carrier with a frequency f _xy - f _y , and this signal is detected, highlighting the signals of lines 2s - 1 and 2s of the image recording. 12. The system according to claims 3 and 10, characterized in that when receiving the combined processing of the delayed and uncontrolled PMC packages E _yQ (t) of brightness from the same row numbers of adjacent frames, they are carried out directly at the frequency of the brightness subcarrier f _y =

by multiplying one premise by a harmonic signal of the form U ₁ (t) = 2cosω _y t, another premise by a harmonic signal of the form U ₂ (t) = 2cos

t +

(2d + 1)

the stresses obtained as a result of the first and second multiplications are algebraically summed up, directly isolating the signal E _{yQ (2s-1)} (t) of the brightness of the line 2s - 1 of the image recording by multiplying one package by a harmonic signal of the form U ₃ (t) = 2 sinω _y t, and the other package - to a harmonic signal of the form U ₄ (t) = 2sin

t +

(2d + 1)

and by algebraic summing of the stresses resulting from these multiplications, the brightness signal E _{yQ 2s} (t) of the brightness of the image recording line 2s is directly _extracted . 13. The system of claim 10, characterized in that when receiving signal processing channels of each image from the signals of the corresponding image arriving at their inputs, color signals E _c ^* (t) are extracted and repeated by a delay of T ₁ =

τ _n, then placed undelayed sending signal E _c ^* (t) chrominance reconstructed signal blanking interval E _y (t) luminance 2s rows - 1 of the image, and a delayed sending signal E _c ^* (t) chrominance placed in the reconstructed signal blanking interval E _y (t) of the brightness of the line 2s - 1 + (z + 1) / 2 of the same image, restoring the PCTS E _m (t) of the corresponding image. 14. The system according to PP.4 - 6, characterized in that the PCTS during the duration of the two lines transmit stretched in time PMCs containing information about the brightness and color of two adjacent spatial lines of the image, doing this by stretching twice the transmission time of the signals E _y (t), E _c ^* (t) the brightness and color of each image line and the formation of pairs of time-stretched transmissions and simultaneously transmitted signals of two adjacent spatial lines of the image of the _PCTS E _MQexp (t) with the transmission frequency of the lines f _n / 2 and a duration of 2τ _n kazh th line extended in time, and transmit real-time signals of television images with the original number of scanning lines z ₁ = f _n / f _p and the number of frames N = 1 / f _r 1 with a frequency band required for the transmission of television image signals , at the same time, during transmission, the signals E _y (t), E _c ^* (t) of the brightness and color of two fields of one image frame are stored, placing sequentially in the recording lines the signals of space-adjacent image lines from the first and second fields, and in line 2s - 1 entries contain brightness information and the colors from line 2s - 1 of the first field, and the line 2s of the record contains information about the brightness and color from line 2S-1 +

of the second field, from lines 2s - 1 and 2s of the record, signals containing chroma information are read at the same time, and algebraically summing them, they obtain a common color signal E _c ^* (t) for the lines of records 2s - 1 and 2s on a subcarrier with a frequency f ₀ when the phase difference Δφ _{0 of the} unmodulated color subcarrier in the color signals formed from the signals of the recording lines 2s - 1 and 2s and the recording lines 2s + 1 and 2s + 2, component Δφ _o ≈

(2n-1), the signals containing information about the brightness recorded in lines 2s - 1 and 2s of the recording are also transmitted simultaneously by reflex quadrature modulation of the brightness subcarrier, for which the signals E _{y (2s-1} , read from the recording lines 2s - 1 and 2s) ₎ (t), E _y2s (t) of brightness, as the video signals E _1-1 (t) and E _1-2 (t), modulate the voltage of the subcarrier in phases "0" and

, forming a PMC E _yQ (t) of brightness, which is a PMC of the form E ₃ (t) on the brightness subcarrier with a frequency f _y =

f _n , which provides the phase difference φ _{yp of the} brightness subcarrier in the same row numbers of adjacent frames φ _yp =

(2d-1), they double the transmission time of the generated chrominance signals E _c ^* (t) and PMC E _yQ (t) of brightness, thereby narrowing the width of their frequency spectrum by half, and also reducing the frequency values of subcarriers to f ₀ / 2 and f _y / 2, and transmit these signals, respectively, in the blanking intervals and in the intervals of the active part of the _PCTS line E _MQexp (t), and the length of each line of the _PCTS E _MQexp (t) is 2 τ _n , and the number of lines transmitted in frame
Z ₂ =

=

=

,
and when received in the received _PCTS, E _MQexp (t) halves the length of the lines, restoring the original time durations of the color signals E _c ^* (t) in the blanking intervals and the PMC E _yQ (t) brightness in the intervals of the active parts of the lines, restoring the frequency width accordingly the spectra of these signals and the nominal values of the frequencies f ₀ and f _y subcarriers, PTsTS E _MQ (t) with time-compressed lines of length _{n and n are} delayed by the frame time, separated from the delayed by the time of the frame and uncontrolled signals of the same numbers of adjacent frames of the message ki of color signals E _c (t) and PMC E _yQ (t) of brightness, algebraically summarize the sending of signals of E _c (t) color from the same row numbers of adjacent frames, additionally delay sending of the summed signals of E _c (t) color for 2τ _n and choose the phase difference of the harmonic signals, which multiply the delayed and uncontrolled sending of the summed signals E _c (t) color equal to Π + Δφ _o ≈

(2n + 1), the resulting color difference signals E _Ry (t) and E _By (t) are used to reproduce the color information contained in lines 2s - 1 and 2s of the image recording, separated from the same line numbers of adjacent frames, delayed by the frame time and the delayed sending of the PMC E _yQ (t) of brightness are processed by multiplying by harmonic signals in the corresponding phases, the voltage obtained as a result of these multiplications is algebraically summed and the signals of brightness E _{y (2s-1)} (t), E _y2s (t) are _extracted lines 2s - 1 and 2s of the record, with the highlighted signal ls containing information about the brightness and color of the lines 2s of the image recording, delay for a time T ₁ =

τ _n and restore the signals of lines 2s - 1 and 2S-1 +

interlaced source image. 15. The system of claim 14, characterized in that, upon receipt, the delayed and uncontrolled PMC packages E _yQ (t) of brightness are processed by multiplying one of them by a harmonic signal of the form U ₁ (t) = 2cos ω _xy t, and the second by harmonic signal of the form U ₂ (t) = 2cos

t +

(2d + 1)

, where ω _xy = 2π f _xy , f _xy is the carrier frequency satisfying the condition f _xy - f _y above the upper cutoff frequency of the PMC spectrum E _yQ (t) of brightness before it stretches in time, the voltages obtained as a result of multiplication of the PMC packages E _yQ (t) of brightness with harmonic signals, forming a signal with unfolded sidebands on a high-frequency carrier, this signal is detected and signals E _{y (2s-1)} (t), E _y2s (t) of brightness of lines 2s - 1 and 2s of the image recording are _detected . 16. The system according to claims 3 and 14, characterized in that when receiving the combined processing of the delayed and uncontrolled PMC packages E _yQ (t) of brightness from the same row numbers of adjacent frames, they are carried out directly at the brightness subcarrier frequency f _y =

by multiplying one premise by a harmonic signal of the form U ₁ (t) = 2cos ω _y t, another premise by a harmonic signal of the form U ₂ (t) = 2cos

t +

(2d + 1)

, algebraically summarize the voltages obtained as a result of the first and second multiplications, directly highlighting the signal E _{y (2s-1)} (t) of the brightness of the line 2s - 1 of the image recording, by multiplying one package by a harmonic signal of the form U ₃ (t) = 2sin ω _y t, and the other package - to a harmonic signal of the form U ₄ (t) = 2cos

t +

(2d + 1)

and by algebraic summing of the stresses resulting from these multiplications, the brightness signal E _y2s (t) of the image line 2s is directly extracted. 17. The system according to PP.10 and 14, characterized in that when receiving the number of scan lines that provide visual perception of a given vertical definition, choose equal to z ₃ exceeding the number z ₁ lines of decomposition of the signals E _y (t) brightness and color-difference signals E _Ry (t) and E _By (t) in transmission, wherein the number z ₃ lines of reproduction of each of the brightness signals E _y (t) and the color difference signals E _Ry (t) and E _By (t) are obtained from the number z ₁ lines by interpolation, using for the interpolation of each scan line when receiving the signals l lines of decomposition of the image when n soap has, in this case of the number l of lines half the lines are advancing, the second half - subsequent to reproduced on the screen of the interpolated lines of the image, and when transmitting the number of rows z ₁ expansion is selected to match the characteristics of the interpolation method number z ₃ rows of numbers z ₁ rows. 18. The system of claims. 10 and 14, characterized in that when transmitting during the formation of color signals E _c (t) and PMC E _yQ (t) luminance, color difference signals E _Ry (t), E _By (t) and luminance signals E _y (t) used as modulating, respectively, the color subcarrier and the brightness subcarrier of video signals of type E _1-1 (t) and E _1-2 (t), are subjected to preliminary correction, while the corrected video signal E _1-1 (t), E _1-2 (t) modulating the subcarrier is delayed by a time equal to the duration of two frames 2τ _p, the difference signal _{Δ E 1-1 (t), Δ} E 1-2 (t), representing the difference znach Nij predkorrektiruemogo video _{E 1-1 (t), E 1-2} (t) at time t and t - 2 τ _p, produce the necessary processing of the difference signal _{Δ E 1-1 (t), Δ} E 1-2 (t ), including the operations of frequency filtering and noise reduction, algebraically sum the difference signal Δ E _1-1 (t), Δ E _1-2 (t) with a pre-corrected video signal E _1-1 (t), E _1-2 (t), delayed for a time equal to
the duration τ _{p of the} frame, and corrected signals are used as modulating the brightness subcarrier and the color subcarrier in the formation of a PMC of the form E ₃ (t) included in the PCTC E _MQ (t). 19. The system according to claims 10 and 14, characterized in that during the generation of luminance signals E _c (t) and RMS E _yQ (t) luminance, color difference signals E _Ry (t), E _By (t) and signals E _y (t) the brightness used as modulating the color subcarrier and the brightness subcarrier of video signals of type E _1-1 (t), E _1-2 (t), is subjected to special processing, including recording signals of each line with a clock frequency f _s1 , reading signals each line with a clock frequency varying along the line
f _S2 (t) =

,
where φ ₁ (t) =

-t

, t varies in the range 0 - τ _n , τ _n is the length of the string, Δ τ _n is the length of the blanking interval for the string, w ₁ > 2,

is the absolute value of φ ₁ (t) at t =

carry out frequency correction of the processed video signals E _1-2 (t), E _1-1 (t) and modulate them respectively with the color subcarrier and the subcarrier of brightness when generating signals E _c (t) of color and PMC E _yQ (t) of brightness, which are PMC of the form E ₃ (t) that are part of the PCTS E _MQ (t), and when received, the selected luminance signals E _y (t) and the color difference signals E _Ry (t), E _By (t) are recorded line by line with a clock frequency f _s3 and read with a variable along the line clock frequency
f _S4 (t) =

20. The system according to claim 19, characterized in that when processing the subcarrier modulating video signals E _1-1 (t), E _1-2 (t) during transmission, the recording clock frequency f _s1 (t) is selected to vary in the time interval t equal to field duration τ _v :
f _S1 (t) =

,
where φ ₂ (t) =

- t

, t varies in the range 0 - τ _v , Δ τ _v is the duration of the field blanking interval, w ₂ > 2,

is the absolute value of φ ₂ (t) at t =

, f _s1 (t) = f _s1 for cosφ ₂ (t) =

cosφ ₂ (t) dφ and, when processing the brightness signals E _y (t) and the color difference signals E _Ry (t), E _By (t), selected during reception, the recording clock frequency f _s3 is chosen to vary in the interval of the field duration τ _ν :
f _S3 (t) =

where f _s3 (t) = f _s3 ,
for cosφ ₂ (t) =

cosφ ₂ (t) dφ. 21. The system according to PP.19 - 20, characterized in that when processing the modulating subcarrier video signals E _1-1 (t), E _1-2 (t) during transmission, the recording frequency f _s1 is selected to vary in the time interval t equal to the duration τ _v fields according to the expression
f _S1 (t) =

F _S1

C ₁ τ _v + (1-C ₁ )

+ Δτ _v -2t

,
Where

+ Δτ _v -2t

is the modulus of the quantity (τ _v + Δ τ _v - 2t), a non-zero positive number C ₁ is a coefficient equal to the ratio of the value of f _s1 (t) at t =

to the value of f _s1 (t) at t =

, f _S1 is the value of f _S1 (t) at t =

+

the clock frequency f _s2 (t) of reading is selected varying in the interval of duration τ _{n of the} line in accordance with the expression
f _S2 (t) =

F _S1 (t)

C ₂ τ _n + (1-C ₂ )

+ Δτ _n -2t

,
Where

+ Δτ _n -2t

is the modulus of the quantity (τ _n + Δ τ _n - 2t), t varies in the range 0 - τ _n , a nonzero positive number C ₂ is a coefficient equal to the ratio of the value of f _s2 (t) at t =

to the value f _s2 (t) at t =

and when receiving, the clock frequency f _s3 (t) of the recording is selected to change over time t equal to the duration τ _{v of the} field in accordance with the expression
f _S3 (t) = f _S3

,
where f _s3 is the value of f _S4 (t) at t =

, and the clock frequency f _s4 (t) of reading - varying in the interval of duration τ _n lines in accordance with the expression
f _S4 (t) = f _S3 (t)

,
where t varies between 0 - τ _n .

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