KR102390566B1 - Method and apparatus for transmitting discovery signal, and method and apparatus for receiving discovery signal - Google Patents

Abstract

A method of transmitting a base station is provided. The base station generates a first discovery signal block including a first primary synchronization signal (PSS) and a first secondary synchronization signal (SSS). The base station generates a second discovery signal block including a second PSS and a second SSS. The base station transmits the first discovery signal block and the second discovery signal block.

Description

A method and apparatus for transmitting a discovery signal, and a method and apparatus for receiving a discovery signal

The present invention relates to a method and apparatus for transmitting and receiving a discovery signal.

A wireless communication system supports a frame structure according to a standard. For example, a 3rd generation partnership project (3GPP) long term evolution (LTE) system supports three types of frame structures. The three types of frame structures include a type 1 frame structure applicable to frequency division duplex (FDD), a type 2 frame structure applicable to time division duplex (TDD), and a type 3 frame for transmission of unlicensed frequency bands. include structure.

In a wireless communication system such as an LTE system, a transmission time interval (TTI) means a basic time unit in which an encoded data packet is transmitted through a physical layer signal.

The TTI of the LTE system consists of one subframe. That is, the length of the time axis of a physical resource block (PRB) pair, which is the minimum unit of resource allocation, is 1 ms. In order to support transmission in 1ms TTI units, most physical signals and channels are also defined in subframe units. For example, a cell-specific reference signal (CRS) is fixedly transmitted in every subframe, a physical downlink control channel (PDCCH), a physical downlink shared hannel (PDSCH), a physical uplink control channel (PUCCH), and a physical uplink control channel (PUSCH). uplink shared channel) may be transmitted for each subframe. On the other hand, a primary synchronization signal (PSS) and a secondary synchronization signal (SSS) exist every 5th subframe, and a physical broadcast channel (PBCH) exists every 10th subframe.

On the other hand, there is a need for a technology for transmitting and receiving a signal for a heterogeneous frame structure based on a plurality of numerology in a wireless communication system.

An object of the present invention is to provide a method and apparatus for transmitting and receiving a signal for a heterogeneous frame structure based on a plurality of numerology in a wireless communication system.

According to an embodiment of the present invention, a transmission method of a base station is provided. The transmission method of the base station includes: generating a first discovery signal block including a first primary synchronization signal (PSS) and a first secondary synchronization signal (SSS); generating a second discovery signal block including a second PSS and a second SSS; and transmitting the first discovery signal block and the second discovery signal block.

The time and frequency distance between the resource for the first PSS and the resource for the first SSS may be the same as the time and frequency distance between the resource for the second PSS and the resource for the second SSS.

The first discovery signal block may further include a first physical broadcast channel (PBCH), and the second discovery signal block may further include a second PBCH.

The time and frequency distance between the resource for the first PSS and the resource for the first PBCH may be the same as the time and frequency distance between the resource for the second PSS and the resource for the second PBCH.

The generating of the second discovery signal block may include applying time division multiplexing (TDM) between the first discovery signal block and the second discovery signal block.

A time distance between the first discovery signal block and the second discovery signal block may be determined based on a first predefined value.

A time distance between the first PRACH block and the second PRACH block for the base station to receive a physical random access channel (PRACH) may be determined based on a second predefined value.

The first PRACH block and the second PRACH block may exist within a cell search bandwidth that is a bandwidth of subbands occupied by the first discovery signal block and the second discovery signal block.

The resource occupied by the first discovery signal block may include consecutive time domain symbols.

In the first discovery signal block, the first PSS may precede the first SSS in time.

The transmission method of the base station may further include determining a time distance between the first PRACH block and the second PRACH block for the base station to receive a physical random access channel (PRACH).

The generating of the second discovery signal block may include determining a time distance between the first discovery signal block and the second discovery signal block based on traffic conditions.

Also, according to another embodiment of the present invention, a method of transmitting a base station is provided. The transmission method of the base station includes: generating at least one discovery signal block including a primary synchronization signal (PSS) and a secondary synchronization signal (SSS); and allocating some or all of resources belonging to a predefined resource pool for transmission of a discovery signal to the at least one discovery signal block.

The at least one discovery signal block may be plural.

The transmission method of the base station may further include determining a time distance between the plurality of discovery signal blocks according to traffic conditions.

The transmission method of the base station includes the steps of setting the duration and periodicity of a discovery signal measurement window (DMW) to the terminal so that the terminal receives the at least one discovery signal block. may include more.

In the step of setting the length and period of the DMW, when the terminal and the base station are RRC-connected, a value greater than a period value predefined for another terminal not RRC-connected to the base station setting the DMW period to , and setting the DMW length to a value smaller than a length value predefined for the other terminal.

The at least one discovery signal block may be plural.

The allocating may include transmitting some of the plurality of discovery signal blocks in the DMW.

The transmission method of the base station may further include arbitrarily determining a time distance between a plurality of PRACH blocks for the base station to receive a physical random access channel (PRACH).

The transmission method of the base station includes transmitting at least one of a plurality of physical random access channel (PRACH) formats to the terminal through a physical broadcast channel (PBCH) included in a first discovery signal block among the at least one discovery signal block. It may include further steps.

The time distance between the plurality of discovery signal blocks may be applied as the same value for each period of the discovery signal occurrence.

Also, according to another embodiment of the present invention, a receiving method of a terminal is provided. The reception method of the terminal may include: determining a discovery signal measurement window (DMW); monitoring a physical synchronization signal (PSS) in the DMW; and selecting one of the plurality of PSSs when a plurality of PSSs corresponding to a plurality of discovery signal blocks are found in the DMW.

In the determining step, if the base station is not connected to a radio resource control (RRC), based on a predefined length value and a period value, determining a length (duration) and a period (periodicity) for the DMW may include

The determining may include receiving a length and periodicity setting for the DMW from the base station when a radio resource control (RRC) connection is established with the base station.

The DMW period set by the base station may have a value greater than a period value predefined for other terminals not RRC-connected to the base station.

The DMW length set by the base station may have a smaller value than a length value predefined for the other terminal.

The reception method of the terminal may further include monitoring a secondary synchronization signal (SSS) or a physical broadcast channel (PBCH) included in the first discovery signal block corresponding to the selected PSS.

The selecting may include selecting a PSS having the best reception performance or satisfying a predefined reception performance condition from among the plurality of PSSs.

According to an embodiment of the present invention, a transmission/reception method and apparatus for a heterogeneous frame structure based on a plurality of numerologies may be provided.

1 is a diagram illustrating a type 1 frame structure of an LTE system.
2 is a diagram illustrating a type 2 frame structure of an LTE system.
3 is a diagram illustrating a carrier raster and carrier allocation based on method M101 or method M102, according to an embodiment of the present invention.
4 is a diagram illustrating a case in which a plurality of pneumorollers are used within a common frequency band.
5 is a diagram illustrating a carrier raster and carrier allocation based on method M112 or method M113, according to an embodiment of the present invention.
6 is a diagram illustrating a synchronization signal resource region based on method M201 according to an embodiment of the present invention.
7 is a diagram illustrating a synchronization signal's numerology and a synchronization signal resource region based on a method M202 according to an embodiment of the present invention.
8 is a diagram illustrating a synchronization signal resource region and a numerology of a synchronization signal based on method M203 according to an embodiment of the present invention.
9 is a diagram illustrating a synchronization signal numerology and a synchronization signal resource region based on a method M210 according to an embodiment of the present invention.
FIG. 10 is a diagram illustrating the numerology of a synchronization signal and a resource region of the synchronization signal with respect to a carrier composed of a plurality of numerologies according to an embodiment of the present invention.
11 is a diagram illustrating components of a discovery signal according to an embodiment of the present invention.
12 is a diagram illustrating a resource configuration of a discovery signal occasion based on method M300 according to an embodiment of the present invention.
13 is a diagram illustrating a resource configuration of a discovery signal occasion based on a method M310 according to an embodiment of the present invention.
14 is a diagram illustrating a case in which TDM is applied between signal blocks in method M300 or method M310 according to an embodiment of the present invention.
15 is a diagram illustrating a case in which a discovery signal occasion is transmitted within a discovery signal measurement window according to an embodiment of the present invention.
16 is a diagram illustrating a discovery signal and PRACH resource configuration based on method M310 according to an embodiment of the present invention.
17 is a diagram illustrating a configuration of a discovery signal and a PRACH resource based on methods M320 and M330 according to an embodiment of the present invention.
18 is a diagram illustrating a configuration of a discovery signal and a PRACH resource based on methods M321 and M331 according to an embodiment of the present invention.
19 is a diagram illustrating a computing device according to an embodiment of the present invention.

Hereinafter, with reference to the accompanying drawings, the embodiments of the present invention will be described in detail so that those of ordinary skill in the art to which the present invention pertains can easily implement them. However, the present invention may be embodied in several different forms and is not limited to the embodiments described herein. And in order to clearly explain the present invention in the drawings, parts irrelevant to the description are omitted, and similar reference numerals are attached to similar parts throughout the specification.

In the present specification, duplicate descriptions of the same components will be omitted.

Also, in this specification, when it is said that a certain element is 'connected' or 'connected' to another element, it may be directly connected or connected to the other element, but other elements in the middle It should be understood that there may be On the other hand, in this specification, when it is mentioned that a certain element is 'directly connected' or 'directly connected' to another element, it should be understood that the other element does not exist in the middle.

In addition, the terms used herein are used only to describe specific embodiments, and are not intended to limit the present invention.

Also, in this specification, the singular expression may include the plural expression unless the context clearly dictates otherwise.

Also, in this specification, terms such as 'include' or 'have' are only intended to designate that the features, numbers, steps, operations, components, parts, or combinations thereof described in the specification exist, and one or more It is to be understood that the existence or addition of other features, numbers, steps, operations, components, parts, or combinations thereof, is not precluded in advance.

Also in this specification, the term 'and/or' includes a combination of a plurality of described items or any item of a plurality of described items. In this specification, 'A or B' may include 'A', 'B', or 'both A and B'.

Also in the present specification, a terminal is a mobile terminal, a mobile station, an advanced mobile station, a high reliability mobile station, a subscriber station, It may refer to portable subscriber station, access terminal, user equipment (UE), etc., mobile terminal, mobile station, advanced mobile station, high reliability mobile station, subscriber station, portable subscriber station , may include all or part of the functions of access terminals, user equipment, and the like.

Also in this specification, a base station (base station, BS) is an advanced base station (advanced base station), a high reliability base station (HR-BS), a Node B (node B, NB), an advanced Node B ( evolved node B, eNodeB, eNB), an access point, a radio access station, a base transceiver station, a mobile multihop relay (MMR)-BS, a relay performing the role of a base station station), a high reliability relay station serving as a base station, repeater, macro base station, small base station, etc. may refer to, and advanced base station, HR-BS, NodeB, eNodeB, access point, wireless access It may include all or part of the functions of a station, a transceiver base station, an MMR-BS, a repeater, a high-reliability repeater, a repeater, a macro base station, and a small base station.

1 is a diagram illustrating a type 1 frame structure of an LTE system.

One radio frame (radio frame) has a length of 10ms (=307200T _s ), and consists of 10 subframes (subframe). Here, T _s is a sampling time, and has a value of T _s =1/(15kHz*2048). Each subframe has a length of 1 ms, and one subframe consists of two slots having a length of 0.5 ms. One slot consists of 7 time domain symbols (eg, orthogonal frequency division multiplexing (OFDM) symbols) in the case of a normal cyclic prefix (CP), and 6 time domain symbols in the case of an extended CP (eg, OFDM symbol). In the present specification, the time domain symbol may be an OFDM symbol, a single carrier (SC)-frequency division multiple access (FDMA) symbol, or the like. However, this is only an example, and the embodiment of the present invention can be applied even when the time domain symbol is a symbol different from the OFDM symbol or the SC-FDMA symbol.

2 is a diagram illustrating a type 2 frame structure of an LTE system.

The relationship between the radio frame, the subframe, and the slot and the length of each are the same as in the case of the type 1 frame structure. As a difference between the Type 2 frame structure and the Type 1 frame structure, in the Type 2 frame structure, one radio frame is a downlink (DL) subframe, an uplink (UL: uplink) subframe, and a special subframe. is composed of

The special subframe exists between a downlink subframe and an uplink subframe, and includes a downlink pilot time slot (DwPTS), a guard period (GP), and an uplink pilot time slot (UpPTS).

One radio frame includes two special subframes when the downlink-uplink switching period is 5 ms, and includes one special subframe when the downlink-uplink switching period is 10 ms. Specifically, FIG. 2 exemplifies a case where the downlink-uplink switching period is 5 ms and subframes 1 and 6 are special subframes.

DwPTS is used for cell search, synchronization, or channel estimation. GP is a period for removing interference occurring in the uplink of the base station due to the multi-path delay difference of the terminals. In the UpPTS section, it is possible to transmit a physical random access channel (PRACH) or a sounding reference signal (SRS). A wireless communication system according to an embodiment of the present invention may be applied to various wireless communication networks. For example, the wireless communication system may be applied to a wireless communication network based on a current radio access technology (RAT), or a wireless communication network after 5G and 5G. 3GPP is developing a new RAT-based 5G standard that meets the international mobile telecommunications (IMT)-2020 requirements, and this new RAT is called NR (new radio). In this specification, for convenience of description, an NR-based wireless communication system will be described as an example. However, this is only an example, and the present invention is not limited thereto and may be applied to various wireless communication systems.

As one of the differences between NR and conventional 3GPP systems (eg, code division multiple access (CDMA), LTE, etc.), NR utilizes a wide range of frequency bands to increase transmission capacity. In this regard, the world radiocommunication conferences (WRC)-15 hosted by the International Telecommunication Union (ITU) set the next WRC-19 agenda, which uses the 24.25~86GHz band as a candidate frequency band for IMT-2020. including review. 3GPP considers a band from 1 GHz to 100 GHz as a candidate NR band.

As a waveform technology for NR, orthogonal frequency division multiplexing (OFDM), Filtered OFDM, generalized frequency division multiplexing (GFDM), FBMC (filter bank multi-carrier), UFMC (universal filtered multi-carrier), etc. are candidates technology is being discussed.

In this specification, it is assumed that CP-based OFDM (CP-OFDM) is used as a waveform technology for wireless access. However, this is only for convenience of description, and the present invention is not limited to CP-OFDM and can be applied to various waveform technologies. In general, the category of CP-OFDM technology includes windowed and/or filtered CP-OFDM technology or spread spectrum OFDM technology (eg, DFT-spread OFDM).

Table 1 below shows an example of OFDM system parameter configuration for an NR system.

In Table 1 (example of OFDM system parameter configuration), the frequency band of 700 MHz to 100 GHz is divided into three regions (ie, low frequency band (~6 GHz), high frequency band (3-40 GHz), and very high frequency band (30-100 GHz)) and a different OFDM numerology is applied to each frequency band. At this time, one of the biggest factors determining the subcarrier spacing of the OFDM system is a carrier frequency offset (CFO) experienced by the receiving end. The carrier frequency offset (CFO) has a characteristic that increases in proportion to the operating frequency due to the Doppler effect and phase drift. Therefore, in order to prevent performance degradation due to the carrier frequency offset, the subcarrier spacing should increase in proportion to the operating frequency. On the other hand, if the subcarrier spacing is too large, there is a disadvantage in that CP overhead increases. Therefore, the subcarrier spacing should be defined as an appropriate value in consideration of the channel and radio frequency (RF) characteristics for each frequency band. The subcarrier spacings of SETs A, B, and C illustrated in Table 1 are 16.875 kHz, 67.5 kHz, and 270 kHz, respectively, and are approximately proportional to the target operating frequency and are configured to differ by a factor of four from each other.

Set A Set B Set C carrier frequency Low freq. (~6GHz) High freq. (3~40GHz) Very high freq. (30~100GHz) Subcarrier spacing 16.875kHz 67.5kHz 270kHz CP overhead 5.2% 5.2% 5.2% Number of OFDM symbols per 1ms 16 64 256

Meanwhile, the values of the subcarrier spacing used in Table 1 are only examples, and the subcarrier spacing may be designed with other values. For example, the existing LTE subcarrier spacing of 15 kHz is used as the base numerology, and subcarrier spacings (eg, 30 kHz, 60 kHz, 120 kHz, 240 kHz, etc.) scaled by an exponential power of 2 based on this are used as the numerology. It can be used for scaling. This is illustrated in Table 2 (example of OFDM system parameter configuration) below. Configuring the subcarrier spacings so that they differ by a power of two between the subcarrier spacings of the heterogeneous numerologies is a function of the behavior between heterogeneous numerologies (e.g., carrier aggregation, double connectivity, or In the case of multiplexing, etc.), it may be advantageous.

Set A Set B Set C Set D Set E Subcarrier spacing 15 kHz 30 kHz 60kHz 120kHz 240 kHz CP overhead 6.7% 6.7% 6.7% 6.7% 6.7% Number of OFDM symbols per 1ms 14 28 56 112 224

One neurology may be basically used for one cell (or carrier), and may be used for a specific time-frequency resource in one carrier. As illustrated in Table 1, the heterogeneous numerology may be used for different operating frequency bands and may be used to support different service types within the same frequency band. As an example of the latter, SET A of Table 1 is used for an enhanced mobile broadband (eMBB) service in a band below 6 GHz, and SET B or C in Table 1 is for an ultra-reliable low latency communication (URLLC) service in a band below 6 GHz. can be used Meanwhile, in order to support an mMTC or multimedia broadcast multicast services (MBMS) service, a numerology having a subcarrier interval smaller than the subcarrier interval of the basic numerology may be used. To this end, when the subcarrier spacing of the basic numerology is 15 kHz, the subcarrier spacing of 7.5 kHz or 3.75 kHz may be considered.

Hereinafter, a method and apparatus for transmitting a signal for a heterogeneous frame structure based on a plurality of numbers in a wireless communication system will be described.

[ carrier raster]

In order to discover a cell (or carrier) in the initial cell search process, the UE must be able to detect a synchronization signal of a corresponding cell for all candidate frequencies on a carrier raster within a frequency band to which the corresponding cell belongs. The synchronization signal may be transmitted using one of the candidate frequencies as a reference. For example, in the LTE system, the interval between carrier raster scales is 100 kHz, and a direct current (DC) subcarrier, which is the center of subcarriers through which a synchronization signal is transmitted, is aligned on a specific carrier raster scale.

And, when the terminal succeeds in detecting the synchronization signal, the center frequency position of the cell (or carrier) may be derived from the frequency value of the corresponding carrier raster scale. In the case of the LTE system, since the center frequency of the synchronization signal and the center frequency of the cell (or carrier) coincide, the terminal can obtain the center frequency of the cell (or carrier) without the aid of the base station.

Meanwhile, in order to increase frequency resource utilization efficiency, a new carrier raster may be designed. Hereinafter, the carrier raster may mean a set of candidate reference frequencies of a synchronization signal or a set of candidate center frequencies of a cell (or carrier). The former and the latter can generally be distinguished from each other.

In the case of intra-band contiguous carrier aggregation, in order to minimize the idle band that inevitably occurs between carriers, the frequency interval of the carrier raster may be determined as a multiple of the subcarrier interval. This is referred to as method M100.

Alternatively, when it is assumed that one resource block is configured with N resource elements on the frequency axis, the raster spacing may be determined as a multiple of (the product of the subcarrier spacing and N). This is referred to as method M101. For example, the spacing of the carrier raster for a frequency band in which a numerology having a subcarrier spacing of 15 kHz is used may be a multiple of 15 kHz by the method M100. At this time, assuming that N=12, the raster interval may be 180 kHz or a multiple of 180 kHz by method M101.

3 is a diagram illustrating a carrier raster and carrier allocation based on method M101 or method M102, according to an embodiment of the present invention.

Specifically, in FIGS. 3A and 3B , a case in which the carrier raster interval is equal to the bandwidth occupied by one resource block is exemplified as an embodiment of the method M101.

As illustrated in (a) of FIG. 3 , two adjacent carriers (Carrier 1, Carrier 2) have an even number (eg, 4) of resource blocks (eg, RB 0, RB 1, RB 2, RB 3), the method M101 may perform carrier allocation so that there is no idle band (or band gap) between the carriers (Carrier 1 and Carrier 2). This can be applied equally or similarly even when both adjacent carriers have an odd number of resource blocks.

However, as illustrated in (b) of FIG. 3 , one carrier (Carrier 1) has an even number (eg, 4) of resource blocks (eg, RB 0 to RB 3) and adjacent other carriers (Carrier 2) ) has an odd number of (eg, 3) resource blocks (eg, RB 0 to RB 2), an idle band (or band gap) between carriers (Carrier 1, Carrier 2) may occur.

In order to solve the above-mentioned problem, the raster interval (the product of the subcarrier interval and N/2), that is, may be determined to be half of the frequency band occupied by one resource block. This is referred to as method M102. For example, when the subcarrier interval is 15 kHz and N=12, the raster search interval may be 90 kHz. An embodiment of the method M102 is illustrated in (c) of FIG. 3 .

As illustrated in (c) of FIG. 3, one carrier (Carrier 1) has an even number (eg, 4) of resource blocks (eg, RB 0 to RB 3) and another carrier adjacent to it (Carrier 2) Even when has an odd number of (eg, 3) resource blocks (eg, RB 0 to RB 2), so that there is no idle band (or band gap) between carriers (Carrier 1, Carrier 2), method M102 is a carrier assignment can be performed.

In method M101 and method M102, center frequency location design is important. If, like LTE downlink, one subcarrier of the center frequency is defined as a direct current (DC) subcarrier and the DC subcarrier is excluded from the configuration of the resource block, even if method M101 or method M102 is used, the Due to the frequency band, an idle band between carriers may occur. On the other hand, like LTE uplink, when the center frequency is defined as the middle of two subcarriers and a resource block is configured using all subcarriers (however, subcarriers of the guard band are excluded), the above-described effect of method M101 or method M102 can be obtained. This may be similarly established in the methods to be described later.

Meanwhile, as described above, a plurality of pneumatologies may be used within one frequency band. Here, one frequency band means a specific frequency range, and the specific frequency range may be wide or narrow. For example, the specific frequency range may be the bandwidth of one carrier, may be one frequency band having a bandwidth of generally several to several hundreds of MHz, or may be a wider area than that.

4 is a diagram illustrating a case in which a plurality of pneumatology is used within a common frequency band. Specifically, FIG. 4 exemplifies a case in which three heterogeneous numerology (Numerology 1, Numerology 2, and Numerology 3) are used within a common frequency band.

In FIG. 4 , it is assumed that the subcarrier spacing of pneumatology 2 is larger than the subcarrier spacing of pneumology 1, and the subcarrier spacing of pneumology 3 is larger than the subcarrier spacing of pneumology 2. This is expressed as a difference in length of a time axis of a resource grid (a difference in length of OFDM symbols) or a difference in length of a frequency axis of a resource grid in FIG. 4 . For example, when the subcarrier spacing of pneumatology 1 is 15 kHz, the subcarriers spacing of pneumology 2 and pneumology 3 may be 30 kHz and 60 kHz, respectively.

A plurality of heterogeneous neuroleptics may be used for different carriers, respectively, or may be used together in one carrier. Specifically, FIG. 4 exemplifies a case in which pneumatology 1 and pneumology 2 coexist in one carrier and pneumology 3 alone constitutes one carrier.

On the other hand, when a plurality of pneumatologies are used within one frequency band, the carrier raster may be defined for each pneumatology. This is referred to as method M110. In this case, the offset of the carrier raster scale may be determined so that the scale of the carrier raster is differentiated for each pneumatology. This is referred to as method M111.

For example, the carrier raster of Numerology 1 may have an offset of 0 kHz and an interval of 100 kHz, and the carrier raster of Numerology 2 may have an offset of 50 kHz and an interval of 200 kHz. That is, frequencies such as 100 kHz, 200 kHz, and 300 kHz may be center frequency candidates of pneumology 1, and frequencies such as 50 kHz, 250 kHz, and 450 kHz may be center frequency candidates of pneumology 2. At this time, for example, when the terminal initially searches only a cell (or carrier) having Numerology 2, the terminal searches only candidate center frequencies having an offset of 50 kHz and an interval of 200 kHz. In this case, the UE may consider that Numerology 2 is applied to all or a part of the cell (or carrier) in which the UE has succeeded in discovery.

Meanwhile, in the case of the method M110, it may be defined so that the scales of the carrier rasters for the numerology have an inclusive relationship with each other. This is referred to as method M112.

For example, the carrier raster of Numerology 1 may have an offset of 0 kHz and an interval of 100 kHz, and the carrier raster of Numerology 2 may have an offset of 0 kHz and an interval of 200 kHz. In this case, frequencies such as 100 kHz, 300 kHz, and 500 kHz may be center frequency candidates of pneumology 1, and frequencies such as 200 kHz, 400 kHz, and 600 kHz may be center frequency candidates of pneumology 1 and pneumology 2.

When the UE initially searches for a cell (or carrier) for a plurality of numerology within a certain frequency band, the method M112 may reduce the number of carrier raster scales that the UE needs to search, compared to the method M111. In this case, in the above example, when the terminal detects a cell at a frequency of 200 kHz, 400 kHz, 600 kHz, etc., there is a need for a method for the terminal to distinguish whether the detected cell is pneumology 1 or pneumology 2 . This will be described in detail in the 'Synchronous Signal Design' section to be described later.

Meanwhile, in the case of the method M110, the method M111, or the method M112, the frequency interval of the carrier raster for the pneumatology may be determined to be proportional to the subcarrier spacing of each pneumophile. This is referred to as method M113. For example, in the case where pneumatology 1 and pneumology 2 have subcarrier spacings of 15 kHz and 30 kHz, respectively, the carrier raster spacing of the pneumatology 2 may be twice the carrier raster spacing of the pneumatology 1. In this case, as a method of defining the carrier raster interval, method M101 and method M102 may be used.

On the other hand, when N _RE , which is the number of resource elements that one resource block has on the frequency axis, is the same for all numbers, method M113 may help to minimize idle bands between carriers within the same band.

5 is a diagram illustrating a carrier raster and carrier allocation based on method M112 or method M113, according to an embodiment of the present invention. Specifically, in FIG. 5 , it is assumed that the subcarrier spacing of the neurology 2 ( N2 ) is twice the subcarrier spacing of the neurology 1 ( N1 ).

By method M112 the carrier raster for pneumatology 1 (N1) comprises a carrier raster for pneumatology 2 (N2), and by method M113 the carrier raster spacing for pneumatology 2 (N2) is pneumoroller twice the carrier raster spacing for point 1 (N1).

At this time, assuming that N _RE (the number of resource elements that one resource block has on the frequency axis) is the same for neurology 1 (N1) and neurology 2 (N2), as illustrated in FIG. Similarly, a resource block of carrier 2 (Carrier 2) occupies a bandwidth twice as wide as a resource block of carrier 1 (Carrier 1).

In Fig. 5, it is assumed that method M101 is used to define the raster interval. That is, the raster interval of Numerology 1 (N1) is equal to the bandwidth occupied by one resource block of Carrier 1, and the raster interval of Numerology 2 (N2) is occupied by one resource block of Carrier 2. equal to bandwidth.

As an effect on this, regardless of whether the number of resource blocks of carrier 2 is even (eg, in FIG. 5 (a)) or odd (eg, in FIG. 5 (b)), carrier 1 has an even number of resource blocks (RB0 to RB3) Carrier allocation may be performed so that there is no idle band (or guard band) between the carriers (Carrier1, Carrier2) in the case of having .

If method M102 is used instead of method M101, carrier allocation may be performed so that there is no idle band between carriers even when carrier 1 has an odd number of resource blocks. Instead, the cell search complexity may increase due to the reduced carrier raster spacing.

On the other hand, one carrier raster may be defined in common with respect to a plurality of pneumophiles. This is referred to as method M120. For example, a carrier raster defined based on a numerology having the smallest subcarrier spacing within one frequency band may be used for a plurality of numerologies. In this case, since the UE may have to perform cell search for a plurality of numerologies for all carrier raster scales, the method M120 may increase complexity compared to the method M112.

Meanwhile, the carrier raster may be defined for each frequency band. For example, in the high frequency band, it may be defined to use only the neurology(s) having a relatively large subcarrier spacing. In this case, the carrier raster for the high frequency band may have a wider interval than the carrier raster for the low frequency band.

[Synchronous signal]

As described above, the UE may have to assume a plurality of numerologies for one carrier raster scale and a corresponding synchronization signal or cell (or carrier) in the initial cell search process.

Hereinafter, a description will be given of a method in which the base station transmits a synchronization signal for initial cell search of the terminal when a plurality of numerologies are used within a common frequency range.

First, consider the case of a carrier composed of a single pneumatology. At this time, according to the relationship between the pneumometry of the synchronization signal and the pneumatology of the carrier, a method M200 and a method M210 exist.

Method M200 is a method in which the numerology applied to the synchronization signal follows the numerology of the carrier to which the synchronization signal belongs.

According to the method M200, since there is no interference between the synchronization signal and the signal in the adjacent frequency domain, the method M200 has an advantage that there is no need to additionally set a guard band.

The terminal may attempt to detect a synchronization signal for each pneumatology with respect to a plurality of pneumatology candidates. When there is a synchronization signal successfully detected by the terminal, the terminal may regard the detected synchrony of the synchronization signal as the numerology of the carrier to which the detected synchronization signal belongs.

When the synchronization signal detection is performed in the time domain, the process may be performed through sampling, filtering, and a correlator. Here, the filtering may be low-pass filtering when the synchronization signal is symmetrically disposed with respect to the center frequency, like LTE. The correlator may be implemented as an auto-correlator or self-correlator, a cross-correlator, or the like according to the characteristics of the synchronization signal sequence.

As the sequence of the synchronization signal, a Zadoff-Chu sequence, a gold sequence, or the like may be used. When the resource region of the synchronization signal consists of a plurality of OFDM symbols, the sequence of the synchronization signal may be defined for each OFDM symbol or may be a long sequence occupying the plurality of OFDM symbols.

Hereinafter, method M201 and method M202, which are detailed methods of method M200, will be described.

Method M201 is a method in which the time-frequency resource element configuration of the synchronization signal resource region is the same for a plurality of neurons. That is, the method M201 is the same method in which resource element mapping of the synchronization signal is performed regardless of the neurology.

6 is a diagram illustrating a synchronization signal resource region based on method M201 according to an embodiment of the present invention.

Specifically, FIG. 6 exemplifies a case in which method M201 is applied to two different numerology (Numerology 1, Numerology 2). In FIG. 6 , it is assumed that the sequence length of the synchronization signal is 6 and the subcarrier interval of Numerology 2 is greater than the subcarrier interval of Numerology 1. As shown in FIG.

According to the method M201, the resource region of the synchronization signal for both the Numerology 1 and the Numerology 2 occupies one resource element (ie, one OFDM symbol) in the time axis and 6 consecutive resource elements in the frequency axis occupy

F _BW,1 represents the bandwidth occupied by the synchronization signal to which Numerology 1 is applied, and F _BW,2 represents the bandwidth occupied by the synchronization signal to which Numerology 2 is applied. F _BW,2 is greater than F _BW,1 .

When method M201 is used, since the UE may have to apply different sampling, different filtering, and/or different correlators for each neurology, complexity and delay time for initial cell search of the UE may increase. there is. In addition, when the number of subcarriers is large, the bandwidth used for initial cell search is widened, and thus a required sampling rate may increase. For example, when the subcarrier spacing of the carrier is 60 kHz, a sampling rate 4 times higher than that in the case where the subcarrier spacing is 15 kHz may be required. On the other hand, since the period in which the synchronization signal is transmitted becomes shorter as the subcarrier interval is increased, the method M201 may be advantageous for beam sweeping-based transmission in a high frequency band.

In this specification, the resource region of the synchronization signal basically means a set of resource elements to which the synchronization signal is mapped. Meanwhile, when bandpass filtering for detecting the synchronization signal of the terminal is non-ideal, guard bands may have to be inserted at both ends of the bandwidth of the synchronization signal. For example, in LTE, 5 adjacent subcarriers existing at both ends of bandwidths of PSS and SSS are defined as guard bands. In this case, the resource region of the synchronization signal may mean a region including both the resource region to which the synchronization signal is mapped and the guard band.

Method M202 is a method of defining a bandwidth so that the bandwidth occupied by the synchronization signal resource region is the same or similar irrespective of the number.

7 is a diagram illustrating a synchronization signal's numerology and a synchronization signal resource region based on a method M202 according to an embodiment of the present invention.

Specifically, in FIG. 7 , a case in which method M202 is applied to two different numerology (Numerology 1, Numerology 2) is exemplified. In FIG. 7 , it is assumed that the subcarrier spacing (2*K) for the neurology 2 is twice the subcarrier spacing (K) for the neurology 1. That is, in FIG. 7 , it is assumed that the OFDM symbol length L for Numology 1 is twice the OFDM symbol length L/2 for Numology 2.

In FIG. 7 , it is assumed that the number of resource elements constituting the resource region of the synchronization signal is 8 in the case of Numerology 1 and 12 in the case of Numerology 2.

According to method M202, the resource region of the synchronization signal includes 8 resource elements on the frequency axis and 1 resource element on the time axis in case of Numerology 1, and 4 resources on the frequency axis in case of Numerology 2 It contains three resource elements in terms of element and time axis. In this case, F _BW,1 and F _BW,2 , which are bandwidths of the synchronization signal resource region, are the same (ie, F _BW,1 =F _BW,2 =F). Therefore, the method M202 has an advantage that the UE can apply the same filtering to a plurality of neuroleptics in the initial cell search process. In addition, the method M202 may transmit the synchronization signal with a narrow bandwidth regardless of the subcarrier spacing of the neuron. On the other hand, in the method M202, since the number of OFDM symbols occupied by the synchronization signal resource region may be different for each neurology, a sequence design taking this into consideration and a design for coexistence with other signals and other channels taking this into account are required.

The fact that the bandwidths of the synchronization signal resource region in method M202 are similar irrespective of the number means that the bandwidths are sufficiently similar (eg, subcarrier difference within several) for the terminal to apply common filtering to a plurality of numbers. ) can mean

Meanwhile, in method M202, a method of performing mapping such that not only the bandwidth of the synchronization signal resource region but also the length of the time interval is the same or similar regardless of the number may be considered. This is referred to as method M203.

8 is a diagram illustrating a synchronization signal resource region and a numerology of a synchronization signal based on method M203 according to an embodiment of the present invention.

Specifically, in FIG. 8 , it is assumed that the subcarrier spacing (2*K) for pneumatology 2 is twice as large as the subcarrier spacing (K) for pneumology 1, as in the embodiment of FIG. 7 . That is, in FIG. 8 , it is assumed that the OFDM symbol length (L) for Numology 1 is twice the OFDM symbol length (L/2) for Numology 2.

In FIG. 8 , it is assumed that the number of resource elements constituting the synchronization signal resource region is 8 in both cases of Numerology 1 and Numerology 2 .

According to method M203, the resource region of the synchronization signal includes 8 resource elements on the frequency axis and 1 resource element on the time axis in case of Numerology 1, and 4 resources on the frequency axis in case of Numerology 2 It contains two resource elements as an element and a time axis. That is, the bandwidth (F _BW,1 ) occupied by the synchronization signal resource region for numerology 1 and the bandwidth occupied by the synchronization signal resource region for numerology 2 (F _BW,2 ) are the same, and The time interval length (T) occupied by the synchronization signal resource area for role 1 and the time interval length (T) occupied by the synchronization signal resource area for role 2 are the same.

Also, in the method M202 or the method M203, not only the frequency bandwidth of the synchronization signal resource region but also the frequency resource region may be the same for a plurality of numerologies. For example, the sync signal can occupy the center of the system bandwidth, F _BW,1 Hz or F _BW,2 Hz, regardless of the number.

Method M210 is a fixed method irrespective of the number of carriers applied to the synchronization signal, regardless of the number of carriers to which the synchronization signal belongs.

9 is a diagram illustrating a synchronization signal numerology and a synchronization signal resource region based on a method M210 according to an embodiment of the present invention.

Specifically, FIG. 9 exemplifies a case in which both the synchronization signal of the carrier to which the Numerology 1 is applied and the synchronization signal of the carrier to which the Numerology 2 is applied follow Numerology 1. For example, in the case of Numerology 1, the resource region for the synchronization signal includes 8 resource elements on the frequency axis and 1 resource element on the time axis. That is, the bandwidth (F) and the time interval length (T) occupied by the synchronization signal resource region for neurology 1 are the bandwidth F and the time interval occupied by the synchronization signal resource region for neurology 2 equal to the length (T).

In FIG. 9 , it is assumed that the subcarrier spacing (2*K) for the neurology 2 is twice the subcarrier spacing (K) for the neurology 1. That is, in FIG. 9 , it is assumed that the OFDM symbol length L for Numology 1 is twice the OFDM symbol length L/2 for Numology 2.

Method M210 may be applied within a specific frequency range.

The method M210 may preset a numerology for the synchronization signal as one of numerologies allowed within a specific frequency range. For example, in a frequency band of 6 GHz or less, a synchronization signal may always be transmitted along a numerology having a subcarrier interval of 15 kHz.

According to method M210, the UE may search for a synchronization signal through a single neurology in the initial cell search process.

However, since the pneumatology of the synchronization signal and the pneumatology of the carrier may be different, a separate method is required for the UE to know which pneumatology is applied to the carrier. The UE may explicitly or implicitly acquire carrier numerology through synchronization signal reception. Alternatively, the terminal may acquire the carrier's numerology through a signal or channel (eg, PBCH) that the terminal receives after the synchronization signal. In this case, the signal or channel received by the terminal after the synchronization signal follows the same number of the synchronization signal. In the method M210, since the numerology of a signal and a channel adjacent to the sync signal on the frequency axis may be different from that of the sync signal, additional guard bands may need to be inserted at both ends of the bandwidth of the sync signal.

Next, consider the case of a carrier composed of a plurality of pneumophiles.

A plurality of numerology in one carrier may be multiplexed through time division multiplexing (TDM) or may be multiplexed through frequency division multiplexing (FDM) as in the embodiment of FIG. 4 . In this case, a method in which a plurality of neurons share one synchronization signal (hereinafter, 'method M220') and a method in which a synchronization signal is transmitted for each neurology (hereinafter, 'method M230') may be used.

Similar to method M200, in the case where a plurality of neuronologies share one synchronization signal, the number of the synchronization signals may follow one of the plurality of neurons in the carrier. This is referred to as method M221. Method M221 will be described with reference to FIG. 10 .

FIG. 10 is a diagram illustrating the numerology of a synchronization signal and a resource region of the synchronization signal with respect to a carrier composed of a plurality of numerologies according to an embodiment of the present invention.

In FIG. 10 , a case in which two numerology 1 and Numerology 2 constitute one carrier is exemplified.

In FIG. 10 , it is assumed that the subcarrier spacing for pneumatology 2 is larger than the subcarrier spacing for pneumology 1 . That is, in FIG. 10, it is assumed that the OFDM symbol length for Numology 1 is greater than the OFDM symbol length for Numology 2.

As illustrated in FIG. 10 , a synchronization signal resource region may be defined within a resource region to which the same numerology as that of the synchronization signal (eg, Numerology 1) is applied. FIG. 10 exemplifies a case in which a resource region for a synchronization signal includes six resource elements on a frequency axis and one resource element on a time axis.

The numerology of the synchronization signal may be used as a base numerology in one carrier. That is, the terminal accessing the carrier may receive a signal using the basic neurology within a specific time-frequency resource region until the terminal is separately configured.

When only one synchronization signal exists in a carrier composed of a plurality of numbers, the synchronization signal may be defined at the center of the carrier bandwidth (eg, to be symmetrical with respect to the center frequency). In this case, when a plurality of numerologies are multiplexed through FDM, the terminal may assume at least the same numerology as that of the synchronous signal with respect to the central bandwidth occupied by the synchronous signal.

As a method for configuring a resource region of a synchronization signal, the above-described method (eg, method M201, method M202, method M203, etc.) may be used.

On the other hand, in the case where a plurality of pneumophiles share one synchronization signal, similarly to the method M210, the pneumatology of the synchronization signal may follow a predetermined number irrespective of carrier pneumatologies. This is referred to as method M222.

When a synchronization signal is transmitted for each number in one carrier, the number of each synchronization signal may follow the number of a resource region in which the synchronization signal is defined. This is referred to as method M231. Method M231 can be seen as a method M200 applied in one carrier.

In this case, the configuration of the synchronization signal resource region may follow the above-described method (eg, method M201, method M202, method M203, etc.).

Unlike the method M231, the numerology of all synchronization signals in one carrier may follow one of a plurality of numerologies constituting the carrier. This is referred to as method M232.

Alternatively, the numerology of all synchronization signals in one carrier may follow a predetermined numerology regardless of the numerology of the carrier. This is referred to as method M233.

When the above-described methods are applied to a carrier composed of a plurality of numerology, the capability of the terminal may be considered.

In the case where the NR terminal has the ability to receive a plurality of numerology by default, the method M220 may be used. A terminal supporting eMBB and URLLC may correspond to this. In this case, the terminal may use different numerology for synchronization signal reception and data reception.

On the other hand, for a terminal that does not have the ability to receive a plurality of neurology, method M230 may be used. This may correspond to a low-cost terminal that supports only a specific null roller for mMTC transmission. In this case, the terminal uses the same neurology for synchronization signal reception and data reception.

Method M220 and method M230 may be mixed and used in one carrier.

In the above-described methods (eg, methods M200 to M233), the synchronization signal transmission time and period may be the same for a plurality of neurons.

On the other hand, since heterogeneous frame structures having different numerologies may have different subframe lengths or sets of subframe numbers, the synchronization signal transmission time and period may be expressed by different equations for each frame structure.

When the synchronization signal transmission time and period are the same, the initial cell search complexity of the UE may be reduced.

Meanwhile, in the above-described methods, another signal (or another channel) may be mapped to the resource region of the synchronization signal. That is, a synchronization signal and a signal (or channel) other than the synchronization signal may coexist within the synchronization signal resource region. For example, when a synchronization signal is mapped to discontinuous resource elements on the frequency axis, resource elements to which the synchronization signal is not mapped may be used for transmission of another signal (or another channel).

The above-described synchronization signal may be limited to the purpose of searching for a center frequency of a cell (or carrier) in the initial cell search process of the terminal. In this case, in a frequency domain that does not support a standalone operation of a cell (or carrier), the synchronization signal may not exist. Alternatively, when the cell (or carrier) operates only as a secondary cell, the synchronization signal may not exist.

Meanwhile, the above-described synchronization signal may be used not only for center frequency search, but also for obtaining synchronization of a terminal, tracking synchronization, and/or obtaining a cell ID.

In addition, the above-described synchronization signal may be used as a pilot for channel estimation (or data decoding).

In particular, when the synchronization signal is used not only for center frequency search but also for other purposes, the synchronization signal may be composed of a plurality of synchronization signals. For example, the synchronization signal may include a first synchronization signal and a second synchronization signal. When the synchronization signal includes a plurality of synchronization signals, the above-described method (eg, methods M200 to M210) may be applied only to some synchronization signals (eg, the first synchronization signal). Alternatively, the above-described methods (eg, methods M200 to M210) may be applied to a plurality of synchronization signals (eg, a first synchronization signal and a second synchronization signal). In this case, the synchronization signal resource region defined for the above-described method (eg, method M200 to method M210) may include only some synchronization signals in the former case, and may include a plurality of synchronization signals in the latter case. there is.

[Signal configuration for initial connection]

Since NR supports a wide range of frequencies, the operation of the high frequency band and the operation of the low frequency band may be different from each other.

Transmission beamforming and/or reception beamforming may be applied to a high frequency band having a large signal path loss. Beamforming may be applied not only to a data channel but also to a common signal and a control channel in order to extend the coverage of a cell or a terminal. In this case, when a beam having a small beamwidth is formed through a plurality of antennas, a signal is transmitted or received several times through a plurality of beams having different directivity in order to cover the entire coverage of a cell or sector. it may have to be When a signal to which beamforming is applied is transmitted multiple times through different resources on a time axis, it is referred to as beam sweeping.

On the other hand, in a low frequency band in which the path loss of a signal is relatively small, even if the common signal and the control channel are transmitted only once, the entire coverage of a cell or sector can be covered.

The initial access procedure of NR must be capable of supporting all of the different beam operations.

Hereinafter, a resource configuration and transmission method for signals for initial access of the terminal will be described. A method (band-agnostic or beam operation-agnostic method) that can be commonly used regardless of a frequency band or beam operation will be described.

For initial access of the UE, a downlink discovery signal and an uplink PRACH may be used.

First, a downlink discovery signal will be described.

The discovery signal is a downlink signal for cell search, system information acquisition, and beam acquisition and tracking of the terminal, and may be periodically transmitted to the terminal. A discovery signal occurrence may be defined.

11 is a diagram illustrating components of a discovery signal according to an embodiment of the present invention.

As illustrated in (a) of FIG. 11 , the discovery signal occasion may include a synchronization signal and a PBCH.

The synchronization signal is used for time-frequency synchronization and cell ID acquisition, and the PBCH may be used to transmit system information (SI) essential for initial access. A cell (or base station) that does not support initial access may not transmit the PBCH. That is, the discovery signal occasion may not include the PBCH.

The synchronization signal may be composed of a plurality of synchronization signals. For example, the synchronization signal may include a primary synchronization signal (PSS) and a secondary synchronization signal (SSS).

Alternatively, the discovery signal occasion may be composed of a synchronization signal, a PBCH, and a beam reference signal (BRS), as illustrated in FIG. 11B or 11C .

BRS may be used for beam or beam ID acquisition, radio resource management (RRM) measurement, and/or channel estimation for PBCH decoding. TDM may be applied between the PBCH and the BRS. Alternatively, for higher PBCH decoding performance, as illustrated in FIG. 11C , the PBCH and the BRS may coexist in a common region.

Alternatively, the discovery signal occasion may include a reference signal for measuring and reporting channel state information (CSI), that is, a reference signal (CSI-RS). Alternatively, the discovery signal occasion may include a separate reference signal for beam tracking. The CSI-RS and/or the beam tracking reference signal may be configured to be UE-specific.

When the discovery signal occasion is used for the initial cell search of the UE, the transmission period and offset of the discovery signal occasion may be predefined fixed values.

It is assumed that M time-frequency resources exist for each of the synchronization signal, the PBCH, and/or the BRS within one discovery signal occasion period. Here, M is a natural number. That is, each of the component signals included in the discovery signal occasion may use M resources. M resources for each component signal have the same bandwidth and the same time axis length (eg, the number of OFDM symbols).

When M>1, beam sweeping may be applied to each of the synchronization signal, PBCH, and/or BRS through a plurality of resources. When M=1, a single beam may be transmitted or a plurality of beams may be transmitted through spatial division multiplexing (SDM) on the same resource.

The discovery signal occasion may consist of a plurality of signal blocks. A resource occupied by one signal block is continuous on the time-frequency axis. That is, a resource occupied by one signal block may include consecutive time domain symbols on the time axis. In this case, the method M300 and the method M310 may be considered according to component signals constituting the signal blocks.

The method M300 is a method in which the discovery signal occasion is composed of heterogeneous signal blocks. That is, the discovery signal occasion may be composed of a synchronization signal block(s) and a PBCH block. In this case, if the BRS exists for decoding the PBCH, the BRS may be included in the PBCH block.

12 is a diagram illustrating a resource configuration of a discovery signal occasion based on method M300 according to an embodiment of the present invention.

Specifically, FIG. 12 exemplifies a case in which the discovery signal occasion is composed of three heterogeneous signal blocks (a first signal block, a second signal block, and a third signal block).

The first signal block is a PSS block and includes M PSS resources identified through TDM. The second signal block is an SSS block and includes M SSS resources identified through TDM. The third signal block is a PBCH block and includes M PBCH resources and/or M BRS resources identified through TDM.

As another example, the discovery signal occasion may include two heterogeneous signal blocks (a first signal block and a second signal block). The first signal block is a PSS and SSS block, and includes M PSS resources and M SSS resources that are distinguished through TDM. The second signal block is a PBCH block and includes M PBCH resources and/or M BRS resources identified through TDM. At this time, the PSS and SSS resources in the first signal block are {PSS #0, SSS #0, PSS #1, SSS #1, ..., PSS #(M-1), SSS #(M-) 1)} can be cross-arranged on the time axis.

The method M310 is a method in which the discovery signal occasion is composed of the same type of signal block(s), that is, the discovery signal block(s). Method M310 will be described with reference to FIG. 13 .

13 is a diagram illustrating a resource configuration of a discovery signal occasion based on a method M310 according to an embodiment of the present invention. 13 to 18, DS means a discovery signal.

A discovery signal occasion consists of M discovery signal block(s), and one discovery signal block includes one synchronization signal resource, one PBCH resource, and/or one BRS resource.

13 exemplifies a case in which a synchronization signal is composed of PSS and SSS and TDM is applied between PSS resources, SSS resources, and PBCH resources within each discovery signal block. One synchronization signal resource included in one discovery signal block is divided into a PSS resource and an SSS resource.

When the UE receives the PSS first and then the SSS, it is advantageous that the PSS is transmitted temporally earlier than the SSS within one discovery signal block.

Meanwhile, in the method M300 and the method M310, TDM and/or FDM may be applied between signal blocks.

14 is a diagram illustrating a case in which TDM is applied between signal blocks in method M300 or method M310 according to an embodiment of the present invention.

When the discovery signal occasion occupies only one subband, TDM may be applied between signal blocks. Such a case is exemplified in Figs. 14(a), 14(b), and 14(c). When the discovery signal occasion occupies a plurality of subbands, both TDM and FDM may be applied between signal blocks.

14(a) and 14(b) show an embodiment of the method M300, and FIG. 14(c) shows an embodiment of the method M310.

In (a) of FIG. 14, the time distance between the PSS block (including M PSS resources) and the SSS block (including M SSS resources) is T _B,0 , and the SSS block and the PBCH block (including M PBCH resources and / or (including M BRS resources) the time distance is T _B,1 .

In FIG. 14B, the time distance between the PSS/SSS block (including M PSS resources and M SSS resources) and the PBCH block (including M PBCH resources and/or _M BRS resources) is TB.

In (c) of FIG. 14 , a time distance between M discovery signal blocks is T _S,0 , T _S,1 , ..., T _{S,( M-2)} . Each discovery signal block includes one synchronization signal resource (PSS resource, SSS resource), one PBCH resource, and/or one BRS resource.

Bandwidth(s) of subbands occupied by one discovery signal occasion may all be the same. This bandwidth is referred to as a cell search bandwidth.

When guard bands are inserted at both ends of the bandwidth of the synchronization signal, the bandwidth of the synchronization signal including the guard band may be the same as the bandwidth of the PBCH.

Method M310 has several advantages over method M300.

First, since the channel change within one discovery signal block is relatively small, when the antenna port of the PSS/SSS and the antenna port of the PBCH are the same, the PSS/SSS can be helpful for decoding the PBCH or measuring the BRS-based RRM. there is.

Second, in the method M300, when M>1, since beam sweeping must be performed for each signal block, a fast beamforming change is required. However, since the method M310 may change the beamforming only between discovery signal blocks and apply the same or similar beam within the discovery signal block, the beamforming change may occur less frequently.

Finally, according to method M300, the relative distances (eg, time axis distance and frequency axis distance) between the mth PSS resource, the mth SSS resource, and the mth PBCH resource may vary depending on the beamforming mode, that is, the M value. there is. Here, m is a resource index and is an integer of 0 or more (M-1) or less. Therefore, after the terminal receives the PSS, it may be necessary to receive resource location information of the SSS or PBCH from the base station in order to receive the SSS or PBCH. For example, in order to know the resource location of the SSS or PBCH, the UE may need to obtain the M value through PSS reception.

On the other hand, according to the method M310, the relative distances (eg, time axis distance and frequency axis distance) between the mth PSS resource, the mth SSS resource, and the mth PBCH resource are constant regardless of the M value. In this specification, the frequency axis distance between resources means a relative distance between frequency domains occupied by the resources. This can be applied even when the frequency domains overlap each other on the frequency axis. For example, the time and frequency distance between the PSS (or PSS resource) and the SSS (or SSS resource) included in the m-th discovery signal block generated by the base station is the (m+1)-th discovery signal block generated by the base station It is the same as the time and frequency distance between the PSS (or PSS resource) and the SSS (or SSS resource) included in the . That is, the time axis distance between the PSS resource and the SSS resource included in the mth discovery signal block is the same as the time axis distance between the PSS resource and the SSS resource included in the (m+1)th discovery signal block, and in the mth discovery signal block The frequency axis distance between the included PSS resource and the SSS resource is the same as the frequency axis distance between the PSS resource and the SSS resource included in the (m+1)-th discovery signal block. Similarly, the time and frequency distance between the SSS (or SSS resource) and the PBCH (or PBCH resource) included in the m-th discovery signal block is the SSS (or SSS resource) and PBCH (or SSS resource) included in the (m+1)-th discovery signal block ( or PBCH resources) and is equal to the time and frequency distance. Similarly, the time and frequency distance between the PSS (or PSS resource) and the PBCH (or PBCH resource) included in the m-th discovery signal block is the (m+1)-th discovery signal block included in the PSS (or PSS resource) and PBCH ( or PBCH resources) and is equal to the time and frequency distance.

Therefore, after the UE detects the PSS, the UE receives the SSS or PBCH at a predetermined position within the discovery signal block (eg, the m-th discovery signal block) including the PSS resource (eg, the m-th PSS resource) in which the PSS is detected. can That is, the UE does not need to know the resources of all signal blocks constituting the discovery signal occasion, and it is sufficient for the UE to assume that one discovery signal block including the PSS resource in which the PSS is detected is transmitted. Therefore, according to method M310, the UE does not need to know the beamforming mode, that is, the value of M, in the process of receiving a discovery signal for initial cell search.

Meanwhile, the UE may assume (or determine) a discovery signal measurement window (DMW) in order to receive a discovery signal occasion.

15 is a diagram illustrating a case in which a discovery signal occasion is transmitted within a discovery signal measurement window according to an embodiment of the present invention.

In FIG. 15 , it is assumed that TDM is applied between M discovery signal blocks.

The UE may monitor, discover, and measure the discovery signal within the discovery signal measurement window.

When the method M310 is applied to the resource configuration of the discovery signal occasion and PSS, SSS, and PBCH are included in the discovery signal occasion as element signals, the UE may monitor the PSS within the discovery signal measurement window.

In this case, the UE may discover one or more PSS beams transmitted from the same cell. When the UE discovers one or more PSS(s) corresponding to one or more discovery signal block(s) within the discovery signal measurement window, one or more PSS(s) may be selected.

In order to select one from among the one or more PSS beam(s) found, the UE monitors the entire time period of the discovery signal measurement window, and then the PSS beam (or PSS beam) with the best reception performance among the discovered PSS beam(s). A method of selecting a PSS resource corresponding to (hereinafter referred to as 'first selection method') may be used. Alternatively, in order to select one from the one or more PSS beam(s) found, the terminal performs monitoring until it finds one PSS beam (or PSS resource corresponding to the PSS beam) that satisfies a predetermined reception performance condition. (hereinafter 'second selection method') may be used. The first selection method provides higher reception performance than the second selection method, but may increase the complexity of receiving a discovery signal of the terminal.

And the terminal is a discovery signal block (eg, the m-th discovery signal) corresponding to the PSS (eg, the PSS having the best reception performance or satisfying a predefined reception performance condition) selected by the first selection method or the second selection method block) at a predetermined position, SSS or PBCH may be monitored.

Meanwhile, FIG. 15 exemplifies a case in which the discovery signal measurement window is continuously set on the time-frequency axis within one DMW period (periodicity).

On the other hand, the discovery signal measurement window may be discontinuous in the time or frequency axis. That is, a plurality of resource blocks may constitute a discovery signal measurement window on a time axis or a frequency axis within one discovery signal measurement window period. In this case, each resource block means a set of continuous resources on the time axis and the frequency axis, and the resource blocks may be discontinuous on the time axis and/or the frequency axis.

A UE not connected to radio resource control (RRC) may assume discovery signal measurement window information (eg, DMW length and DMW period) as a predetermined value. That is, the terminal that is not RRC-connected to the base station may determine a duration and a period for the discovery signal measurement window based on a predefined length value and a period value. For example, a discovery signal measurement window period for a terminal attempting initial access is defined as 5 ms as in LTE, and a discovery signal measurement window length for the terminal may be defined as a fixed value of 5 ms or less. When the length and period of the discovery signal measurement window match, the UE not connected to RRC may monitor the discovery signal in the entire time domain.

Meanwhile, an RRC-connected terminal (or a terminal that is not RRC-connected but in a state capable of receiving system information from the base station) may receive discovery signal measurement window information (eg, DMW length and DMW period) configured from the base station. At this time, in order to reduce the reception complexity of the terminal, the discovery signal measurement window period may be set longer than a value assumed by the non-RRC-connected terminal, and the discovery signal measurement window length is assumed by the non-RRC-connected terminal It can be set shorter than the specified value. For example, the period and length of the discovery signal measurement window may be set to 40 ms and 2 ms, respectively. That is, the base station may set the DMW period for the terminal RRC-connected to the base station to a value larger than a predetermined period value for the terminal not RRC-connected to the base station. In addition, the base station may set the DMW length for the terminal RRC-connected to the base station to a value smaller than a length value predefined for the terminal not RRC-connected to the base station.

The RRC-connected terminal may not perform discovery signal measurement when discovery signal measurement window information (eg, DMW length and DMW period) is not configured from the base station. That is, the discovery signal measurement window information (eg, DMW length and DMW period) may be set in the UE only when the UE needs to measure the discovery signal. Alternatively, in this case, the RRC-connected UE may assume discovery signal measurement window information (eg, DMW length and DMW period) as the same value as the value assumed by the non-RRC-connected UE.

Discovery signal measurement window information (eg, DMW length and DMW period) may be signaled UE-specifically.

15 illustrates a case in which all signals (eg, M discovery signal blocks) constituting a discovery signal occasion are transmitted by a base station within a discovery signal measurement window. On the other hand, within the UE-specific discovery signal measurement window, only a portion of the signals constituting the discovery signal occasion (eg, one or a plurality of discovery signal blocks) may be transmitted. Alternatively, within the discovery signal measurement window, no signals constituting the discovery signal occasion may be transmitted.

Meanwhile, a resource pool (hereinafter, 'discovery signal resource pool') for transmitting a discovery signal occasion may be defined. That is, the discovery signal occasion may be transmitted within a predefined discovery signal resource pool. In this case, the period of the discovery signal occasion is not separately defined, but the period of the discovery signal resource pool may be defined instead.

The base station may allocate some or all of resources belonging to a predefined discovery signal resource pool to at least one discovery signal block for transmission of a discovery signal. FIG. 15 exemplifies a case in which the base station allocates some of the resources belonging to the discovery signal resource pool to M discovery signal blocks constituting the discovery signal occasion.

15 illustrates a case in which the area of the discovery signal resource pool coincides with the area of the discovery signal measurement window. However, the area of the discovery signal resource pool and the area of the discovery signal measurement window may not match.

Hereinafter, the relationship between the discovery signal and the PRACH will be described.

In the NR system, the PRACH may be used for random access of a terminal or terminal discovery by a base station, as in LTE.

The UE may transmit a preamble or an encoded signal through the PRACH. Specifically, an operation related to a PRACH resource configuration method for a case in which method M310 is used will be described. For this, a PRACH occasion may be defined.

As in the method M310, the discovery signal occasion is composed of M discovery signal blocks, the PRACH occasion also includes M PRACH blocks (or PRACH resources) within one PRACH occasion period for receive beamforming of the base station (provided that, m=0, 1, ..., M-1). Resources occupied by one PRACH block are continuous on the time-frequency axis.

16 is a diagram illustrating a discovery signal and PRACH resource configuration based on method M310 according to an embodiment of the present invention.

Specifically, FIG. 16 exemplifies a case in which M discovery signal blocks and M PRACH blocks for PRACH reception by the base station exist within one cell search bandwidth as an embodiment of the resource configuration of the PRACH occasion.

In FIG. 16 , T _S,m (eg, T _S,0 , T _S,1 , ..., T _{S,( M-2)} ) is the m-th discovery signal block and the (m+1)-th discovery signal block. _{Represents the} time _{axis distance between} Represents the time axis distance between blocks, and T _G,m (eg, T _G,0 , T _G,1 , ..., T _{G,( M-1)} ) is between the mth discovery signal block and the mth PRACH block. Represents the time axis distance. However, the embodiment of FIG. 16 is only an example, and a case in which signal blocks are mapped to different frequency resources may be considered.

The base station attempts to receive the PRACH in all M PRACH blocks. In this case, the base station may derive a reception beam for the m-th PRACH block among the M PRACH blocks based on the transmission beam for the m-th discovery signal block among the M discovery signal blocks. As in TDD, when reciprocity between an uplink channel and a downlink channel is established, the transmit beam and the receive beam may be the same or similar.

When the UE succeeds in detecting the synchronization signal and/or BRS in the m-th discovery signal block, the UE transmits a preamble in the m-th PRACH block. This terminal operation is referred to as method M311. If the terminal also performs beamforming, similarly to the base station, the transmission beam of the m-th PRACH block may be derived based on the reception beam of the m-th discovery signal block. According to methods M310 and M311, the UE only needs to know the resource location of the mth PRACH block among the M PRACH blocks.

The resource location of the m-th PRACH block may be expressed by a time offset and a frequency offset from the resource of the m-th discovery signal block. In the embodiment of FIG. 16, since the frequency offset is 0, the resource location of the m-th PRACH block is the time offset T _G,m can be expressed only as

In this case, the time offset {T _G,m } may be defined to have the same value T _G for all m (however, m=0, 1, ..., M-1). This is referred to as method M320. On the other hand, it may be allowed for the time offset {T _G,m } to have different values according to m. This is referred to as method M321.

In the case of method M320, the T _G value may be predefined in the standard or may be transmitted to the terminal by a discovery signal. In the case of method M321, the T _G,m value may be transmitted to the UE by the m-th discovery signal block. Method M321 has a burden of notifying the UE of resource configuration information of the PRACH block, but has a higher degree of flexibility in resource configuration than method M320.

When a frequency offset exists between the PRACH block and the discovery signal block, the above-described methods may be similarly applied to the frequency offset.

Meanwhile, {T _S,m } and {T _R,m } may be predefined in the standard. This is referred to as method M330. For example, T _S,0 =T _S,1 =...=T _{S,( M-2)} =T _S , and T _R,0 =T _R,1 =...=T _{R,( M -2)} =T _R , and (T _S , T _R ) may have a fixed value. As T _S and T _R values are smaller, the time required for beam sweeping may be reduced. That is, the time distance between the m-th discovery signal block and the (m+1)-th discovery signal block is determined based on a predefined T _S value, and the time distance between the m-th PRACH block and the (m+1)-th PRACH block is predefined. It is determined based on the value of T _R .

17 is a diagram illustrating a configuration of a discovery signal and a PRACH resource based on methods M320 and M330 according to an embodiment of the present invention.

17 illustrates a case in which (T _S , T _R )=(0, 0) as an embodiment of method M330. That is, the time axis distance between the m-th discovery signal block and the (m+1)-th discovery signal block is 0, and the time axis distance between the m-th PRACH block and the (m+1)-th PRACH block is 0.

In addition, as an embodiment of the method M320, FIG. 17 exemplifies a case in which the time offset {T _G,m } between the discovery signal block and the PRACH block is the same. That is, the time axis distance between the m-th discovery signal block and the m-th PRACH block is T _G .

To this end, the time resource length of each discovery signal block and the time resource length of each PRACH block may be designed such that _TB is the same.

On the other hand, {T _S,m } and {T _R,m } are not defined in the standard, and the base station may arbitrarily set the values of {T _S,m } and {T _R,m }. This is referred to as method M331. For example, the base station may determine the time distance between the m-th discovery signal block and the (m+1)-th discovery signal block, based on traffic conditions. Through this, the base station can dynamically adjust the DL interval and the UL interval. Also, the base station may arbitrarily determine the time distance between the m-th PRACH block and the (m+1)-th PRACH block. In the method M331, the time distance between the m-th discovery signal block and the (m+1)-th discovery signal block may be generally expressed as an integer number of OFDM symbol lengths. Alternatively, assuming that the number of OFDM symbols constituting the discovery signal block is N _DS , the time distance between the m-th discovery signal block and the (m+1)-th discovery signal block may be an integer multiple of N _DS .

18 is a diagram illustrating a configuration of a discovery signal and a PRACH resource based on methods M321 and M331 according to an embodiment of the present invention.

Specifically, the case where M=4 is exemplified in FIG. 18 . That is, four discovery signal blocks and four PRACH blocks exist within one cell search bandwidth.

18 illustrates a case in which {T _S,m } has different values according to m and {T _R,m } is 0 for all m as an embodiment of method M331. That is, the time axis distance between the m-th discovery signal block and the (m+1)-th discovery signal block has a different value according to m. The time axis distance between the m-th PRACH block and the (m+1)-th PRACH block is 0 regardless of m.

Also, FIG. 18 exemplifies a case in which {T _G,m } may have different values according to m as an embodiment of the method M321. That is, the time axis distance between the m-th discovery signal block and the m-th PRACH block has a different value according to m.

According to the method M331, since the base station has some degree of freedom in resource setting of the discovery signal block and the resource setting of the PRACH block, all resources can be flexibly operated. For example, as illustrated in FIG. 18 , a traffic situation in which downlink transmission and uplink transmission must be rapidly crossed in subframe units (eg, DL subframe -> UL subframe -> special subframe -> special sub frame->UL subframe), the base station can efficiently manage resources by distributing and allocating the discovery signal block and the PRACH block to appropriate positions within one period.

Also, the method M331 is advantageous over the method M330 in terms of forward compatibility. {T _G,m }, {T _S,m }, and/or {T _R,m } may have a fixed value for all periods of the discovery signal occasion, or may have different values for each period. When the location of the resource is changed for each period of the discovery signal occasion, the RRM measurement accuracy of the UE may be deteriorated. Accordingly, the base station determines the parameters (eg, T _G,m , T _S,m , T _R,m etc.) may be arbitrarily determined, but the base station may be limited in changing the resource location for each period. For example, the parameters (eg, T _G,m , T _S,m , T _R,m , etc.) may have the same value for each period of the discovery signal occasion. That is, parameters (eg, T _G,m , T _S,m , T _R,m , etc.) may be applied with the same value for each period of the discovery signal occasion.

Meanwhile, when the UE performs random access, a plurality of PRACH formats may be used to satisfy various uplink coverage requirements.

In general, as the size of the time-frequency resource of the PRACH increases, the random access coverage and the probability of access collision between terminals are improved. A plurality of PRACH formats used in LTE have the same bandwidth, but have different time-axis resource lengths depending on whether the neurology or preamble sequence is repeated.

Similarly in NR, there are requirements for various coverage and access attempt probabilities, so a plurality of PRACH formats are required.

For example, in the case of a small cell, since coverage is small and the number of terminals attempting access is small, a short random access preamble may be required. Also, as in method M310, when there are M PRACH resources and the UE attempts to access one of the M PRACH resources, the probability that an access collision occurs in each PRACH resource is further reduced. On the other hand, in the case of a macro cell or when the value of M is small in the method M310, the coverage is wide and the access collision probability is high, so a long random access preamble or repeated transmission may be required.

When a plurality of PRACH formats exist, the base station may transmit the PRACH format to the terminal through a discovery signal. This is referred to as method M340. The UE may generate a random access preamble according to a PRACH format obtained through discovery signal reception, and transmit the random access preamble on a PRACH resource. The PRACH format or PRACH resource configuration information is system information, and may be transmitted through a PBCH rather than a synchronization signal or BRS. For example, the base station may transmit at least one of a plurality of PRACH formats to the terminal through the PBCH included in the discovery signal block.

The above-described discovery signal, PRACH resource configuration method, and initial access procedure may always be applied to any neurology. In the case of a carrier composed of a plurality of neurons, as in the case of the above-described synchronization signal, the plurality of neurons may share a common discovery signal and PRACH. At this time, with respect to the numerology of the discovery signal, method M221 or method M222 may be applied.

Alternatively, the discovery signal and the PRACH in one carrier may be defined for each neurology. At this time, with respect to the numerology of the discovery signal, method M231, method M232, or method M233 may be applied. The pneumatology of the PRACH may be the same as that of the discovery signal, or a separate pneumatology may be used for the PRACH.

19 is a diagram illustrating a computing device according to an embodiment of the present invention. The computing device TN100 of FIG. 19 may be a base station or a terminal described herein. Alternatively, the computing device TN100 of FIG. 19 may be a wireless device, a communication node, a transmitter, or a receiver.

In the embodiment of FIG. 19 , the computing device TN100 may include at least one processor TN110 , a transmission/reception device TN120 connected to a network to perform communication, and a memory TN130 . In addition, the computing device TN100 may further include a storage device TN140 , an input interface device TN150 , an output interface device TN160 , and the like. Components included in the computing device TN100 may be connected by a bus TN170 to communicate with each other.

The processor TN110 may execute a program command stored in at least one of the memory TN130 and the storage device TN140. The processor TN110 may mean a central processing unit (CPU), a graphics processing unit (GPU), or a dedicated processor on which methods according to an embodiment of the present invention are performed. The processor TN110 may be configured to implement procedures, functions, and methods described in connection with an embodiment of the present invention. The processor TN110 may control each component of the computing device TN100 .

Each of the memory TN130 and the storage device TN140 may store various information related to the operation of the processor TN110. Each of the memory TN130 and the storage device TN140 may be configured as at least one of a volatile storage medium and a nonvolatile storage medium. For example, the memory TN130 may include at least one of a read only memory (ROM) and a random access memory (RAM).

The transceiver TN120 may transmit or receive a wired signal or a wireless signal. In addition, the computing device TN100 may have a single antenna or multiple antennas.

On the other hand, the embodiment of the present invention is not implemented only through the apparatus and/or method described so far, and a program for realizing a function corresponding to the configuration of the embodiment of the present invention or a recording medium in which the program is recorded may be implemented. And, such an implementation can be easily implemented by those skilled in the art to which the present invention belongs from the description of the above-described embodiments.

Although the embodiments of the present invention have been described in detail above, the scope of the present invention is not limited thereto, and various modifications and improvements by those skilled in the art using the basic concept of the present invention as defined in the following claims are also provided. is within the scope of the right.

Claims (24)

A method of transmitting a discovery signal performed in a base station, comprising:
determining M discovery signal resources for a carrier (where M is a natural number greater than or equal to 1) from a discovery signal resource pool based on a first subcarrier interval;
M each including a first synchronization signal (PSS), a second synchronization signal (SSS), a physical broadcast channel (PBCH), and a reference signal for demodulating the PBCH generating discovery signal blocks; and
Transmitting an m-th discovery signal block through an m-th discovery signal resource among M discovery signal resources based on the first subcarrier interval, wherein m is a natural number within 1 to M.
Each of the M discovery signal resources consists of the same number of symbol(s) and the same number of subcarrier(s) irrespective of m and the first subcarrier interval, and within each of the M discovery signal resources, the PSS , the locations of the resources to which the SSS, the PBCH and the reference signal are mapped are the same across the M discovery signal resource blocks regardless of m and the first subcarrier interval,
The first subcarrier interval is predetermined according to a frequency band in which the M discovery signal blocks are transmitted, and the second subcarrier interval of the carrier is indicated through the PBCH of each of the M discovery signal blocks, characterized in that ,
How to transmit a discovery signal. The method according to claim 1,
Each of the M discovery signal resources is characterized in that it has the same frequency resource region as the frequency resource region of the discovery signal resource pool,
A method for transmitting a discovery signal. delete The method according to claim 1,
Each of the M discovery signal blocks comprises at least one guard subcarrier at the edges of the bandwidth of the PSS in symbol(s) to which the PSS is mapped,
How to transmit a discovery signal. The method according to claim 1,
In each of the M discovery signal blocks, the symbol(s) to which the PSS is mapped precedes the symbol(s) to which the SSS is mapped,
How to transmit a discovery signal. The method according to claim 1,
The M discovery signal blocks are characterized in that periodically transmitted through the M discovery signal resources,
How to transmit a discovery signal. The method according to claim 1,
Antenna port(s) for the PSS, SSS, PBCH and reference signal constituting the m-th discovery signal block are the same,
How to transmit a discovery signal. The method according to claim 1,
A time distance between two discovery signal blocks among the M discovery signal blocks in the discovery signal resource pool corresponds to a positive integer number of symbol(s),
How to transmit a discovery signal. The method according to claim 1,
Providing, to the terminal, measurement configuration information including a time duration and a periodicity of a measurement window in which the terminal performs a measurement based on at least a part of the M discovery signal blocks Characterized in that it further comprises,
How to transmit a discovery signal. 10. The method of claim 9,
The measurement performed in the measurement window by the terminal is characterized in that for radio resource management or beam acquisition,
How to transmit a discovery signal. A discovery signal reception method performed in a terminal, comprising:
It belongs to the discovery signal resource pool based on the first subcarrier interval and is one of M discovery signal blocks through one discovery signal resource among M (where M is a natural number greater than or equal to 1) discovery signal resources for a carrier. Receiving a first synchronization signal (PSS) and a second synchronization signal (secondary synchronization signal; SSS) belonging to the discovery signal block; and
Receiving, by the terminal, a physical broadcast channel (PBCH) and a reference signal for demodulating the PBCH from the discovery signal block through the discovery signal resource from which the PSS and the SSS have been received,
An m-th discovery signal block is transmitted through an m-th discovery signal resource among the M discovery signal resources based on the first subcarrier interval, where m is a natural number from 1 to M, and each of the M discovery signal resources is Consists of the same number of symbol(s) and the same number of subcarrier(s) regardless of m, and within each of the M discovery signal resources, the PSS, the SSS, the PBCH, and the resources to which the reference signal is mapped. locations are the same across the M discovery signal resource blocks regardless of m,
The first subcarrier interval is predetermined according to a frequency band in which the M discovery signal blocks are transmitted, and the second subcarrier interval of the carrier is indicated through the PBCH of each of the M discovery signal blocks, characterized in that ,
How to receive a discovery signal. 12. The method of claim 11,
Each of the M discovery signal resources is characterized in that it has the same frequency resource region as the frequency resource region of the discovery signal resource pool,
How to receive a discovery signal. delete 12. The method of claim 11,
The terminal is characterized in that it receives the PSS, the SSS, the PBCH and the reference signal without information on the M,
How to receive a discovery signal. 12. The method of claim 11,
Each of the M discovery signal blocks comprises at least one guard subcarrier at the edges of the bandwidth of the PSS in symbol(s) to which the PSS is mapped,
How to receive a discovery signal. 12. The method of claim 11,
In each of the M discovery signal blocks, the symbol(s) to which the PSS is mapped precedes the symbol(s) to which the SSS is mapped,
How to receive a discovery signal. 12. The method of claim 11,
The terminal is characterized in that it is assumed that the M discovery signal blocks are periodically transmitted through the M discovery signal resources,
How to receive a discovery signal. 12. The method of claim 11,
Antenna port(s) for the PSS, SSS, PBCH and reference signals constituting the m-th discovery signal block are the same
How to receive a discovery signal. 12. The method of claim 11,
Receiving, from the base station, measurement configuration information including a time duration and periodicity of a measurement window in which the terminal performs a measurement based on at least a part of the M discovery signal blocks, from the base station characterized in that it further comprises,
How to receive a discovery signal. 20. The method of claim 19,
The terminal is characterized in that it performs a measurement for radio resource management (radio resource management) or beam acquisition (beam acquisition) in the measurement window,
How to receive a discovery signal. The method according to claim 1,
The PSS and the resource element mapping for the SSS is characterized in that the same regardless of the first subcarrier interval,
How to transmit a discovery signal. The method according to claim 1,
The discovery signal resource pool includes L (L is a natural number greater than or equal to M) discovery signal resources, and the M discovery signal resources are determined from among the L discovery signal resources,
How to transmit a discovery signal. 12. The method of claim 11,
The PSS and the resource element mapping for the SSS is characterized in that the same regardless of the first subcarrier interval,
How to receive a discovery signal. 12. The method of claim 11,
The discovery signal resource pool includes L (L is a natural number greater than or equal to M) discovery signal resources, and the M discovery signal resources are determined from among the L discovery signal resources,
How to receive a discovery signal.

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