KR101704688B1 - Millimeter wavelength range wireless transceiver - Google Patents

Abstract

The present invention relates to a millimeter-wave low-power transceiver structure for high-speed data communication, the millimeter-wave band wireless transceiver including a first local oscillator for generating a local oscillation signal having a second frequency lower than a transmission frequency, And a plurality of transmitting mixers for receiving digital I data and Q data on a carrier by a first local oscillator, wherein the transmitting mixers are arranged in a first Sequentially upconverts the digital transmission data through a carrier of a pair of third frequencies that are in phase and quadrature with the first frequency, the second frequency, and the second frequency to generate a transmission signal of a millimeter wave band.

Description

[0001] MILLIMETER WAVELENGTH RANGE WIRELESS TRANSCEIVER [0002]

Embodiments of the present invention relate to a millimeter wave band wireless transceiver, and more particularly to a millimeter wave low power transceiver structure for high speed data communication.

Currently, mobile communication is being developed to handle a wide range of multimedia services such as video and data. For this purpose, high-speed wireless communication is required, and millimeter-wave and terahertz-band communication systems are being studied to meet the demand for high-speed wireless communication.

1 shows a structure of a conventional direct conversion type transmitter and a receiver. 1, Tx denotes a transmission signal transmitted through an antenna, PA denotes a power amplifier, PLL denotes a phase locked loop, DAC denotes a digital analog converter, Rx denotes a reception signal received through an antenna, LNA denotes a low noise amplifier, AGC denotes an automatic gain controller And the ADC represents an analog digital converter, respectively.

1 (a) and 1 (b), the transmitter structure 2 and the receiver structure 4 directly generate I and Q, which are orthogonal signals, so that the conventional structure of an industrial, scientific and medical (ISM) ) Is used as a transceiver structure for low power in a conventional communication system using a frequency lower than the millimeter wave band.

The 802.11ad high-speed WiFi, which was recently established as a standard, is a communication system using a 60 GHz carrier. The strength of the communication system using this method is that high-speed data communication at Gbps is possible. However, the millimeter-wave transceiver structure for high-speed communication of FIG. 1 has the following disadvantages.

First, power consumption is very large. That is, it must generate a Direct I / Q signal from a digital analog converter (DAC) at 60 GHz frequency. In other words, the power consumption of a phase-locked loop (PLL) for a transceiver and a local oscillator (e.g., a voltage-controlled oscillator, VCO) that delivers a signal to the mixer is significant Power consumption is a problem on the local frequency generation side for overall system configuration.

Second, a high-speed analog digital converter (ADC) suitable for the frequency of the millimeter wave band is required, thereby causing significant power consumption in the baseband signal processing device (e.g., Digital Signal Processor, DSP). In other words, for high-speed data communication, a high-speed ADC whose sampling rate of the ADC operates at twice the data rate is required. In general, when the speed of the ADC is increased more than twice, Or more. Thus, there is a problem that the power consumption of the ADC increases considerably as the data rate increases. In addition, the power consumption of the DSP for processing the ADC signal is also considerable, so that the minimum power consumption reported in the 802.11ac standard system when developed with the existing structure of FIG. 1 is almost 1W.

Figure 2 shows a conventional millimeter wave band wireless transceiver structure. As shown in Figures 2 (a) and 2 (b), a conventional millimeter waveband radio transceiver, including a transmitter structure 6 and a receiver structure 8, typically has a phase locked A loop (PLL) creates 2/3 times the frequency of X and divides it by 2 to create a 1 / 3X frequency to form the entire transceiver system. This configuration can reduce the operating frequency of the phase locked loop and the power of the local oscillator driving the mixer. However, the conventional millimeter-wave band wireless transceiver shown in FIG. 2 uses an analog-to-digital converter and is still not suitable as a low-power structure.

In order to solve the above technical problem, an embodiment of the present invention is to provide a millimeter wave band wireless transceiver capable of optimizing power consumption required to generate a carrier wave by having an operating frequency of a lower phase locked loop.

Another embodiment of the present invention provides a millimeter wave band wireless transceiver capable of omitting ADC power consumption and reducing power consumption of a digital signal processor (DSP) by not using an analog digital converter (ADC).

According to an aspect of the present invention, there is provided a millimeter wave band wireless transceiver including a first local oscillator for generating a local oscillation signal having a second frequency lower than a transmission frequency; A reference frequency signal generator for transmitting a reference signal to the local oscillator; And a plurality of transmit mixers for receiving digital I data and Q data on a carrier by a first local oscillator, wherein the transmit mixers are configured to receive a carrier of a first frequency, a carrier of a second frequency, And upconverts the digital transmission data sequentially through a pair of carriers that are in phase and quadrature with the carrier of the second frequency to generate a transmission signal of the millimeter wave band.

In one embodiment, the transmitting mixers include two first-stage mixers for up-converting I data and Q data to a carrier of a first frequency lower than the second frequency, respectively; A two-stage mixer for mixing up the outputs of two one-stage mixers to a carrier of a second frequency and up-converting the outputs; A local oscillation I-signal having a frequency that is equal to the oscillation frequency and a local oscillation Q-signal having a frequency that is quadrature with the oscillation frequency may be mixed with the output of the two-stage mixer to up-convert the three-stage mixer.

In one embodiment, the millimeter waveband wireless transceiver includes: a frequency divider receiving a local oscillation signal from a first local oscillator and dividing the local oscillation signal of a second frequency by three and delivering the local oscillation signal to two first stage mixers, respectively; And a polyphase (PP) filter for receiving a local oscillation signal from the first local oscillator and converting the local oscillation signal to a local oscillation I-signal on the same phase and a local oscillation Q-signal on a quadrature phase and delivering the local oscillation signal to a three- .

In one embodiment, the millimeter waveband wireless transceiver may further comprise a receiver for demodulating the received signal received from the antenna using a local oscillation I-signal and a local oscillation Q-signal of the same frequency as the first PP filter have.

In one embodiment, the receiver comprises: a first down-mixer receiving the received signal received at the antenna; A second local oscillator that receives a reference signal from the reference frequency signal generator and generates a local oscillation signal having a second frequency lower than a reception frequency of the reception signal; A second PP (Polyphase) which receives the local oscillation signal of the second frequency from the second local oscillator and converts the local oscillation signal to a local oscillation I-signal of the same phase and a local oscillation Q- ) filter; A second down-mixer for down-converting the output of the first down-mixer and the local oscillation signal to output a received signal of the first frequency; And an analog signal processing unit for analog-processing the reception signal of the first frequency outputted from the second down-mixer to demodulate the I data and the Q data.

In one embodiment, the analog signal processing unit comprises: a first loop mixer receiving a received signal at a first frequency and receiving an I-signal at a first frequency from a voltage regulator; A first low pass filter for filtering the output of the first loop mixer; A first limiter for limiting the output of the first low-pass filter to a predetermined level and outputting I data; A second loop mixer receiving a received signal of the first frequency and receiving a Q-signal of the first frequency from the voltage regulator; A second low pass filter for filtering the output of the second loop mixer; A second limiter for limiting the output of the second low-pass filter to a predetermined level to output Q data; A third loop mixer for mixing the output of the first limiter and the output of the second low pass filter; A fourth loop mixer for mixing the output of the second limiter and the output of the first low pass filter; An error detector for comparing the output of the third loop mixer with the output of the fourth loop mixer; And a loop filter for adjusting an input voltage of the voltage regulator according to an error signal output from the error detector.

According to another aspect of the present invention, there is provided a millimeter wave band wireless transceiver including: a transmitter for transmitting a transmission signal modulated with digital I data and Q data at a transmission frequency of a millimeter wave band to an antenna; A receiver for demodulating a reception signal of a reception frequency of a millimeter wave band received from the antenna and outputting digital I data and Q data; And a reference frequency signal generator for transmitting a reference signal to a first local oscillator of the transmitter and a second local oscillator of the receiver, wherein the transmitter, receiver, An oscillation signal can be used.

In one embodiment, the mixers of the transmitter include two first-stage mixers for first up-converting the carrier of the frequency 0.1 times the transmit frequency and the digital I data and the Q-data as a first frequency lower than the second frequency; A two-stage mixer for up-converting the outputs of the two first-stage mixers and the carrier of the second frequency; And a three-stage mixer for up-converting the local oscillation I-signal that is in phase with the carrier of the second frequency and the local oscillation Q-signal that is orthogonal to the carrier of the second frequency to the output of the two-stage mixer.

In one embodiment, the millimeter waveband wireless transceiver includes at least one local oscillator for generating a local oscillation signal; A reference frequency signal generator for transmitting a reference signal to at least one local oscillator; And an analog-to-digital converter connected to the receiver.

According to the present invention, in the millimeter wave band wireless transceiver, the power consumption required to generate the carrier wave can be optimized by having the operating frequency of the lower phase locked loop.

In addition, according to the present invention, since the analog-to-digital converter (ADC) is not used in the millimeter wave band wireless transceiver, the power consumption of the ADC can be reduced and the power consumption of the digital signal processor (DSP) can be reduced.

Further, according to the present invention, extremely low-power millimeter wave communication becomes possible, which can contribute to formation of a new product group in the proximity high-speed communication market.

1 is a block diagram of a radio transceiver structure of a conventional direct conversion structure
Figure 2 is a block diagram of a conventional millimeter wave band wireless transceiver architecture.
3 is a block diagram of a millimeter wave band wireless transceiver according to an embodiment of the present invention.
4 is a block diagram of an analog signal processing unit usable in the millimeter wave band wireless transceiver of FIG.
Figure 5 is a block diagram of an analog to digital converter capable of being coupled to the millimeter waveband wireless transceiver of Figure 3;

Hereinafter, preferred embodiments will be described in detail with reference to the accompanying drawings. In the following description, well-known functions or constructions are not described in detail to avoid unnecessarily obscuring the subject matter of the present invention. In addition, the size of the constituent elements in the drawings may be exaggerated for explanatory purposes and does not mean a size actually applied. In the following description, like parts are denoted by similar reference numerals throughout the specification.

3 is a block diagram of a millimeter wave band wireless transceiver according to an embodiment of the present invention.

Referring to FIG. 3, a millimeter wave band wireless transmitting / receiving device (hereinafter simply referred to as a wireless transceiver) 10 according to the present embodiment includes a transmitting unit 11, a receiving unit 12, and a reference frequency signal generating unit 13 . The reference frequency signal generating unit 13 may be a separate component from the transmitting unit 11 and the receiving unit 12 but is not limited thereto and may be included in the transmitting unit 11 or included in the receiving unit 12 Or may be included in the transmitting unit 11 and the receiving unit 12, respectively.

The transmitter 11 includes two first stage mixers 111 and 112, a second stage mixer 113 and a third stage mixer 114, . The transmission unit 111 includes a local oscillator (LO) 115, a frequency divider 116, and a polyphase filter 117. The transmission unit 111 includes a power amplifier (PA) 118. The transmitter 11 transmits the digital I data I data and the Q data Q data to a carrier wave generated using a relatively low frequency and radiates the digital I data I data and Q data Q outside through the antenna 119.

In the transmitter 11, the first mixer 111 of the two first-stage mixers receives I data (I Data) to be transmitted to the outside in a predetermined carrier wave of a millimeter wave band. The preset carrier wave corresponds to a transmission signal having a transmission frequency (hereinafter referred to as X). The baseband I data can be amplified through a predetermined amplifier and input to the first mixer 111. [

The first mixer 111 receives an I signal having a frequency obtained by dividing the predetermined oscillation frequency of the local oscillator 115 by three (hereinafter, referred to as a frequency dividing frequency) from the frequency divider 116. Here, the oscillation frequency is set to 0.3 times the transmission frequency (X), so that the divided frequency (Divided Frequency) is 0.1 times the transmission frequency (X). In this embodiment, the first mixer 111 outputs an I-transmission signal having a frequency of 0.1 times the transmission frequency X by placing I data on a carrier wave having a frequency dividing frequency that is 0.1 times the transmission frequency X.

The second mixer 112 of the two first-stage mixers may be substantially the same as the first mixer 111 except that the Q data Q data is input. That is, the second mixer 112 outputs the Q-transmission signal having the frequency of 0.1 times the transmission frequency X by loading the Q-data to the carrier having the frequency of division which is 0.1 times the transmission frequency X. Here, the dividing frequency of the Q-transmission signal has a value obtained by dividing the oscillation frequency, which is 0.3 times the transmission frequency X, by three, so that the Q-transmission signal has a frequency of 0.1 times the transmission frequency X.

The two-stage mixer 113 receives the I-transmission signal from the first mixer 111 and the Q-transmission signal from the second mixer 112. The two-stage mixer 113 also receives a local oscillation signal having a frequency 0.3 times the transmission frequency X from the local oscillator 115. In this embodiment, the two-stage mixer 113 up-converts the I-transmission signal and the Q-transmission signal and the local oscillation signal to output a second stage transmission signal. The frequency of the second-stage transmission signal is the sum of the I-transmission signal and the Q-transmission signal at a frequency that is 0.1 times the transmission frequency (X) and the local oscillation signal at a frequency 0.3 times the transmission frequency (X) It doubles.

The three-stage mixer 114 receives the two-stage transmission signal from the two-stage mixer 113. The three-stage mixer 114 may also be referred to as a harmonic mixer and receives two local oscillator I-signals (LOI) and a local oscillation Q-signal (LOQ) that are independent of the PP filter 117. The local oscillation I-signal LOI is set to an in-phase signal of the same frequency as the local oscillation signal having a frequency 0.3 times the transmission frequency X and the local oscillation Q-signal LOQ is set to an in- Is set to a quadrature signal having the same frequency as that of the local oscillation signal having a frequency of 0.3 times the frequency (X).

In this embodiment, the three-stage mixer 114 up-converts a pair of local oscillation I-signal LOI and local oscillation Q-signal LOQ and a two-stage transmission signal to output a three-stage transmission signal. The third-stage transmission signal is the final transmission signal of the mixer block which is transmitted to the power amplifier 118. The frequency of the third-stage transmission signal is a frequency of a two-stage transmission signal having a frequency of 0.4 times the transmission frequency X, (LOI) and the local oscillation Q-signal (LOQ), each having a frequency of 0.3 times the frequency of the local oscillation I-signal (LOI), respectively.

The local oscillator 115 refers to a means for generating and outputting a local oscillation signal or a component performing a function corresponding to this means. The local oscillation signal may be a sine waveform signal having a frequency 0.3 times the frequency (transmission frequency, X) of a transmission signal to be transmitted through a predetermined frequency, for example, the antenna 19. The local oscillator 115 is installed in the transmitter 11 and may be referred to as a first local oscillator.

The local oscillator 115 may be implemented by a transistor oscillator using a transistor (Tr), a diode oscillator using a diode, or the like, but is not limited thereto. For example, the local oscillator 115 generates a local oscillation signal having a frequency 0.3 times the transmission frequency X in accordance with the variable transmission frequency X when the transmission / reception device 10 uses a plurality of transmission frequencies And a voltage controlled oscillator (VCO) for outputting the output voltage.

The local oscillator 115 may be connected to the reference frequency signal generator 13 to receive the reference signal and to correct or stabilize the local oscillation signal using the reference signal. Depending on the implementation, the local oscillator 115 may be operated or implemented to vary the frequency of the local oscillation signal to a desired frequency in accordance with the variation of a specific part of the reference frequency signal generator 13. [

The frequency divider 116 refers to a frequency divider or a frequency divider and receives a local oscillation signal from the local oscillator 115 and outputs the frequency of the local oscillation signal (input frequency) Output frequency). The divider 116 may be implemented using a digital counter circuit. Also, the frequency divider 116 may be implemented with a fixed divider or a variable frequency divider.

The PP filter 117 refers to a filter capable of performing time-shift in a time domain and reversible conversion of a phase-shift in a frequency domain in digital signal processing. In this embodiment, the PP filter 117 receives the local oscillation signal from the local oscillator 115 and converts the local oscillation signal to a local oscillation I-signal LOI on the same phase and a quasi-local oscillation Q-signal LOQ do. That is, the three-stage mixer 114 mixes the local oscillation (LO) signal at a frequency 0.3 times the transmission frequency by the PP filter 117 with the local oscillation I-signal (LOI) with the 90 degree phase difference and the local oscillation Q- (LOQ) as an input, and mixes the frequency of the input signal with twice the frequency of the local oscillator 115. In this embodiment, the PP filter 117 may be referred to as a first PP filter.

The power amplifier 118 amplifies an output current or a voltage in proportion to an input current or a voltage. The power amplifier 118 may be implemented using a bipolar junction transistor (BJT), a field effect transistor (FET), or the like. In the present embodiment, the power amplifier 118 receives the three-stage transmission signal of the three-stage mixer 114, amplifies the three-stage transmission signal, and outputs the amplified signal to the antenna 119.

As described above, the transmitting unit 11 is a digital I / P converter that does not use a digital-to-analog converter (DAC), a digital I-path, a Q-path and an I / Q modulation And a plurality of mixers to be performed. When the final transmission frequency is X, the initial input to the plurality of mixers is 0.1 times the frequency of the transmission frequency (X). More sophisticated I / Q data can be generated by generating I / Q data at such a low frequency. That is, a signal having a frequency 0.1 times higher than the transmission frequency up-converted in the 1-stage mixer will again meet the up-mixer (2-stage mixer). At this time, the two-stage mixer receives a local oscillation (LO) signal at a frequency 0.3 times the transmission frequency. Therefore, in the two-stage mixer, an output of 0.4 times frequency is generated, and the output of the generated frequency of 0.4 times again meets the up-mixer (three-stage mixer or harmonic mixer). At this time, a harmonic mixer receives a pair of local oscillation I-signals and local oscillation Q-signals each having a frequency 0.3 times the transmission frequency. Therefore, the frequency of the carrier output from the harmonic mixer becomes the same frequency as the transmission frequency X.

According to the structure of the transmitter described above, the DAC can be eliminated by using direct modulation, and it is possible to generate sophisticated I / Q data using a frequency of 0.1 times of the transmission frequency (X) The frequency of a PLL (Phase Locked Loop) used in the PLL is only 0.3 times the operating frequency or the transmission frequency of the transmitter, so that the transmitter and the transmitter / receiver can be designed with extremely small power. In addition, since the operating frequency is low, the phase noise of the phase locked loop is also more advantageous than generating the same frequency as the transmitting frequency.

3, the receiver 12 includes a low noise amplifier 121, a first down mixer 122, a second down mixer 123, an analog signal processor (ASP) 124, a local oscillator 125 and a PP filter 126. The reception unit 12 receives the reception signal of a specific frequency (for example, X GHz) in the millimeter wave band through the antenna 120 and processes the reception signal to generate digital I data I data and Q data Q data .

In the receiving section 12, the low noise amplifier 121 amplifies a weak signal caught by the antenna 120. The low noise amplifier 121 may be installed near the antenna to reduce the attenuation in the transmission line. The low noise amplifier 121 may be implemented by a parametric amplifier, a field effect transistor (FET) amplifier, a tunnel diode amplifier, a low noise traveling wave tube amplifier (TWTA), or the like. In this embodiment, the received signal amplified by the low-noise amplifier 121 and having a specific reception frequency X in the millimeter waveband is transmitted to the first down-mixer 122.

The first down-mixer 122 is a harmonic mixer that receives a local oscillation (LO) signal at a frequency 0.3 times higher than the reception frequency X by a PP filter 126 as a local oscillation I- signal (LO) and a local oscillation Q-signal (LOQ), respectively. In this configuration, the local oscillator 125 receives a frequency (reception frequency, X) of a reception signal input through the antenna 120, Of the frequency (oscillation frequency). In the present embodiment, the first down-mixer 122 downconverts the first received signal having a frequency of 0.4 times the reception frequency X to the second down-mixer 123.

The second down-mixer 123 receives a first-stage reception signal having a frequency 0.4 times the reception frequency X from the first down-mixer 122 and receives a first-stage reception signal and a local oscillation signal of the local oscillator 125 And outputs a 2-stage reception signal having a frequency of 0.1 times the reception frequency X.

The analog signal processing section 124 is for effectively modulating I data and Q data contained in a received signal (second-stage received signal) having a frequency 0.1 times the reception frequency X with low power consumption. In this embodiment, the analog signal processing unit 124 uses a Costas Loop which is an analog BPSK (Binary Phase Shift Keying) demodulation circuit, but is not limited thereto. That is, the analog signal processing unit 124 of the present embodiment is configured to extract digital I data and Q data by installing a limiter in the existing Costas loop, but the present invention is not limited thereto. In other words, in the present embodiment, digital I data and Q data can be easily extracted by passing the demodulated signals ZI and ZQ obtained through a low pass filter (LPF) through a limiter, It is also possible to input demodulated signals to a separate analog digital converter to perform demodulation in various manners.

The local oscillator 125 may be substantially the same as the local oscillator 115 used in the transmitter 11 except that it is used in the receiver 12. [ The local oscillator 125 converts the local oscillation signal having a frequency 0.3 times the reception frequency X of the reception signal received by the antenna 120 or 119 of the transceiver 10 into a mixer group . The local oscillator 125 may be referred to as a second local oscillator.

The PP filter 126 may be substantially the same as the PP filter 126 used in the transmitter 11 except that it is used in the receiver 12. [ In this embodiment, the PP filter 126 converts the local oscillation signal of the local oscillator 125 into a local oscillation I-signal of the same phase and a local oscillation Q-signal of a quadrature phase to supply it to the first downward mixer 123 . PP filter 126 may be referred to as a second PP filter.

The phase locked loop PLL of the reference frequency signal generating unit 13 for supplying the reference frequency signal to the receiving unit 12 has the same frequency as the receiving frequency X, The power consumption can be minimized. In addition, since the I / Q data is demodulated by an analog method using a block called an analog signal processing unit (ASP), a digital signal processor (DSP) that processes the output signal of an analogue digital converter (ADC) The power consumption can be reduced.

Referring again to FIG. 3, the reference frequency signal generator 13 generates a reference signal having the same frequency as the frequency of the local oscillation signal generated by the local oscillators 115 and 125. The reference frequency signal generator 13 supplies a reference signal having a reference frequency to the local oscillators 115 and 125 so that the oscillation frequencies of the local oscillation signals change according to the ambient environment Lt; / RTI > Of course, the reference frequency signal generator 13 may be implemented to vary the frequency of the local oscillation signal to a desired frequency (oscillation frequency) according to the implementation.

In addition, the millimeter wave band wireless transceiver apparatus 10 according to the present embodiment may be configured to use multiple transmit antennas or multiple receive antennas using at least one switch 14 connecting between antennas during a transmit operation and a receive operation can do.

That is, in this embodiment, the antennas 119 and 120 may be provided independently of the transmitting unit 11 and the receiving unit 12, but the present invention is not limited thereto. The first and second antennas 119 and 119 are connected to connect the first antenna 119 on the transmitter 11 side to the receiver 12 side or to connect the second antenna 120 on the receiver 12 side to the transmitter 11 side. , And a switch (14) installed between the first and second switches (120, 120). In this case, a plurality of antennas may be connected and controlled according to the transmission mode and the reception mode, so that the transmission / reception device operates in a multi-input multiple-output (MIMO) manner.

4 is a block diagram of an analog signal processing unit employable in the millimeter wave band wireless transceiver of FIG.

4, the analog signal processing unit 124 according to the present embodiment includes a first loop mixer 1241, a second loop mixer 1242, a first low pass filter (LPF) 1243, 2 low pass filter 1244, a first limiter 1245, a second limiter 1246, a third loop mixer 1247, a fourth loop mixer 1248, an error detector 1249, a loop filter Filter 1250, and a voltage-controlled oscillator 1251.

The analog signal processor 124 includes a first loop mixer 1241, a first low pass filter 1243, a first limiter 1245, a third loop mixer 1247, an error detector 1249, a loop filter 1250 and the voltage-controlled oscillator 1251 extract the I data I data or the demodulated I signal ZI from the reception signal input to the analog signal processing unit 124 and having a frequency of 0.1 times the reception frequency X Thereby forming a first loop. Similarly, the second loop mixer 1242, the second low-pass filter 1244, the second limiter 1246, the fourth loop mixer 1248, the error detector 1249, the loop filter 1250, The oscillator 1251 is connected to the analog signal processing unit 124 and includes a second loop for extracting the Q data Q data or the demodulated Q signal ZQ from a reception signal having a frequency of 0.1 times the reception frequency X, .

The first limiter 1245 and the second limiter 1246 refer to a means for limiting the voltage of the input signal (alternating voltage) to a predetermined level or converting the sinusoidal wave into a square wave or a function performing a function corresponding to this means. In this embodiment, the first limiter 1245 operates to limit the signal modulated by the first low-pass filter 1243 to a preset level and output I data. Similarly, the second limiter 1246 operates to limit the modulated signal through the second low-pass filter 1244 to a predetermined level and output the Q data.

The third loop mixer 1247 receives the output signal of the first limiter 1245 and receives the output signal of the second low-pass filter 1244 and mixes the output signals. Similarly, the fourth loop mixer 1248 receives the output signal of the second limiter 1246 and receives the output signal of the first low-pass filter 1243 and mixes the output signals.

The error detector 1249 receives the output signal of the third loop mixer 1247 and the output signal of the fourth loop mixer 1248 and outputs the difference therebetween. The error detector 1249 may be referred to as a phase detector or a comparator. The error detector 1249 may be implemented as a means for receiving two frequency signal inputs to find out how much frequency or phase difference there is in the two signals or a component performing a function corresponding to this means.

The loop filter 1250 operates to raise or lower the output voltage of the voltage regulator 1251 at the subsequent stage by a predetermined voltage in accordance with an error Er input from the error detector 1249. The loop filter 1250 may have a LPF (Low Pass Filter) type structure including a capacitor connected in parallel on a line, a series circuit of a resistor and a capacitor connected in parallel on the line, or a combination thereof. In this case, the voltage across the capacitor is changed according to the amount of charge accumulated in the capacitor, so that the voltage at the input terminal of the voltage regulator can be varied proportionally. In accordance with the implementation of error detector 1249, loop filter 1250 may include a charge pump at the input to convert the pulse to a voltage.

The voltage regulator 1251 may be a voltage controlled oscillator that outputs a signal of a predetermined voltage, but is not limited thereto. In this embodiment, the voltage regulator 1251 outputs a voltage adjustment signal at a frequency 0.1 times the reception frequency X of the receiving unit 12. [ That is, the voltage regulator 1251 outputs a voltage adjustment signal of phase I, which is the same as the phase of the reception signal received by the receiver 11, to the first loop mixer 1241, To the second loop mixer 1242. The second loop mixer 1242 outputs the voltage adjustment signal to the second loop mixer 1242. [

The operation principle of the analog signal processing unit 124 of the present embodiment will be described using the following equation.

A signal (Vrf) input to a high frequency input (RF Input) is represented by the following Equation (1).

As shown in Equation (1), since the signal carrying the I data and the Q data is expressed by Equation (2), the demodulated signals (ZI and ZQ) can be expressed by Equation (3).

The output waveforms LI and LQ obtained by limiting the demodulated signals ZI and ZQ as shown in Equation (3) are I (t) and Q (t ). ≪ / RTI >

The signal er from the error detector 1249 in the analog signal processing unit 124 is expressed by Equation (5).

That is, as shown in Equation (5), the phase of the input signal (received signal) of 0.1 times frequency can be automatically adjusted by negative feedback so that the signal er in the error detector 1249 becomes zero have.

According to the present embodiment, data of I (t) and Q (t) contained in a reception signal of a millimeter wave band can be detected without using an analog-to-digital converter (ADC). Therefore, digital I / Q data can be extracted without using an ADC or a DSP, thus enabling high-speed data communication with considerably less power.

5 is a block diagram of an analog to digital converter that can be coupled to the millimeter waveband wireless transceiver of FIG.

Referring to FIG. 5, the millimeter wave band wireless transceiver according to the present embodiment may further include an analog-to-digital converter 15 connected to a receiver in addition to a transmitter, a receiver, and a reference frequency signal generator.

The analog digital converter 15 in the present embodiment is different from the analog digital converter 15 installed in the conventional millimeter wave band wireless transceiver in that the low pass filter of the analog signal processor 124 described above with reference to FIGS. 1243 and 1244, respectively.

That is, the analog-to-digital converter 15 receives the demodulated signals ZI and ZQ from the analog signal processing unit and demodulates the demodulated signals according to at least any one of the conventional demodulation schemes, Can be extracted. Various demodulation schemes include, but are not limited to, Quadrature Amplitude Modulation (QAM), Phase Shift Keying (PSK), Frequency Shift Keying (FSK), and the like.

According to this embodiment, in addition to extracting digital I data and Q data simply through the receiver of the millimeter wave band wireless transceiver, it is possible to demodulate the information data contained in the received signal in various existing demodulation schemes. Accordingly, the present invention can be easily applied to a transmitting / receiving apparatus using various modulation / demodulation schemes, thereby contributing greatly to high-speed data communication and low power consumption of a millimeter wave band wireless transmitting / receiving apparatus.

While the present invention has been particularly shown and described with reference to exemplary embodiments thereof, it is to be understood that the invention is not limited to the disclosed embodiments, but, on the contrary, It will be apparent to those skilled in the art that various combinations and modifications may be made without departing from the scope of the present invention. Therefore, it should be understood that the technical contents related to the modifications and applications that can be easily derived from the embodiments of the present invention are included in the present invention.

10: Millimeter wave band wireless transceiver
11: Transmitter
12: Receiver
13: Reference frequency signal generator
14: Switch
15: ADC (Analog Digital Converter)

Claims (10)

A first local oscillator for generating a local oscillation signal having a second frequency lower than the transmission frequency;
A reference frequency signal generator for transmitting a reference signal to the local oscillator; And
A plurality of transmission mixers for mixing digital I data and Q data with a carrier by the first local oscillator;
≪ / RTI >
The transmission mixers may comprise:
Two first-stage mixers for up-converting the I data and the Q data to a carrier having a first frequency lower than the second frequency, respectively;
A two-stage mixer for mixing up the outputs of the two one-stage mixers to a carrier of the second frequency and up-converting the mixed outputs; And
Stage mixer that mixes a local oscillation I-signal having a frequency equal to the second frequency and a local oscillation Q-signal having a frequency that is orthogonal to the second frequency with the output of the two-stage mixer and up-converts the output;
Gt; and / or < / RTI > the millimeter wave band wireless transceiver. delete The method according to claim 1,
A frequency divider for receiving the local oscillation signal from the first local oscillator and dividing the local oscillation signal of the second frequency by three and delivering a carrier of a first frequency lower than the second frequency to the two first stage mixers; And
A first polyphase (PP) circuit for receiving the local oscillation signal from the first local oscillator and converting the local oscillation signal to a local oscillation I-signal of the same phase and a local oscillation Q-signal of a quadrature phase to deliver the local oscillation signal to the three- filter;
Further comprising: an antenna for transmitting the radio frequency signal. The method of claim 3,
And a receiver for demodulating a received signal received from the antenna using a local oscillation I-signal and a local oscillation Q-signal having the same frequency as the first PP filter. The method of claim 4,
The receiver may further comprise:
A first down-mixer receiving a received signal received at the antenna;
A second local oscillator that receives the reference signal from the reference frequency signal generator and generates a local oscillation signal having a second frequency lower than a reception frequency of the reception signal;
A second local oscillator for receiving the local oscillation signal of the second frequency and converting the local oscillation signal into a local oscillation I-signal of the same phase and a local oscillation Q-signal of a quadrature phase and delivering the local oscillation signal to the first down- A poly phase (PP) filter;
A second down-mixer for down-converting the output of the first down-mixer and the local oscillation signal to output a received signal of the first frequency; And
An analog signal processing unit for analog-processing the reception signal of the first frequency outputted from the second down mixer to demodulate I data and Q data;
Gt; and / or < / RTI > the millimeter wave band wireless transceiver. The method of claim 5,
Wherein the analog signal processor comprises:
A first loop mixer receiving a received signal of the first frequency and receiving an I- signal of a first frequency from a voltage regulator;
A first low pass filter for filtering the output of the first loop mixer;
A first limiter for limiting the output of the first low-pass filter to a predetermined level and outputting I data;
A second loop mixer receiving the received signal of the first frequency and receiving the Q-signal of the first frequency from the voltage regulator;
A second low pass filter for filtering the output of the second loop mixer;
A second limiter for limiting the output of the second low-pass filter to a predetermined level and outputting Q data;
A third loop mixer for mixing the output of the first limiter and the output of the second low pass filter;
A fourth loop mixer for mixing the output of the second limiter and the output of the first low pass filter;
An error detector for comparing an output of the third loop mixer with an output of the fourth loop mixer; And
A loop filter for adjusting an input voltage of the voltage regulator according to an error signal output from the error detector;
Gt; and / or < / RTI > the millimeter wave band wireless transceiver. The method of claim 3,
And the second frequency is 0.3 times the transmission frequency. The method of claim 7,
Wherein the carrier of the first frequency lower than the second frequency has a frequency of 0.1 times the transmission frequency by dividing the frequency of the local oscillation signal of the second frequency by the frequency divider.
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