JPS6139774B2 - - Google Patents
Info
- Publication number
- JPS6139774B2 JPS6139774B2 JP10347880A JP10347880A JPS6139774B2 JP S6139774 B2 JPS6139774 B2 JP S6139774B2 JP 10347880 A JP10347880 A JP 10347880A JP 10347880 A JP10347880 A JP 10347880A JP S6139774 B2 JPS6139774 B2 JP S6139774B2
- Authority
- JP
- Japan
- Prior art keywords
- winding
- line
- transmission
- impedance
- transformer
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired
Links
- 230000005540 biological transmission Effects 0.000 claims description 39
- 238000004804 winding Methods 0.000 claims description 19
- 238000010586 diagram Methods 0.000 description 4
- 230000001012 protector Effects 0.000 description 4
- 230000000903 blocking effect Effects 0.000 description 3
- 238000000926 separation method Methods 0.000 description 2
- 230000000694 effects Effects 0.000 description 1
- 239000003381 stabilizer Substances 0.000 description 1
Classifications
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B3/00—Line transmission systems
- H04B3/54—Systems for transmission via power distribution lines
- H04B3/56—Circuits for coupling, blocking, or by-passing of signals
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B2203/00—Indexing scheme relating to line transmission systems
- H04B2203/54—Aspects of powerline communications not already covered by H04B3/54 and its subgroups
- H04B2203/5404—Methods of transmitting or receiving signals via power distribution lines
- H04B2203/5425—Methods of transmitting or receiving signals via power distribution lines improving S/N by matching impedance, noise reduction, gain control
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B2203/00—Indexing scheme relating to line transmission systems
- H04B2203/54—Aspects of powerline communications not already covered by H04B3/54 and its subgroups
- H04B2203/5462—Systems for power line communications
- H04B2203/5483—Systems for power line communications using coupling circuits
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B2203/00—Indexing scheme relating to line transmission systems
- H04B2203/54—Aspects of powerline communications not already covered by H04B3/54 and its subgroups
- H04B2203/5462—Systems for power line communications
- H04B2203/5491—Systems for power line communications using filtering and bypassing
Description
【発明の詳細な説明】
本発明は電力線を伝送路として利用する搬送通
信装置の線路結合器に関する。DETAILED DESCRIPTION OF THE INVENTION The present invention relates to a line coupler for a carrier communication device that uses a power line as a transmission path.
第１図は従来の線路結合器の一列を示す図であ
る。図において参照数字１は入力端子、同数字２
は送信帯域フイルタ、同数字３は保安器、同数字
４は線路入出力端子、同数字５は受信帯域フイル
タおよび同数字６は出力端子である。 FIG. 1 is a diagram showing a row of conventional line couplers. In the figure, reference number 1 is an input terminal, and reference number 2 is an input terminal.
3 is a transmitting band filter, 3 is a protector, 4 is a line input/output terminal, 5 is a receiving band filter, and 6 is an output terminal.
入力端子１から入力された高出力の送信信号は
送信帯域フイルタ２を介して波され、送信線路
周波数として、線路サージ電流から装置を保護す
るための保安器３を介して線路入出力端子４から
線路に送出する。 A high-output transmission signal inputted from an input terminal 1 is waved through a transmission band filter 2, and is output as a transmission line frequency from a line input/output terminal 4 via a protector 3 for protecting the device from line surge current. Send it out to the railroad tracks.
一方、線路から前記線路入出力端子４を介して
入力された受信線路周波数は前記保安器３を通過
したあと受信帯域フイルタ５で波された出力端
子６に出力される。このときのコロナ雑音および
線路開閉雑音等の線路雑音は大きく、このため、
送信信号レベルを出来るだけ大きくして伝送する
必要があり、送信帯域フイルタは通過損失を極力
小さくするように設計される。また、受信信号レ
ベルは送信信号レベルに較べ小さいため、入力端
子１からの入力端子が廻り込まないように受信帯
域フイルタ５は帝域外減衰量すなわち阻止減衰量
を大きくするように設計される。 On the other hand, the receiving line frequency inputted from the line via the line input/output terminal 4 passes through the protector 3 and then is outputted to the output terminal 6 where it is filtered by the receiving band filter 5. At this time, line noise such as corona noise and line switching noise is large, and therefore,
It is necessary to make the transmission signal level as high as possible for transmission, and the transmission band filter is designed to minimize the transmission loss. Furthermore, since the received signal level is smaller than the transmitted signal level, the receiving band filter 5 is designed to increase the amount of extra-band attenuation, that is, the amount of blocking attenuation, so that the input terminal from the input terminal 1 does not go around.
このため、高出力送信信号を通過または阻止す
るためのフイルタは大形でしかも高価なものとな
り、送信および受信帯域フイルタの２種類が必要
となる。さらに、フイルタは通過帯域および阻止
帝域を常に組にして設計しなければならず、１対
向（１組２台の端局装置）で考えると４種類の帯
域フイルタが必要となる。また、フイルタの特性
上、送信伝送帯域と受信伝送帝域間の間隔が適当
にとられた分離周波数間隔が必要となる。したが
つて、分離周波数間隔を取り除いて線路周波数の
有効利用を行なうことは困難である。また、線路
と装置との整合をとることはできず、不整合減衰
量の調整が不可能であるという欠点がある。 Therefore, filters for passing or blocking high-power transmission signals are large and expensive, and two types of filters, transmitting and receiving band filters, are required. Furthermore, a filter must always be designed with a pass band and a blocking band as a set, and four types of band filters are required when one pair is considered (two terminal devices in one set). Further, due to the characteristics of the filter, a separation frequency interval with an appropriate interval between the transmission transmission band and the reception transmission band is required. Therefore, it is difficult to remove the separation frequency interval and make effective use of the line frequency. Another disadvantage is that it is impossible to match the line and the device, and it is impossible to adjust the amount of mismatch attenuation.
本発明の目的は上述の穴点を除去した電力線搬
送通信装置の線路結合器を提供することにある。 An object of the present invention is to provide a line coupler for a power line carrier communication device that eliminates the above-mentioned holes.
本発明の結合器は送信伝送路とアース間に接続
され送信信号の中の送信線路周波数を通過させる
帝域通過フイルタと、前記送信線路に一端が接続
された第１の巻線とこの第１の巻線と電磁気的に
結合した第２の巻線とを有し、前記フイルタ出力
を第２の巻線に出力するとともに前記第２の巻線
に供給された受信信号を前記第１の巻線に出力す
る第１のトランスと、前記第１の巻線の他端とア
ース間に接続された第１のインピーダンスと、前
記送信線路に一端が接続された平衡結線網と、こ
の結線網の他端とアース間に接続された第２のイ
ンピーダンスと、前記平衡結線網および前記第２
のインピーダンスの接続点と前記第１の巻線およ
び前記第１のインピーダンスの接続点との間に第
１の巻線が接続され、一端が受信線路に接続され
他端がアースに接続された第２の巻線を有する第
２のトランスとから構成され、前記第２のトラン
スを介して前記受信信号を得ることを特徴として
いる。 The coupler of the present invention includes an impedance pass filter that is connected between a transmission transmission line and ground and passes the transmission line frequency in the transmission signal, a first winding whose one end is connected to the transmission line, and a first winding connected to the transmission line at one end. a second winding that is electromagnetically coupled to a winding of a first impedance connected between the other end of the first winding and ground; a balanced wiring network having one end connected to the transmission line; a second impedance connected between the other end and ground; the balanced wiring network and the second impedance;
A first winding is connected between the impedance connection point of the first winding and the first impedance connection point, and one end is connected to the receiving line and the other end is connected to ground. and a second transformer having two windings, and the received signal is obtained through the second transformer.
次に本発明について図面を参照して詳細に説明
する。 Next, the present invention will be explained in detail with reference to the drawings.
第２図は本発明の一実施例を示す図であり、第
１図と同一部分は同一参照数字で示されているの
でその説明は省略する。図において、送信帯域フ
イルタ２の出力端子は変成器Ｔ１の端子１０１お
よび平衡結線網７の一端に接続され、変成器Ｔ１
の端子１０２は変成器Ｔ２の端子１０６とインピ
ーダンス素子Z1の一端とに接続されている。変成
器Ｔ２の端子１０５は平衡結線網７の他端とイン
ピーダンス素子Z2の一端とに接続され、変成器Ｔ
２の端子１０８とインピーダンス素子Z1およびZ2
の他端とが接地されている。出力端子６は変成器
Ｔ２の端子１０７に接続され、変成器Ｔ１の端子
１０３および１０４は歩安器３に接続されてい
る。ここで、平衡結線網７と変成器Ｔ１およびＴ
２とインピーダンス素子Z1およびZ2とにより不平
衡形ハイブリツドを形成している。 FIG. 2 is a diagram showing an embodiment of the present invention, and the same parts as in FIG. 1 are designated by the same reference numerals, so the explanation thereof will be omitted. In the figure, the output terminal of the transmission band filter 2 is connected to the terminal 101 of the transformer T1 and one end of the balanced wiring network 7,
A terminal 102 of is connected to a terminal 106 of transformer T2 and one end of impedance element Z1 . The terminal 105 of the transformer T2 is connected to the other end of the balanced wiring network 7 and to one end of the impedance element Z2 ;
2 terminals 108 and impedance elements Z 1 and Z 2
The other end is grounded. Output terminal 6 is connected to terminal 107 of transformer T2, and terminals 103 and 104 of transformer T1 are connected to step stabilizer 3. Here, the balanced wiring network 7 and the transformers T1 and T
2 and impedance elements Z1 and Z2 form an unbalanced hybrid.
変成器Ｔ１の端子０１および１０２から線路側
を見たインピーダンスをＺL、平衡結線網のイン
ピーダンスをＺBおよび送信帯域フイルタの出力
端子より入力端子１側を見たインビーダンスをＺ
Fとする。本回路においては、ブリツジの構成条
件としてＺB＞√L×2＞Z1となるように各イン
プーダンスを決定する。また、ＺLとZ1との位置
を交換しても回路は成立し、Z1またはZ2を可変イ
ンピーダンス素子としてもよい。 Z L is the impedance seen from terminals 01 and 102 of transformer T1 on the line side, Z B is the impedance of the balanced wiring network, and Z is the impedance seen from the output terminal of the transmission band filter on the input terminal 1 side.
Let it be F. In this circuit, each impedance is determined so that Z B > √ L × 2 > Z 1 as a bridge configuration condition. Further, the circuit may be established even if the positions of Z L and Z 1 are exchanged, and Z 1 or Z 2 may be a variable impedance element.
ここで、例えば、Z1＝3.75（Ω），Z2＝75
（Ω），ＺL＝75（Ω），ＺF＝75（Ω）として説明
する。 Here, for example, Z 1 = 3.75 (Ω), Z 2 = 75
(Ω), Z L = 75 (Ω), and Z F = 75 (Ω).
最初に送信信号を考える。インピーダンスＺL
が75（Ω）であるから、平衡結線網７のインピー
ダンスＮBを1.5（ＫΩ）とすると、Z1，Z2，Ｚ
B，ＺLおよび変成器Ｔ２から成るブリツジは平衡
条件を満たし変成器Ｔ２の端子１０５および１０
６間に電流は流れないから、送信信号が出力端子
６に廻り込むことはない。 First, consider the transmitted signal. Impedance Z L
is 75 (Ω), so if the impedance N B of the balanced wiring network 7 is 1.5 (KΩ), then Z 1 , Z 2 , Z
The bridge consisting of B , Z L and transformer T2 satisfies the equilibrium condition and terminals 105 and 10 of transformer T2
Since no current flows between the terminals 6 and 6, the transmission signal does not go around to the output terminal 6.
しかも、送信帯域フイルタ２通過後の送信信号
は、損失が少なく、大部分が入出力端子４を介し
て線路に送出される。 Moreover, the transmission signal after passing through the transmission band filter 2 has little loss, and most of it is sent out to the line via the input/output terminal 4.
帯域フイルタ２および変成器Ｔ１の通過損をそ
れぞれαおよびβとし、送信時の不平衡形ハイブ
リツドの通過損を0.4（dB）とすると、入力端子
１に入力された送信信号がラインに送出されるま
でに受ける減衰量はα＋β＋0.4（dB）となる。 Assuming that the passing losses of the bandpass filter 2 and the transformer T1 are α and β, respectively, and that the passing loss of the unbalanced hybrid during transmission is 0.4 (dB), the transmitting signal input to the input terminal 1 is sent out to the line. The amount of attenuation received up to this point is α + β + 0.4 (dB).
一方、線路からの受信信号は変成器Ｔ２を介し
て出力端子６に与えられる。出力端子６の受信信
号レベルは非常に低いが線路雑音と受信信号レベ
ルとのSN比は変化がないから問題はない。 On the other hand, the received signal from the line is applied to the output terminal 6 via the transformer T2. Although the received signal level at the output terminal 6 is very low, there is no problem because the SN ratio between the line noise and the received signal level does not change.
変成器Ｔ２の通過損をγとし、受信時の不平衡
ハイブリツドの通過損を26.4（dB）とすると、
受信信号の受ける減衰量は26.4＋β＋γ（dB）
である。 If the passing loss of transformer T2 is γ, and the passing loss of the unbalanced hybrid during reception is 26.4 (dB),
The amount of attenuation received by the received signal is 26.4 + β + γ (dB)
It is.
なお、ここでハイブリツドの受信信号の通過損
が大きくなつているのは、前述したように、コロ
ナ雑音や線路雑音が大きいため、できるだけ大き
な送信出力を得るよう送信信号に対するハイブリ
ツドの損失を小さくするためである。このように
設定しても、受信信号から信号を十分取出せ、必
要に応じて増幅器を使用することも可能である。 Note that the reason why the transmission loss of the hybrid reception signal is large here is because, as mentioned above, the corona noise and line noise are large, so in order to obtain as large a transmission output as possible, the hybrid reception signal loss must be minimized. It is. Even with this setting, a sufficient signal can be extracted from the received signal, and an amplifier can be used if necessary.
また、線路変動により装置と線路とに不整合が
生じても平衡結線網を調整することにより簡単に
整合をとることができ、使用する帯域フイルタは
送信帯域フイルタのみであるため、従来の結合器
に較べてフイルタは1/2の個数で済み経済的であ
る。さらに、受信帯域フイルタの代わりにハイブ
リツド回路を用いることにより送信伝送帯域と受
信伝送帯域との間の分周波数間隔を取り除くこと
ができ線路舟波数の有効活用を計ることができ
る。 In addition, even if mismatching occurs between the equipment and the line due to line fluctuations, matching can be easily achieved by adjusting the balanced connection network, and since the only band filter used is the transmission band filter, conventional couplers It is economical as it only requires 1/2 the number of filters. Furthermore, by using a hybrid circuit in place of the reception band filter, it is possible to eliminate the frequency interval between the transmission transmission band and the reception transmission band, and to make effective use of the line wave number.
以上、本考案には、送信帯域域フイルタと不平
衡形ハイブリツドを用いて線路結合器を構成する
ことによりフイルタの使用個数の減少、線路周波
数の有効活用および装置と線路との整合調整の簡
単化が達成できるという効果がある。 As described above, the present invention uses a transmission bandpass filter and an unbalanced hybrid to configure a line coupler, thereby reducing the number of filters used, effectively utilizing the line frequency, and simplifying the matching adjustment between the device and the line. The effect is that it can be achieved.
第１図は従来の線路結合器のブロツク図および
第２図は本発明の一実施例を示すブロツク図であ
る。
図において、１……入力端子、２……送信帯域
フイルタ、３……保安器、４……線路入出力端
子、５……受信帯域フイルタ、６……出力端子、
７……平衡結線網、Z1，Z2……インピーダンス素
子、Ｔ１，Ｔ２……変成器、１０１〜１０８……
端子。
FIG. 1 is a block diagram of a conventional line coupler, and FIG. 2 is a block diagram showing an embodiment of the present invention. In the figure, 1...input terminal, 2...transmission band filter, 3...protector, 4...line input/output terminal, 5...reception band filter, 6...output terminal,
7...Balanced wiring network, Z1 , Z2 ...Impedance element, T1, T2...Transformer, 101-108...
terminal.
Claims (1)
の中の送信線路周波数を通過させる帯域通過フイ
ルタと、 前記送信線路に一端が接続された第１の巻線
と、この第１の巻線と電磁気的に結合した第２の
巻線とを有し、前記フイルタ出力を第１の巻線に
出力するとともに第２の巻線に供給された受信信
号を前記第１の巻線に出力する第１のトランス
と、 前記第１の巻線の他端とアース間に接続された
第１のインピーダンスと、 前記送信線路に一端が接続された平衡結線網
と、 この平衡結線網の他端とアース間に接続された
第２のインピーダンスと、 前記平衡結線網および前記第２のインピーダン
スの接続点と前記第１の巻線および前記第１のイ
ンビーダンスの接続点との間に第３の巻線が接続
され、一端が受信線路に接続され他端がアースに
接続された第４の巻線を有する第２のトランスと
から構成され、前記第２のトランスを介して前記
受信信号を得ることを特徴とする電力線搬送通信
装置の線路結合器。[Scope of Claims] 1. A bandpass filter connected between a transmission transmission line and ground and passing the transmission line frequency in the transmission signal; a first winding having one end connected to the transmission line; It has a second winding that is electromagnetically coupled to the first winding, and outputs the filter output to the first winding and transmits the received signal supplied to the second winding to the first winding. a first transformer outputting to a winding; a first impedance connected between the other end of the first winding and ground; a balanced wiring network having one end connected to the transmission line; and the balanced wiring. a second impedance connected between the other end of the network and the ground; and a connection point between the balanced wiring network and the second impedance and a connection point between the first winding and the first impedance. a second transformer having a third winding connected therebetween, and a fourth winding having one end connected to the reception line and the other end connected to ground, and through the second transformer. A line coupler for a power line carrier communication device, characterized in that the received signal is obtained.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP10347880A JPS5728436A (en) | 1980-07-28 | 1980-07-28 | Line coupler for power line carrier communication device |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP10347880A JPS5728436A (en) | 1980-07-28 | 1980-07-28 | Line coupler for power line carrier communication device |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JPS5728436A JPS5728436A (en) | 1982-02-16 |
| JPS6139774B2 true JPS6139774B2 (en) | 1986-09-05 |
Family
ID=14355112
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP10347880A Granted JPS5728436A (en) | 1980-07-28 | 1980-07-28 | Line coupler for power line carrier communication device |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JPS5728436A (en) |
Families Citing this family (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| GB8504683D0 (en) * | 1985-02-22 | 1985-03-27 | Exxon Chemical Patents Inc | Road marking compositions |
| EP0192439B1 (en) * | 1985-02-22 | 1991-11-21 | Exxon Chemical Patents Inc. | Road marking compositions |
| JP2003174387A (en) * | 2001-09-28 | 2003-06-20 | Sumitomo Electric Ind Ltd | Hybrid circuit and power-line carrying modem using the same |
-
1980
- 1980-07-28 JP JP10347880A patent/JPS5728436A/en active Granted
Also Published As
| Publication number | Publication date |
|---|---|
| JPS5728436A (en) | 1982-02-16 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| US3731234A (en) | Combined voice frequency transmission and dc signaling circuit | |
| JPS6345925A (en) | Method and apparatus for connecting transceiver for ac power supply line carrier system | |
| US3778563A (en) | Voice frequency repeater | |
| US4074087A (en) | Bidirectional voice frequency repeater | |
| JP3015094B2 (en) | Distortion canceling method for optical fiber transmission system and its apparatus and system | |
| CA1233531A (en) | Electronic hybrid circuit | |
| US4025737A (en) | Repeater monitoring and fault location | |
| US4163878A (en) | Electronic hybrid and hybrid repeater with bridge circuit | |
| US5343158A (en) | Amplifier device for a cable television distribution network | |
| US6426970B1 (en) | Bi-directional signal coupler method and apparatus | |
| JPS6139774B2 (en) | ||
| US3889072A (en) | Bi-directional amplification apparatus | |
| US1900045A (en) | Two-way negative resistance repeater | |
| US2938084A (en) | Hybrid branching networks | |
| US3775704A (en) | Hybrid filter | |
| US3946169A (en) | Bilateral signal transmission system | |
| US4127750A (en) | Apparatus for transmitting and receiving pulses | |
| JPS6347293B2 (en) | ||
| US2886654A (en) | Equivalent four-wire repeaters | |
| CA1108327A (en) | Electronic hybrid and hybrid repeater with bridge circuit | |
| US6754338B1 (en) | Bidirectional loss/slope equalizer arrangement | |
| JP2646669B2 (en) | Electronic hybrid circuit | |
| JP3023846U (en) | Out-of-band signal separation and superposition circuit | |
| JPS58147221A (en) | Branching device | |
| JP3302061B2 (en) | Optical space communication device |