JPS60220695A - Chrominance signal processor - Google Patents
Chrominance signal processorInfo
- Publication number
- JPS60220695A JPS60220695A JP59076925A JP7692584A JPS60220695A JP S60220695 A JPS60220695 A JP S60220695A JP 59076925 A JP59076925 A JP 59076925A JP 7692584 A JP7692584 A JP 7692584A JP S60220695 A JPS60220695 A JP S60220695A
- Authority
- JP
- Japan
- Prior art keywords
- frequency
- burst
- output
- period
- signal
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Pending
Links
Classifications
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04N—PICTORIAL COMMUNICATION, e.g. TELEVISION
- H04N9/00—Details of colour television systems
- H04N9/79—Processing of colour television signals in connection with recording
- H04N9/80—Transformation of the television signal for recording, e.g. modulation, frequency changing; Inverse transformation for playback
- H04N9/82—Transformation of the television signal for recording, e.g. modulation, frequency changing; Inverse transformation for playback the individual colour picture signal components being recorded simultaneously only
- H04N9/83—Transformation of the television signal for recording, e.g. modulation, frequency changing; Inverse transformation for playback the individual colour picture signal components being recorded simultaneously only the recorded chrominance signal occupying a frequency band under the frequency band of the recorded brightness signal
Landscapes
- Engineering & Computer Science (AREA)
- Multimedia (AREA)
- Signal Processing (AREA)
Abstract
Description
【発明の詳細な説明】
産業上の利用分野
本発明はビデオテープレコーダに用いられる低域変換搬
送色信号の処理装置に関するものである。DETAILED DESCRIPTION OF THE INVENTION FIELD OF INDUSTRIAL APPLICATION The present invention relates to a processing device for a low frequency conversion carrier color signal used in a video tape recorder.
従来例の構成とその問題点
民生用ビデオテープレコーダで良く用いられている色信
号処理回路は、副搬送色信号を低域搬送色信号に周波数
変換して記録し、再生時に再び周波数変換して副搬送色
信号に戻し、その時に回転シリンダのジッタによって生
じる色信号のジッタを取り除くカラーアンダーと呼ばれ
る方法である。Conventional configuration and its problems The color signal processing circuit commonly used in consumer video tape recorders converts the frequency of the sub-carrier color signal into a low-frequency carrier color signal for recording, and converts the frequency again during playback. This is a method called color under which returns the color signal to the sub-carrying color signal and removes the jitter of the color signal caused by the jitter of the rotating cylinder at that time.
第1図にカラーアンダ一方式の従来のアナログ回路によ
る再生系の一例を示す。同図において、再生された低域
変換色信号は平衡変調器1を通り副搬送色信号に周波数
変換され、バンドパスフィルタ2で平衡変調の際に生じ
る不要成分を除去し、遅延線3と減算器12で構成され
るくし形フィルタ13で、隣接トラックからのクロスト
ークを除去して出力する。FIG. 1 shows an example of a reproduction system using a conventional analog circuit of color under type. In the figure, the reproduced low-pass converted color signal passes through a balanced modulator 1, is frequency-converted into a subcarrier color signal, is removed by a bandpass filter 2, unnecessary components generated during balanced modulation, and is subtracted by a delay line 3. A comb filter 13 composed of a filter 12 removes crosstalk from adjacent tracks and outputs the result.
一方、出力からパーストゲート4によシバ−ストを取り
出し、基準発振器11と位相比較器5で位相を比較する
。位相誤差はローパスフィルタ6を通って電圧制御発振
器(以下、vcoと呼ぶ)7を制御する。VCO7の出
力は水平同期信号(fH)をフェーズ0ロ゛ツクド・ル
ープ(PLL)回路1oで40倍した周波数と平衡変調
器8でたし合わされ、バンドパスフィルタ9を通って平
衡変調器1のキャリアを得る。このようにして出力は常
に基準発振器11に位相が同期するように回路が作動す
る。On the other hand, a burst gate 4 extracts a burst from the output, and a reference oscillator 11 and a phase comparator 5 compare the phases. The phase error passes through a low-pass filter 6 to control a voltage controlled oscillator (hereinafter referred to as VCO) 7. The output of the VCO 7 is added to the frequency obtained by multiplying the horizontal synchronizing signal (fH) by 40 in a phase 0 locked loop (PLL) circuit 1o in a balanced modulator 8, and then passes through a bandpass filter 9 to the balanced modulator 1. Get a career. In this way, the circuit operates so that the output is always synchronized in phase with the reference oscillator 11.
しかし、この構成では低域変換搬送色信号のジッタに速
く応答させるためにループの利得を大きくすると、ルー
プ内にくし形フィルタ13が入っているため応答が不安
定になる欠点がある。However, in this configuration, when the gain of the loop is increased in order to quickly respond to the jitter of the low-pass conversion carrier color signal, there is a drawback that the response becomes unstable because the comb filter 13 is included in the loop.
また、くシ形フィルタ13を取り除くと隣接トラックか
らのクロストーク成分を除去できないという欠点がある
。また、バースト期間のみくし形フィルタを外す方法も
あるが、クロストークにより位相比較器6が誤動作しや
すい欠点があった。Furthermore, there is a drawback that if the comb filter 13 is removed, crosstalk components from adjacent tracks cannot be removed. There is also a method of removing the comb filter only during the burst period, but this method has the disadvantage that the phase comparator 6 tends to malfunction due to crosstalk.
発明の目的
本発明の目的は低婢変換−輿−堺牟信号を色副搬送波周
波数を有する搬送色信号に変換し、くシ形フィルタで隣
接クロストークを除去する時、クロストークによる誤動
作が少なく、かつ装置の応答を不安定にせずに速く出来
る色信号処理装置を提供することにある。OBJECTS OF THE INVENTION The purpose of the present invention is to reduce malfunctions due to crosstalk when converting a low-intensity conversion signal into a carrier color signal having a color subcarrier frequency and removing adjacent crosstalk using a comb filter. It is an object of the present invention to provide a color signal processing device that can perform the processing quickly without making the response of the device unstable.
発明の構成
本発明の色信号処理装置は、低域変換搬送色信号を周波
数変換する周波数変換器と、前記周波数変換器の出力を
遅延させる遅延回路と、前記遅延回路の出力と前記周波
数変換器の出力とを所定の合成比率で合成する演算回路
と、前記演算回路の出力信号のうちのバースト信号の位
相によって前記周波数変換器の周波数変換量を制御する
制御回路を具備し、前記演算回路の比率をバースト信号
期間だけ別の値に設定するように構成したものである。Structure of the Invention The color signal processing device of the present invention includes a frequency converter that converts the frequency of a low-pass conversion carrier color signal, a delay circuit that delays the output of the frequency converter, and an output of the delay circuit and the frequency converter. an arithmetic circuit that synthesizes the output of the arithmetic circuit at a predetermined synthesis ratio; and a control circuit that controls the amount of frequency conversion of the frequency converter according to the phase of a burst signal among the output signals of the arithmetic circuit; The ratio is configured to be set to a different value only during the burst signal period.
実施例の説明
以下、本発明の実施例について図面を参照しながら説明
する。第2図は本発明の一実施例の構成を示したブロッ
ク阻−で一壱る0同図において、スカ端子36より入力
された再生低域変換搬送色信号は平衡変調器20で搬送
色信号に変換され、バンドパスフィルタ21を通ってく
し形フィルタ26に入力される。DESCRIPTION OF EMBODIMENTS Hereinafter, embodiments of the present invention will be described with reference to the drawings. FIG. 2 is a block diagram showing the configuration of an embodiment of the present invention. In the same figure, the reproduced low-pass conversion carrier color signal inputted from the scar terminal 36 is processed by the balanced modulator 20 to produce the carrier color signal. and is input to the comb filter 26 through the band pass filter 21.
この出力は出力端子36へ出力される一方、パーストゲ
ート27でバースト部分を抜き取られ位相比較器28で
基準発振器29と位相を比較され、その誤差出力がロー
パスフィルタ30を通ってvCO31を制御する。VC
O31(7)出力はPLL回路34の出力と平衡変調器
32で周波数がだし合わされ、バンドパスフィルタ33
を通って平衡変調器20に入り、装置全体としては出力
端子36に現われる信号のバースト位相が基準発振器2
9の位相と等しくなるように帰還制御がかかる。This output is output to an output terminal 36, while a burst portion is extracted by a burst gate 27, and the phase is compared with a reference oscillator 29 by a phase comparator 28. The error output passes through a low-pass filter 30 and controls vCO 31. VC
The output of O31(7) is frequency-combined with the output of the PLL circuit 34 by the balanced modulator 32, and then passed through the bandpass filter 33.
The burst phase of the signal which enters the balanced modulator 20 through the reference oscillator 20 and appears at the output terminal 36 of the device as a whole is
Feedback control is applied so that the phase is equal to that of 9.
なお、PLL回路34は水平同期信号を40倍した出力
を与えるものでちり、原理的ICU固定発振器でもよい
。Note that the PLL circuit 34 provides an output that is 40 times the horizontal synchronization signal, and may be an oscillator fixed to the ICU in principle.
次に、クシ形フィルタ26について説明する。Next, the comb filter 26 will be explained.
くし形フィルタ2eは、遅延線22.増幅器23゜24
と減算器26とで構成され、増幅器23 、24は入力
端子37から入力されるバースト期間を表わすバースト
フラグ信号によってバースト期間のみ増幅率を別の値に
することが出来る。ここでは。The comb filter 2e is connected to the delay line 22. Amplifier 23°24
and a subtracter 26, and the amplifiers 23 and 24 can change the amplification factor to a different value only during the burst period in response to a burst flag signal input from an input terminal 37 representing the burst period. here.
たとえば増幅器23.24のそれぞれの増幅率を。For example, the amplification factors of each of amplifiers 23 and 24.
バースト期間以外は0.6と0.5にし、バースト期間
には0.3と0.7として説明する。第3図(a)にく
し形フィルタ26の利得の周波数特性を示す。実線がバ
ースト以外の期間の特性を示し、破線がバースト期間の
特性を示す。なお、信号成分は(n + 2 ) f
Hに、クロストーク成分はnfH(nは整数)pペクト
ラムが集中する。また、第3図(均は入力端子36にス
テップ位相変化を与えた時の出力端子360位相の時間
軸応答を示している。The description will be made using 0.6 and 0.5 for periods other than the burst period, and 0.3 and 0.7 for the burst period. FIG. 3(a) shows the frequency characteristics of the gain of the comb filter 26. The solid line shows the characteristics of periods other than the burst, and the broken line shows the characteristics of the burst period. Note that the signal component is (n + 2) f
As a crosstalk component, the nfH (n is an integer) p spectrum is concentrated in H. Further, FIG. 3 shows the time axis response of the phase of the output terminal 360 when a step phase change is applied to the input terminal 36.
横軸は時間を表わし、縦軸は位相の変化量を表わす。な
お入力に与えた位相変化量は1である。実線は増幅器2
3.24の利得をそれぞれ0.6と0.5に固定した時
の応答であり、破線は増幅器23゜24の利得をそれぞ
れα3とへ7にした時の応答である。本実施例では前に
説明したように出力のバースト信号の位相が基準発振器
29の位相と等しくなるように制御がかかるため、応答
はバースト信号期間のくし形フィルタ26の特性で決定
される。従って本実施例では第5図(blの破線の応答
を示す。The horizontal axis represents time, and the vertical axis represents the amount of change in phase. Note that the amount of phase change given to the input is 1. The solid line is amplifier 2
The broken lines are the responses when the gains of the amplifiers 23 and 24 are set to α3 and α7, respectively. In this embodiment, as described above, control is applied so that the phase of the output burst signal is equal to the phase of the reference oscillator 29, so the response is determined by the characteristics of the comb filter 26 during the burst signal period. Therefore, in this embodiment, the response shown by the broken line in FIG. 5 (bl) is shown.
一方、従来のくし形フィルタは遅延線の出力と遅延線を
通らない出力を1対1で減算するものであるから、第3
図(blに実線で示した応答をする。On the other hand, the conventional comb filter subtracts the output of the delay line and the output that does not pass through the delay line on a one-to-one basis.
The response shown in the figure (bl) is shown by the solid line.
この図から明らかなように、本実施例においては従来例
に比べ装置の応答が速い。また第3図(→の破線の特性
から判るように山の周波数における利得に対し、谷の周
波数における利得は0.4倍になっており、クロストー
ク成分は谷の周波数に現われるから0.4倍に抑圧する
ことが可能である。従って、くシ形フィルタを取り除い
た場合に比べてバースト信号のSN比を改善することが
出来る。As is clear from this figure, the response of the device is faster in this embodiment than in the conventional example. Also, as can be seen from the characteristics of the broken line in Figure 3 (→), the gain at the valley frequency is 0.4 times the gain at the peak frequency, and the crosstalk component appears at the valley frequency, so it is 0.4 Therefore, the SN ratio of the burst signal can be improved compared to when the comb filter is removed.
また、第3図(→の破線の特性を示すのは、バースト期
間のみであり、それ以外の期間、即ち映像信号の色情報
のある期間においては(−)の実線の特性を持ち、大き
なりロストーク除去効果が得られる。In addition, the characteristics indicated by the broken line in Figure 3 (→) are only shown during the burst period; other periods, that is, periods where the color information of the video signal is present, have the characteristics indicated by the solid line (-), and Lostalk removal effect can be obtained.
なお本実施例では、増幅器23.2Aの利得をバースト
期間にはそれぞれ0.3と0.7としたが、これは−例
であり、この値に限定されるものではない。In this embodiment, the gains of the amplifier 23.2A are set to 0.3 and 0.7 during the burst period, but this is just an example and is not limited to these values.
発明の効果
以上の説明から明らかなように、本発明はくし形フーイ
ルタの周波数特性をバースト期間だけ、谷の周波数の利
得を持ち上げるように制御することにより、入力信号の
位相変動に対する応答を速めることが出来るものである
。また、バースト期間においてクロストーク除去効果が
あるためSN比の良好なバースト信号を得ることが出来
、しかも、バースト期間以外ではさらに大きなりロスト
ークの除去効果を得ることができる。Effects of the Invention As is clear from the above explanation, the present invention can speed up the response to phase fluctuations of the input signal by controlling the frequency characteristics of the comb filter to increase the gain of the valley frequency only during the burst period. It is possible. Further, since there is a crosstalk removal effect during the burst period, a burst signal with a good SN ratio can be obtained, and an even greater crosstalk removal effect can be obtained outside the burst period.
第1図は従来例の構成を示したブロック図、第2図は本
発明の一実施例の構成を示したブロック図、第3図(→
は本発明の実施例に用いたくし形フィルタの特性図、第
3図(均は本発明の一実施例の応答を表わした特性図で
ある。
22・・・・・・遅延線、23,24・・・・・・増幅
器、26・・・・・・加算器、26・・・・・・くし形
フイルり。Figure 1 is a block diagram showing the configuration of a conventional example, Figure 2 is a block diagram showing the configuration of an embodiment of the present invention, and Figure 3 (→
3 is a characteristic diagram of a comb filter used in an embodiment of the present invention (the average is a characteristic diagram showing the response of an embodiment of the present invention. 22... Delay line, 23, 24 ......Amplifier, 26...Adder, 26...Comb filter.
Claims (1)
換器と、前記周波数変換器の出力を遅延させる遅延回路
と、前記遅延回路の出力と前記周波数変換器の出力とを
所定の合成比率で合成する演算回路と、前記演算回路の
出力信号のうちのバースト信号の位相によって前記周波
数変換器を作動させる周波数を与える発振器の位相を制
御する制御回路を具備し、前記演算回路の合成比率をバ
ースト信号期間だけ別の値に設定することを特徴とする
色信号処理装置。 (→ 演算回路の合成比率は、バースト期間以外では1
対1とし、バースト期間はd対(1−a)(ただし、a
は実数で、o<a<1 )とすることを特徴とする特許
請求の範囲第(1)項記載の色信号処理装置。(1) A frequency converter that converts the frequency of a low-pass conversion carrier color signal, a delay circuit that delays the output of the frequency converter, and an output of the delay circuit and an output of the frequency converter at a predetermined synthesis ratio. a control circuit that controls the phase of an oscillator that provides a frequency for operating the frequency converter according to the phase of a burst signal among the output signals of the arithmetic circuit; A color signal processing device characterized in that only a signal period is set to a different value. (→ The synthesis ratio of the arithmetic circuit is 1 except during the burst period.
1 vs. 1, and the burst period is d vs. (1-a) (however, a
The color signal processing device according to claim 1, wherein is a real number and o<a<1.
Priority Applications (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP59076925A JPS60220695A (en) | 1984-04-17 | 1984-04-17 | Chrominance signal processor |
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP59076925A JPS60220695A (en) | 1984-04-17 | 1984-04-17 | Chrominance signal processor |
Publications (1)
Publication Number | Publication Date |
---|---|
JPS60220695A true JPS60220695A (en) | 1985-11-05 |
Family
ID=13619288
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
JP59076925A Pending JPS60220695A (en) | 1984-04-17 | 1984-04-17 | Chrominance signal processor |
Country Status (1)
Country | Link |
---|---|
JP (1) | JPS60220695A (en) |
-
1984
- 1984-04-17 JP JP59076925A patent/JPS60220695A/en active Pending
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