JPH10191647A - Power source and discharge lamp lighting apparatus - Google Patents

Abstract

PROBLEM TO BE SOLVED: To reduce harmonic wave components and to improve a peak factor by connecting an inverter in parallel with a partial smoothing circuit, and generating a high frequency voltage by a switching operation of a switching element. SOLUTION: When an inverter 3 is oscillated by switching a transistor Q1 by a control circuit 5, a high frequency voltage is generated by resonance of a primary winding Tr1a of an inverter transformer Tr1 and a charging capacitor C3, and a high frequency voltage is also induced in a secondary winding Tr1b. When the transistor Q1 is turned ON, current flows to the winding Tr1a of the transformer Tr1, current flows through the capacitor C3, inductor L1 and diode D3 to charge the capacitor C3. A DC voltage lower than a peak value of a pulsating voltage from a full-wave rectifier 1 can be stored in the capacitor C3.

Description

DETAILED DESCRIPTION OF THE INVENTION

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a power supply device and a discharge lamp lighting device in which harmonics of an input current are reduced.

[0002]

2. Description of the Related Art Conventionally, as a discharge lamp lighting device of this type, for example, a structure described in Japanese Patent Application Laid-Open No. Hei 5-212774 is known. In the discharge lamp lighting device described in Japanese Patent Application Laid-Open No. 5-217774, a full-wave rectifier circuit is connected to a commercial AC power supply, and a first capacitor and a second capacitor are connected to output terminals of the full-wave rectifier circuit. ing. Also,
A partial smoothing circuit having a charging capacitor and an inductor is connected to the second capacitor, and a parallel resonance circuit and a transistor of the capacitor and the inductor are connected in series to the partial smoothing circuit. , A fluorescent lamp is connected.

[0003] By the high-frequency switching operation of the transistor, resonance occurs in the parallel resonance circuit, a resonance voltage is generated, and the fluorescent lamp is lit at high frequency.

[0004]

However, in the discharge lamp lighting device described in Japanese Patent Application Laid-Open No. 5-221774, the voltage from the second capacitor and the partial smoothing circuit is not sufficient, so that the crest factor is slightly reduced. Problem.

SUMMARY OF THE INVENTION The present invention has been made in view of the above problems, and has as its object to provide a power supply device and a discharge lamp lighting device in which harmonic components are reduced and a crest factor is improved.

[0006]

According to a first aspect of the present invention, there is provided a power supply device comprising: a rectifier for rectifying an AC from an AC power supply; a first capacitor connected in parallel to an output terminal of the rectifier; And a diode connected in series with one polarity to one end of the first capacitor, and the first
A second capacitor connected in parallel with the capacitor of
A partial smoothing circuit having an inductance element and a charging capacitor, connected in parallel to the second capacitor for charging the charging capacitor with a voltage lower than the maximum instantaneous voltage value of the output of the rectifier; A parallel resonance circuit having one resonance capacitor and a resonance inductor, a switching element connected in series to the parallel resonance circuit,
An inverter circuit that has a second resonance capacitor connected in parallel to the switching element, is connected in parallel to the partial smoothing circuit, and generates a high-frequency voltage by the switching operation of the switching element. Things. The inverter circuit supplies the input current from the first capacitor and the second capacitor when the output level of the rectifier is equal to or higher than the charge level of the charging capacitor, and the output level of the rectifier is lower than the charge level of the charging capacitor. Sometimes, an input current is supplied from a partial smoothing circuit, and the switching operation of the switching element causes the parallel resonance circuit and the second resonance capacitor to perform a resonance operation to reduce harmonics. High frequency output with improved rate.

According to a second aspect of the present invention, a first capacitor connected to an AC power supply, a rectifier connected to the first capacitor, and a second capacitor connected to the rectifier.
And a second capacitor for charging the charging capacitor with a voltage lower than the maximum instantaneous voltage value of the output of the rectifier.
, A parallel resonance circuit having a first resonance capacitor and a resonance inductor, a switching element connected in series to the parallel resonance circuit, and a parallel connection to the switching element. An inverter circuit having a second resonance capacitor connected thereto, connected in parallel with the partial smoothing circuit, and generating a high-frequency voltage by a switching operation of the switching element. The inverter circuit supplies the input current from the first capacitor and the second capacitor when the output level of the rectifier is equal to or higher than the charge level of the charging capacitor, and the output level of the rectifier is lower than the charge level of the charging capacitor. Sometimes, an input current is supplied from a partial smoothing circuit, and the switching operation of the switching element causes the parallel resonance circuit and the second resonance capacitor to perform a resonance operation to reduce harmonics. High frequency output with improved rate.

According to a third aspect of the present invention, a rectifier for rectifying an AC from an AC power supply, a first capacitor connected in parallel to an output terminal of the rectifier, and a first capacitor connected to the first capacitor. And a second capacitor connected in parallel to the diode, an inductance element and a charging capacitor, and charging the charging capacitor with a voltage lower than the maximum instantaneous voltage value of the output of the rectifier. A partial smoothing circuit connected in parallel to the first capacitor via a second capacitor and a diode, a parallel resonance circuit having a first resonance capacitor and a resonance inductor, connected in series to the parallel resonance circuit A switching element, having a second resonance capacitor connected in parallel to the switching element; And it is connected in parallel, by the switching operation of the switching element is obtained by including an inverter circuit for generating a high frequency voltage. The inverter circuit supplies the input current from the first capacitor and the second capacitor when the output level of the rectifier is equal to or higher than the charge level of the charging capacitor, and the output level of the rectifier is lower than the charge level of the charging capacitor. Sometimes, the input current is supplied from the partial smoothing circuit, and the switching operation of the switching element causes the parallel resonance circuit and the second
By causing the resonance capacitor to perform a resonance operation to reduce harmonics, and by flowing a resonance current into the second capacitor, a high-frequency output with an improved crest factor is output.

According to a fourth aspect of the present invention, there is provided the power supply device according to the first or third aspect, further comprising a short-circuit means for short-circuiting a diode in accordance with an output level of the rectifying means, wherein a resonance point is changed. This reduces the burden on the switching element.

According to a fifth aspect of the present invention, there is provided the power supply device according to any one of the first to fourth aspects, further comprising a capacitance changing unit that changes the capacitance of the second capacitor. Suitably, the voltage value is dropped to 0 when the voltage of the second capacitor is low to further reduce harmonics.

According to a sixth aspect of the present invention, there is provided the power supply device according to any one of the first to fifth aspects, wherein the first resonance capacitor and the second resonance capacitor have substantially the same capacitance, thereby further improving the waveform.

According to a seventh aspect of the present invention, there is provided a discharge lamp lighting device including the power supply device according to any one of the first to sixth aspects and a discharge lamp connected to the power supply device.

[0013]

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS A discharge lamp lighting device according to one embodiment of the present invention will be described below with reference to the drawings.

As shown in FIG. 1, an input terminal of a full-wave rectifier circuit 1 as a rectifier of a diode bridge is connected to a commercial AC power supply e, and an output terminal of the full-wave rectifier circuit 1 has a large capacity first terminal. A capacitor C1 is connected, and a series circuit of a diode D1 and a second capacitor C2 having a smaller capacity than the first capacitor C1 is connected to the first capacitor C1.

Further, a partial smoothing circuit 2 is connected to the second capacitor C2. The partial smoothing circuit 2 is connected to a series circuit of a charging capacitor C3, an inductor L1 and a diode D2, and an inductor L1 and a diode D2. In the meantime,
Diode D3 is connected.

Further, an inverter circuit 3 is connected to the partial smoothing circuit 2. The inverter circuit 3 includes a leakage flux type inverter transformer as a resonance inductor.
The parallel resonance circuit 4 of the primary winding Tr1a of Tr1 and the first resonance capacitor C4 and the collector and the emitter of the transistor Q1 serving as a switching element are connected. further,
A second resonance capacitor C5 is connected between the emitter and the collector of the transistor Q1.

A control circuit 5 is connected to the base of the transistor Q1.

Further, filaments FL1 and FL2 of a fluorescent lamp FL as a discharge lamp are connected to the secondary winding Tr1b of the inverter transformer Tr1.
, FL2 is connected to a starting capacitor C6.

The load circuit 6 is composed of the fluorescent lamp FL and the like.

Next, the operation of the above embodiment will be described.

First, when the inverter circuit 3 oscillates by the switching operation of the transistor Q1 by the control circuit 5, a high-frequency voltage is generated by the resonance between the primary winding Tr1a of the inverter transformer Tr1 and the charging capacitor C3, and the secondary A high-frequency voltage is also induced in the winding Tr1b.

When the transistor Q1 is turned on, a current flows through the primary winding Tr1a of the inverter transformer Tr1, and a current flows through the charging capacitor C3, the inductor L1, and the diode D3, thereby charging the charging capacitor C3. Then, a DC voltage lower than the peak value of the pulsating voltage from the full-wave rectifier circuit 1 can be stored in the charging capacitor C3.

Here, a description will be given of a section in which the pulsating voltage of the full-wave rectifier circuit 1 is higher than a charging voltage of the charging capacitor C3 and a section in which the pulsating voltage is lower than the charging voltage.

First, when the transistor Q1 of the inverter circuit 3 is turned on at an arbitrary time in a section where the pulsating voltage of the full-wave rectifier circuit 1 is higher than the charging voltage of the charging capacitor C3, the primary winding Tr1a of the inverter transformer Tr1 is turned on. Most of the current is supplied from the first capacitor C1, and part of the current is supplied from the second capacitor C2. The combined capacity of the first capacitor C1 and the second capacitor C2 is a capacity sufficient to provide the energy required by the inverter circuit 3. These first capacitor C1 and second capacitor C2
In accordance with the current supply from the above, energy becomes an input current and flows in from the commercial AC power supply e side. Then, an operation is performed so as to accompany the switching operation of the transistor Q1 in response to the change of the pulsating voltage, and the small and equal amplitude of the high frequency of the inverter operation of the inverter circuit 3 along the sine wave value of the AC voltage becomes full-wave. The voltage value of the rectifier circuit 1 is superimposed on all high sections.

That is, in the section where the voltage value of the full-wave rectifier circuit 1 is high, the first capacitor C1 and the second capacitor C2
Is a value obtained by satisfying the energy given by the supplied pulsating voltage with respect to the energy required by the inverter circuit 3.

For this reason, both the first capacitor C1 and the second capacitor C2 have a small ripple component, a small amount of heat generation, and can improve the operation reliability.

Then, in a section where the voltage value of the full-wave rectifier circuit 1 is high, the charging capacitor C3 is charged when the transistor Q1 is turned on. Note that, in a section where the voltage value of the full-wave rectifier circuit 1 is high, the discharge is not performed from the charging capacitor C3 to the inverter circuit 3 side.

Next, in a section where the voltage value of the full-wave rectifier circuit 1 is low, when the pulsating sine wave voltage of the full-wave rectifier circuit 1 starts to decrease with respect to the charging voltage of the charging capacitor C3, the transistor Q1 is turned on. When turned on, the current to the primary winding Tr1a of the inverter transformer Tr1 is first supplied from the second capacitor C2. Since the capacity of the second capacitor C2 is not enough to provide the energy required by the inverter circuit 3, the current flowing through the primary winding Tr1a after the transistor Q1 is turned on increases as the current of the second capacitor C2 increases. The voltage drops. Then, from the time when the voltage of the second capacitor C2 decreases to the voltage of the first capacitor C1, the first capacitor C1 supplies energy to the inverter circuit 3 that is insufficient in the second capacitor C2.

Then, the voltage is supplied until the transistor Q1 is turned off. However, the decrease in the voltage of the second capacitor C2 after the start of the energy supply from the first capacitor C1 is reduced. In addition, the energy supply from the first capacitor C1 to the inverter circuit 3 causes a corresponding amount of energy to flow as an input current from the commercial AC power supply e side.

On the other hand, the release of energy of the charging voltage of the charging capacitor C3 is delayed due to the transient impedance of the inductor L1, and the energy is released immediately before the transistor Q1 is turned off. And transistor Q1
Is turned off, the charging voltage of the charging capacitor C3 becomes a voltage supply source to the series circuit of the inductor L1, the diode D2, and the second capacitor C2. Here, since the inductor L1 and the second capacitor C2 are set so as to obtain an oscillating resonance, the charging of the second capacitor C2 is performed in a sine wave shape. This charging is increased in the inverter circuit 3 to a voltage at which the energy supply does not become insufficient when the transistor Q1 is turned on next time. Also,
By turning off the transistor Q1, the first resonance capacitor C4
And a second resonance capacitor C5 and an inverter transformer
Resonates with the primary winding Tr1a of Tr1. This resonance current is supplied to the second resonance capacitor C5 and the inverter transformer Tr.
1 primary winding Tr1a, the second capacitor C2, and the second
Flows through the path of the resonance capacitor C5 of the second capacitor C2
Is charged to generate an oscillating voltage. At this time, as shown in FIG. 2, the voltage between both ends of the second capacitor C2 is almost equal to the DC voltage at the highest instantaneous voltage portion and the lowest instantaneous voltage portion of the commercial AC power supply e.

Then, as the voltage of the first capacitor C1 decreases with respect to the charging voltage of the charging capacitor C3, the voltage of the second capacitor C2 decreases.
Of the capacitor C2 increases. Further, although the input current decreases, the current flows continuously.

As described above, the continuous flow of the input current from the commercial AC power supply e prevents a harmonic component from intervening in the input current.

Further, by increasing the fluctuation of the voltage value of the second capacitor C2, as shown in FIG. 3, the crest factor of the lamp current waveform of the fluorescent lamp FL is improved, and the crest factor is improved.

Next, another embodiment will be described with reference to FIG.

The embodiment shown in FIG. 4 differs from the embodiment shown in FIG. 1 in that the diode D1 is removed and the full-wave rectifier circuit 1 is connected between the first capacitor C1 and the second capacitor C2. It is.

As described above, by eliminating the diode D1, the circuit configuration can be simplified while the basic operation is substantially the same.

Another embodiment will be described with reference to FIG.

The embodiment shown in FIG. 5 is different from the embodiment shown in FIG. 1 in that the second capacitor C2 is replaced by a diode.
It is connected in parallel to D1.

In such a configuration, the basic operation is as shown in FIG.
This is the same as the embodiment shown in FIG.

Further, another embodiment will be described with reference to FIG.

The embodiment shown in FIG. 6 is different from the embodiment shown in FIG. 1 in that a series circuit of a capacitor C11 and a field effect transistor Q2 is connected in parallel with the second capacitor C2. Transistor Q2
Is connected to a control circuit 11.

The control of the field effect transistor Q2 by the control circuit 11 changes the substantial combined capacitance with the second capacitor C2. For example, when the output of the inverter circuit 3 changes due to a temperature change or the like. To
By changing the combined capacitance of the second capacitor C2 and the capacitor C11, the voltage value surely drops to 0 in a portion where the voltage of the second capacitor C2 is low. To prevent

The same effect can be obtained by adding this configuration to the embodiment shown in FIG.

Still another embodiment will be described with reference to FIG.

The embodiment shown in FIG. 7 is different from the embodiment shown in FIG. 1 in that a thyristor Q3 as short-circuit means is connected in anti-parallel to the diode D1.
The control circuit 12 is connected to the gate of Q3.

Normally, the inverter circuit 3 is operated by boosting the voltage due to the resonance between the inverter transformer Tr1 of the inverter circuit 3 and the second capacitor C2. For example, when the lamp current of the fluorescent lamp FL increases, ,
Turn on the thyristor Q3, pass a current in the opposite direction to the diode D1, and connect the inverter transformer Tr1 and the first capacitor.
Stepping down by resonance with C1 and the second capacitor C2,
The load on the transistor Q1 is reduced by changing the resonance point as compared with the case of the second capacitor C2.

The same effect can be obtained by adding this configuration to the embodiment shown in FIGS.

FIGS. 8 to 10 show another embodiment.
This will be described with reference to FIG.

The embodiment shown in FIGS. 8 to 10 differs from the embodiment shown in FIGS. 1, 4 and 5 in that
Charging capacitor C3 and inductor for partial smoothing circuit 2
A diode D6 is connected in parallel with the series circuit of L1.

When charging the charging capacitor C3, the magnetic energy of the inductor L1 is supplied to the charging capacitor C3 via the diode D6, whereby the charging capacitor C3 can be charged. Also, by flowing a current through the diode D3, the current flows through the diode D2 only when charging the charging capacitor C3, and the voltage of the transistor Q1 is applied to the diode D3 while the transistor Q1 is off. Inductor L1 and diode
The voltage applied to D2 is reduced, and the size of the device can be reduced.

Further, another embodiment will be described with reference to FIG.

The embodiment shown in FIG. 11 is different from the embodiment shown in FIG. 8 in that the second embodiment is similar to the embodiment shown in FIG.
A capacitor C11 and a series circuit of a field effect transistor Q2 are connected in parallel with the capacitor C2,
The control circuit 11 is connected to the field effect transistor Q2.

The same effect can be obtained by adding this configuration to the embodiment shown in FIGS. 9 and 10.

Still another embodiment will be described with reference to FIG.

The embodiment shown in FIG. 12 is different from the embodiment shown in FIG. 8 in that, like the embodiment shown in FIG.
Q3 is connected, and the control circuit 12 is connected to the gate of the thyristor Q3.

The same effect can be obtained by adding this configuration to the embodiment shown in FIG.

FIGS. 13 to 1 show another embodiment.
This will be described with reference to FIG.

The embodiment shown in FIGS. 13 to 15 differs from the embodiment shown in FIGS. 1, 4 and 5 in that a first resonance capacitor C4 is used instead of the leakage flux type inverter transformer Tr1. For parallel resonance
Connect L3, and in parallel with this resonance inductor L3,
Primary winding Tr2a of ballast L4 and isolation type transformer Tr2
And a fluorescent lamp FL is connected to the secondary winding Tr2b of the transformer Tr2.

The function of the inverter transformer Tr1 is distributed to the resonance inductor L3, the ballast L4, and the insulation type transformer Tr2.
And operates similarly to FIG.

Further, another embodiment will be described with reference to FIG.

The embodiment shown in FIG. 16 differs from the embodiment shown in FIG. 13 in that a capacitor C11 and a field-effect transistor Q2 are connected in parallel with the second capacitor C2, similarly to the embodiment shown in FIG. And a control circuit 11 is connected to the field-effect transistor Q2.

The same effect can be obtained by adding this configuration to the embodiment shown in FIGS.

Still another embodiment will be described with reference to FIG.

In the embodiment shown in FIG. 17, a thyristor Q3 as a short-circuit means is connected to the diode D1 in anti-parallel to the embodiment shown in FIG. 13, similarly to the embodiment shown in FIG. The control circuit 12 is connected to the gate of this thyristor Q3.
Are connected.

The same effect can be obtained by adding this configuration to the embodiment shown in FIG.

FIGS. 18 to 2 show another embodiment.
0 will be described.

The embodiment shown in FIGS. 18 to 20 is different from the embodiment shown in FIGS. 13 to 15 in that the partial smoothing circuit 2 is similar to the embodiment shown in FIGS.
The diode D6 is connected in parallel to the series circuit of the charging capacitor C3 and the inductor L1.

Further, another embodiment will be described with reference to FIG.

The embodiment shown in FIG. 21 differs from the embodiment shown in FIG. 18 in that a capacitor C11 and a field-effect transistor Q2 are connected in parallel to the second capacitor C2, similarly to the embodiment shown in FIG. And a control circuit 11 is connected to the field-effect transistor Q2.

The same effect can be obtained by adding this configuration to the embodiment shown in FIGS. 19 and 20.

Still another embodiment will be described with reference to FIG.

In the embodiment shown in FIG. 22, a thyristor Q3 as a short-circuit means is connected to the diode D1 in antiparallel to the embodiment shown in FIG. 18, similarly to the embodiment shown in FIG. The control circuit 12 is connected to the gate of this thyristor Q3.
Are connected.

A similar effect can be obtained by adding this configuration to the embodiment shown in FIG.

FIGS. 23 to 2 show another embodiment.
This will be described with reference to FIG.

In the embodiments shown in FIGS. 23 to 25, the insulating transformer Tr2 is omitted from the embodiments shown in FIGS. 18 to 20, and the filament of the fluorescent lamp FL is removed.
The capacitor C6 on the other end of FL1 and FL2 is deleted, and the starting capacitor C12 is connected on one end, simplifying the configuration.

Although the filaments FL1 and FL2 cannot be preheated, the basic operation is the same as in the embodiment shown in FIGS.

Further, another embodiment will be described with reference to FIG.

The embodiment shown in FIG. 26 differs from the embodiment shown in FIG. 23 in that a capacitor C11 and a field-effect transistor Q2 are connected in parallel to the second capacitor C2, similarly to the embodiment shown in FIG. And a control circuit 11 is connected to the field-effect transistor Q2.

The same effect can be obtained by adding this structure to the embodiment shown in FIGS. 24 and 25.

Still another embodiment will be described with reference to FIG.

In the embodiment shown in FIG. 27, a thyristor Q3 as a short-circuit means is connected to the diode D1 in antiparallel to the embodiment shown in FIG. 23 in the same manner as the embodiment shown in FIG. The control circuit 12 is connected to the gate of this thyristor Q3.
Are connected.

A similar effect can be obtained by adding this configuration to the embodiment shown in FIG.

FIGS. 28 to 3 show another embodiment.
0 will be described.

The embodiment shown in FIGS. 28 to 30 is different from the embodiment shown in FIGS. 23 to 25 in that the partial smoothing circuit 2 is similar to the embodiment shown in FIGS.
The diode D6 is connected in parallel to the series circuit of the charging capacitor C3 and the inductor L1.

Further, another embodiment will be described with reference to FIG.

The embodiment shown in FIG. 31 differs from the embodiment shown in FIG. 28 in that a capacitor C11 and a field-effect transistor Q2 are connected in parallel to the second capacitor C2, similarly to the embodiment shown in FIG. And a control circuit 11 is connected to the field-effect transistor Q2.

The same effect can be obtained by adding this configuration to the embodiment shown in FIGS. 29 and 30.

Still another embodiment will be described with reference to FIG.

In the embodiment shown in FIG. 31, a thyristor Q3 as a short-circuit means is connected to the diode D1 in antiparallel to the embodiment shown in FIG. 28, similarly to the embodiment shown in FIG. The control circuit 12 is connected to the gate of this thyristor Q3.
Are connected.

A similar effect can be obtained by adding this configuration to the embodiment shown in FIG.

Next, a load circuit 6 according to another embodiment will be described with reference to FIGS. The load circuit 6 shown in FIGS. 32 to 42 can be used in any of the discharge lamp lighting devices shown in FIGS. 1 and 3 to 31.

First, the load circuit 6 shown in FIG. 33 includes a starting capacitor C12 and a filament FL of a fluorescent lamp FL connected to a secondary winding Tr1b of a leakage flux type inverter transformer Tr1.
1 and one end of FL2 are connected.

The load circuit 6 shown in FIG.
The filament FL1 of the fluorescent lamp FL of the load circuit 6 shown in FIG.
A capacitor C6 for preheating is connected to the other end of FL2.

Further, the load circuit 6 shown in FIG. 35 connects a primary winding Tr2a of an insulation type transformer Tr2 via a ballast L3, and connects a fluorescent lamp to a secondary winding Tr2b of the transformer Tr2.
One end of each of the filaments FL1 and FL2 of the FL is connected, and a capacitor C6 is connected to the other end.

Further, the load circuit 6 shown in FIG.
The secondary winding Tr2b of the transformer Tr2 of the load circuit 6 shown in FIG.
Is connected to the capacitor C12 and the capacitor C6 is deleted.

The load circuit 6 shown in FIG.
Filament of the fluorescent lamp FL of the load circuit 6 shown in FIG.
A capacitor C6 is connected between the other ends of FL1 and FL2.

A load circuit 6 shown in FIG. 38 is connected to one end of filaments FL1 and FL2 of a fluorescent lamp FL via a ballast L4 to a secondary winding Tr2b of an insulation type transformer Tr2.
The other end is connected to a capacitor C6.

Further, the load circuit 6 shown in FIG.
In place of the capacitor C6 of the load circuit 6 shown in FIG. 8, a capacitor C12 is connected to one end of the filaments FL1 and FL2.

Further, the load circuit 6 shown in FIG.
In this configuration, a capacitor C6 is connected to the other ends of the filaments FL1 and FL2 of the load circuit 6 shown in FIG.

Further, the load circuit 6 shown in FIG.
The ballast L4 and the primary winding Tr2a of the insulating transformer Tr2 are connected to the resonance inductor L3, and the capacitor C12 and the filaments FL1 and FL2 of the fluorescent lamp FL are connected to the secondary winding Tr2a.
Are connected at one end.

The load circuit 6 shown in FIG.
The filament FL1 of the fluorescent lamp FL of the load circuit 6 shown in FIG.
The capacitor C6 is connected to the other end of FL2.

[0102]

According to the power supply device of the first aspect, the inverter circuit supplies the input current from the first capacitor and the second capacitor when the output level of the rectifier is equal to or higher than the charging level of the charging capacitor. When the output level of the rectifier is lower than the charge level of the charging capacitor, an input current is supplied from the partial smoothing circuit, and the switching operation of the switching element causes the parallel resonance circuit and the second resonance capacitor to perform a resonance operation to reduce harmonics. At the same time, a high frequency output with an improved crest factor can be obtained by flowing the resonance current into the second capacitor.

According to the power supply device of the second aspect, the inverter circuit includes the first capacitor and the second capacitor when the output level of the rectifier is equal to or higher than the charging level of the charging capacitor.
When the output level of the rectifier is lower than the charging level of the charging capacitor, the input current is supplied from the partial smoothing circuit, and the parallel resonance circuit and the second resonance capacitor are switched by the switching operation of the switching element. A high frequency output with an improved crest factor can be obtained by causing the resonance operation to reduce the harmonics and to flow the resonance current into the second capacitor.

According to the third aspect of the present invention, when the output level of the rectifier is equal to or higher than the charging level of the charging capacitor, the inverter circuit includes the first capacitor and the second capacitor.
When the output level of the rectifier is lower than the charging level of the charging capacitor, the input current is supplied from the partial smoothing circuit, and the parallel resonance circuit and the second resonance capacitor are switched by the switching operation of the switching element. A high frequency output with an improved crest factor can be obtained by causing the resonance operation to reduce the harmonics and to flow the resonance current into the second capacitor.

According to the power supply device of the fourth aspect, in addition to the power supply device of the first or third aspect, the short-circuit means for short-circuiting the diode according to the output level of the rectifying means is provided. By doing so, the burden on the switching element can be reduced.

According to the power supply device of the fifth aspect, in addition to the power supply device of any one of the first to fourth aspects, there is provided a capacitance changing means for changing the capacitance of the second capacitor.
By appropriately setting the capacity of the second capacitor, the voltage value can be reduced to 0 in a state where the voltage of the second capacitor is low, so that harmonics can be further reduced.

According to the power supply device of the sixth aspect, in addition to the power supply device of any one of the first to fifth aspects, the first resonance capacitor and the second resonance capacitor have substantially the same capacitance, so that the waveform is further improved. it can.

According to the discharge lamp lighting device of the seventh aspect,
Since the discharge lamp connected to the power supply device according to any one of claims 1 to 6 is provided, respective effects can be obtained.

[Brief description of the drawings]

FIG. 1 is a circuit diagram showing one embodiment of a discharge lamp lighting device of the present invention.

FIG. 2 is a waveform diagram showing a voltage of a second capacitor according to the first embodiment;

FIG. 3 is a waveform chart showing a lamp current of the fluorescent lamp.

FIG. 4 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.

FIG. 5 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.

FIG. 6 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.

FIG. 7 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.

FIG. 8 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.

FIG. 9 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.

FIG. 10 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.

FIG. 11 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.

FIG. 12 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.

FIG. 13 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.

FIG. 14 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.

FIG. 15 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.

FIG. 16 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.

FIG. 17 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.

FIG. 18 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.

FIG. 19 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.

FIG. 20 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.

FIG. 21 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.

FIG. 22 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.

FIG. 23 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.

FIG. 24 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.

FIG. 25 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.

FIG. 26 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.

FIG. 27 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.

FIG. 28 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.

FIG. 29 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.

FIG. 30 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.

FIG. 31 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.

FIG. 32 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.

FIG. 33 is a circuit diagram showing a load circuit according to another embodiment of the present invention;

FIG. 34 is a circuit diagram showing a load circuit according to another embodiment of the present invention;

FIG. 35 is a circuit diagram showing a load circuit according to another embodiment of the present invention;

FIG. 36 is a circuit diagram showing a load circuit according to another embodiment of the present invention;

FIG. 37 is a circuit diagram showing a load circuit according to another embodiment of the present invention;

FIG. 38 is a circuit diagram showing a load circuit according to another embodiment of the present invention;

FIG. 39 is a circuit diagram showing a load circuit according to another embodiment of the present invention;

FIG. 40 is a circuit diagram showing a load circuit according to another embodiment of the present invention;

FIG. 41 is a circuit diagram showing a load circuit according to another embodiment of the present invention;

FIG. 42 is a circuit diagram showing a load circuit according to another embodiment of the present invention;

[Explanation of symbols]

 1 Full-wave rectifier circuit as rectifier 2 Partial smoothing circuit 3 Inverter circuit 4 Parallel resonance circuit C1 First capacitor C2 Second capacitor C3 Charging capacitor C4 First resonance capacitor C5 Second resonance capacitor D1 Diode e Commercial AC power supply FL Fluorescent lamp as discharge lamp L1 Inductor Q1 Transistor as switching element Q3 Thyristor as short-circuit means Tr Inverter as resonant inductor

 ──────────────────────────────────────────────────続 き Continuing on the front page (72) Inventor Tetsushi Takeda 6-78, Minamicho, Mishima-shi, Shizuoka Prefecture Inside the Tec Mishima Plant (72) Inventor Kazuyuki Yamamoto 6-78, Minami-cho, Mishima-shi, Shizuoka Tec, Inc. Mishima factory

Claims (7)

[Claims] 1. A rectifier for rectifying an alternating current from an AC power supply, a first capacitor connected in parallel to an output terminal of the rectifier, and one end of the first capacitor connected in series with a forward polarity. A second capacitor connected in parallel to the first capacitor via the diode, an inductance element and a charging capacitor, and the charging capacitor has a maximum instantaneous voltage of the output of the rectifier means. A partial smoothing circuit connected in parallel to the second capacitor for charging at a voltage lower than a value, a parallel resonance circuit having a first resonance capacitor and a resonance inductor, and switching connected in series to the parallel resonance circuit A second resonant capacitor connected in parallel to the switching element, and connected in parallel to the partial smoothing circuit. Is, the power supply apparatus characterized by comprising an inverter circuit for generating a high frequency voltage by a switching operation of the switching element. A first capacitor connected to the AC power supply, a rectifier connected to the first capacitor, a second capacitor connected to the rectifier, an inductance element and a charging capacitor. A partial smoothing circuit connected in parallel to the second capacitor for charging the charging capacitor with a voltage lower than the maximum instantaneous voltage value of the output of the rectifier, a first resonance capacitor and a resonance inductor A parallel resonance circuit having a switching element connected in series to the parallel resonance circuit, a second resonance capacitor connected in parallel to the switching element, and connected in parallel to the partial smoothing circuit. An inverter circuit for generating a high-frequency voltage by a switching operation of the switching element. Location. 3. A rectifier for rectifying AC from an AC power supply, a first capacitor connected in parallel to an output terminal of the rectifier, a diode connected to the first capacitor, It has a second capacitor connected in parallel, an inductance element and a charging capacitor, and charges the charging capacitor with the second capacitor and the diode which are charged with a voltage lower than the maximum instantaneous voltage value of the output of the rectifier. A partial smoothing circuit connected in parallel to the first capacitor via a first resonance capacitor, a parallel resonance circuit having a first resonance capacitor and a resonance inductor, a switching element connected in series to the parallel resonance circuit, A second resonance capacitor connected in parallel to the partial smoothing circuit, Serial power supply and characterized by including an inverter circuit that generates a high-frequency voltage by a switching operation of the switching element. 4. The power supply device according to claim 1, further comprising short-circuit means for short-circuiting the diode in accordance with the output level of the rectifier. 5. The apparatus according to claim 1, further comprising a capacitance varying means for varying the capacitance of the second capacitor.
The power supply according to any one of the above. 6. The power supply device according to claim 1, wherein the first resonance capacitor and the second resonance capacitor have substantially equal capacities. 7. A discharge lamp lighting device comprising: the power supply device according to claim 1; and a discharge lamp connected to the power supply device.