JPH0690221A - Searcher receiver for receiver for spread spectrum communication - Google Patents

Abstract

PURPOSE:To scan plural code systems with simple constitution and low power consumption extending over designated measuring time in a searcher receiver for spread spectrum communication of direct diffusion system. CONSTITUTION:All the correlation patterns of a reception signal divided at every four bit unit are calculated by an all correlation processor 22, and are supplied to complex correlation value calculators 24a, 25a, and 26a. The pattern processor 32 of the correlation value calculator calculates the high-order three bits of a PN code stored in an S/P converter 31 and the correlation pattern to be selected from a code bit, and supplies them to a selector 33. The selector 33 selects a correlation value in accordance with the correlation pattern instructed by the pattern processor 32 out of the correlation values in accordance with the correlation patterns supplied from the all correlation processor 22, and multiplies it by the code of code bit, then, outputs it to a mean part 45 and executes a correlation arithmetic operation. The sum of squares of the correlation value obtained similarly is taken by decided combination, and pilot signal strength can be found.

Description

Detailed Description of the Invention

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a searcher receiver of a spread spectrum communication receiver, and particularly, a simple structure for simultaneously scanning a plurality of pseudo noise (PN) codes for correlation processing over a designated observation time. Regarding the searcher receiver.

[0002]

2. Description of the Related Art A direct spread (DS) spread spectrum communication system (hereinafter referred to as an SS system) has advantages such as strong resistance to interference and less interference, and small capacity communication using a satellite line, It is being developed as one of communication methods for mobile communication such as car phones, mobile phones, cordless phones and the like.

FIG. 8 shows USP (US Patent) 5,103,
The schematic configuration of the receiving device of the CDMA cellular telephone system disclosed in No. 459 is shown. This mobile CDM
The telephone system A includes an antenna 1 and an analog receiver 3 and a power amplifier 4 via a diplexer 2.
Connected to. The antenna 1 receives the SS signal from the base station (cell site) and supplies the reception signal to the analog receiver 3 via the diplexer 2. The analog receiver 3 includes a down converter, converts the supplied reception signal into a baseband signal, and further converts it into a digital signal with an A / D converter. The baseband signal converted into a digital signal is supplied to the searcher receiver 5 and the two digital data receivers 6 and 7.

When the SS signal reaches the receiving device through a plurality of paths, a difference occurs in the reception time of each signal. The digital data receivers 6 and 7 can select which path signal is to be tracked and received. As shown in FIG. 8, if there are two data receivers, two separate paths will be tracked in parallel.

On the other hand, the searcher receiver 5 scans the time domain near the reference timing of the received pilot signal in order to detect the pilot signals included in the received multipath signals from the cell site based on the control signal from the control processor 8. To do. Then, the searcher receiver 5 compares the intensities of the received signals with each other and outputs the intensity signal to the control processor 8 to instruct the signal of the highest intensity.

Similarly, the searcher receiver compares the signal strengths of the received pilot signals with each other in order to detect multipath pilot signals from different sectors at the adjacent cell site or the same cell site based on the control signal from the control processor 8. Then, a signal timing and an intensity signal corresponding to the signal timing are output to the control processor.

Then, the control processor 8 supplies a control signal to the digital data receivers 6 and 7 to cause the respective receivers to process different strongest signals and the like.

The control processor compares the signal strengths provided by the searcher receivers and, if necessary, initiates a handoff process to adjacent cells. In that case, the plurality of digital data receivers operate to receive signals from different cell sites or signals from different sectors at the same cell site. Note that these handoff operations are performed by PCT / US90 / 06416 (WO
-91/07020, USP510501).

The received pilot signal has different levels and phases for each path depending on the distance from the base station and the state of the communication path in addition to the timing. The analog receiver multiplies the multipath received signal by the common carrier wave and outputs the baseband received signal. Will remain.
Therefore, the searcher receiver needs to measure the strength of the received pilot signal regardless of the phase difference. FIG. 15 shows a circuit configuration for measuring the strength of a pilot signal having an arbitrary phase difference. The operation will be described below.

Now, suppose that the received pilot signal of the first bus from a certain cell site is given by the following equation in complex envelope representation.

Ρ _i A [PN _I (t _i ) + jPN _Q (t _i )] exp (jθ _i ), where ρ _i is the attenuation factor of the path, A is the transmission voltage of the pilot signal, and θ _i is the carrier wave of the path. And PN _I and PN _Q are the phase difference between the carrier of the analog receiver and the carrier of the analog receiver, and pseudo noise (P
N) code and t _i are timings of the PN code, which are delayed from the PN code timing of the transmitting side by the propagation time of the path.

The following equation is obtained by dividing the above equation into a real number component and an imaginary number component.

= Ρ _i A [PN _I (t _i ) cos θ _i + PN _Q (t _i ) sin θ _i ] + j ρ _i A [PN _Q (t _i ) cos θ _i + PN _I (t _i ) sin θ _i ] The real number of the above equation The component is input as an in-phase axis reception signal and the imaginary number component is input as an orthogonal axis reception signal from the analog receiver. In addition,
In addition to this, received pilot signals from different paths, received pilot signals from different sectors at different cell sites and the same cell site, etc. are also included.

The in-phase axis received signal is a correlator PN _I correlator PN
_Entered in _Q. In the correlator PN _I , the input signal is correlated with the PN code PN _I '(' indicates the same PN code, but the timings do not always match). Similarly, the correlator PN _Q correlates the input signal with the PN code PN _Q '. Taking the correlation means multiplying the input signal by the PN code and integrating.
When the integration time is T, the output of the correlator _{PN I, ∫ρ i A [PN} I cosθ i -PN Q sinθ i] PN I 'dt = ρ i A∫ [PN I PN I' cosθ i -PN Q PN _I 'sin θ _i ] dt By the way, PN _Q and PN _I are PN codes different from each other, and due to the nature of the PN code, it becomes zero on average at all timings, so the correlator PN _I output is approximately It is shown by the formula.

[0015] ρ _i A∫PN _I PN _I in the same manner _{'cosθ i dt = ρ i Acosθ} i ∫PN I PN I' dt, the output of the correlator PN _Q, approximately -ρ _i Asinθ _i ∫PN _Q the PN _Q 'dt. Also for the orthogonal axis received signal, the correlators PN _I and PN _Q correlate with the input signal, and the respective results are approximately the values shown by the following equation.

[0016] _{ρ i Asinθ i ∫PN I PN I} 'dt ρ i Acosθ i ∫PN Q PN Q' dt Further, if the integration time T is the period time or a positive integer multiple thereof PN code, the following relationship Holds.

[0017] _{∫PN I PN I 'dt = T} · R I (τ) ∫PN Q PN Q' dt = T · R Q (τ) _{wherein, R I (τ), R} Q (τ) respectively PN _I , P
In the normalized autocorrelation function of N _Q , τ represents the time difference between PN _I and PN _I 'and PN _Q and PN _Q '. By the nature of the PN _{code, R I (0), R} Q (0) ( when the timing is matched) are both 1, and when the tau ≠ 0 is R _I
(Τ) and R _Q (τ) are values considerably smaller than 1 and are zero on average.

Therefore, as shown in FIG. 15, by adding and subtracting the respective correlator outputs in a crosswise manner, ρ _i ATcos θ _i [R _I (τ) + R _Q (τ)] ρ _i ATsin θ _i [R _I ( τ) + R _Q (τ)] is obtained. Then, the square circuits 103 and 104 and the adder 105 take the sum of squares of the outputs of the adders 100 and 101, and the output of the adder 105 is given by the following equation. (Ρ _i A [R _I (τ) + R _Q (τ)] cos θ _i ) ² + (ρ _i A [R _I (τ) + R _Q (τ)] sin θ _i ) ² = ρ _i ² A ² [R _I (Τ) + R _Q (τ)] ² (cos θ _i ² + sin θ _i ² ) = ρ _i ² A ² [R _I (τ) + R _Q (τ)] ^{2 In} this way, only when the PN code timings match ,
A value related to the received pilot signal power is obtained from the adder regardless of the value of the phase difference θ _i , and if the timings do not match, a value that is zero on average is obtained.

[0019]

Since the searcher receiver scans multipath pilot received signals from the same ceresite / sector, the timing of PN _I 'and PN _Q ' used in the searcher receiver is set to a time near the reference timing. The pilot signal power is measured using the timing corresponding to the region. Sliding correlation method for correlator (active correlation method for multiplication and addition of PN code)
Then, the correlator P having the timing corresponding to the time domain
There is a problem that a plurality of N _I and correlators PN _Q are required and the hardware scale increases. Different cell sites,
The increase is significant when it is necessary to scan pilot signals from different sectors at the same cell site.

In order to deal with this, it is conceivable that the number of correlators is not increased to a certain extent, but instead the timing of the PN code to be input is switched to use the correlators in a time division manner. Since the integration time T is required to obtain the reception strength at one timing, in that case, there is a problem that the time required to obtain the reception pilot strength in the entire time domain increases. In addition, if the time required is suppressed, the effect of averaging becomes smaller, the effect of noise, or the effect of the omitted part in the equation that is approximately zero, increases, and the measurement accuracy deteriorates. The problem arises.

Alfred and Bayer are IEEE TR
ANSACTIONS ON COMMUNICATI
ONS Vol, COM-32 No. 4 April
1984 pp. 354-361, a method of using a matched filter for the four correlators shown in FIG. 15 is disclosed. Since the matched filter multiplies each tap output of the delay line with taps by the PN code that correlates and adds the multiplication result by the adder, it is possible to serially obtain the correlation result obtained by the sliding correlator.

However, since the applicable PN code sequence length is limited, there remains a problem that it is not suitable as a correlator for a PN code having a long sequence length.
Further, when different PN codes are used for each cell site / sector, it is necessary to prepare a matched filter corresponding to each PN code, which leaves a problem that the hardware scale increases. .

The present invention has been made in view of the above problems of the prior art, and an object thereof is SS communication capable of simultaneously scanning a plurality of code sequences over a designated time domain with a simple configuration. The purpose of the present invention is to provide a searcher receiver for a receiver.

[0024]

In order to achieve the above object, a searcher receiver according to claim 1 uses a pseudo-noise code of an in-phase axis and a pseudo-noise code of an orthogonal axis to provide a direct spread method to the in-phase axis and the orthogonal axis. In the searcher receiver device of the receiver for spread spectrum communication that receives a signal that has been spread spectrum, performs correlation processing with the pseudo noise code from this received signal, and outputs the timing and signal strength of the received pilot signal, the in-phase axis Storing means for storing received signals in a predetermined number unit, all correlation processing means for in-phase axis received signals for outputting correlation values corresponding to all correlation patterns of in-phase axis received signals stored in the storing means, and quadrature axis Storing means for storing the received signal in a predetermined number of units and outputting correlation values corresponding to all the correlation patterns of the orthogonal axis received signals stored in the storing means. All the correlation processing means for the orthogonal axis received signal, and a plurality of corresponding correlation processing means output corresponding to the observation time, from the output of all the correlation processing means for the in-phase axis received signal and the orthogonal axis received signal, in-phase spreading code or orthogonal axis A complex correlation value calculator that selects a partial correlation value corresponding to a correlation pattern of a predetermined number of partial code sequences of spread codes, and outputs a pilot signal strength using the selected partial correlation value, and the plurality of complex correlation values And a correlation value table storing the pilot signal strength of the calculator output.

Further, in order to achieve the above object, a second aspect is provided.
The searcher receiver described, by the pseudo-noise code of the in-phase axis and the pseudo-noise code of the quadrature axis, receives the signal spread spectrum to the in-phase axis and the quadrature axis by the direct spreading method,
In the searcher receiver of the spread spectrum communication receiver that performs correlation processing with the pseudo noise code from the received signal and outputs the timing and signal strength of the received pilot signal, a storage means for storing the in-phase axis received signal in a predetermined number unit. A total correlation processing means for the in-phase axis received signal, which outputs correlation values corresponding to all correlation patterns of the in-phase axis received signal stored in the storage means, and a storage means for storing the orthogonal axis received signal in a predetermined number unit. An all-correlation processing unit for the orthogonal axis received signal, which outputs correlation values corresponding to all correlation patterns of the orthogonal axis received signal stored in the storage unit,
Correlation patterns of a predetermined number of partial code sequences of the in-phase axis spreading code and the orthogonal axis spreading code are provided from all the correlation processing means outputs for the in-phase axis received signal and the orthogonal axis received signal, which are provided corresponding to the observation time. , A complex correlation value calculator that outputs pilot signal strengths using the selected partial correlation values, and a correlation that stores pilot signal strengths of the outputs of the plurality of complex correlation value calculators. And a value table.

Further, in order to achieve the above object, claim 3
The searcher receiver described, by the pseudo-noise signal of the in-phase axis and the pseudo-noise code of the quadrature axis, receives the signal spectrum-spread with respect to the in-phase axis and the quadrature axis by the direct spreading method,
In the searcher receiver of the spread spectrum communication receiver that performs correlation processing with the pseudo noise code from the received signal and outputs the timing and signal strength of the received pilot signal, a storage means for storing the in-phase axis received signal in a predetermined number unit. A total correlation processing means for the in-phase axis received signal, which outputs correlation values corresponding to all correlation patterns of the in-phase axis received signal stored in the storage means, and a storage means for storing the orthogonal axis received signal in a predetermined number unit. An all-correlation processing unit for the orthogonal axis received signal, which outputs correlation values corresponding to all correlation patterns of the orthogonal axis received signal stored in the storage unit,
A plurality of partial correlation values corresponding to the observation time, corresponding to the correlation pattern of a predetermined number of partial code sequences of the in-phase axis spreading code, from the output of all correlation processing means for the in-phase axis received signal and the orthogonal axis received signal. And a correlation value table that stores pilot signal strengths of the outputs of the plurality of complex correlation value calculators. Is characterized by.

Further, in order to achieve the above object, claim 4
The searcher receiver described, by the pseudo-noise code of the in-phase axis and the pseudo-noise code of the quadrature axis, receives the signal spread spectrum to the in-phase axis and the quadrature axis by the direct spreading method,
In the searcher receiver of the spread spectrum communication receiver that performs correlation processing with the pseudo noise code from the received signal and outputs the timing and signal strength of the received pilot signal, a storage means for storing the in-phase axis received signal in a predetermined number unit. A total correlation processing means for the in-phase axis received signal, which outputs correlation values corresponding to all correlation patterns of the in-phase axis received signal stored in the storage means, and a storage means for storing the orthogonal axis received signal in a predetermined number unit. An all-correlation processing unit for the orthogonal axis received signal, which outputs correlation values corresponding to all correlation patterns of the orthogonal axis received signal stored in the storage unit,
A plurality of partial correlation values corresponding to the observation time, corresponding to the correlation pattern of the predetermined number of partial code sequences of the orthogonal axis spread code from the output of all correlation processing means for the in-phase axis received signal and the orthogonal axis received signal. And a correlation value table that stores pilot signal strengths of the outputs of the plurality of complex correlation value calculators. Is characterized by.

Further, in order to achieve the above object, a fifth aspect is provided.
The searcher receiver described, by the pseudo-noise code of the in-phase axis and the pseudo-noise code of the quadrature axis, receives the signal spread spectrum to the in-phase axis and the quadrature axis by the direct spreading method,
The in-phase axis or quadrature axis received signal is stored in a predetermined number unit in the searcher receiver of the spread spectrum communication receiving device that performs correlation processing with the pseudo noise code from this received signal and outputs the timing and signal strength of the received pilot signal. Storing means, all-correlation processing means for outputting correlation values corresponding to all correlation patterns of the in-phase axis or quadrature-axis received signals stored in the storing means, and a plurality of in-phase axes are provided corresponding to the observation time. From the outputs of all correlation processing means for the received signal or the orthogonal axis received signal, partial correlation values corresponding to the correlation patterns of a predetermined number of partial code sequences of in-phase axis orthogonal code and orthogonal axis spread code are selected, and the selected portion is selected. A plurality of correlation value calculators that output the correlation value for the in-phase axis spreading code and the correlation value for the orthogonal axis spreading code using the correlation value, A plurality of squarers and adders that calculate the pilot signal strength by taking the square sum of the correlation value for the in-phase axis spreading code and the correlation value for the orthogonal axis spreading code, and the correlation that stores the pilot signal strength And a value table.

Further, in order to achieve the above-mentioned object, claim 6
The searcher receiver described, by the pseudo-noise code of the in-phase axis and the pseudo-noise code of the quadrature axis, receives the signal spread spectrum to the in-phase axis and the quadrature axis by the direct spreading method,
In the searcher receiver of the spread spectrum communication receiver for performing correlation processing with the pseudo noise code from the received signal and outputting the timing and signal strength of the received pilot signal, a storage means for storing the in-phase axis received signal in a predetermined number unit. , All correlation processing means for outputting correlation values corresponding to all correlation patterns of the in-phase axis received signals stored in the storage means, and a plurality of all correlation processing means provided for the in-phase axis received signals according to the observation time. From the output, select a partial correlation value corresponding to the correlation pattern of a predetermined number of partial code sequences for in-phase and orthogonal axis spreading codes, and use the selected partial correlation value to determine the correlation value for the in-phase axis spreading code. And a plurality of correlation value calculators that respectively output the correlation values for the spreading codes for the orthogonal axis, and the correlation values for the spreading code for the in-phase axis and the direct values. 2 between the correlation values with respect to the axial spreading code
The present invention is characterized by having a plurality of squarers and adders for calculating a pilot signal strength by taking a sum of multiplications, and a correlation value table for storing the pilot signal strength.

Further, in order to achieve the above object, claim 7
The searcher receiver described, by the pseudo-noise code of the in-phase axis and the pseudo-noise code of the quadrature axis, receives the signal spread spectrum to the in-phase axis and the quadrature axis by the direct spreading method,
In the searcher receiver of the spread spectrum communication receiver that performs correlation processing with the pseudo noise code from this received signal and outputs the timing and signal strength of the received pilot signal, a storage means for storing the orthogonal axis received signal in a predetermined number unit. , All correlation processing means for outputting correlation values corresponding to all correlation patterns of the quadrature received signal stored in the storage means, and a plurality of all correlation processing means provided corresponding to the observation time for the quadrature axis received signal From the output, select the partial correlation value corresponding to the correlation pattern of the predetermined number of partial code sequences of the in-phase axis and orthogonal axis spreading codes respectively, and use the selected partial correlation value, the correlation value for the in-phase axis spreading code And a plurality of correlation value calculators that respectively output the correlation values for the spreading codes for the orthogonal axis, and the correlation values for the spreading code for the in-phase axis and the direct values. 2 between the correlation values with respect to the axial spreading code
The present invention is characterized by having a plurality of squarers and adders for calculating a pilot signal strength by taking a sum of multiplications, and a correlation value table for storing the pilot signal strength.

Further, in order to achieve the above-mentioned object, claim 8
The searcher receiver described in any one of claims 1 to 7.
In the searcher receiver described, it is configured to output a partial correlation value between a predetermined number of shift registers and a plurality of adder / subtractors, and the received signal stored in the shift register and all code patterns of a predetermined number. It is characterized by having a featured total correlation processor.

Further, in order to achieve the above object, a claim 9
A searcher receiver described in any one of claims 1 to 4 is provided with a complex correlation value processor, or a correlation value processor according to claim 5 to claim 7, characterized in that the receiver for spread spectrum communication. In the searcher receiver, when selecting a partial correlation value corresponding to the input PN code from the partial correlation values corresponding to all the correlation value patterns given by the all correlation processor according to claim 8, PN
One bit of code data is regarded as a polarity bit, and when the polarity bit is positive, all the remaining bits are output as they are as select signals. When the polarity bit is negative, all the remaining bits are inverted and the select signal is output. It is characterized by outputting as.

Further, in order to achieve the above-mentioned object, claim 1
The searcher receiver according to claim 0 is the searcher receiver of the spread spectrum communication receiving device according to any one of claims 1 to 7, and the partial correlation values corresponding to all correlation value patterns given by the all correlation processing device according to claim 8. Is selected, the averaging process is performed by performing cyclic addition on the selected partial correlation values, and a value related to the correlation value of the entire sequence is obtained, and an averaging unit is provided.

[0034]

The searcher receiver of the present invention has such a configuration, and instead of taking the correlation with the same PN code over the observation window, the searcher receiver with the PN code time-shifted according to the observation window time By taking the correlation,
At the same time, the correlation output with the PN signal over the observation window, that is, the signal strength is calculated.

Correlation values corresponding to all correlation patterns (chip patterns) of a predetermined number of chips (for example, four chips) of the received signal are calculated for the received signal.

When performing the correlation processing of a plurality of PN sequences, the correlation values of all patterns are calculated for a predetermined chip length. Therefore, if there are PN sequences having the same chip pattern, this result is calculated. It can be shared and redundant operations can be omitted.

Further, when calculating the correlation value corresponding to this correlation pattern, redundancy is eliminated by unifying the polarities by using the identification by the code bit to simplify the correlation pattern and simplify the hardware configuration. Aim to reduce power consumption.

[0038]

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS A preferred embodiment of a searcher receiver of an SS communication receiving apparatus according to the present invention will be described below with reference to the drawings.

The schematic configuration of the SS communication receiver of this embodiment is the same as that of the conventional receiver shown in FIG. Connected to. The analog receiver 3 converts the supplied reception signal into a baseband signal, and receives the in-phase axis (I axis) reception signal and the quadrature axis (Q axis).
Axial) received signals are obtained and further converted into digital signals by A / D converters. Then, the in-phase axis reception signal and the quadrature axis reception signal converted into digital signals are input to the searcher receiver.

An embodiment of the present invention will be described below with reference to the drawings. FIG. 1 is a diagram showing the overall configuration of a searcher receiver in this embodiment. In the searcher receiver of this embodiment, the in-phase all-correlation processor 22 and the quadrature-axis all-correlation processor 23 calculate partial correlations with all the code sequence patterns of the respective received signals to calculate a plurality of complex correlation values. Bowl 2
The calculation result is output to 4, 25, ..., 26. The complex correlation value calculator 24 includes a PN code sequence PN _I (1), PN used for spread spectrum on the in-phase axis and the quadrature axis on the transmission side.
_Q (1) also input simultaneously, the code sequence PN _I, PN
Partial correlation values corresponding to _Q, which are given by all correlation processors, are extracted, cumulative addition is performed, the sum of squares is determined by a predetermined combination, and the pilot signal strength is calculated.
The calculation result is output to the correlation value table 27. The operations of the complex correlation value calculators 25 and 26 are similar. The PN sequence input to each complex correlation value is the PN code of the received pilot signal and the PN code whose timing is shifted according to the observation time domain. Here, the case where all cell sites use the same PN codes PN _I and PN _Q and a code whose timing is offset by an amount determined for the cell sites / sectors is shown, but for each cell site / sector When using different PN codes, the corresponding PN code may be input to the complex correlation value calculator. The signal strength of the complex correlation value calculator is output to the correlation value table 27, and the signal strength is supplied to the control processor via this correlation value table.

Here, the total correlation processors 22 and 23 divide the received signal into units of a predetermined chip (4 chips in this embodiment), calculate the received signal of this 4 chips and all partial correlation patterns, and correlate them. The value calculator 24, 25, 26 is supplied. FIG. 2 shows the configuration of all the correlation processors 22 and 23. The total correlation processors 22 and 23 are configured by combining a register 22a that sequentially stores the reception data of 4 chips and a plurality of adder / subtractors 22b to 22m. Adder / subtractor 2
The output of the fourth bit (a in the figure) of the register 22a and the data of the third bit (b) of the register 22a are input to 2b, and both data are added. Also, the adder / subtractor 22c
Is input with the third bit of the register 22a and the fourth bit of the register 22a, and the difference between the data of the fourth bit and the data of the third bit is calculated and output. Further, the data of the first bit (d in the figure) of the register 22a and the data of the second bit (c in the figure) of the register 22a are input to the adder / subtractor 22d, and both data are added and output. Further, the first bit of the register 22a and the second bit of the register 22a are input to the adder / subtractor 22e, and the difference between the data of the second bit and the data of the first bit is calculated and output. The output of the adder / subtractor 22b and the output of the adder / subtractor 22d are input to the adder / subtractor 22f, and both data are added and output. Therefore, the output from the adder / subtractor 22f is the addition result of each bit stored in the register 22a (hereinafter, this output is referred to as (++++) for convenience). The output from the adder / subtractor 22b and the output from the adder / subtractor 22e are input to the adder / subtractor 22j, and both data are added and output. Therefore, the output from the adder / subtractor 22j is the result of adding the data of the second to fourth bits of the register 22a and further subtracting the data of the first bit (hereinafter referred to as (+
++-))). In this way, the outputs from the eight adder / subtractors 22f to 22n in total are (++++) and (++
+-), (++-), (++-+), (+-++),
A partial correlation value corresponding to the correlation pattern of (+-+-), (+ ---), (+-+) is output.

Since the reception data is sequentially input to the register 22a for each chip, the adders / subtractors 22f to 22f are added.
Correlation values corresponding to these correlation patterns are output from m at every chip interval T _c . Then, the correlation values corresponding to these correlation patterns are calculated by a plurality of complex correlation value calculators 2
4, 25, 26.

In order to improve the resolution of data timing tracking, an analog receiver may supply an oversampled reception signal (for example, 4 times oversampling per chip). FIG. 3 shows a configuration example of the total correlation processor that calculates the total correlation pattern in such a case.

In FIG. 3, Tc / is stored in the register 22p.
One sample data is sequentially stored every 4 (Tc: chip interval). Then, adjacent 4-bit data is supplied to the adder 22q and degenerated to 1 bit. Then, these data determined for each Tc / 4 are supplied to the above-described register 22a, and in the same manner, a partial correlation value corresponding to the entire correlation pattern is calculated for each Tc / 4 by the adder / subtractor. . In this case, the operation of the complex correlation value calculator, which will be described later, also operates corresponding to the partial correlation value output every Tc / 4. Although FIG. 3 shows an example in which oversampled data is added, another method is also conceivable, for example, a method of extracting sample data at a rate of one out of four sample data and outputting the sample data to the register 22a.

FIG. 4 shows a complex correlation value calculator 24, 25, 2
Six configurations are shown. Complex correlation value calculator 24, 2
5,26 is, PN code PN _I, serial-to-parallel (S / P) converter 31, 35 for converting the parallel data to PN _Q in the unit (4 chips in this embodiment) predetermined chip,
Pattern processors 32 and 36 for determining the correlation value corresponding to the correlation pattern to be selected based on the PN code stored in the S / P converters 31 and 35, and this pattern processor 3
Selectors 33, 37, 39, 41 for selecting the correlation value corresponding to the correlation pattern determined in 2, 36, multipliers 34, 38, 40, 42 for polarity inversion, and an average for cyclically adding the multiplier results. It is configured to include the conversion units 45 and 46. Since the operations of the complex correlation value calculators 25 and 26 are the same, the operation of the complex correlation value calculator 24 will be described below.

The complex correlation calculator 24a is composed of a portion for calculating a correlation value between PN _I and PN _Q for the in-phase axis received signal and the quadrature axis received signal. The multiplier 34 PN codes PN _I and partial correlation value of the in-phase axis received signal and the phase axis is output to the output, orthogonal axis received signal to the multiplier 38 and PN _Q
, A partial correlation value between the in-phase axis received signal and PN _Q is output to the multiplier 40, and a partial correlation value between the orthogonal axis received signal and PN _I is output to the multiplier 42. The correlation value is output. Here, the partial correlation value means not the multiplication and integration result over the entire received signal and the PN code sequence, but the multiplication and integration result for a part thereof.

The outputs of the multipliers 34 and 35 are the adder 4
The result of the addition is averaged by the averaging unit 45, and the correlation value over the entire sequence is calculated from the partial correlation value. Similarly, the outputs of the multipliers 40 and 42 are added by the adder 44, and the addition results are averaged by the averaging unit 46, and the correlation value over the entire sequence is calculated from the partial correlation values. The outputs of the respective averaging units are squared by the squarers 47 and 48 and then accelerated by the adder 49 to generate PN _I and PN _Q.
The complex correlation value strength with is output. Here, the adder 43
Is shown in 101 of FIG. 15 and the adder 44 is shown in 102 of FIG.
The multiplier 47 is 103 in FIG. 15, and the square 48 is 1 in FIG.
02, the adder 49 corresponds to 105 in FIG. 15, and has a configuration for calculating the signal strength of the received pilot signal without being affected by the phase difference between the carriers.

As described above, the PN code PN _I (1) is supplied to the S / P converter 31 of the complex correlation value calculator 24. The S / P converter 31 every 4 chip interval 4T _c 4
In order to determine the bit, 4T _c retains its stored data. Then, the 4-bit data determined every 4T _c is supplied to the pattern processor 32. Pattern processor 32
Then, the correlation pattern output from all the correlation processors 22 is selected as follows based on the input 4-bit data of the PN code. That is, as shown in FIG.
It is determined whether the 4th bit (a in the figure) of the N code 4bit data is 1 or -1 (data is BASIC).
Then, when the fourth bit is -1, all the bits a, b, c, d are inverted to -a, -b, -c, -d.
(S102) The sign bit is set to -1 (that is, the value of the fourth bit a). Then, the select signal of the correlation value corresponding to the correlation pattern to be selected is output to the selector as the inverted bit values -b, -c, -d.

On the other hand, if NO in S101, that is, if the data of the fourth bit a is 1, the sign bit is set to the value 1 of the fourth bit (S105) and corresponds to the correlation pattern to be selected. B as the correlation value select signal,
c and d are output to the selector (S106). The operation of the pattern processor 32 will be described below based on a specific example.
Note that, for convenience, the data -1 is described as 0. Total correlation processor 2
The received data stored every 1 T _c is input to the 4-bit register 22a of 2 and the content of the shift register is (100
0), (0100), (0010), (1001). It is also assumed that the PN code data stored in the shift S / P converter 31 of the complex correlation value calculator 24 during this 4T _c is (1000). At this time, S /
Since the value of the fourth bit of the P converter 31 is 1, the sign bit becomes 1 and (000) as the select signal.
Will be output for 4 Tc. Hereinafter, similarly, different selector signals are output from the pattern processor 32 to the selector every 4T _c . Here, the select signal indicates which correlation value corresponding to the correlation pattern (++++, ++++, etc.) output from the above-described all correlation processors 22 is selected, and 1 is + and 0 is −. Therefore, when the select signal output from the pattern processor 32 is (000), the correlation value selected is the correlation pattern (+ / −−) output from the adder / subtractor 22g of all the correlation processors 22. −) Correlation value corresponding to. Therefore, when the received data stored in the shift register 22a is (1000), the adder / subtractor 22g outputs (+
The correlation value 4 corresponding to the correlation pattern of ---) is output. This indicates that the correlation value between (1000) and (1000) is 4. Also, when (0100) is input to the shift register 22a, the selected pattern is the same as (1000), that is, the pattern of (000), that is, the output from the multiplier 22g is selected. The value 0 is selected and output. This is (100
The correlation value between 0) and (0100) is 0. Further, the S / P converter 31 outputs the PN code data (10
00) is stored and 4T _c has passed, a new P
It is assumed that (1100) is stored in the N code data. S
While 1100 is output from the / P converter 31, the received data stored in the shift register 22a of the total correlation processor 22 is (1100), (0110), (1011),
It is assumed that it has changed to (0101). In this case, since (1100) is stored in the S / P converter 31 of the complex correlation value calculator 23, the select signal output from the pattern processor 32 is (100). Of the correlation patterns calculated by the correlation processor 22, (++-
The correlation value corresponding to the correlation pattern corresponding to −) will be selected. Therefore, when the received data stored in the shift register 22a is (1100), the correlation value 4 output from the adder / subtractor 22g is output. This indicates that the correlation value between (1100) and (1100) is 4. Similarly, the shift register 22a
When the data (0110) after the next T _c is input to, the correlation value becomes 0. The correlation value is obtained by subtracting the number of bit mismatches from the number of bit matches. For example, (1100) and (1100) are 4
Since the bits also match, the correlation value is 4, and (11
00) and (0110) have a match count of 2 (the second bit and the fourth bit).
Since the number of mismatches is 2 (1st bit and 3rd bit), the correlation value is 2−2 = 0.

The selector 3 of the complex correlation value calculator 24
The output from 3 is also input to the multiplier, but when the 4th bit of the PN code is -1 in the pattern processor 32, the sign bit is used to invert the obtained correlation value. This is for multiplying the sign of. For example, the S / P converter 3
Consider the case where the PN code (0111) is input to 1.
In this case, since the data of the fourth bit is 0, that is, -1, the sign bit is -1, and the select signal is the inverted bit (000) of the remaining bits. Therefore, the selected correlation pattern is the output (+ ---) from the adder / subtractor 22g.
However, the correlation pattern corresponding to the PN code (0111) is (-++++). Therefore, in order to restore this original correlation pattern, the original correlation value can be obtained by multiplying the output from the selector 33 by the sign bit -1.

The above operation is the same for the orthogonal axis received signal and the PN code, and the PN code PN _Q (1) is stored in the S / P converter 35 every 4T _c and output from the total correlation processor 23. Among the correlation values corresponding to each correlation pattern, the correlation value corresponding to the desired correlation pattern is determined and output for each T _c . Then, the correlation value output obtained in this manner is used for the orthogonal axis received signal given by the multiplier 38 and the PN _Q
The correlation value output with (1) and the adder 43 add,
It is supplied to the averaging unit mean45. FIG. 6 shows the configuration of the averaging units 45 and 46 of this embodiment, which is a configuration in which the correlation values output from the selectors 33 and 37 for each T _c are cyclically added to perform averaging. That is, each of the averaging units 45 and 46 has a register and sequentially performs predetermined weighting and averaging without confusing the correlation value given for each Tc, and calculates the correlation value over the entire sequence. The effect of noise is removed.

The manner in which the signal timing of the pilot signal from the cell site is searched using the searcher receiver which operates as described above will be described below. still,
The handling of the in-phase axis and quadrature axis received signals in the case where there is a phase difference between the carrier wave of the reception path signal and the carrier wave used in the analog receiver is the same as that described with reference to FIG. Only the part will be described. Now, the PN _I code used on a pilot signal transmitted from one cell site (000 100 110
1011110). This pilot signal arrives as a signal having a different delay time due to multipath propagation, and it is assumed that the received signal of one of these pilot signals arrives at the signal timing shown in FIG. 9 (1). The first 4 bits are stored in the shift register 22a, and the input data shifts to the right one by one as shown in (2) to (16) for each chip time unit. As a result, the contents of the shift register 22a are square. It changes like the part surrounded by. Data enclosed in the drawing [] corresponds to the PN _I code of the next period. In the case of this embodiment, since the predetermined number of chips of all the correlation processors is 4, four PN sequences PN _I (1), in which the PN code is shifted by 4 chips, are searched for the signal timing of this pilot signal.
Prepare PN _I (2), PN _I (3), and PN _I (4) with the searcher receiver. That is, four complex correlation value calculators are prepared. PN _I (1) to PN prepared in Figure 10
_I (4) is shown. S / P that stores PN _I (1)
The converter 31 is fixed in units of 4 chips. That is, FIG.
As shown in 0, 000 in the time of the first 4-chip unit
1, next is 0011, next is 0101, and last is 1110
Is. When the left end is the first bit, the rightmost fourth bit is used as the sign bit. PN _I (2)
The same applies to PN _I (4). The symbol S is used to indicate the state of the pattern fixed in units of 4 chips.
1, S2, S3, S4 are shown in FIG.

FIG. 11 shows the contents of the shift register 22a and the contents of the S / P converter 31 corresponding to FIGS. 9 and 10 corresponding to the time timings (1) to (16) in FIG. At the same time, the output of the selector 33 and the output value of the multiplier at each timing are also shown. The output of the selector 33 has the values shown in FIG. 11 because the total correlation processor 22 and the complex correlation value calculator 2 described above are used.
It is clear from the explanation of the operation of No. 4. In this case, since the encoded bits S1, S2, S3 are 1 and only S4 is 0, the polarity inversion at the output of the multiplier is S4.
Only. The right column of FIG. 11 shows the output of the cyclic adder 45. Here, the case where the weight of the cyclic adder is 1 (r = 1) is shown. When the weight is 1, the addition is simple. For example, in (5), the output (= 4) of the multiplier (= 4) obtained at the timing of (5) is added to the content (= 4) of the cyclic adder of (1). And new content (= 8), and in (7), a new value (=-) obtained by adding the multiplier output (= -2) of (7) to the content (= 0) of 45 of (3). 2)
Becomes From timing (13) to timing (1
Over 6) switch of FIG. 6 16,0,0,0 as the value of the correlation value A (1) for PN _I (1) when turned ON by the control of the CLK signal is continuously output. To show the temporal correspondence of these four values, in FIG.
The symbols A (1) a, A (1) b, A (1) c, and A (1) d are attached. It should be noted that the read control of the cyclic adder 45 by CLK is appropriately set by the period of the PN code or the like, or by the averaging time for removing the influence of noise or the like. Although not shown in the figure, CLK
Therefore, when the correlation value is output, the contents of the register may be cleared as necessary.

The same operation as described above is performed by the PN.
_{Also for I} (2), the output value at each timing (1) to (16) in the correlation value calculator 24 is shown.

Similar correlation values are calculated for PN _I (3) and PN _I (4). As a result, the correlation values shown in FIG. 13 are output for A (1) to A (4). This value is the target PN code (0001
It is nothing but the autocorrelation function of 00110101110). Therefore, the structure of the searcher receiver according to the present invention enables the correlation processing of the pilot signal to the PN. Even when the same pilot signal arrives at the receiver with different delay times due to multipath propagation, it is received as a linearly added signal. With the strength corresponding to the received electric field of, the correlation value is obtained in the form of being added to the value of FIG. Further, even when there is a phase difference between carrier waves, the signal strength can be detected by taking the square sum of the correlation value outputs with respect to the coaxial and orthogonal axes as shown in FIG.
Therefore, the searcher receiver according to the present invention can obtain the signal power corresponding to the signal strength in a limited time (here, the timing from (13) to (16)), and the relationship between the arrival time and the signal strength is clear. Therefore, by storing this result in the correlation value table and outputting it to the control processor, the function as a searcher receiver is realized.

Also, when pilot signals by multipath propagation from other cell sites are simultaneously received,
The delay time and the signal strength can be obtained by preparing the PN code used for the pilot signal in the same manner as in the above-described embodiment and performing the same processing. FIG. 14 is a diagram showing that the hardware scale by the pattern processor can be reduced. In order to perform the 4-bit total correlation, it is originally necessary to perform 2 ⁴ = 16 patterns, but according to the searcher receiver according to the present invention, the leftmost bit of the selected pattern can be seen from FIG. By setting 1 to 1, only 2 ³ = 8 patterns need to be calculated, and the number of calculations is reduced by half. Then, when the same select signal is obtained in the same state, the calculation results of all the correlation processors can be shared,
Eliminates redundant calculations. In FIG. 14, PN (1) and PN (4) are S1 and PN (3) and PN (4) are S2.
Then, PN (2) and PN (3) are S3, and PN (1) and P
N (2) shares the operation result in S4. Although the PN code having a very short code length of 16 has been shown in the embodiment, the degree of sharing is small, but when searching for a pilot signal of a longer code length, the PN code to be prepared (shown in FIG. 1). PN (j), j = 1, 2, ...
・ The number of n) increases. The larger n becomes, the more P
Due to the random nature of the N code, the degree of sharing the correlation value according to the code pattern calculated by all the correlation processors increases, and accordingly, the degree of efficiency increases by not performing redundant calculation. That is, since there are a large number of PN (j) having the same pattern in units of 4 chips and the calculation result for obtaining the correlation value according to the correlation pattern can be used, it is necessary to perform redundant correlation calculation. Disappears. For example, if the number of codes is from PN (1) to PN (40), these select signals are 000 to 11
It is one of eight ways to 1 and is 40 / on average
It is possible to commonly use the calculation results of the partial correlation values corresponding to the select patterns of about 8 = 5.

In the present invention, instead of taking the correlation with the same PN code over the observation window, the correlation with the PN code time-shifted according to the observation window time is taken, so that the observation window is simultaneously reached. Since this is a method of calculating the correlation output with the PN code, that is, the signal strength, it is necessary to simultaneously supply PN codes that are time-shifted with the same PN code. As a method of supplying this, P
A method of storing the N code in a memory such as a ROM and controlling the calling address of the ROM is conceivable, but the method described below can also be used.

In the above-mentioned US Pat. No. 5,103,459, 1
From the M-sequence code with a sequence length of 32767 generated by the 5-stage shift register, a P with a sequence length of 32768, which is obtained by inserting a chip zero after 14 consecutive chip zeros, is obtained.
N code is used for the pilot signal. Such P
As a method of obtaining a time-shifted PN code when the N code is used, a method shown in FIG. 7 can be considered. This utilizes the Cycle And Add characteristic of the M-sequence code, and utilizes the property that the sum of the M-sequence codes with different delay amounts becomes the M-sequence obtained by shifting the original sequence by a specific time. is doing. However, that is, since the content in the shift register is the M-sequence code,
Even if the values taken from different stages are added, the original M
The fact that a time-shifted version of the sequence code is obtained is used to determine in the mask pattern whether the contents of each shift register should be included or not added. By appropriately defining the mask pattern in this way, it is possible to obtain a PN code that is shifted in any time. However, in the above-described embodiment, the corrected PN sequence is used instead of the M sequence code. In order to cope with this, FIG. 7 is provided with a gate circuit in the clock portion for controlling the shift of the shift register, and when the contents of the shift register at the stage of outputting 14 chip zeros are decoded, the CNTR
This circuit outputs the L signal and stops the shift register shift for one chip clock. That is, if the decoder outputs a CNTRL signal as shown in FIG. 7B at the moment of being decoded, the SYSCLK and CNTRL signal and
As a result, GENCLK is stopped for one chip clock. A desired time-shifted PN sequence can be obtained by using this circuit.

As described above, in the present embodiment, it is possible to reduce the calculation amount by half (16 to 8) by assuming all the correlation patterns of the received data and distinguishing the polarities of the correlation patterns by the code bits of the PN code. Therefore, it is possible to reduce the hardware scale and power consumption.

In this embodiment, the processing unit of all correlation processors is four chips. This is because the window size of the pilot signal to be searched and the number of pilot signals to be searched (the number of cell sites). Alternatively, it may be set according to the number of sectors), and is not particularly limited in the present invention. If the processing unit is 2 chips or more, the operation as described in the embodiment is executed, and the same effect is obtained depending on the processing unit, the window size, and the number of pilot signals.

FIG. 16 shows another embodiment of the complex correlation value calculator according to the present invention. Further, FIG. 17 shows the entire configuration for removing the influence of the above-mentioned phase difference between carrier waves. In FIG. 15, for the in-phase axis received signal, PN
_I, obtains a correlation value between PN _Q, the correlation value between the PN _I, PN _Q with respect to the orthogonal axis received signal at the same time, was calculated pilot signal strength using four correlation values, the present embodiment in is configured to determine only the correlation value between PN _I also orthogonal axes received signal also phase axis received signal. However, each, cos [theta], because the term including sinθ is obtained by obtaining these square sum, albeit only for PN _I, it is possible to obtain a value for the pilot signal strength. From Figure 16,
Compared to FIG. Since the number of pattern processors and selectors is halved, the circuit scale is significantly reduced.

FIG. 18 shows another embodiment of the complex correlation value calculator according to the present invention. Further, FIG. 19 shows the entire configuration for removing the influence of the above-mentioned phase difference between carrier waves. While FIG. 16 finds the correlation value for PN _I , FIG. 18 is configured to calculate the pilot signal strength using PN _Q. With this configuration, PN
_Although it is only for _Q , a value relating to the pilot signal strength can be obtained, and the number of pattern processors and selectors is halved compared to FIG. 4, so the circuit scale is significantly reduced.

FIG. 20 shows another embodiment of the searcher receiver according to the present invention. In the embodiment described above,
In contrast to the configuration in which the pilot signal strength is obtained using the in-phase axis reception signal and the quadrature axis reception signal, in the present embodiment, the pilot signal strength is obtained using only the in-phase axis reception signal. Since only the in-phase axis received signal is handled, the correlation value is calculated from the complex correlation value calculator to the correlation value calculator, and the squared sum of the respective outputs is calculated to obtain the pilot signal strength. FIG. 21 shows an outline of this method. From the correlator output using PN _I , PN
_The correlation value for I is obtained and the correlation value for PN _Q is obtained from the correlator output using PN _Q. R _I (τ),
R _Q (tau) is originally an autocorrelation function of the different codes, so PN _I, PN _Q are transmitted synchronously from the base station, both tau = 0 at 1, otherwise, the average Has a small value that becomes zero, the signal strength can be obtained even if handled in the same way in the sense of measuring the pilot signal strength. In FIG. 21, R _I (τ) = R _Q (τ) = R
A method of removing the influence of the phase difference by treating it as (τ) is disclosed.

FIG. 22 shows an embodiment of the correlation value calculator used in the searcher receiver shown in FIG. The correlation value calculator includes an S / P converter, a pattern processor,
The operation of each unit including the selector and the averaging unit is the same as that of the complex correlation value calculator.

In the embodiment of FIG. 20, the obtained pilot signal strength is halved compared to the case of using the complex correlation value calculator of FIG. It is reduced.

FIG. 23 shows another embodiment of the searcher receiver according to the present invention. In the embodiment of FIG. 20,
In contrast to the configuration in which the pilot signal strength is obtained from the received signal on the in-phase axis, FIG. 23 is configured to obtain the pilot signal strength from the received signal on the orthogonal axis. FIG. 24 shows a signal structure corresponding to FIG. 23 for removing the influence of the phase difference. As in the case of FIG. 21, R _I (τ), R
By treating _Q (τ) in the same way, the signal strength is obtained.

Although all of the above-described embodiments have been described as operating on the pilot signal, since basically the sum of squares operation for removing the phase difference between the carrier waves is performed, the data modulation is applied. It is possible to scan even such signals by setting the output timing of the averaging unit in units of data intervals.

Further, since the correlation value table has a buffer memory-like function for notifying the control processor of the signal strength, it may be omitted depending on the situation, such as when the access time to the control processor is sufficiently fast. It is possible.

It is also possible to provide a threshold at the output of the complex correlation value calculation and the output of the correlation value calculator so as to give a pilot signal strength and timing higher than the threshold.

[0070]

As described above, according to the searcher receiver of the spread spectrum communication receiver according to the present invention, the redundancy of the correlation calculation can be eliminated and the received signal can be searched with a simple structure.

[Brief description of drawings]

FIG. 1 is an overall configuration block diagram of a searcher receiver in this embodiment.

FIG. 2 is a configuration diagram of a total correlation processor in the embodiment.

FIG. 3 is a block diagram of another configuration of the total correlation processor in the embodiment.

FIG. 4 is a configuration block diagram of a complex correlation value calculator in the embodiment.

FIG. 5 is an operation flowchart of the pattern processor in the embodiment.

FIG. 6 is a configuration diagram of an averaging unit in the embodiment.

FIG. 7 is a configuration diagram of a PN code generator in the present embodiment.

FIG. 8 is a configuration block diagram of a conventional device.

FIG. 9 is a diagram for explaining the operation of the searcher receiver.

FIG. 10 is a diagram illustrating an operation of a searcher receiver.

FIG. 11 is a diagram for explaining the operation of the searcher receiver.

FIG. 12 is a diagram for explaining the operation of the searcher receiver.

FIG. 13 is a diagram for explaining the operation of the searcher receiver.

FIG. 14 is an explanatory diagram in which the hardware scale can be reduced by the pattern processor.

FIG. 15 is a diagram showing a conventional connection configuration for removing a phase difference between carrier waves.

FIG. 16 is a configuration block diagram of a complex correlation value calculator in another embodiment according to the present invention.

FIG. 17 is a diagram illustrating the connection configuration of FIG. 16.

FIG. 18 is a configuration block diagram of a complex correlation value calculator in another embodiment according to the present invention.

FIG. 19 is a diagram illustrating the connection configuration of FIG. 18.

FIG. 20 is an overall configuration block diagram of a searcher receiver in another embodiment according to the present invention.

FIG. 21 is a diagram illustrating the connection configuration of FIG. 20.

FIG. 22 is a configuration block diagram of a correlation value calculator according to the present invention.

FIG. 23 is an overall configuration block diagram of a searcher receiver in another embodiment according to the present invention.

FIG. 24 is a diagram illustrating the connection configuration of FIG. 23.

[Explanation of symbols]

 5,20 Searcher receiver 6,7 Digital data receiver 22 Total correlation processor 23,24,25 Correlation value calculator

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[Procedure amendment]

[Submission date] September 8, 1993

[Procedure Amendment 1]

[Document name to be amended] Statement

[Name of item to be amended] Claims

[Correction method] Change

[Correction content]

[Claims]

[Procedure Amendment 2]

[Document name to be amended] Statement

[Correction target item name] 0013

[Correction method] Change

[Correction content]

[0013] _{= ρ i A [PN I (} t i) cosθ i - PN Q (t i) sinθ i] + jρ i A [PN Q (t i) cosθ i + PN I (t i) sinθ i] of the above equation The real number component is input as an in-phase axis received signal and the imaginary number component is input as an orthogonal axis received signal from the analog receiver. In addition,
In addition to this, received pilot signals from different paths, received pilot signals from different sectors at different cell sites and the same cell site, etc. are also included.

[Procedure 3]

[Document name to be amended] Statement

[Correction target item name] 0014

[Correction method] Change

[Correction content]

[0014] phase-axis received signal correlator PN _I, correlator P
Input to N _Q. In the correlator PN _I , the input signal is correlated with the PN code PN _I '(' indicates the same PN code, but the timings do not always match). Similarly, the correlator PN _Q correlates the input signal with the PN code PN _Q '. Correlation means
This means multiplying the input signal by the PN code and integrating. When the integration time is T, the output of the correlator _{PN I, ∫ρ i A [PN} I cosθ i -PN Q sinθ i] PN I 'dt = ρ i A∫ [PN I PN I' cosθ i -PN Q PN _I 'sin θ _i ] dt By the way, PN _Q and PN _I are PN codes different from each other, and due to the nature of the PN code, it becomes zero on average at all timings, so the correlator PN _I output is approximately It is shown by the formula.

[Procedure amendment 4]

[Document name to be amended] Statement

[Correction target item name] 0039

[Correction method] Change

[Correction content]

The schematic configuration of the SS communication receiver of this embodiment is the same as that of the conventional receiver shown in FIG. Connected to. The analog receiver 3 converts the supplied reception signal into a baseband signal, and receives the in-phase axis (I axis) reception signal and the quadrature axis (Q axis).
Axial) received signals are obtained and further converted into digital signals by A / D converters. Then, the in-phase axis reception signal and the quadrature axis reception signal converted into digital signals are input to the searcher receiver.

[Procedure Amendment 5]

[Document name to be amended] Statement

[Name of item to be corrected] 0045

[Correction method] Change

[Correction content]

FIG. 4 shows a complex correlation value calculator 24, 25, 2
Six configurations are shown. Complex correlation value calculator 24, 2
5,26 is, PN code PN _I, serial-to-parallel (S / P) converter 31, 35 for converting the parallel data to PN _Q in the unit (4 chips in this embodiment) predetermined chip,
Pattern processors 32 and 36 for determining the correlation value corresponding to the correlation pattern to be selected based on the PN code stored in the S / P converters 31 and 35, and this pattern processor 3
Selectors 33, 37, 39, 41 for selecting a correlation value corresponding to the correlation pattern determined in 2, 36, and if necessary.
Correspondingly is configured to include an averaging unit 45, 46 which cyclic addition multipliers 34,38,40,42 and the multiplier result polarity reversal. Here, the complex correlation value calculator 25, 2
Since the operation of 6 is the same, hereinafter, the complex correlation value calculator 24
The operation of will be described.

[Procedure correction 6]

[Document name to be amended] Statement

[Correction target item name] 0046

[Correction method] Change

[Correction content]

The complex correlation calculator 24a is composed of a portion for calculating a correlation value between PN _I and PN _Q for the in-phase axis received signal and the quadrature axis received signal. The multiplier 34 PN codes PN _I and partial correlation value of the in-phase axis received signal and the phase axis is output to the output, orthogonal axis received signal to the multiplier 38 and PN _Q
, A partial correlation value between the in-phase axis received signal and PN _Q is output to the multiplier 40, and a partial correlation value between the orthogonal axis received signal and PN _I is output to the multiplier 42. The correlation value is output. Here, indicates that a partial correlation value, instead of the multiplication result of integration over the entire received signal and the PN code sequence, a multiplication result of integration with respect to a portion the same aspirations.

[Procedure Amendment 7]

[Document name to be amended] Statement

[Correction target item name] 0047

[Correction method] Change

[Correction content]

The outputs of the multipliers 34 and 38 are the adder 4
The result of the addition is averaged by the averaging unit 45, and the correlation value over the entire sequence is calculated from the partial correlation value. Similarly, the outputs of the multipliers 40 and 42 are added by the adder 44, and the addition results are averaged by the averaging unit 46, and the correlation value over the entire sequence is calculated from the partial correlation values. The outputs of the respective averaging units are squared by the squarers 47 and 48 and then accelerated by the adder 49 to generate PN _I and PN _Q.
The complex correlation value strength with is output. Here, the adder 43
Is shown in 101 of FIG. 15 and the adder 44 is shown in 102 of FIG.
The multiplier 47 is 103 in FIG. 15, and the square 48 is 1 in FIG.
02, the adder 49 corresponds to 104 in FIG. 15, and has a configuration for calculating the signal strength of the received pilot signal without being affected by the phase difference between the carriers described above.

[Procedure Amendment 8]

[Document name to be amended] Statement

[Correction target item name] 0048

[Correction method] Change

[Correction content]

As described above, the PN code PN _I (1) is supplied to the S / P converter 31 of the complex correlation value calculator 24. The S / P converter 31 every 4 chip interval 4T _c 4
In order to determine the bit, 4T _c retains its stored data. Then, the 4-bit data determined every 4T _c is supplied to the pattern processor 32. Pattern processor 32
Then, the correlation pattern output from all the correlation processors 22 is selected as follows based on the input 4-bit data of the PN code. That is, as shown in FIG.
It is determined whether the 4th bit (a in the figure) of the N code 4bit data is 1 or -1 (data is binary ). If the fourth bit is -1, all bits a, b, c, d are inverted to -a, -b, -c, -d (S102). , The value of the fourth bit a). Then, the select signal of the correlation value corresponding to the correlation pattern to be selected is output to the selector as the inverted bit values -b, -c, -d.

[Procedure Amendment 9]

[Document name to be amended] Statement

[Correction target item name] 0049

[Correction method] Change

[Correction content]

On the other hand, if NO in S101, that is, if the data of the fourth bit a is 1, the sign bit is set to the value 1 of the fourth bit (S105) and corresponds to the correlation pattern to be selected. B as the correlation value select signal,
c and d are output to the selector (S106). The operation of the pattern processor 32 will be described below based on a specific example.
Note that, for convenience, the data -1 is described as 0. Total correlation processor 2
The received data stored every 1 T _c is input to the 4-bit register 22a of 2 and the content of the shift register is (100
0), (0100), (0010), (1001). It is also assumed that the PN code data stored in the shift S / P converter 31 of the complex correlation value calculator 24 during this 4T _c is (1000). At this time, S /
Since the value of the fourth bit of the P converter 31 is 1, the sign bit becomes 1 and (000) as the select signal.
Will be output for 4 Tc. Hereinafter, similarly, different selector signals are output from the pattern processor 32 to the selector every 4T _c . Here, the select signal indicates which correlation value corresponding to the correlation pattern (++++, ++++, etc.) output from the above-described all correlation processors 22 is selected, and 1 is + and 0 is −. Therefore, when the select signal output from the pattern processor 32 is (000), the correlation value selected is the correlation pattern (+ -−) output from the adder / subtractor 22 i of all the correlation processors 22. It becomes a correlation value corresponding to −−). Therefore, when the received data stored in the shift register 22a is (1000), the adder / subtractor 22 i (+
The correlation value 4 corresponding to the correlation pattern of ---) is output. This indicates that the correlation value between (1000) and (1000) is 4. Also, when the shift register 22a is (0100) is input, the pattern selected pattern in the same manner as previously described (1000) (000), that is, the output from the acceleration adder 22 i is selected , The output value 0 is selected and output. This is (100
The correlation value between 0) and (0100) is 0. Further, the S / P converter 31 outputs the PN code data (10
00) is stored and 4T _c has passed, a new P
And N code data (1100) is stored. S / P
While the converter 31 outputs 1100, the received data stored in the shift register 22a of the total correlation processor 22 is (1100), (0110), (1011), (0
101). In this case, since (1100) is stored in the S / P converter 31 of the complex correlation value calculator 23, the select signal output from the pattern processor 32 is (100). Among the correlation patterns calculated by the correlation processor 22, (++ ---)
The correlation value corresponding to the correlation pattern corresponding to is selected. Therefore, when the received data stored in the shift register 22a is (1100), the adder / subtractor 2
Correlation value 4 output from 2g is output.
This indicates that the correlation value between (1100) and (1100) is 4. Similarly, when the data (0110) after the next T _c is input to the shift register 22a,
The correlation value becomes 0. The correlation value is obtained by subtracting the number of bit mismatches from the number of bit matches. For example, since (1100) and (1100) match with 4 bits, the correlation value is 4, and (110
Since 0) and (0110) have a match count of 2 (the second bit and the fourth bit) and a mismatch count of 2 (the first bit and the third bit), the correlation value is 2−2 = 0.

[Procedure Amendment 10]

[Document name to be amended] Statement

[Correction target item name] 0055

[Correction method] Change

[Correction content]

Similar correlation values are calculated for PN _I (3) and PN _I (4). As a result, the correlation values shown in FIG. 13 are output for A (1) to A (4). This value is the target PN code (0001
It is nothing but the autocorrelation function of 00110101110). Therefore, the structure of the searcher receiver according to the present invention enables the correlation processing of the pilot signal to the PN. Even when the same pilot signal arrives at the receiver with different delay times due to multipath propagation, it is received as a linearly added signal. With the strength corresponding to the received electric field of, the correlation value is obtained in the form of being added to the value of FIG. Further, as shown in FIG. 4 even when the phase difference between the carrier waves are present, it is possible to detect the signal intensity by taking the sum of squares of the correlation value output for the phase axis, orthogonal axes. Therefore, the searcher receiver according to the present invention allows a limited time (here, (13) to (16)).
The signal power corresponding to the signal strength can be obtained at the timing of (1), and the relationship between the arrival time and the signal strength becomes clear. By storing this result in the correlation value table and outputting it to the control processor, the searcher receiver The function as is realized.

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Claims (10)

[Claims] 1. A signal, which is spectrum-spread with respect to an in-phase axis and a quadrature axis by a direct spreading method, is received by a pseudo-noise code of the in-phase axis and a pseudo-noise code of the quadrature axis. In a searcher receiver device of a spread spectrum communication receiving device that performs correlation processing and outputs the timing and signal strength of a received pilot signal, a storage unit that stores in-phase axis received signals in a predetermined number unit, All correlation processing means for the in-phase axis received signal, which outputs correlation values corresponding to all correlation patterns of the in-phase axis received signal, storage means for storing the quadrature axis received signal in a predetermined number unit, and the storage means stored in the storage means. All correlation processing means for the orthogonal axis received signal, which outputs correlation values corresponding to all correlation patterns of the orthogonal axis received signal, and a plurality of sets corresponding to the observation time. A partial correlation value corresponding to a correlation pattern of a predetermined number of partial code sequences of the in-phase axis spreading code or the orthogonal axis spreading code is selected from all correlation processing means outputs for the in-phase axis received signal and the orthogonal axis received signal. And a complex correlation value calculator that outputs a pilot signal strength using the selected partial correlation value, and a correlation value table that stores the pilot signal strength of the plurality of complex correlation value calculator outputs. Searcher receiver for the spread spectrum communication receiver. 2. A signal, which is spectrum-spread with respect to the in-phase axis and the orthogonal axis by the direct spreading method, is received by the pseudo-noise code of the in-phase axis and the pseudo-noise code of the orthogonal axis, and the correlation with the pseudo-noise code is obtained from the received signal. In a searcher receiver of a receiver for spread spectrum communication that performs processing and outputs the timing and signal strength of a received pilot signal, in-phase axis storage means for storing a received signal in a predetermined number unit, and in-phase axis stored in the storage means All correlation processing means for the in-phase axis received signal that outputs correlation values corresponding to all correlation patterns of the received signal, storage means for storing the orthogonal axis received signal in a predetermined number unit, and the orthogonal axis stored in the storage means All the correlation processing means for the orthogonal axis received signal that outputs the correlation values corresponding to all the correlation patterns of the received signal, and a plurality of them are provided corresponding to the observation time. , A partial correlation value corresponding to a correlation pattern of a predetermined number of partial code sequences of in-phase axis spreading code and orthogonal axis spreading code is selected from all correlation processing means outputs for the in-phase axis received signal and the orthogonal axis received signal. And a complex correlation value calculator that outputs a pilot signal strength using the selected partial correlation value, and a correlation value table that stores the pilot signal strength of the plurality of complex correlation value calculator outputs. Searcher receiver for spread spectrum communication receiver. 3. A signal, which is spectrum-spread with respect to the in-phase axis and the orthogonal axis by a direct spreading method, is received by the pseudo-noise signal of the in-phase axis and the pseudo-noise code of the orthogonal axis, and the correlation with the pseudo-noise code is obtained from the received signal. In a searcher receiver of a receiver for spread spectrum communication that performs processing and outputs the timing and signal strength of a received pilot signal, in-phase axis storage means for storing a received signal in a predetermined number unit, and in-phase axis stored in the storage means All correlation processing means for the in-phase axis received signal that outputs correlation values corresponding to all correlation patterns of the received signal, storage means for storing the orthogonal axis received signal in a predetermined number unit, and the orthogonal axis stored in the storage means All the correlation processing means for the orthogonal axis received signal that outputs the correlation values corresponding to all the correlation patterns of the received signal, and a plurality of them are provided corresponding to the observation time. , A partial correlation value corresponding to the correlation pattern of a predetermined number of partial code sequences of the in-phase axis spreading code is selected from all the correlation processing means outputs for the in-phase axis received signal and the orthogonal axis received signal, and the selected part Reception for spread spectrum communication, comprising: a complex correlation value calculator that outputs a pilot signal strength by using a correlation value; and a correlation value table that stores pilot signal strengths of the outputs of the plurality of complex correlation value calculators. Equipment searcher receiver. 4. A signal, which is spectrum-spread with respect to the in-phase axis and the orthogonal axis by a direct spreading method, is received by the pseudo-noise code of the in-phase axis and the pseudo-noise code of the orthogonal axis, and the correlation with the pseudo-noise code is obtained from the received signal. In a searcher receiver of a receiver for spread spectrum communication that performs processing and outputs the timing and signal strength of a received pilot signal, in-phase axis storage means for storing a received signal in a predetermined number unit, and in-phase axis stored in the storage means All correlation processing means for the in-phase axis received signal that outputs correlation values corresponding to all correlation patterns of the received signal, storage means for storing the orthogonal axis received signal in a predetermined number unit, and the orthogonal axis stored in the storage means All the correlation processing means for the orthogonal axis received signal that outputs the correlation values corresponding to all the correlation patterns of the received signal, and a plurality of them are provided corresponding to the observation time. , A partial correlation value corresponding to a correlation pattern of a predetermined number of partial code sequences of the orthogonal axis spread code is selected from all the correlation processing means outputs for the in-phase axis received signal and the orthogonal axis received signal, and the selected part Reception for spread spectrum communication, comprising: a complex correlation value calculator that outputs a pilot signal strength by using a correlation value; and a correlation value table that stores pilot signal strengths of the outputs of the plurality of complex correlation value calculators. Equipment searcher receiver. 5. A signal, which is spectrum-spread with respect to the in-phase axis and the orthogonal axis by the direct spreading method, is received by the pseudo-noise code of the in-phase axis and the pseudo-noise code of the orthogonal axis, and the correlation with the pseudo-noise code is obtained from the received signal. In the searcher receiver of the receiver for spread spectrum communication that performs processing and outputs the timing and signal strength of the received pilot signal, storage means for storing in-phase axis or quadrature axis received signals in a predetermined number unit, and stored in the storage means. All correlation processing means for outputting correlation values corresponding to all correlation patterns of the in-phase axis or quadrature axis received signals, and a plurality of correlation processing means provided corresponding to the observation time for all in-phase axis received signals or quadrature axis received signals. From the output of the correlation processing means, partial correlation values corresponding to the correlation patterns of a predetermined number of partial code sequences of in-phase axis and orthogonal axis spreading codes are respectively obtained. A plurality of correlation value calculators that output a correlation value for the in-phase axis spreading code and a correlation value for the orthogonal axis spreading code using the selected partial correlation value, and a correlation value for the in-phase axis spreading code And a plurality of squarers and adders for calculating the pilot signal strength by taking the square sum of the correlation value for the orthogonal axis spreading code, and a correlation value table for storing the pilot signal strength. Searcher receiver for spread spectrum communication receiver. 6. A signal, which is spread spectrum with respect to an in-phase axis and a quadrature axis by a direct spreading method by a pseudo-noise code of the in-phase axis and a pseudo-noise code of the quadrature axis, is correlated with the pseudo-noise code from the received signal. In the searcher receiver of the receiver for spread spectrum communication that performs processing and outputs the timing and signal strength of the received pilot signal, a storage unit that stores the in-phase axis received signal in a predetermined number unit, and an in-phase axis that is stored in the storage unit. All correlation processing means for outputting correlation values corresponding to all correlation patterns of the received signal, and a plurality of correlation processing means provided in accordance with the observation time, from the output of all correlation processing means for the in-phase axis received signal, for the in-phase axis and the quadrature axis A partial correlation value corresponding to the correlation pattern of a predetermined number of partial code sequences of the spread code is selected, and in-phase axis spreading is performed using the selected partial correlation value. A plurality of correlation value calculators that respectively output a correlation value for the code and a correlation value for the orthogonal axis spreading code, and a square sum of the correlation value for the in-phase axis spreading code and the correlation value for the orthogonal axis spreading code. A searcher receiver for a spread spectrum communication receiver, comprising: a plurality of squarers and adders for calculating pilot signal strength; and a correlation value table for storing the pilot signal strength. 7. A signal, which is spectrum-spread with respect to the in-phase axis and the orthogonal axis by a direct spreading method, is received by the pseudo-noise code of the in-phase axis and the pseudo-noise code of the orthogonal axis, and the correlation with the pseudo-noise code is obtained from the received signal. In a searcher receiver of a spread spectrum communication receiver that performs processing and outputs the timing and signal strength of a received pilot signal, a storage unit that stores a predetermined number of orthogonal axis reception signals, and an orthogonal reception unit that is stored in the storage unit. All correlation processing means for outputting correlation values corresponding to all correlation patterns of the signal, and a plurality of correlation processing means provided corresponding to the observation time, from all correlation processing means outputs for the quadrature axis received signal, for in-phase axis and quadrature axis A partial correlation value corresponding to the correlation pattern of a predetermined number of partial code sequences of the spread code is selected, and in-phase axis spreading is performed using the selected partial correlation value. A plurality of correlation value calculators that respectively output a correlation value for the code and a correlation value for the orthogonal axis spreading code, and a square sum of the correlation value for the in-phase axis spreading code and the correlation value for the orthogonal axis spreading code. A searcher receiver for a spread spectrum communication receiver, comprising: a plurality of squarers and adders for calculating pilot signal strength; and a correlation value table for storing the pilot signal strength. 8. A partial correlation value of a predetermined number of shift registers and a plurality of adders / subtractors, which outputs a partial correlation value between the received signal stored in the shift register and all the code patterns of a predetermined number. 8. A searcher receiver for a spread spectrum communication receiving apparatus according to claim 1, wherein said searcher receiver has all correlation processors. 9. From partial correlation values corresponding to all correlation value patterns given by the all correlation processor according to claim 8,
When selecting the partial correlation value corresponding to the input PN code, 1 bit of PN code data is regarded as the polarity bit, and when the polarity bit is positive, all the remaining bits are output as they are as the select signal, and the polarity When the bit is negative,
The complex correlation value processor according to any one of claims 1 to 4 or the correlation value processor according to any one of claims 5 to 7, characterized in that all remaining bits are inverted and output as a select signal. A searcher receiver of a receiver for spread spectrum communication. 10. An averaging process is performed by selecting partial correlation values corresponding to all correlation value patterns given by the all correlation processing unit according to claim 8 and performing cyclic addition on the selected partial correlation values. A searcher receiver for a spread spectrum communication receiving apparatus according to claim 1, further comprising: an averaging unit that obtains a value relating to a correlation value of the entire sequence.