JP7432257B1 - Floating offshore microwave power repeater and offshore microwave power transmission system - Google Patents

Abstract

The present invention provides a floating offshore microwave power relay device and an offshore microwave power transmission system that enable effective use of renewable energy. [Solution] A floating offshore microwave power relay device is a microwave power transmission system that is installed on the ocean in a floating state and includes a power transmission antenna that transmits power using microwaves and a power reception antenna that receives microwave power. used for. The floating offshore microwave power relay device includes a first reflecting plate that receives microwaves transmitted from a power transmission antenna and reflects them in a first angle direction on a horizontal plane, and receives the microwaves reflected by the first reflecting plate. a second reflector that emits the power in the direction of the receiving antenna; a base that relatively fixes the first reflector and the second reflector; Equipped with multiple dielectric resonator antennas that perform total internal reflection at the reference phase. [Selection diagram] Figure 1

Description

The present invention relates to a floating offshore microwave power repeater and an offshore microwave power transmission system that enable highly efficient use of, for example, renewable energy in the ocean.

Renewable energy in the ocean includes solar power, wind power, wave power, etc. Efficient use of these renewable energies will lead to reductions in greenhouse gas emissions and significant improvements in energy security.

Renewable energy is generally widely distributed, so in order to use ocean renewable energy with high efficiency, a large number of power generation devices are placed on the coast and the power generated by those many power generation devices is combined. Power will be sent via cable to a power receiving point on land.

Patent Document 1 discloses a wind power generation system in which a plurality of wind power generation devices are connected to each other with a power cable to generate a large amount of power as a whole, and the power is sent to a power receiving unit at one location on land using the power cable. has been done.

JP 2022-20208 Publication

Generally, in normal power plants such as nuclear power plants and thermal power plants, it is essential to cool the heat generating parts. Seawater is required for cooling, so these power plants have to be located on land along the coastline. Furthermore, from a macroscopic perspective, electricity consumers use electricity at locations along the coastline. Since the power transmission path to these power consumers can be short, it is effective to install the power plant on land along the coastline in order to suppress power loss in the power transmission path.

On the other hand, there are fundamental limiting factors in the use of currently available renewable energies such as solar, wind, and wave power, as listed below.

(1) With the exception of photosynthesis by plants and phytoplankton caused by sunlight, most of the energy is once converted into thermal energy, and the three-dimensional temperature distribution and non-thermal equilibrium state produce usable energy. Sunlight provides light and temperature to plants and animals on the ground, in the sea, and in the atmosphere, but if the receiving area of sunlight is close to our residential area, this naturally limits its use as it degrades our living environment. be.

(2) Renewable energy that can be converted into electricity with high efficiency is thin, wide, and unevenly distributed, so a large amount of space is required. In other words, there are usage limits depending on the spatial density of plants, animals, and population density.

(3) Since huge so-called renewable energy structures tend to appear in natural landscapes and tourist spots, there is a limit due to landscape deterioration.

(4) Since material circulation routes through mountains, rivers, coasts, etc. are subject to change (deterioration), there is a limit due to the deterioration of the ecological environment.

(5) Since the continental shelf is an economic zone where marine industries develop, there are limits to its use in terms of cooperation with other industries such as fishing.

(6) Huge wind turbines installed on land or on the coast may cause serious problems such as interference with weather radars and defense radars. In other words, if it interferes with weather radar, there is a limit to its use in terms of natural disaster forecasting, and if it interferes with defense radar, there is a limit to its use in terms of security.

As mentioned above, extracting large amounts of renewable energy on land within a small national territory is disadvantageous in terms of cost, culture, and security. Furthermore, even if renewable energy power plants are installed in the same coastal areas as nuclear power plants and thermal power plants, there are limits to where they can be installed, so there is a limit to increasing energy self-sufficiency as a nationally unique resource.

An object of the present invention is to provide a floating offshore microwave power repeater and an offshore microwave power transmission system that avoid the above-mentioned basic limiting factors and enable effective use of renewable energy in distant and distant waters. There is a particular thing.

A floating offshore microwave power repeater as an example of the present disclosure includes:
A microwave relay device used in a microwave power transmission system comprising a power transmission antenna that is installed on the ocean in a floating state and transmits power using microwaves, and a power reception antenna that receives the microwave power,
a flat first reflecting plate that receives microwaves transmitted from the power transmission antenna and reflects them in a first angular direction on a horizontal plane;
a flat second reflecting plate that receives the microwave reflected by the first reflecting plate and emits it to the power receiving antenna side;
a base that relatively fixes the first reflector and the second reflector;
A plurality of lenses arranged on the first reflecting plate, totally reflecting at a first reference phase at a resonant frequency, and changing the reflection phase from the first reference phase by changing the resonant frequency as the distance from the center of the first reflecting plate increases. a first dielectric resonator;
A plurality of components arranged on the second reflecting plate, totally reflecting at a second reference phase at a resonant frequency, and changing the reflection phase from the second reference phase by changing the resonant frequency as the distance from the center of the second reflecting plate increases. a second dielectric resonator;
A Fresnel lens type microwave mirror is configured by the first reflector and a first dielectric resonator antenna formed by the plurality of first dielectric resonators, and the second reflector and the plurality of second dielectric resonators constitute a Fresnel lens type microwave mirror. The second dielectric resonator antenna according to the present invention constitutes a Fresnel lens type microwave mirror.

According to the present invention, for example, power transmission between a plurality of power generating devices or power receiving devices floating on the sea surface of the ocean, or between a plurality of power generating devices or power receiving devices floating on the sea surface of the ocean and a plurality of power generating devices or power receiving devices installed on a distant land. Since power can be transmitted between the power generation device or the power receiving device without using power wire cables, there are no limitations on usage due to the deterioration of our living environment, the spatial density of animals and plants, population density, and the deterioration of the ecological environment, as mentioned above. can be avoided and renewable energy can be used effectively.

FIG. 1 is a diagram showing the main parts of a system that utilizes renewable energy at sea. FIG. 2 is a diagram showing how the microwave beam MB emitted from the floating offshore wind power generation device 300 etc. is reflected by the microwave mirror 510 and enters the power receiving antenna 520. FIG. 3 is a diagram showing the positional relationship between the power receiving antenna 520 provided on the platform 500 and the power transmitting antennas 311 of the multiple floating offshore wind power generators 300. FIG. 4 is a diagram illustrating the microwave power transmission efficiency when the power transmitting antenna and the power receiving antenna have different diameters (asymmetrical). FIG. 5 is a diagram showing the structure of a microwave mirror 510 and a power receiving antenna 520 provided on the platform 500, and the structure of an inverse dam 600 provided below the platform 500. FIG. 6 is a diagram illustrating a case where the offshore energy collection system of this embodiment is installed within Japan's exclusive economic zone (EEZ). FIG. 7 is a diagram showing the structure of a floating offshore wind power generation device 300. FIG. 8 is a diagram showing the structure of a floating offshore wind power generation device 300. FIG. 9 is a diagram showing the torque balance of the floating offshore wind power generation device 300. FIG. 10 is a diagram showing the torque balance of the floating offshore wind power generation device 300. FIG. 11 is a diagram showing the relationship among the platform 500, the parasitic relay station 700, the microwave power receiving device 100, and the like. FIG. 12 is a diagram showing an example in which microwave power beams are transmitted from the power transmitting device 200A to three power receiving devices 100A, 100B, and 100C, respectively. 13(A) and 13(B) are diagrams illustrating an example in which microwave power beams are transmitted from the power transmitting device 200A to three power receiving devices 100A, 100B, and 100C, respectively. FIG. 14 is a diagram showing how power is transmitted from the power transmission device 200B provided on the platform 500 to the ship 800 using a microwave beam. FIG. 15 is a diagram showing the structure of one inverse dam 600. FIG. 16 is an example of an arrangement structure of various tanks provided on the upper part of the platform 500. FIG. 17 is a configuration diagram of power transmission device 200 to show a common configuration of power transmission devices 200A and 200B. FIG. 18(A) is a diagram showing the relationship between the beam pilot signal and power waves of the power transmission system in this embodiment, and FIG. 18(B) is a diagram showing the relationship between the pilot signal and power waves in the power transmission system of the comparative example. FIG. FIG. 19 is a diagram showing the polarization relationship between beam pilot signals and power waves. FIG. 20(A) is a perspective view of one element antenna, and FIG. 20(B) is a perspective view of the inside thereof. FIG. 21 is a diagram showing the dimensions of each part of the element antenna. FIG. 22(A) is a diagram showing the configuration of the power feeding section connected to the first pair of magnetic coupling probes (Px1, Px2), and FIG. 22(B) is a diagram showing the configuration of the power feeding section connected to the first pair of magnetic coupling probes (Py1, Py2). FIG. FIG. 23(A) is a diagram showing magnetic flux generated when the current shown in FIG. 22(A) flows. FIG. 23(B) is a diagram showing the distribution of magnetic field strength generated when the current shown in FIG. 22(A) flows. FIG. 24(A) is a perspective view of a magnetic probe provided in the dielectric body of one element antenna, and FIG. 24(B) is a plan view of one element antenna. FIG. 25 is a diagram showing a circuit connected to the X polarization port and the Y polarization port of the two 180° hybrid circuits shown in FIGS. 22(A) and 22(B). 26(A), FIG. 26(B), and FIG. 26(C) are diagrams showing the structure of an array antenna as a small-scale model. FIG. 27 is a diagram showing a comparison example between the conventional phased array antenna method and the minimum beam waveguide method. FIG. 28 is a diagram showing the configuration of a circuit connected to one element antenna of the power receiving array antenna 111 and a circuit connected to one element antenna of the power transmitting array antenna 221. FIG. 29 is a diagram showing how microwave beams are converged by bidirectional retrodirective operation. FIG. 30 is a diagram showing how microwave beams are converged by bidirectional retrodirective operation. FIG. 31 is a diagram showing the relationship between the beam convergence rate η and energy leakage with respect to the number of repetitions N. FIG. 32 is a diagram showing a one-dimensional model of an S matrix using a power transmitting antenna and a power receiving antenna. FIG. 33 is a diagram showing the state of microwave propagation when a microwave absorber is present in the microwave propagation path. FIG. 34 is a diagram showing the state of microwave propagation when a microwave absorber is present in the microwave propagation path. FIG. 35 is a front view showing the configuration of parasitic relay station 700. FIG. 36 is a plan view showing the configuration of parasitic relay station 700. FIG. 37 is a diagram showing an example in which two parasitic relay stations 700A and 700B are arranged between the power transmitting device 200 and the power receiving device 100. FIG. 38 is a diagram showing the principle of a microwave repeater that absorbs minute rotations in three axes caused by the first microwave mirror 711 and the second microwave mirror 712. FIG. 39 is a diagram showing the principle of a microwave repeater that absorbs minute rotations in three axes caused by the first microwave mirror 711 and the second microwave mirror 712. FIG. 40 is a diagram showing the configuration of a repeater that emits microwaves at a constant angle with respect to the incident direction. FIG. 41 is a sectional view showing the configuration of a microwave mirror. FIG. 42 is a diagram showing the structure of one unit of a microwave mirror including a dielectric resonator 721, a reflecting plate 722, and the like. FIG. 43 is a diagram showing another example of a microwave mirror.

Embodiments of the present invention will be described with respect to a system to which the present invention is applied. In addition, each element constituting the system will be explained in order.

《Offshore energy collection system》
First, the overall configuration of the offshore energy collection system will be illustrated.

FIG. 1 is a diagram showing the main parts of a system that uses renewable energy offshore (hereinafter referred to as an "offshore energy system"). The offshore energy system includes an offshore energy collection system, an offshore energy storage device, and a floating offshore microwave power repeater. However, the above-mentioned floating offshore microwave power repeater is located outside of FIG. 1, and this floating offshore microwave power repeater will be illustrated later.

As shown in FIG. 1, a large number of floating offshore wind power generators 300 are arranged in a floating state on the ocean. Further, a platform 500 is placed in a floating state on the ocean. A plurality of inverse dams 600 are provided at the bottom of this platform 500. The platform 500 receives the buoyancy of the plurality of inverse dams 600, and the bottom surface of the platform 500 is positioned above the sea level due to the buoyancy of the plurality of inverse dams 600. That is, the lower surface of the platform 500 is exposed in the air without being immersed in the sea surface. As a result, the platform 500 is less susceptible to stress due to ocean currents, and the platform 500 can be maintained in a predetermined position even if the thrust by the screw, which will be described later, is small.

The inverse dam 600 converts input electrical energy into gravitational energy, and converts gravitational energy into electrical energy. Its structure and operation will be described later.

The floating offshore wind power generation device 300 includes a generator that converts wind energy into electrical energy and a power transmission device that transmits the electrical energy as microwave power to the platform 500. Although the floating offshore wind power generators 300 are floating on the ocean, they are each controlled to have a predetermined positional relationship. The structure and operation of the floating offshore wind power generation device 300 will be described later.

The platform 500 has a rectangular plate shape of, for example, 500 m x 1 km in plan view. A substation 540 is provided at the top of this platform 500. A donut-shaped or ring-shaped power receiving antenna 520 is arranged on the roof of the substation 540. An inverted conical microwave mirror 510 is provided above the power receiving antenna 520. This microwave mirror 510 and power receiving antenna 520 are in a coaxial relationship. The power receiving antenna 520 and the microwave mirror 510 constitute a microwave power receiving section. This microwave power receiving part is, for example, the ground boundary layer (the air layer up to several tens of meters from the earth's surface, the lowest layer of the atmosphere that is fully influenced by the earth's surface, specifically the vertical boundary layer of momentum and heat). It is located at a higher position than the air layer whose directional flux can be considered to be equal to the value at the ground surface. Further, in this example, a solar power generation panel 530 is provided above the microwave mirror 510.

At the top of the platform 500, power transmission devices (or power transmission and reception devices) 200A and 200B are provided. The power transmitting device 200A includes a microwave mirror 210A, and transmits microwave power to a power receiving device installed on land, for example. Further, the power transmission device 200B includes a microwave mirror 210B, and transmits microwave power to a power receiving device provided on the ship 800 on the ocean.

The platform 500 is equipped with port facilities including cranes for loading and unloading containers onto and from ships and ship berthing facilities. Further, near the platform 500, there is provided a solar power generation device that floats in the ocean and generates electricity using solar energy, or a wave power generation device that floats in the ocean and generates electricity using ocean wave power. Since these power generating devices can be placed in the vicinity of the platform 500, power supply means can also be provided for supplying the generated power to the platform via a power cable rather than transmitting the generated power by microwaves.

Note that the floating offshore wind power generation device 300 may be provided with a device that receives power using microwaves, and the solar power generation device or the wave power generation device may be provided with a device that transmits power using microwaves. As a result, the floating offshore wind power generation device 300 combines its own wind power generation power with the power generated by the solar power generation device and the wave power generation device and supplies it to the platform using microwaves without going through a power cable. It may be configured as follows. In other words, the power feeding point may be on the floating offshore wind power generator 300 side. As a result, the power cable does not obstruct the navigation of the ship, so that the ship's route can be configured close to the platform.

The platform 500 includes, for example, a chemical plant that converts seawater into fresh water (H2O), a chemical plant that generates green hydrogen from fresh water, and a chemical plant that generates ammonia (NH3) from hydrogen and nitrogen. It is also equipped with a tank for temporarily storing LNG, biodiesel fuel (BDF (registered trademark)), etc.

According to this embodiment, both the platform 500 and the floating offshore wind power generation device 300 are floating structures that do not use caissons or wire cables, so deep seabed excavation work and mooring work are not required. , easy to construct.

FIG. 2 is a diagram showing how the microwave beam MB emitted from the floating offshore wind power generation device 300 and the like is reflected by the microwave mirror 510 and enters the power receiving antenna 520. The upper part of FIG. 2 is a perspective view, and the lower part of FIG. 2 is a plan view. In this example, the main part of the inverted conical microwave mirror 510 is made of a metal plate. The width of the upper part of this microwave mirror 510 is 300 m, and the width along the circumference of the light receiving part of the donut-shaped power receiving antenna 520 is 75 m. The width along the circumference of this light receiving section is larger than 50 m, which is the width of the microwave beam, and the reflected wave of the microwave beam is received without omission. Although each microwave beam MB has a circular cross section, it is reflected by the microwave mirror 510 having an inverted conical shape, so that the microwave beam having a substantially elliptical shape is incident on the power receiving antenna 520. Here, since the microwave mirror 510 is a metal surface, even if the microwave is obliquely incident on the microwave mirror 510, it is totally reflected. Therefore, even if the elevation angle is shallow, the microwave beam enters the power receiving antenna 520 in a nearly perpendicular state. This suppresses a decrease in power reception efficiency.

FIG. 3 is a diagram showing the positional relationship between the power receiving antenna 520 provided on the platform 500 and the power transmitting antennas 311 of the multiple floating offshore wind power generators 300. A large number of floating offshore wind power generation devices 300 are distributed in a 10 km square. However, in FIG. 3, the floating offshore wind power generation device 300 is not shown, and the power transmission antenna 311 is represented by a dot. The power receiving antenna 520 of the platform 500 is placed in the center of this 10 km square. The configuration of the floating offshore wind power generation device 300 will be described later.

Each floating offshore wind power generator 300 generates, for example, 12 MW, and 108 units generates 1.29 GW. The power transmission antenna of each floating offshore wind power generator 300 is an array antenna with a diameter of 17 m. The donut-shaped power receiving antenna 520 on the platform 500 side is an array antenna with a diameter of 250 m. The storage capacity of the inverse dam 600, which will be described later, is 200 MWh x 16 = 3.2 GWh. This corresponds to a rating of 200,000 kW x 16 hours, for example.

The positional relationship is such that microwave power is transmitted along a straight path from the power transmission antenna 311 of each floating offshore wind power generator to the power reception antenna 520. Basically, the power transmission antenna 311 of each floating offshore wind power generation device is placed at the intersection of the equally spaced grid, but in exceptional cases, the floating offshore wind power generation device 300 is placed at a position that is not placed at the intersection of the equally spaced grid. be done. If another floating offshore wind power generation device 300 exists on the straight path between the power transmission antenna 311 and the power reception antenna 520, that floating offshore wind power generation device 300 becomes a shield. Therefore, the floating offshore wind power generation device 300 serving as the shield is set at a position shifted by a predetermined distance in the X direction or the Y direction along the grid. Alternatively, when there is another floating offshore wind power generation device 300 in the middle of the straight path between the floating offshore wind power generation device 300 whose position should be determined (the focus is on) and the power receiving antenna 520, the above-mentioned focused The floating offshore wind power generation device 300 is set at a position shifted by a predetermined distance in the X direction or the Y direction along the grid.

In the above example, all the floating offshore wind power generators 300 are located on a grid, but they may be arranged along concentric circles with the power receiving antenna 520 at the center. Further, when another floating offshore wind power generation device 300 is present on the straight path between the power transmitting antenna 311 and the power receiving antenna 520, it may be placed at a position shifted by a predetermined distance along the concentric circles. Further, the position of each floating offshore wind power generation device 300 is not limited to a grid pattern or a concentric pattern, but may be arranged randomly. However, in either case, it is important to determine the spacing between each floating offshore wind power generation device 300 so as not to be adversely affected by turbulence generated behind the propeller of the floating offshore wind power generation device 300.

In addition, in the example shown in FIG. 3, the floating offshore wind power generation device 300 is provided so as to surround the power receiving antenna 520. 500, a route through which ships can navigate may be provided. This facilitates the approach of a ship to the platform 500, and the ease with which it can leave and dock on the platform 500.

FIG. 4 is a diagram illustrating the microwave power transmission efficiency when the diameters of the power transmitting antenna and the power receiving antenna (the antenna formed by the microwave mirror 510 and the power receiving antenna 520) of the floating offshore wind power generation device 300 are different (asymmetrical). It is. In this example, when a power transmitting antenna with a diameter of 25 m and a power receiving antenna with a diameter of 50 m are separated by 5 km, the transmission efficiency of microwave power is 99.995%.

FIG. 5 is a diagram showing the structure of a microwave mirror 510 and a power receiving antenna 520 provided on the platform 500, and the structure of an inverse dam 600 provided below the platform 500. The microwave mirror 510 is an inverted cone-shaped microwave mirror in which the side surface of the cone is made of a metal plate (metal surface). The power receiving antenna 520 is an array antenna in which antenna elements are arranged in a donut shape.

Microwave beams transmitted from the floating offshore wind power generators 300 located in a plurality of directions are incident on the microwave mirror 510 , are totally reflected by the microwave mirror 510 , and are incident on the power receiving antenna 520 . For example, one microwave beam has a power of 10 MW. As shown in FIG. 2, even if the microwave beam incident on the microwave mirror 510 has a circular cross section, it is reflected by the inverted conical surface, so that a microwave beam having an approximately elliptical shape is incident on the power receiving antenna 520. do.

The substation 540 rectifies, transforms, and converts the microwave power received by the power receiving antenna 520 into DC. The power generated by the solar power generation panel 530 is used as part of the power supply for a substation, for example.

An inverse dam 600 provided at the bottom of the platform 500 is an energy storage device. One inverse dam 600, for example, has a height (depth) of 200 m and generates 200 MWh of pumped storage power, but the total buoyancy generated by this one inverse dam 600 is about 1.6 million tons. Furthermore, since the weight of the inverse dam 600 is approximately 780,000 tons, the buoyant force exerted by the inverse dam 600 to lift the platform 500 is extremely large, as the difference is approximately 820,000 tons. By providing these inverse dams 600 that generate large buoyancy below the platform 500, a large number of inverse dams 600 can be stably provided together with the platform 500. That is, a large number of inverse dams 600 that generate these large buoyancy forces can be easily provided together with the platform 500 in a well-balanced manner.

As described above, the inverse dam 600 generates buoyancy in the ocean, and due to the distribution of a large number of inverse dams 600, the platform 500 is suspended in a stable state in the vertical direction by the buoyancy. That is, the plurality of inverse dams 600 are arranged in a distributed manner so that a restoring force is generated that suppresses the tilting of the platform 500 along the sea surface.

The buoyancy of each inverse dam 600 is constant regardless of the amount of water in the first water tank 601 and the second water tank 602. Therefore, the stress that the inverse dam 600 applies to the platform 500 is constant, and the repeated stress and vibration caused by repeated pumping power generation are small. Therefore, mechanical deterioration is small and the life can be extended. In addition, since the draft does not change, not only the position of the platform 500 but also the height direction is stabilized, so stable operations at the port can be performed and the port function can be maintained.

The lower surface of the platform 500 may be in contact with the sea surface, but the buoyancy of the plurality of inverse dams 600 lifts the lower surface of the platform 500 above the sea surface, exposing the lower surface of the platform 500 to the air. Buoyancy may also be determined. According to this structure, a waterline is generated not on the platform 500 but on each inverse dam 600, and it is possible to suppress the wave force and frictional resistance that the platform and each inverse dam 600 receive as a whole. Furthermore, since the entire platform 500 is not affected by ocean currents, stress caused by ocean currents can be suppressed. Therefore, the maximum thrust of the thrust generating device that keeps the platform 500 in a predetermined position can be small. Furthermore, the horizontal accuracy and positional accuracy of the platform 500 can also be improved.

Note that it is also effective to uniformly distribute bubble or microbubble ejection ports at a plurality of locations on the bottom surface of the platform 500 and to provide a microbubble generator using ultrasonic waves or the like. That is, by forming an air layer between the bottom surface of the platform 500 and the seawater by the microbubbles blowing out from the bottom surface of the platform 500, the friction between the platform 500 and the seawater can be reduced. In order to prevent the microbubbles themselves or the air in the air layer from leaking to the sides of the platform 500, an enclosure for preventing air leakage may be provided around the bottom surface of the platform 500. Since the microbubbles and air themselves float up to the sea surface along the sides of the platform 500, they have almost no effect of reducing friction between the platform 500 and the seawater. Therefore, it is preferable that the waterline of the platform 500 be close to the lower surface of the platform 500. Unlike the case of a ship, the platform 500 has a small relative speed to the seawater, so the bubbles are hardly carried away by the sea current. With this configuration, the restoring force of the platform 500 can be stabilized even by a method that does not allow the bottom surface of the platform 500 to float above the sea surface.

Since the platform 500 is not moored to the seabed or the like, earthquakes can occur both when the bottom surface of the platform 500 is underwater (that is, when the waterline is on the platform 500) and when the waterline is at a predetermined position on the inverse dam 600. and tsunamis. In other words, since the platform 500 is not moored, the platform 500 and the inverse dam 600 generally follow the changing long wavelength wave front that occurs during an earthquake or tsunami. This makes it highly resistant to stress caused by earthquakes and tsunamis.

Platform 500 may collect energy from multiple photovoltaic panels. In that case, a plurality of floating offshore wind power generation devices 300 floating on the ocean and a plurality of solar panels floating on the ocean are provided, and the plurality of floating offshore wind power generation devices 300 are adjacent to each other. The devices 300 may be arranged at predetermined intervals that do not interfere with each other, and the solar cell panels may be arranged at the predetermined intervals (for example, within the grid spacing shown in FIG. 3). These solar panels may be placed in a submerged position without being exposed above the sea surface. The solar power generation device includes a solar panel that generates electricity by receiving sunlight on the ocean (near the ocean surface), a propulsion unit that detects the position of the solar panel and fixes the position of the solar panel on the ocean, It is sufficient to include a power transmission unit that transmits power generated by the solar panel to the platform using microwaves.

Note that by submerging the solar panel shallowly in water, the power generation efficiency of the solar panel can be maintained at a high level. In other words, the higher the temperature of a solar panel, the lower its power generation efficiency, but if the solar panel is submerged in water, the temperature will not exceed 30 degrees Celsius. Therefore, the power generation efficiency of the solar cell panel can be maintained at a high level. Furthermore, if the solar panel is submerged shallowly in water, the dust on the surface of the solar panel will be constantly washed away and its cleanliness will be maintained. However, even in a clean ocean like the EEZ, it is not completely free of marine deposits, so it is preferable to automatically perform simple cleaning on a regular basis with a robot. Furthermore, by shallowly submerging the solar panel in water, the solar panel is mechanically protected from the impact of waves. Seawater absorbs sunlight, so submerging solar panels too deeply reduces power generation efficiency. Therefore, it is effective to submerge the solar panel within a range of about 3 m to 5 m, for example. Also, changing this depth depending on the weather is an effective measure to improve durability and power generation efficiency.

The inverse dam 600 includes a first water tank 601 that is installed in the sea and has a predetermined volume for storing fresh water, and a second water tank 602 that is installed in the sea and is located below the first water tank 601 and has a predetermined volume for storing fresh water. , a single or plural communication path 604 that communicates the first aquarium 601 and the second aquarium 602; an electric water pump 603 that pumps water from the second aquarium 602 to the first aquarium 601 through the communication path 604; It has a generator 606 that generates electricity by using falling water flowing from the water tank 601 to the second water tank 602 through the communication path 604. In other words, pumped storage power generation is performed.

The electric water pump 603 pumps water in the second water tank 602 to the first water tank 601 using the power energy input to the electric water pump 603, thereby converting (accumulating) the power energy into gravitational energy. Furthermore, the generator 606 converts (releases) gravitational energy into electrical energy due to water falling from the first water tank 601 to the second water tank 602 .

Note that the single or plural communication paths 604 that communicate the first aquarium 601 and the second aquarium 602 are very short paths that communicate the first aquarium 601 and the second aquarium 602 that are adjacent in the direction of gravity. , the loss that occurs when water flows through this communication path is kept very small. Therefore, the overall loss of pumped storage power generation can be reduced.

In this example, a weight 607 is provided between the first water tank 601 and the second water tank 602 to adjust the buoyancy and shift the center of gravity of the platform 500 downward.

Since the total mass of fresh water in inverse dam 600 is constant, the buoyancy of inverse dam 600 is constant and the waterline of inverse dam 600 is constant. Note that a machine room 610 in FIG. 5 controls the electric water pump 603 and the generator 606.

FIG. 6 is a diagram illustrating a case where the offshore energy collection system of this embodiment is installed within Japan's exclusive economic zone (EEZ). If the wind speed in this sea area is 12 m/s, it is possible to generate 10 MW of power per 1 km square, so 900 GW of power can be generated in a 300 km square area. Incidentally, since there are very few birds flying in such an EEZ, the problem of bird strikes against the wind turbine of the floating offshore wind power generation device 300 hardly occurs.

7 and 8 are diagrams showing the structure of a floating offshore wind power generation device 300. This floating offshore wind power generation device 300 includes a wind turbine 301 that rotates in response to wind power, screws 302X and 302Y that generate thrust underwater, a plurality of iron columns 303, a water tank 304, a weight 305, and a power transmission antenna 311. The screws 302X and 302Y are thrust generating devices that maintain a predetermined position in the ocean.

The water tank 304 contains fresh water 304W, and a cavity 304C is formed in the upper part of the water tank 304.

For example, the diameter of the wind turbine 301 is 150 m, and the distance from the center of the wind turbine 301 to the sea level is 125 m. Further, the distance from the sea level to the bottom of the weight 305 is 200 m. The steel column 303 has a height of 6 m, and the balance in the height direction is adjusted so that the average sea level is at the center height of the steel column 303.

This floating offshore wind power generation device 300 is effective to be used in deep sea areas with weak ocean currents outside the Kuroshio Current channel within the EEZ.

The generator 306 generates electricity by rotating the windmill 301, the electric motor 307X rotationally drives the screw 302X, and the electric motor 307Y rotationally drives the screw 302Y. The screws 302X and 302Y have a large area, and are driven at low rotational speeds to offset the drag of the wind turbine and to maintain the position of the floating offshore wind power generator 300 at a predetermined position. This makes it possible to implement fixed point holding control (DPS).

Here, an example of a rough estimate of the electric power and thrust required for the wind turbine 301 to generate power and remain stationary on the ocean will be shown.

In the above formula, V _A is the wind speed, V _W is the water flow speed, P _A is the power generated by the wind turbine, P _W is the power required for the screw, and N is the number of screws. Once the structural parameters are determined, the screw needs to create a water flow proportional to the wind speed. The proportionality constant is the square root of the area ratio of the wind turbine to the screw; the larger the area of the screw, the less static power is required. The physical meaning of this is that by slowly discharging a large amount of water, the momentum (force) is kept constant and the kinetic energy of the water, which is proportional to the square of the velocity, is reduced.

In the example of the fixed point stop power in the above formula, the wind speed V _A is 10 m/s, the diameter of the wind turbine is 150 m, and the number of screws is 16, with a diameter of 12 m. The mass density of air is 1.225 kg/m ³ , the mass density ratio of water to air is 816, and the energy efficiency Cp is 0.593.

In this way, by increasing the diameter of the screw by about 1/10 or more of the diameter of the wind turbine, the fixed point stop power can be suppressed to about 10% of the power generated by the wind turbine.

9 and 10 are diagrams showing the torque balance of the floating offshore wind power generation device 300. For example, if the wind pressure applied to the wind turbine 301 is 100 tons, the screw 302X is propelled at 100 tons in the opposite direction to the wind pressure. Considering the structures shown in FIGS. 8 and 9 as calculation examples, the torque is balanced at an inclination angle of 3.41 degrees.

《Offshore microwave power transmission system》
FIG. 11 is a diagram showing the relationship among the platform 500, the parasitic relay station 700, the microwave power receiving device 100, and the like.

The platform 500 includes a position detection device that obtains extremely accurate position information using positioning satellites such as GPS satellites and quasi-zenith satellites that detect positions in the ocean. The platform 500 also includes a thrust generator that maintains a predetermined position in the ocean.

A screw 608 as the thrust generating device is provided at the bottom of the platform 500. The screw 608 is composed of a plurality of screws oriented to move at least in the longitudinal direction and the latitudinal direction. This makes it possible to implement fixed point control (DPS) of the platform 500.

The configurations of power receiving device 100 provided on the coast of land and power transmitting device 200A provided on platform 500 are similar. The power transmitting device 200A faces the parasitic relay station 700, and the power receiving device 100 also faces the parasitic relay station 700.

The parasitic relay station 700 includes a microwave mirror device 701, a floating body 706, a screw 702, an iron pole 703, and a weight 705. The iron pillar 703 supports the microwave mirror device 701 at a predetermined height from the floating body 706. The weight 705 balances the gravity and the buoyancy of the floating body 706, etc., and keeps the height of the microwave mirror device 701 constant.

For example, the total displacement of platform 500 is 1.6 million tons, and the total displacement of unpowered relay station 700 is 4000 tons. Further, the distance from the power transmitting device 200A to the parasitic relay station 700 is 20 km, and the distance from the power receiving device 100 to the parasitic relay station 700 is 20 km. The height of the power transmission device 200A is 120 m, the distance from the sea surface to the lower end of the microwave beam is 60 m, and the lower end of the microwave beam is higher than the ground boundary layer.

FIG. 12, FIG. 13(A), and FIG. 13(B) are diagrams showing an example in which microwave power beams are transmitted from the power transmitting device 200A to three power receiving devices 100A, 100B, and 100C, respectively. The power transmitting device 200A is not limited to transmitting a microwave power beam to a single power receiving device. The power transmission device 200A transmits a microwave power beam in the direction of the pilot signal in response to transmission and reception of the pilot signal.

In the example shown in FIG. 12, the power transmitting device 200A includes a power transmitting antenna with a diameter of 50 m, and the power receiving devices 100A, 100B, and 100C are 10 km apart from the power transmitting device 200A. Further, the distance between the power receiving device 100A and the power receiving device 100B is 70 m, and the distance between the power receiving device 100A and the power receiving device 100C is 90 m. 1000 kW of microwave power is transmitted from the power transmitting device 200A to the power receiving device 100A, 360 kW of microwave power is transmitted from the power transmitting device 200A to the power receiving device 100B, and 90 kW of microwave power is transmitted from the power transmitting device 200A to the power receiving device 100C. Ru.

In FIG. 12, the energy density is expressed in dB shading. FIG. 13(A) shows the energy density in the power receiving devices 100A, 100B, and 100C in linear shading, and FIG. 13(B) shows the energy density in the power receiving devices 100A, 100B, and 100C in a graph.

FIG. 14 is a diagram showing how power is transmitted from the power transmission device 200B provided on the platform 500 to the ship 800 using a microwave beam. Power transmission device 200B includes a power transmission side array antenna 221B and a microwave mirror 210B. The configurations of power transmission device 200B and power transmission device 200A are similar. In this example, the power transmission side array antenna 221B has a diameter of 50 m, and the power receiving antenna 810 of the ship 800 is configured with an array antenna with a side of 15 m. The distance from the power transmission device 200B to the ship 800 is 30 m to 100 m, and microwaves of 100 to 300 MW are transmitted.

《Offshore energy storage device》
FIG. 15 is a diagram showing the structure of one inverse dam 600. The structure is different from the inverse dam 600 shown in FIG. The inverse dam 600 shown in FIG. 15 includes a first water tank 601 installed in the sea and having a predetermined volume for storing fresh water, and a second water tank 601 installed in the sea and having a predetermined volume for storing fresh water and located below the first water tank 601. 2 aquarium 602, communication passages 604, 605 that communicate the first aquarium 601 and the second aquarium 602, an electric water pump 603 that pumps water from the second aquarium 602 to the first aquarium 601 through the communication passage 604, It has a generator 606 that generates electricity by using falling water flowing from the first water tank 601 to the second water tank 602 through the communication path 605. A weight 607 is provided at the bottom of the second water tank 602 to adjust the buoyancy and shift the center of gravity of the platform 500 downward.

In this example, the inner diameter of the first water tank 601 and the second water tank 602 is 100 m, and the total height of the first water tank 601 and the second water tank 602 is 200 m. The weight of fresh water, the weight of the inverse dam 600 body, the generator 606, and the electric water pump 603 are 828,000 tons, and the buoyancy (displacement amount of water approximately equal to the external volume of the inverse dam body) is 1.57 million tons. be. The weight of the weight 607 is 742,000 tons, which is equal to the difference between the above 1,570,000 tons and 828,000 tons.

In the example shown in FIG. 15, there are a plurality of communication paths 604 and 605 that communicate the first water tank 601 and the second water tank 602, and an electric motor that pumps water from the second water tank 602 to the first water tank 601 through the communication path. An example has been shown in which a water pump 603 and a generator 606 that generates electricity from falling water flowing from the first water tank 601 to the second water tank 602 through the communication path are provided. An electric water pump that pumps up water and a generator that generates electricity using falling water flowing from the first water tank 601 to the second water tank 602 through the communication path may also be used. Further, the first water tank 601 and the second water tank 602 may have a single communication path.

FIG. 16 is an example of an arrangement structure of various tanks provided on the upper part of the platform 500. This platform 500 is equipped with port facilities and has the characteristics of a "sea station" that can provide logistics, water, fuel (electricity, hydrogen, LNG, biodiesel fuel (BDF (registered trademark)), ammonia (NH3)), food, etc. has.

The energy storage capacity of Platform 500 is 200 MWh x 4 = 800,000 kWh, and the power generation capacity is rated at 200 MW (200,000 kW) and maximum at 400 MW. The primary energy sources are floating offshore wind power generation equipment and offshore solar power generation, and it has hydrogen production and storage capacity and freshwater production and storage capacity. The tank 501 stores hydrogen, fresh water, LNG, biogas, etc. These tanks 501 are arranged above the inverse dam 600. As a result, the point of action of the buoyant force of the inverse dam 600 and the center of gravity of the tank 501 coincide on the vertical line, and the stress applied to the platform 500 and the tank 501 can be reduced.

《Offshore microwave power transmission system》
Power transmission devices 200A and 200B shown in FIG. 1 have similar configurations. FIG. 17 is a configuration diagram of power transmission device 200 to show a common configuration of power transmission devices 200A and 200B. The power transmission device 200 includes a power transmission side array antenna 221 in which a plurality of element antennas are arranged, and a microwave mirror 210. The power transmission side array antenna 221 sends out power waves in the vertical direction, and the microwave mirror 210 reflects the power waves at 90 degrees and guides them in the horizontal direction (direction parallel to the sea surface).

As shown in FIG. 17, the power transmission side array antenna 221 includes a plurality of arrayed element antennas 21.

As will be detailed later, the power receiving device transmits a beam-formed pilot signal (beam pilot signal) from the power receiving array antenna by controlling the amplitude and phase of the received signal of the multiple element antennas of the power receiving array antenna. and a circuit for receiving power waves transmitted from the power transmitting array antenna 221. Further, the power transmission device 200 generates a phase conjugate signal having a phase conjugate relationship from the received signal caused by the plurality of element antennas of the power transmission side array antenna 221 receiving the beam pilot signal, and amplifies this phase conjugate signal. The power transmission side element antenna circuit transmits power waves by driving the element antenna.

Note that, as described later, in a steady state, the beam pilot signal is not a dedicated signal but a signal transmitted from the array antenna on the power receiving device side. For convenience of sequential explanation, it is assumed that a beam pilot signal is first transmitted from the array antenna on the power receiving device side, and a power wave is transmitted from the power transmitting side array antenna 221 based on this beam pilot signal.

FIG. 18(A) is a diagram showing the relationship between the beam pilot signal and power waves of the power transmission system in this embodiment, and FIG. 18(B) is a diagram showing the relationship between the pilot signal and power waves in the power transmission system of the comparative example. FIG.

In the power transmission system of the comparative example shown in FIG. 18(B), an array antenna 111C for pilot signal transmission is provided in a very small part of the center of the power receiving antenna, and an array antenna 111C for receiving power waves is provided in most of the surrounding area. 111P is provided. Further, a pilot signal receiving array antenna 221C is provided in a very small part of the center of the power transmission antenna, and an array antenna 221P for power wave transmission is provided in most of the surrounding area. The power receiving station transmits a pilot signal using the array antenna 111C for pilot signal transmission of the power receiving antenna, and the power transmitting station receives the pilot signal using the array antenna 221C for pilot signal reception of the power transmitting antenna. The arrival direction of the pilot signal is detected, and a beam-formed power wave is transmitted in that direction using the array antenna 221P for power wave transmission.

In this way, in the power receiving antenna of the comparative example, in order to use most of the array antenna (large area) for power transmission, the remaining part of the array antenna is used for sending and receiving pilot signals, so the power receiving antenna In other words, it transmits a spread pilot signal. Therefore, in the power transmission system of this comparative example, the pilot signal is reflected by the sea surface or scatterers, resulting in multipaths to the pilot signal receiving array antenna 221C of the power transmission station. As a result, retrodirectives become inaccurate and power transfer efficiency is significantly reduced.

On the other hand, in the power transmission system of this embodiment shown in FIG. It is transmitted to the antenna 221. Each element antenna of the power transmission side array antenna 221 generates a phase conjugate signal having a phase conjugate relationship of the received signal from the received signal by receiving the beam pilot signal, and drives the element antenna with this phase conjugate signal. , transmitting the resulting beamformed power waves. That is, the beam pilot signal is transmitted using all or most of the element antennas of the power receiving array antenna, and the beam pilot signal is received and the power wave is transmitted using all or most of the element antennas of the power transmitting array antenna. It will be done. The above-mentioned "mostly" means that the beam pilot signal is not necessarily generated using all the element antennas; for example, the beam pilot signal is generated using 90% or more of the element antennas. Good too.

According to this embodiment, the pilot signal is transmitted as a beam (self-convergent beam to be described later) that is sharply directed toward the power transmitting array antenna 221, so there is little reflection on the sea surface, etc., and the beam pilot signal is transmitted in a state where there is almost no multipath. The signal is transmitted to the power transmitting array antenna 221. Therefore, the problem caused by multipath of the pilot signal is solved.

FIG. 19 is a diagram showing the polarization relationship between the beam pilot signal and the power wave. Each element antenna of the power receiving array antenna 111 includes an element for horizontal polarization and an element for vertical polarization, and similarly, each element antenna of the power transmitting array antenna 221 includes an element for horizontal polarization and an element for vertical polarization. and a polarization element. In this example, the power receiving array antenna 111 transmits a beam pilot signal with vertical polarization, and the power transmitting array antenna 221 transmits a power wave with horizontal polarization.

In this way, the beam pilot signal and the power wave have orthogonal polarization planes and are independent from each other, so the pilot signal feeding circuit connected to each element antenna of the receiving array antenna 111 affects the power wave. You will not receive any. Furthermore, the pilot signal receiving circuit connected to each element antenna of the power transmission side array antenna 221 is not affected by the power waves transmitted by its own element antenna.

FIG. 20(A) is a perspective view of one element antenna, and FIG. 20(B) is a perspective view of the inside thereof. The element antennas 11 and 21 include a dielectric DH protruding from the conductor plane GP, and two pairs of magnetic coupling probes (Px1, Px2) (Py1, Py2) provided within the dielectric DH.

The dielectric DH has a hemispherical overall shape, and is cross-shaped when viewed in plan from the conductor plane GP. In other words, as shown in FIG. 20(A), a hemispherical dielectric has a shape in which cutouts CO are formed at four locations, or two half-moon-shaped dielectric pieces are combined in a cross shape. It is shaped like a. As shown in FIG. 20(B), if the center of the dielectric DH (the center of the surface of the dielectric DH that is in contact with the conductor plane GP) is the origin of the orthogonal x, y, z coordinates, one of the two dielectric pieces extends in the xz plane, and the other in the yz plane.

The first pair of magnetic coupling probes (Px1, Px2) have their loop planes in the xz plane, and the second pair of magnetic coupling probes (Py1, Py2) have their loop planes in the yz plane. It's within.

FIG. 21 is a diagram showing the dimensions of each part of the element antenna. In this example, the dielectric constant εr of the dielectric DH is 12.6, the diameter d of the dielectric DH is 16 mm, the radius r of the magnetic coupling probes Px1, Px2 is 1.75 mm, and the semicircle of the magnetic coupling probes Px1, Px2 The center height h of the shaped loop is 1.35 mm, and the pitch P from the center to the feeding point of the magnetic coupling probe is 6 mm. By adjusting the height h of the magnetic field coupling probe, the matching between the input/output port and the antenna can be adjusted. The dimensions of each part of the magnetic coupling probes Py1 and Py2 are also the same as those of the magnetic coupling probes Px1 and Px2. Note that the conductor plane GP for each element antenna is a metal disk having a diameter of 30 mm, and is arranged two-dimensionally at predetermined intervals on a metal plate having a diameter of 50 m, for example.

FIG. 22(A) is a diagram showing the configuration of the power feeding section connected to the first pair of magnetic coupling probes (Px1, Px2), and FIG. 22(B) is a diagram showing the configuration of the power feeding section connected to the first pair of magnetic coupling probes (Py1, Py2). FIG. The ends of the first pair of magnetic coupling probes (Px1, Px2) near the center are connected to a conductive plane (ground), and the ends far from the center are supplied with power. The magnetic coupling probes Px1 and Px2 are supplied with signals having a phase difference of 180° from the 180° hybrid circuit, so that the magnetic coupling probes Px1 and Px2 are differentially supplied with power (balanced power supply), and a current flows in the direction of the arrow. This also applies to the second pair of magnetic coupling probes (Py1, Py2).

FIG. 23(A) is a diagram showing magnetic flux generated when the current shown in FIG. 22(A) flows. Moreover, FIG. 23(B) is a diagram showing the distribution of magnetic field strength generated when the current shown in FIG. 22(A) flows. In this way, by differentially feeding the magnetic coupling probes Px1 and Px2, the dielectric body DH is excited by the magnetic coupling probes Px1 and Px2, and the dielectric body DH (having a radiation electromagnetic field equivalent to a magnetic dipole) ₁₁ Acts as an ^X- mode dielectric resonator. This TE ₁₁ ^X mode dielectric resonator is an element antenna for X polarization. Similarly, by differentially feeding the magnetic coupling probes Py1 and Py2, the dielectric DH is excited by the magnetic coupling probes (Py1, Py2), and the dielectric DH (has a radiated electromagnetic field equivalent to a magnetic dipole) TE ₁₁ Acts as ^{a Y-} mode dielectric resonator. This TE ₁₁ ^Y mode dielectric resonator is an element antenna for Y polarization. Since the TE ₁₁ ^X mode and TE ₁₁ ^Y mode are independent of each other, each element antenna acts as a TE 11 dual mode dielectric resonator. In this example, the radiation quality factor (Qrad) of the resonator is approximately 20. This TE11 dual mode dielectric resonator is an example of an orthogonal dual mode dielectric resonator antenna.

Next, another configuration of the element antenna will be described. FIG. 24(A) is a perspective view of a magnetic probe provided in the dielectric body of one element antenna, and FIG. 24(B) is a plan view of one element antenna. This element antenna includes a dielectric DH protruding from the conductor plane GP, and two magnetic coupling probes Px and Py provided within the dielectric DH.

The shape of the dielectric DH is the same as that shown in FIGS. 20(A) and 20(B). The magnetic coupling probe Px has its loop plane in the xz plane, and the magnetic coupling probe Py has its loop plane in the yz plane.

The midpoints of each of the magnetic coupling probes Px and Py are connected to a conductor plane (ground conductor) GP. Each of the magnetic coupling probes Px and Py is differentially powered (balanced powered) from both ends.

Even with this cross-loop structure, magnetic flux similar to that shown in FIGS. 23(A) and 23(B) is generated, and the magnetic coupling probe Px is coupled to the TE ₁₁ ^X mode that has a magnetic dipole moment on the Y axis. However, the magnetic coupling probe Py couples to the TE ₁₁ ^Y mode having a magnetic dipole moment on the X axis.

By using the orthogonal dual mode dielectric resonator antenna shown above, sufficiently high polarization isolation can be obtained between the pilot signal and the power wave, and even though the same frequency is used, the pilot signal and the power wave can be separated. A system without interference can be constructed.

Next, an example will be shown in which each element antenna transmits and receives pilot signals and power waves using circularly polarized waves.

FIG. 25 is a diagram showing a circuit connected to the X polarization port and the Y polarization port of the two 180° hybrid circuits shown in FIGS. 22(A) and 22(B). The Input-port of the 90° hybrid circuit shown in FIG. 25 is an input/output port for right-handed circularly polarized waves, and the Isolated-port of the 90° hybrid circuit is an input/output port for left-handed circularly polarized waves. Since the phase difference between the 0°-port and the 90°-port of the 90° hybrid circuit is 90°, the two pairs of magnetic coupling probes shown in FIGS. 22(A) and 22(B) Powered by phase difference. With this configuration, pilot signals or power waves are transmitted with right-handed circularly polarized waves, and pilot signals or power waves with left-handed circularly polarized waves are received.

In this way, even if the pilot signal and the power wave have different turning directions, the polarization of the received signal and the transmitted signal are orthogonal, so even though the same frequency is used, the pilot signal and the power wave can be It is possible to construct a power transmission system that does not interfere with

26(A), FIG. 26(B), and FIG. 26(C) are diagrams showing the structure of an array antenna as a small-scale model. 26(A) is a plan view of the array antenna, FIG. 26(B) is a front view of the array antenna, and FIG. 26(C) is a bottom view of the array antenna. This array antenna is used as a power transmitting side array antenna or a power receiving side array antenna.

The plurality of element antennas 11 (21) are arranged on the conductor plane GP. In this example, a total of 177 element antennas are arranged vertically and horizontally at a pitch of 0.7λ (36 mm).

As shown in FIG. 26(B), a large number of RF units RFU are arranged between the reference signal grid board GB and the conductor plane GP. These RF units RFU are provided for each element antenna 11 (21). A wiring pattern LP is formed on the reference signal grid board GB, and a reference signal of equal amplitude and equal phase is supplied to each RF unit RFU via this wiring pattern LP.

FIG. 27 is a diagram showing a comparison example between the conventional phased array antenna method and the minimum beam waveguide method. In the conventional phased array antenna system, the electric field strength of each antenna element is distributed flatly, so the Gaussian fundamental mode is selected paraxially as the radio wave propagates. On the other hand, in the minimum beam waveguide method, the electric field propagates with a distribution where the electric field strength is stronger toward the center.

When the diameter of the array antenna is 50 m, the propagation distance is 10 km, and 5.8 GHz microwave is used, the propagation efficiency (completion rate) is 91.25% in the phased array antenna method, whereas the minimum beam waveguide In this method, the propagation efficiency (completion rate) is 99.996%.

FIG. 28 is a diagram showing the configuration of a circuit connected to the power receiving array antenna 111 and a circuit connected to the power transmitting array antenna 221. The power receiving array antenna 111 includes a plurality of element antennas 11 , and the power transmitting array antenna 221 includes a plurality of element antennas 21 . Each element antenna 11 is composed of a vertical polarization element 11V and a horizontal polarization element 11H, and each element antenna 21 is composed of a vertical polarization element 21V and a horizontal polarization element 21H.

A power receiving side element antenna circuit 10 is connected to the element antenna 11 of the power receiving side array antenna. In a steady state, a signal output from the phase conjugate circuit 14 of the power receiving station is amplified by the power amplifier 17 and supplied to the vertical polarization element 11V.

By supplying the signal to the vertically polarized wave element 11V of each element antenna 11 in this manner, a beam pilot signal is transmitted from the power receiving side array antenna 111. The transmission power of the beam pilot signal is, for example, 1 kW.

The power transmitting element antenna circuit 20 is connected to the element antenna 21 of the power transmitting array antenna 221 . The vertically polarized wave element 21V of the element antenna 21 receives the pilot signal and outputs a received pilot signal. The phase conjugate circuit 24 outputs a signal having a phase conjugate relationship with respect to the received pilot signal. Therefore, the frequency of the power wave is the same as the frequency of the pilot signal.

Note that the phase conjugate circuit 14 and the phase conjugate circuit 24 include a fundamental wave generation circuit and a double wave generation circuit, but the source oscillation of the fundamental wave generation circuit and the double wave generation circuit is a common positioning satellite such as a GPS satellite. It is effective to generate radio waves based on radio waves from As a result, it is possible to perform correlated phase conjugation with signals having substantially the same frequency and phase correlation in each transmitting circuit and receiving circuit. Furthermore, this allows the microwave power receiving device to receive coherent microwave power from a large number of microwave power transmitting devices.

Note that in this embodiment, "the same frequency" does not mean that the frequencies are completely the same, but may be substantially the same frequency. In other words, any frequency can be used as long as the microwave does not lose its coherency even if it propagates over a very long distance, and a stable oscillation state can be achieved.

The output signal of the phase conjugate circuit 24 is amplified by a power amplifier 27 and supplied to the horizontal polarization element 21H.

When each element antenna 21 of the power transmission side array antenna 221 performs the above operation, a beam-formed power wave is transmitted from the power transmission side array antenna 221. The transmitted power of this power wave is, for example, 1 MW.

The element 11H of the element antenna 11 receives a signal transmitted from the power transmission side array antenna 221. This signal is divided by a distributor 12, and most of the power is rectified by a rectifier 13 and taken out as power. The remaining distributed signals are applied to the phase conjugate circuit 14. The phase conjugate circuit 14 outputs a signal having a phase conjugate relationship with respect to the signal received from the power transmission side array antenna 221.

Here, assuming that the amplifier amplification factor of the beam pilot signal is 30 dB and a noise level margin of 30 dB, it is important to achieve an isolation level of -60 dB or less. Therefore, isolation of -60 dB or less is ensured between the input and output of the vertical polarization element 21V and the horizontal polarization element 21H of each element antenna 21 of the power transmission side array antenna 221. Similarly, isolation of -60 dB or less is ensured between the input and output of the vertical polarization element 11V and the horizontal polarization element 11H of each element antenna 11 of the power receiving side array antenna 111.

As shown above, the signal transmitted from the power receiving array antenna 111 to the power transmitting array antenna 221 is used as a beam pilot signal for the power transmitting device 200, and is transmitted from the power transmitting array antenna 221 to the power receiving array antenna 111. The power wave is used as a beam pilot signal for power receiving device 100. In this way, a bidirectional retrodirective system is constructed.

By generating a beam pilot signal from the power wave, the vertical polarization element 11V of the power receiving array antenna 111 → propagation path → the vertical polarization element 21V of the power transmitting array antenna 221 → the power transmitting element antenna circuit 20 → Horizontal polarization element 21H of the element antenna 21 of the power transmitting station → Propagation path → Element 11H of the element antenna 11 of the power receiving station → Power receiving side element antenna circuit 10 → Vertical polarization element 11V of the power receiving side array antenna 111. A closed loop is constructed. This closed loop constitutes one oscillation circuit system. Therefore, since a dedicated complicated circuit for generating pilot signals is not required, the configuration of the device is simplified and costs are reduced.

The power receiving array antenna 111 and the power transmitting array antenna 221 are not equipped with a beamforming control circuit for steady operation. However, as will be explained later, due to the operation of each element antenna 21 of the power transmission side array antenna 221 and the power transmission side element antenna circuit 20, the power transmission side array antenna 221 eventually acts as a phased array antenna. Similarly, by the operation of each element antenna 11 of the power receiving side array antenna 111 and the power receiving side element antenna circuit 10, the power receiving side array antenna 111 eventually acts as a phased array antenna.

When the vertical polarization element 21V of each element antenna 21 of the power transmission side array antenna 221 receives the pilot signal, a phase conjugate signal having a phase conjugate relationship of the received signal is generated from the received signal, and this phase The conjugate signal is amplified, and the horizontally polarized wave element 21H of the element antenna is driven. As a result, each element antenna of the power transmission side array antenna 221 transmits a power wave having a phase conjugate relationship with the pilot signal. Therefore, according to the reciprocity theorem, the power wave propagates backward along the propagation path of the beam pilot signal. That is, the power wave propagates to the power receiving array antenna 111 along the same route as the beam pilot signal.

Similarly, when the horizontally polarized wave element 11H of each element antenna 11 of the power receiving array antenna 111 receives (receives) a power wave, a phase conjugate signal having a phase conjugate relationship of the received signal is generated from the received signal. is generated, this phase conjugate signal is amplified, and the vertical polarization element 11V of the element antenna is driven. As a result, each element antenna of the power receiving side array antenna 111 transmits a pilot signal having a phase conjugate relationship with the power wave. Therefore, according to the reciprocity theorem, the beam pilot signal propagates backward along the power wave propagation path. That is, the beam pilot signal propagates to the power transmission side array antenna 221 along the same route as the power wave.

Since the beam pilot signal and the power wave have the same frequency, accurate reciprocity can be expected even if the propagation path has frequency dependence.

FIGS. 29 and 30 are diagrams showing how microwave beams are converged by bidirectional retrodirective operation. In these figures, N indicates the number of times the pilot signal beam propagates and the power beam propagates. When time t=0.000ms, N=1, and when time t=0.034ms, N=2. As shown in FIGS. 29 and 30, the pilot signal beam and the power beam self-converge each time the pilot signal transmission and reception and the power beam transmission and reception are repeated.

FIG. 31 is a diagram showing the relationship between the beam convergence rate η and energy leakage with respect to the number of repetitions N. Thus, when the number N of pilot signal beam propagation and power beam propagation exceeds 6, the beam convergence rate η exceeds 99%, and when the number N exceeds 6, the energy leakage falls below 1%.

FIG. 32 is a diagram showing a one-dimensional model of an S matrix using a power transmitting antenna and a power receiving antenna. i in Si,j is the number of the element antenna on the power receiving side, and j is the number of the element antenna on the power transmitting side. The white circles are element antennas of the array antenna, and the black circles are element antennas virtually arranged in an area that extends infinitely outside the range of the array antenna.

The S matrix when the power receiving antenna is the input end and the power transmitting antenna is the output end is represented by Sj,i. Assume that each terminal is perfectly matched to the load. The Nth wave pilot signal received on the power transmission side is amplified by the gain GjTx and subjected to phase conjugate operation with the reference signal, as shown in the following equation.

Then, the power receiving antenna receives the power re-radiated from the power transmitting antenna, takes the phase conjugate, and further amplifies it, resulting in the N+1 wave pilot signal shown by the following equation.

Here, if GjTx is a constant value GconstTx, the average value of the amplitude of the Nth wave pilot signal and the average value of the amplitude of the N+1th wave pilot signal are expressed by the following equation. Here, δm,i is Kronecker's delta (identity matrix).

If the electromagnetic field strength is maintained between the transmitting and receiving amplifiers, oscillation will continue. Therefore, the oscillation condition is expressed by the following equation.

In this way, the spatially coupled oscillator made up of the array antennas at the power transmitting station and power receiving station, and the transmission line between them can be treated as a single oscillator, and the oscillation conditions can be determined by one loop gain. .

When the array antenna of the power transmitting station and the array antenna of the power receiving station are finite, the radiation waves from the finite antennas are divided into the radiation of the time reversal field from the infinite antenna and the antiphase time reversal field from the virtual antenna area. It can be expressed by combining. This is expressed by the following relationship.

The second term in the conclusion of the above equation is an anti-phase return wave component from the virtual antenna region, and corresponds to spillover loss. If beam formation is fast and the spillover loss can be considered to be 0, the second term is 0, so [Equation 6] can be treated in the same way as [Equation 4].

If the antenna is small and spillover loss occurs even in the optimal state, the pilot signal distribution is first optimized using the second term. With this, even if there is leakage loss, the oscillation conditions can be satisfied by setting the amplification factor of the amplifier.

In this way, a self-healing effect works to eliminate the return wave component from the virtual antenna region.

33 and 34 are diagrams showing the state of microwave propagation when a microwave absorber exists for some reason in the microwave propagation path. In either example, a power transmitting antenna with a diameter of 50 m and a power receiving antenna with a diameter of 25 m are separated by 5 km. In the example of FIG. 33, a microwave absorber with a diameter of 5 m exists in the middle of the transmission path. In this state, after 98 round trip times (2.5ms) between the pilot signal and the microwave power, due to the action of the bidirectional retrodirective system mentioned above, the microwave is transmitted with uneven power distribution at the power transmission antenna, and the absorber The microwave energy of the existing field is canceled out, and the microwave power is received at the receiving antenna position with a transmission efficiency of 99.3%.

In the example of FIG. 34, a microwave absorber with a diameter of 10 m exists in the middle of the transmission path. In this state, after 148 round trip times (3.8ms) between the pilot signal and the microwave power, due to the action of the bidirectional retrodirective system mentioned above, the power transmitting antenna radiates microwaves to avoid obstacles, and the absorber At the location where the microwave is present, a field is formed that surrounds the absorber to avoid scattering and absorption of the microwave, and at the power receiving antenna position, the microwave power is received with a transmission efficiency of 98.2%. If the diameter of the receiving antenna is a little larger, a transmission efficiency close to 100% can be obtained.

《Floating offshore microwave power repeater》
FIG. 35 is a front view showing the configuration of parasitic relay station 700. This unpowered relay station 700 includes a microwave mirror device 701, a floating body 706, a screw 702, an iron pole 703, and a weight 705. The iron pillar 703 supports the microwave mirror device 701 at a predetermined height from the floating body 706. The weight 705 balances the gravity and the buoyancy of the floating body 706 to keep the height of the microwave mirror device 701 constant. The basic configuration is the same as the parasitic relay station 700 shown in FIG.

FIG. 36 is a plan view showing the configuration of parasitic relay station 700. The microwave mirror device 701 includes a first microwave mirror 711, a second microwave mirror 712, and a cylindrical support that supports them. A radome 707 is provided at the microwave input portion of the microwave mirror device 701, and a radome 708 is provided at the output portion.

Incidentally, a radome can be constructed from a conical (umbrella-shaped) resin plate for parabolic antennas of several meters long used for communications, but for very large power transmission radomes that require low leakage, it is not possible to do so. It is practically impossible to adopt such a configuration. In other words, since the dimensions of the radome are extremely large, a reinforcing support is required, but the reinforcing support reflects and absorbs microwaves, causing a large power loss, so in reality, reinforcement is not necessary. It is not possible to insert a support for Furthermore, if an attempt is made to increase the strength of a conventionally structured radome by increasing its thickness, the absorption of microwaves by the radome will increase.

Radomes 707 and 708 shown in FIG. 36 are made of foamed resin such as Styrofoam (registered trademark) having a thickness that is an integral multiple of a half wavelength. Foamed resin such as expanded polystyrene has low dielectric loss and dielectric constant itself, and low reflection loss and transmission loss.

By the way, if you insert a pillar in the center of the radome, such as the radome of a several-meter parabolic antenna used for communications, the strength will be maintained, but scattered waves will be generated and energy will be lost. It is difficult to cover a 50m diameter radome without pillars. Therefore, here, the length of Styrofoam (registered trademark) is utilized to provide strength while maintaining low loss characteristics.

Moreover, this expanded polystyrene (registered trademark) has a honeycomb structure, which has a lower loss than a structure completely filled with expanded polystyrene (registered trademark). In other words, the thickness is gained by creating cavities by taking advantage of the fact that the dielectric constant is close to that of air. Strength can be maintained with the honeycomb structure. Since the radomes 707 and 708 are circular with a diameter of 50 m, their thickness is, for example, about 5 m to 10 m.

Since the radomes 707 and 708 have a very important role in preventing wind waves and rainstorms, a thin half-wavelength resin plate may be provided at the leading end to prevent seawater from entering and to prevent dust. This resin plate may be attached to the surface of a long Styrofoam (registered trademark). If the thickness of this resin plate is an integral multiple of a half wavelength, perfect matching will be achieved. In the case of microwave power transmission, there is no spread in the frequency band, so there is no need to consider the so-called frequency band characteristics in microwave communication, allowing for accurate design. The leading resin plate may be thin, for example, half a wavelength.

The floating offshore microwave power relay device is not limited to providing one parasitic relay station 700 between the power transmitting device and the power receiving device. FIG. 37 is a diagram showing an example in which two parasitic relay stations 700A and 700B are arranged between the power transmitting device 200 and the power receiving device 100. The parasitic relay station 700A is arranged to receive the microwave energy transmitted from the power transmission device 200 with maximum efficiency, and the parasitic relay station 700B receives the microwave energy transmitted from the parasitic relay station 700A with maximum efficiency. Place it like this. Then, the power receiving device 100 receives microwave power from the parasitic relay station 700B with maximum efficiency. In this way, the transmission distance of microwave power can be extended in proportion to the number of parasitic relay stations 700.

Here, the loss of the reflected wave with respect to the incident wave is generally expressed by the following formula.

Pout／Pin＝1 - 2√{(2εo ω)／σ}
Pin: Power of incident wave
Pout: Power of reflected wave εo: Vacuum dielectric constant ω: Frequency of microwave σ: Electrical conductivity of reflector When the reflector is made of copper, the reflection loss at the reflector is 0.03%. Since there are two reflecting plates in one parasitic relay station 700, the loss in one parasitic relay station 700 is 0.06%. For example, even if the signal is transmitted over a distance of 400 km with 20 relays, the power loss due to passing through the unpowered relay station 700 is only 1.2% at most. In addition to reflection loss, there is also dielectric loss, but after 20 relays, the received power only decreases by about 1.2% to 2%. In this way, since the parasitic relay station 700 does not convert energy, it can be relayed with very low loss.

Moreover, regardless of the number of parasitic relay stations 700, the optimal transmission path is selected by the bidirectional retrodirective operation, so that a decrease in transmission efficiency due to the provision of parasitic relay stations 700 can be suppressed.

FIGS. 38 and 39 are diagrams showing the principle of a microwave repeater that uses a first microwave mirror 711 and a second microwave mirror 712 to cancel minute rotations about three axes. FIG. 38 is a perspective view, and FIG. 39 is a plan view. Here, the relationship between the incident light vector and the reflected light vector, determined from the basic equation of reflection, is as follows.

In this way, if the plate is a parallel plate, the reflected light vector is the same as the incident light regardless of the normal vector of the surface. That is, the beam direction is preserved with a parallel reflector having an arbitrary tilt angle. Therefore, a relay device that is resistant to torsional rotation about three axes can be constructed without power supply.

FIG. 40 is a diagram showing the configuration of a repeater that emits microwaves at a constant angle with respect to the incident direction. In the example shown in FIG. 39 etc., the first microwave mirror 711 and the second microwave mirror 712 are in a parallel relationship, and the incident light and the outgoing light are in the same direction. and the second microwave mirror 712 may be non-parallel (in FIG. 40, the rotation vector is parallel to the two mirrors). Thereby, directionality can be maintained against minute rotations of parasitic relay station 700 about an axis perpendicular to the horizontal plane.

FIG. 41 is a sectional view showing the configuration of a microwave mirror. The microwave mirror includes a dielectric resonator 721 and a reflecting plate 722 shown at the bottom of FIG. This microwave mirror can be said to apply the principle of a light condensing Fresnel lens to microwave beams.

In FIG. 41, a dielectric convex lens and its Fresnel lens are shown in the upper part. In an optical Fresnel lens, the lens segments are arranged flat, but due to the limit of processing accuracy at the wavelength of light, it is impossible to process with precision in units of wavelengths. On the other hand, microwave mirrors have longer wavelengths than light. For example, an optical dielectric lens with a diameter of 51.7 mm corresponds to a diameter of 50 m when using a microwave at 5.8 GHz. Therefore, in order to almost completely eliminate the grating lobe, it is possible to continuously adjust the phase for each wavelength. In this example, the dielectric resonators are arranged at intervals of 0.7 wavelength, which is less than one wavelength. In this way, a more accurate Fresnel lens effect can be achieved with microwaves. For example, a microwave mirror with a diameter of 50 m is designed so that a beam waist is generated at a distance of 10 km due to the reflection of the two microwave mirrors.

FIG. 42 is a diagram showing the structure of one unit of a microwave mirror including a dielectric resonator 721, a reflecting plate 722, and the like. The spherical dielectric resonator 721 utilizes resonance in its TE ₁₁ mode. The incident wave with a frequency other than the resonant frequency of the dielectric resonator is totally reflected, and the incident wave with the resonant frequency propagates through the propagation waveguide between the dielectric resonator and the reflection plate 722 and has a 1/2 wavelength (1 /4 wavelength round trip) is emitted with a delay.

The design and operation of phase control of such a dielectric resonator antenna are as follows.

(1) The microwave is matched with the rear propagation waveguide at the resonant frequency of the dielectric resonator.

(2) The passage phase of the microwave at the resonant frequency of the dielectric resonator is set to 0°.

(3) The reflected wave at the resonant frequency of the dielectric resonator is assumed to be π on the reference plane. That is, reflection at the resonant frequency is equivalent to reflection from a metal surface.

(4) Radio waves with a frequency much lower than the resonant frequency of the dielectric resonator are totally reflected at the reference plane, and the reflection phase is +180°.

(5) Radio waves with a frequency much higher than the resonant frequency of the dielectric resonator are totally reflected at the reference plane, and the reflection phase is -180°.

(6) The operating frequency ωoo is fixed, and the phase of the reflected wave is determined by determining the resonance frequency ωoj of each dielectric resonator.

Dielectric resonators are arranged in an array on an antenna substrate, and the center frequency of the dielectric resonator antenna is varied in the radial direction. As a result, a Fresnel lens type microwave mirror having a phase difference of 360 degrees as shown in FIG. 41 is constructed.

FIG. 43 is a diagram showing another example of a microwave mirror. In the examples shown in FIGS. 41 and 42, a propagation waveguide was provided behind the dielectric resonator, but the microwave mirror shown in FIG. 43 does not include this propagation waveguide.

FIG. 43 is a diagram showing the structure of one unit of a microwave mirror including a dielectric resonator 721, a reflecting plate 722, and the like. In the example shown in FIG. 43, the dielectric resonator 721 has a hemispherical shape, and a metal reflection plate 722 is disposed behind it (a surface corresponding to a cut surface of a sphere). The dielectric resonator 721 resonates in the TE ₀₁₁ mode.

In the case of the dielectric resonator antenna having the structure shown in FIG. 43, the microwave frequency is reflected from the metal surface at both the resonant frequency and the non-resonant frequency of the dielectric resonator 721. At non-resonant frequencies, it is reflected directly from the metal surface, and as it approaches the resonant frequency, it is reflected from the metal surface with a shifted phase. That is, by setting the resonant frequency of the dielectric resonator 721, the phase of the reflected microwave wave can be determined.

The closer the dielectric resonator 721 is to the center of the microwave mirror, the more its resonant frequency deviates from the microwave frequency, and the closer the dielectric resonator 721 is to the periphery of the microwave mirror, the closer its resonant frequency is to the microwave frequency. It is better to be close to (resonate with).

The energy distribution in the cross section of the microwave beam is preferably a Gaussian distribution, but as mentioned above, the resonance frequency deviates from the microwave frequency at the center of the microwave mirror where the energy density is high. Since the dielectric loss caused by the dielectric resonator 721 is reduced, by setting the resonant frequency of the dielectric resonator 721 as described above, the loss can be effectively reduced in the entire microwave mirror.

The resonant frequency of the dielectric resonator shown in FIGS. 42 and 43 can be adjusted by forming a cavity inside, cutting a part of the surface, or changing the diameter.

As described above, instead of forming a concave reflector through high-precision machining, the dielectric resonators 721 are arranged on a flat metal reflector, and the reflection phase is adjusted by the path difference caused by the dielectric resonators 721. Since it is set, high machining accuracy is not required. Furthermore, even if a large-diameter concave reflector can be created by machining, such a large-diameter reflector is likely to be distorted by temperature. In contrast, flat metal plates can be made with high precision. Furthermore, although it is generally very difficult to measure the geometrical dimensions of large members with high precision, in this embodiment, instead of forming lenses by machining and measuring geometrical dimensions, each dielectric The resonant frequency of the body resonator 721 can be measured with extremely high accuracy by electrical measurement. Therefore, a dielectric resonator antenna having a predetermined resonant frequency can be easily formed, and a highly accurate Fresnel lens type microwave mirror can be easily obtained.

Finally, the above description of the embodiments is illustrative in all respects and is not restrictive. Modifications and changes can be made as appropriate by those skilled in the art. The scope of the invention is indicated by the claims rather than the embodiments described above. Furthermore, the scope of the present invention is intended to include all changes within the meaning and range of equivalence of the claims.

For example, an offshore energy collection system includes a plurality of floating power generation devices and a platform separated from the floating power generation devices, and the floating power generation device is a power generation unit that generates electricity while floating on the ocean. and a microwave power transmission unit that transmits the power generated by the power generation unit using microwaves, and the platform includes a microwave power reception unit that receives the microwaves transmitted from the microwave power transmission unit of the floating power generation device. The microwave power transmission section and the microwave power reception section each have an array antenna in which a plurality of element antennas are arranged and are provided at a position higher than the ground boundary layer, and the microwave power reception section transmits a pilot signal. , a power receiving unit side element antenna circuit that receives radio waves transmitted from a microwave power transmitting unit, and the microwave power transmitting unit receives a pilot signal and generates a phase conjugate signal having a phase conjugate relationship of the pilot signal. By driving the element antenna of the microwave power transmission unit with the phase conjugate signal, the microwave power reception unit is equipped with a power transmission unit side element antenna circuit that transmits transmitted power to the microwave power reception unit in a retrodirective operation. , the microwave power may be transmitted by a unidirectional retrodirective operation in which coherent microwaves with the same frequency and phase are received from each floating power generation device.

The floating offshore microwave power repeater of the present invention may be provided in each of the following embodiments.

<1>
A microwave relay device used in a microwave power transmission system comprising a power transmission antenna that is installed on the ocean in a floating state and transmits power using microwaves, and a power reception antenna that receives the microwave power,
a flat first reflecting plate that receives microwaves transmitted from the power transmission antenna and reflects them in a first angular direction on a horizontal plane;
a flat second reflecting plate that receives the microwave reflected by the first reflecting plate and emits it to the power receiving antenna side;
a base that relatively fixes the first reflector and the second reflector;
A plurality of lenses arranged on the first reflecting plate, totally reflecting at a first reference phase at a resonant frequency, and changing the reflection phase from the first reference phase by changing the resonant frequency as the distance from the center of the first reflecting plate increases. a first dielectric resonator;
A plurality of components arranged on the second reflecting plate, totally reflecting at a second reference phase at a resonant frequency, and changing the reflection phase from the second reference phase by changing the resonant frequency as the distance from the center of the second reflecting plate increases. a second dielectric resonator;
A Fresnel lens type microwave mirror is configured by the first reflector and a first dielectric resonator antenna formed by the plurality of first dielectric resonators, and the second reflector and the plurality of second dielectric resonators constitute a Fresnel lens type microwave mirror. A Fresnel lens type microwave mirror is constructed with a second dielectric resonator antenna according to
Floating offshore microwave power repeater.

<2>
The plurality of first dielectric resonators and the plurality of second dielectric resonators are each arranged at intervals of less than one wavelength of the microwave,
The floating offshore microwave power relay device according to <1>.

<3>
the first reflecting plate and the second reflecting plate are parallel;
The floating offshore microwave power relay device according to <1> or <2>.

<4>
the first reflecting plate and the second reflecting plate are non-parallel;
The floating offshore microwave power relay device according to <1> or <2>.

<5>
A radome is provided at the incidence part and the emission part of the microwave,
The radome is made of foamed resin filled in the input part and the output part.
The floating offshore microwave power repeater according to any one of <1> to <3>.

<6>
The foamed resin has a honeycomb structure including a cavity,
The floating offshore microwave power relay device according to <5>.

<7>
A resin plate having a thickness that is an integral multiple of a half wavelength of the microwave is provided on the outer surface of the microwave incidence part and the emission part.
The floating offshore microwave power relay device according to <5> or <6>.

<8>
The resonant frequency of the plurality of dielectric resonator antennas is determined so that the beam waist is located at a position approximately 1/2 of the distance between the antenna and the power transmitting antenna or the power receiving antenna.
The floating offshore microwave power repeater according to any one of <1> to <7>.

Moreover, the offshore microwave power transmission system of the present invention may be provided in each of the following aspects.

<9>
The floating offshore microwave power repeater according to any one of <1> to <8> is arranged at predetermined intervals in the microwave transmission direction, and is located at the horizon or further away from the horizon when viewed from the power transmission antenna. An offshore microwave power transmission system that transmits the microwave power to a certain power receiving antenna.

<10>
The floating offshore microwave power repeater according to any one of <1> to <8> is arranged at a position along the path of the propagating microwave, and transmits the microwave from the power transmitting antenna to the power receiving antenna. An offshore microwave power transmission system that transmits electric power.

CO...Notch DH...Dielectric GB...Reference signal grid board LP...Wiring pattern MB...Microwave beams Px1, Px2...Magnetic coupling probe Py1, Py2...Magnetic coupling probe
RFU...RF units 11, 21...Element antenna 11H...Horizontal polarization element 11V...Vertical polarization element 12...Distributor 13...Rectifier 14...Phase conjugate circuit 17...Power amplifier 20...Power transmission side element antenna circuit 21H...Horizontal Polarization element 21V... Vertical polarization element 24... Phase conjugate circuit 27... Power amplifier 100... Power receiving device 100A, 100B, 100C... Power receiving device 111... Power receiving side array antenna 111C... Array antenna 111P... Array antenna 200... Power transmission device 200A, 200B...Power transmission device 210...Microwave mirror 210A, 210B...Microwave mirror 221...Power transmission side array antenna 221B...Power transmission side array antenna 221C...Pilot signal reception array antenna 221P...Array antenna 300...Floating offshore wind power generation device 301...Windmill 302X, 302Y...Screw 303...Iron column 304...Water tank 304C...Cavity 304W...Fresh water 305...Weight 306...Generator 307X, 307Y...Electric motor 311...Power transmission antenna 500...Platform 501...Tank 510...Microwave mirror 520...Power receiving Antenna 530... Solar power generation panel 540... Substation 600... Inverse dam 601... First water tank 602... Second water tank 603... Electric water pump 604, 605... Communication path 606... Generator 607... Weight 608... Screw 610... Machine room 700... Parasitic relay station 700A, 700B... Parasitic relay station 701... Microwave mirror device 702... Screw 703... Steel column 705... Weight 706... Floating body 707, 708... Radome 711... First microwave mirror 712... Second microwave Mirror 721...Dielectric resonator 722...Reflector plate 800...Ship 810...Power receiving antenna

Claims (10)

A microwave relay device used in a microwave power transmission system comprising a power transmission antenna that is installed on the ocean in a floating state and transmits power using microwaves, and a power reception antenna that receives the microwave power,
a flat first reflecting plate that receives microwaves transmitted from the power transmission antenna and reflects them in a first angular direction on a horizontal plane;
a flat second reflecting plate that receives the microwave reflected by the first reflecting plate and emits it to the power receiving antenna side;
a base that relatively fixes the first reflector and the second reflector;
A plurality of lenses arranged on the first reflecting plate, totally reflecting at a first reference phase at a resonant frequency, and changing the reflection phase from the first reference phase by changing the resonant frequency as the distance from the center of the first reflecting plate increases. a first dielectric resonator;
A plurality of components arranged on the second reflecting plate, totally reflecting at a second reference phase at a resonant frequency, and changing the reflection phase from the second reference phase by changing the resonant frequency as the distance from the center of the second reflecting plate increases. a second dielectric resonator;
A Fresnel lens type microwave mirror is configured by the first reflector and a first dielectric resonator antenna formed by the plurality of first dielectric resonators, and the second reflector and the plurality of second dielectric resonators constitute a Fresnel lens type microwave mirror. A Fresnel lens type microwave mirror is constructed with a second dielectric resonator antenna according to
Floating offshore microwave power repeater. The plurality of first dielectric resonators and the plurality of second dielectric resonators are each arranged at intervals of less than one wavelength of the microwave,
The floating offshore microwave power repeater according to claim 1. the first reflecting plate and the second reflecting plate are parallel;
The floating offshore microwave power repeater according to claim 1 or 2. the first reflecting plate and the second reflecting plate are non-parallel;
The floating offshore microwave power repeater according to claim 1 or 2. A radome is provided at the incidence part and the emission part of the microwave,
The radome is made of foamed resin filled in the input part and the output part.
The floating offshore microwave power repeater according to claim 1 or 2. The foamed resin has a honeycomb structure including a cavity,
The floating offshore microwave power repeater according to claim 5. A resin plate having a thickness that is an integral multiple of a half wavelength of the microwave is provided on the outer surface of the microwave incidence part and the emission part.
The floating offshore microwave power repeater according to claim 5. The resonant frequency of the plurality of dielectric resonator antennas is determined so that the beam waist is located at a position approximately 1/2 of the distance between the antenna and the power transmitting antenna or the power receiving antenna.
The floating offshore microwave power repeater according to claim 1 or 2. The floating offshore microwave power repeater according to claim 1 or 2 is arranged at predetermined intervals in the microwave transmission direction to the power receiving antenna located at the horizon or farther from the horizon when viewed from the power transmitting antenna. An offshore microwave power transmission system that transmits the microwave power. The floating offshore microwave power repeater according to claim 1 or 2 is disposed at a position along a propagating microwave path to transmit the microwave power from the power transmitting antenna to the power receiving antenna. Microwave power transmission system.

Images