JP4772728B2 - Matching circuit, connection circuit, transmitter, receiver, transceiver, and radar device - Google Patents

Description

  The present invention relates to a matching circuit having an impedance adjustment function used in high-frequency circuits such as millimeter waves and microwaves, a connection circuit, a transmitter including the matching circuit, a receiver, a transceiver, and a radar apparatus.

  In an advanced information society in recent years, in order to transmit a large amount of data at a high speed, application systems such as information communication devices using high frequencies from a microwave region of 1 to 30 GHz to a millimeter wave region of 30 to 300 GHz are used. It has been proposed. For example, a system using millimeter waves such as a radar device for measuring a distance between vehicles has been proposed.

In a system using such a high frequency, a high frequency circuit is used. In the technical field of high-frequency circuits, due to the high frequency of signals used, there is a problem that impedance mismatch occurs at the connection part of high-frequency components, and reflection of high-frequency signals is increased. For example, since the reactance of a bonding wire increases due to an inductance component as the frequency increases, MMIC (Microwave Monolithic Integrated)
When a high-frequency component such as a circuit is connected to a transmission line designed to 50 ul by a bonding wire, there is a problem in that impedance mismatch occurs and reflection of the high-frequency signal increases. In order to reduce reflection at the connection portion, a matching circuit for matching impedance is provided on the transmission line side, or the length of the bonding wire is adjusted.

  Even if such a matching circuit is provided, the size of the pattern constituting the matching circuit varies, or the mounting position of the MMIC shifts and the magnitude of the inductance component of the bonding wire varies. There is a problem that an impedance mismatch occurs due to deviation from the value. In addition, when manufacturing a high frequency circuit, if the length of the bonding wire deviates from the design value, the magnitude of the inductance component of the bonding wire deviates from the design value, causing impedance mismatch.

  In order to eliminate impedance mismatch caused by variations in manufacturing a high-frequency circuit, there is a matching circuit capable of adjusting impedance.

  In the first conventional technique, a plurality of adjustment lands separated from the matching circuit are formed in advance, and a specific adjustment land is connected to the matching circuit in the step of adjusting the impedance, thereby matching the impedance. (For example, refer to Patent Document 1).

  In the second conventional technique, a varactor diode is connected in parallel to the transmission line. The capacitance is adjusted by adjusting the voltage applied to the varactor diode to match the impedance of the matching circuit (see, for example, Patent Document 2).

JP 62-269402 A JP-A-3-274902

  In the first conventional technique, when adjusting the impedance, a process of connecting a specific adjustment land to the matching circuit is required, so that the time required for adjusting the impedance becomes long. After connecting the impedance element, it is necessary to check whether impedance matching is achieved. If the impedance does not match, it is necessary to repeat the process of connecting another adjustment land to the matching circuit. The time required for the adjustment becomes longer, and the productivity decreases, resulting in an increase in manufacturing cost. In addition, since the impedance is adjusted by connecting the adjustment land provided in advance to the matching circuit, the impedance of the matching circuit cannot be continuously changed, and the impedance cannot be adjusted with high accuracy. There is.

  In the second conventional technique, since the capacitance of the varactor diode connected in parallel to the transmission line is adjusted, even if the applied voltage of the varactor diode is changed, the reflection coefficient on the complex plane is changed only in one direction. There is a problem that it cannot be adjusted to match any impedance deviation.

  Accordingly, an object of the present invention is to provide a matching circuit, a connection circuit, a transmitter including a matching circuit, a receiver, a transceiver, and a radar apparatus that can easily and accurately adjust a deviation in impedance. is there.

The present invention is branched from different sites from each other, the first branch portion and have a second branch portion, the line length between the second branch portion and the first branch site, the wavelength of the electromagnetic wave to be transmitted Assuming λ, the first transmission line is λ / 8 + n · λ / 4 (the symbol “n” represents an arbitrary natural number including 0) ;
A first end connected to the first branch of the first transmission line ; and a second end spaced from the first branch, the first branch of the first transmission line. A second transmission line branching out from and extending;
A first shift end having at least one first connection end, the first connection end being connected to the second end of the second transmission line, and capable of adjusting a phase of an electromagnetic wave reflected by applying a voltage; Phase circuit,
A second end of the first transmission line; a third end connected to the second branch of the first transmission line ; and a fourth end spaced from the second branch. A third transmission line extending from and branching from
A second transition having at least one second connection end, the second connection end being connected to the fourth end of the third transmission line, and capable of adjusting a phase of an electromagnetic wave reflected by applying a voltage; A matching circuit including a phase circuit.

The present invention also includes the matching circuit;
A connection circuit that electrically connects the first transmission line and the electronic component ;
When an electromagnetic wave is input from the electronic component, the reflection coefficient reflected by the connection circuit may be 0 in a range where the amount of phase shift of the first and second phase shift circuits is variable. The connection circuit is characterized in that a line length between a connection body and the first branch part and line lengths of the second and third transmission lines are selected.

The present invention further includes the matching circuit;
A substrate having the first to third transmission lines and the first and second phase shift circuits, and having electrical insulation;
A component placement part formed on one surface of the substrate, having electrical conductivity, on which an electronic component is placed;
A connection body for electrically connecting the first transmission line and the electronic component;
On the one surface, a projecting portion that is formed to extend along the connection body from the component placement portion toward the region where the first transmission line is provided, and has conductivity,
A back electrode formed on the other surface of the substrate;
Including a conductive portion for conducting the protruding portion and the back electrode ;
The protrusion sandwich the component placement side of the end portion of the first transmission line, a connection circuit and having a first projecting portion and a second projecting portion away from each other.
Furthermore, the present invention is characterized in that the projecting portion further includes a third projecting portion and a fourth projecting portion which are spaced apart from each other and sandwich the first projecting portion and the second projecting portion.

Furthermore, the present invention provides a high frequency oscillator for generating a high frequency signal,
A transmission line connected to the high-frequency oscillator and transmitting a high-frequency signal from the high-frequency oscillator;
The matching circuit in which the first transmission line is inserted into the transmission line;
A transmitter including an antenna connected to the transmission line and radiating a high frequency signal.

The present invention further includes an antenna for capturing a high-frequency signal;
A transmission line connected to the antenna and transmitting a high-frequency signal captured by the antenna;
The first transmission line, the matching circuit inserted into the transmission line;
And a high-frequency detector connected to the transmission line for detecting a high-frequency signal transmitted to the transmission line.

Furthermore, the present invention provides a high frequency oscillator for generating a high frequency signal,
A fourth transmission line connected to the high-frequency oscillator for transmitting a high-frequency signal;
The first terminal is connected to the fourth transmission line, and a high-frequency signal applied to the first terminal is selectively applied to the second terminal or the third terminal. An output branching device;
A fifth transmission line connected to the second terminal and transmitting a high-frequency signal applied from the second terminal;
A fourth, fifth, and sixth terminal that outputs a high-frequency signal to the fourth terminal via the fifth transmission line, and outputs a high-frequency signal to the fifth terminal; A duplexer that outputs to the sixth terminal;
A sixth transmission line connected to the fifth terminal for transmitting a high-frequency signal output from the fifth terminal and transmitting a high-frequency signal to the fifth terminal;
An antenna connected to the sixth transmission line for radiating and capturing high-frequency signals;
A seventh transmission line connected to the third terminal and transmitting a high-frequency signal output from the third terminal;
An eighth transmission line connected to the sixth terminal and transmitting a high-frequency signal output from the sixth terminal;
A mixer that is connected to the seventh and eighth transmission lines, mixes high-frequency signals given from the seventh and eighth transmission lines, and outputs an intermediate frequency signal;
The transceiver is characterized in that the first transmission line includes the matching circuit inserted into at least one of the fourth to eighth transmission lines.

Furthermore, the present invention provides a high frequency oscillator for generating a high frequency signal,
A fourth transmission line connected to the high-frequency oscillator for transmitting a high-frequency signal;
The first terminal is connected to the fourth transmission line, and a high-frequency signal applied to the first terminal is selectively applied to the second terminal or the third terminal. An output branching device;
A fifth transmission line connected to the second terminal and transmitting a high-frequency signal applied from the second terminal;
A transmitting antenna connected to the fifth transmission line and emitting a high-frequency signal;
A receiving antenna for capturing high-frequency signals;
A sixth transmission line connected to the receiving antenna and transmitting the captured high-frequency signal;
A seventh transmission line connected to the third terminal and transmitting a high-frequency signal output from the third terminal;
A mixer that is connected to the sixth and seventh transmission lines, mixes high-frequency signals given from the sixth and seventh transmission lines, and outputs an intermediate frequency signal;
The transceiver is characterized in that the first transmission line includes the matching circuit inserted into at least one of the fourth to seventh transmission lines.

Furthermore, the present invention includes the transceiver,
A radar apparatus comprising: a distance detector that detects a distance from the transceiver to a detection target based on an intermediate frequency signal from the transceiver.

  According to the present invention, the first transmission line includes a first stub that functions as a stub by the second transmission line and the first phase shift circuit, and a second stub that functions as a stub by the third transmission line and the second phase shift circuit. Provided. Each of the first and second phase shift circuits can adjust the phase of the reflected electromagnetic wave by applying a voltage. Therefore, by adjusting the voltage applied to the first phase shift circuit, the electrical length of the first stub when the first stub is reciprocated once can be adjusted. Similarly, by adjusting the voltage applied to the second phase shift circuit, the electrical length of the second stub can be adjusted when the second stub is reciprocated once. The impedances of the first branch portion where the second transmission line of the first transmission line branches and the second branch portion where the third transmission line branches depend on the electrical lengths of the first and second stubs, respectively. Therefore, by adjusting the electrical lengths of the first and second stubs, the impedance of the entire matching circuit can be adjusted. As a result, even if variations in the manufacturing process occur in shapes such as the length and line width of the first to third transmission lines, matching is achieved by adjusting the voltage applied to the first and second phase shift circuits. The impedance of the entire circuit can be adjusted as designed.

  Further, when the electronic component is connected to the first transmission line with a connection body such as a bonding wire, the impedance of the connection circuit including the connection body and the matching circuit depends on the mounting state of the electronic component, the length of the connection body, and Depends on the connection status of the connection body such as placement. Even after mounting electronic components in this way and connecting the electronic components with the connection body, the impedance when the connection body and the matching circuit are viewed from the electronic components can be adjusted by adjusting the impedance of the matching circuit. it can. For example, by adjusting the voltage applied to the first phase shift circuit and the second phase shift circuit so as to match the impedance between the connection circuit including the connection body and the matching circuit and the electronic component, it is output from the electronic component. Power can be prevented from being reflected by the matching circuit, and insertion loss at the connection portion connecting the electronic components can be minimized. Further, by adjusting the impedance of the matching circuit, the electronic component can be connected to the designed load and used, and the characteristics as designed of the electronic component can be obtained.

  In the present invention, impedance matching is achieved by adjusting the magnitude of the voltage applied to the first and second phase shift circuits, so that it is more accurate than the first conventional technique for digitally adjusting impedance. Impedance matching can be achieved.

  In the second conventional technique, the capacitance of the varactor diode connected in parallel with the transmission line is adjusted. Therefore, even if the applied voltage of the varactor diode is changed, the reflection coefficient on the complex plane is only in one direction. Although it cannot be changed, in the present invention, by adjusting the electrical lengths of the two stubs, the reflection coefficient on the complex plane can be changed in an arbitrary direction, and an arbitrary impedance deviation is matched. Can be adjusted.

  Further, according to the present invention, the first and second phase shift circuits are configured by the connection circuit that electrically connects the first transmission line and the electronic component and the matching circuit within a range in which the phase shift amount is variable. When an electromagnetic wave is input from the electronic component to the connection circuit, there is a case where the reflection coefficient reflected by the connection circuit becomes 0 in a range where the amount of phase shift of the first and second phase shift circuits is variable. Thus, the line length between the connection body and the first branch part and the line lengths of the second and third transmission lines are selected. Usually, since the range of the phase shift amount that can be adjusted by the voltage applied to the first and second phase shift circuits is limited, the line length of the first to third transmission lines is set to an arbitrary length. In some cases, the reflection coefficient reflected by the connection circuit of the electromagnetic wave input from the electronic component to the connection circuit cannot be adjusted to zero. In the present invention, the connection body and the first branch part are arranged so that the reflection coefficient of the connection circuit may be 0 within the range of the phase shift amount adjustable by the voltage applied to the first and second phase shift circuits. And the lengths of the second and third transmission lines are selected, so that after mounting the electronic component and electrically connecting the electronic component and the matching circuit via the connection body, the first By adjusting the voltage applied to the second phase shift circuit, the electromagnetic wave output from the electronic component can be prevented from being reflected by the connection circuit. As a result, the insertion loss at the connection part connecting the electronic components can be minimized, and the electronic components can be connected to the designed load and used, and the characteristics as designed can be obtained. it can.

Furthermore, according to the present invention, it is formed extending from the component placement portion formed on one surface in the thickness direction of the substrate along the connection body toward the region where the first transmission line is provided. Protrusions having a shape are formed. The protruding portion and the back electrode formed on the other surface in the thickness direction of the substrate are electrically connected via the conductive portion. Moreover, this protrusion has the 1st protrusion part and 2nd protrusion part which mutually space | interpose which pinch | interpose the edge part by the side of the components transmission part of a 1st transmission line. If the protrusion is not provided, the transmission mode is coupled to the parallel plate mode formed by the component placement portion and the back electrode, resulting in leakage and an increase in transmission loss. By providing the projecting portion, transmission in the parallel plate mode can be suppressed and transmission loss can be suppressed, so that electromagnetic waves can be efficiently transmitted from the electronic component to the matching circuit via the connection body.

  Further, according to the present invention, since a matching circuit is inserted in the transmission line, even if, for example, variations in the length and shape of bonding wires and bumps for connecting a high-frequency oscillator and the wiring width of the transmission line occur. By adjusting the impedance of the matching circuit, impedance matching with the high-frequency oscillator can be achieved. As a result, a transmitter having stable oscillation characteristics and a high transmission output can be realized because the insertion loss is suppressed to a small value.

  Furthermore, according to the present invention, the high frequency signal captured by the antenna is transmitted to the transmission line and detected by the high frequency detector. In the present invention, since a matching circuit is inserted in the transmission line, for example, even if there are variations in the length and shape of the bonding wires and bumps for connecting the high-frequency detector and the wiring width of the transmission line, matching is performed. By adjusting the impedance of the circuit, impedance matching with the high-frequency detector can be achieved. As a result, it is possible to realize a receiver having a stable detection characteristic and a high detection output since the insertion loss is suppressed to be small.

  Further, according to the present invention, the high-frequency signal generated by the high-frequency oscillator is transmitted to the fourth transmission line and given to the first terminal of the branching device, and is given to the fifth transmission line from the second terminal of the branching device. It is given to the fourth terminal of the duplexer, given from the fifth terminal of the duplexer to the sixth transmission line, and radiated from the antenna. The high-frequency signal received by the antenna is given to the sixth transmission line, given to the fifth terminal of the duplexer, given from the sixth terminal of the duplexer to the eighth transmission line, and given to the mixer. . In addition, a high-frequency signal generated by the high-frequency oscillator is supplied as a local signal from the third terminal of the branching unit to the mixer via the seventh transmission line. The mixer mixes the high-frequency signal generated by the high-frequency oscillator and the high-frequency signal received by the antenna and outputs an intermediate frequency signal, thereby obtaining information contained in the received high-frequency signal.

  When a matching circuit is inserted into at least one of the fourth to eighth transmission lines, for example, even if variations in wiring width occur, impedance matching is performed by adjusting the impedance of the matching circuit. Can be planned. As a result, for example, a transmitter / receiver having a stable oscillation characteristic and a high transmission output can be realized because the insertion loss is suppressed to a low level, and also, for example, having a stable detection characteristic and a low insertion loss. Therefore, a transceiver having a high detection output can be realized, the reliability of the received high-frequency signal can be improved, and the reliability of an intermediate frequency signal generated by, for example, a mixer can be improved.

  Further, according to the present invention, the high-frequency signal generated by the high-frequency oscillator is transmitted to the fourth transmission line and given to the first terminal of the branching device, and is given to the fifth transmission line from the second terminal of the branching device. Radiated from the antenna. The high-frequency signal received by the receiving antenna is given to the sixth transmission line and given to the mixer. In addition, a high-frequency signal generated by the high-frequency oscillator is supplied as a local signal from the third terminal of the branching unit to the mixer via the seventh transmission line. The mixer mixes the high-frequency signal generated by the high-frequency oscillator and the high-frequency signal received by the receiving antenna and outputs an intermediate frequency signal, thereby obtaining information contained in the received high-frequency signal.

  When a matching circuit is inserted into at least one of the fourth to seventh transmission lines, for example, even if variations in wiring width occur, impedance matching is performed by adjusting the impedance of the matching circuit. Can be planned. As a result, for example, it is possible to realize a transmitter / receiver having a stable oscillation characteristic and a high transmission output since the insertion loss is suppressed to a low level, and also having a stable detection characteristic and a low insertion loss, for example. Therefore, it is possible to realize a transmitter / receiver having a high detection output, to improve the reliability of a received high-frequency signal, and to improve the reliability of an intermediate frequency signal generated by, for example, a mixer .

  Furthermore, according to the present invention, since the distance detector detects the distance from the transceiver to the detection object based on the intermediate frequency signal from the transceiver, the distance to the detection object can be accurately detected. Radar device.

  FIG. 1 is a perspective view showing a matching circuit 1 according to an embodiment of the present invention. The matching circuit 1 is electrically connected to the electronic component 2 through a conductive connection body. The impedance of the matching circuit 1 is adjusted so that an electromagnetic wave (hereinafter referred to as a high frequency signal) input from the electronic component 2 through the connection body is not reflected by the connection circuit 3 including the connection body and the matching circuit 1. That is, the impedance of the matching circuit 1 is adjusted so that the high-frequency signal output from the electronic component 2 is efficiently output from the output port P of the matching circuit 1 with low loss. The electronic component 2 is, for example, a high-frequency oscillator, a mixer, and an amplifier realized by MMIC.

The matching circuit 1 in the present embodiment includes first to third transmission lines 6, 7, 8 provided on the surface of the dielectric substrate 5 in the thickness direction (hereinafter referred to as the third direction Z) Z1, and the first A phase shift circuit 11 and a second phase shift circuit 12 are included. The dielectric substrate 5 has electrical insulation, is formed of a dielectric, and is formed of glass, single crystal, ceramics, resin, or a composite thereof. As glass, quartz glass, crystallized glass, or the like is used. As the single crystal, Si, GaAs, quartz, sapphire, MgO, LaAlO ₃ or the like is used. As the ceramic, alumina, aluminum nitride, glass ceramic, forsterite, cordierite, or the like is used. As the resin, an epoxy resin, a fluorine-containing resin, a liquid crystal polymer, or the like is used. The dielectric substrate 5 is realized by a single layer substrate or a multilayer substrate. In the case of a multilayer substrate, the thickness in the thickness direction (third direction Z) of each layer is selected to be 100 μm to 150 μm.

The dielectric substrate 5 is made into a slurry by adding an appropriate organic solvent and solvent to raw powders such as alumina and silica (SiO ₂ ), for example, and is formed into a sheet-like ceramic green sheet by a doctor blade method or a calender roll method. Next, the ceramic green sheet is formed by appropriate punching, and a plurality of sheets are laminated as necessary, and fired at a high temperature of about 1500 ° C. to 1800 ° C., for example.
On the surface of the other side Z2 of the dielectric substrate 5 in the third direction, a conductive back electrode 9 is formed on the entire surface. Further, the dielectric substrate 5 is provided with a mounting portion 4 on which the electronic component 2 is mounted. The mounting unit 4 includes a component placement table 14 formed on the surface of the dielectric substrate 5 in the third direction one Z1. The electronic component 2 is placed on the component placement table 14.

  The first transmission line 6 is formed to extend linearly on the surface of the dielectric substrate 5 in the third direction one Z1. Hereinafter, a direction in which the first transmission line 6 extends is referred to as a first direction X, and directions perpendicular to the first direction X and the third direction Z are referred to as second directions Y, respectively. The electronic component 2 and the first transmission line 6 are electrically connected by a conductive connection body such as a bump and a bonding wire 15, for example, and are connected by the bonding wire 15 in the present embodiment. When connecting with bumps, bumps are formed as connecting members on the surface of the electronic component 2 facing the dielectric substrate 5, and the bumps and the first transmission line 6 are connected by surface mounting such as flip chip. May be. The first transmission line 6 is arranged such that the free end portion in the first direction X1 is slightly spaced from the component placement table 14. The bonding wire 15 connects the free end portion of the first transmission line 6 in the first direction X1 and the input / output terminal 16 of the electronic component 2. The high-frequency signal output from the input / output terminal 16 of the electronic component 2 passes through the bonding wire 15 and the first transmission line 6, and is output from the output port P at the end of the first transmission line 6 in the other direction X2. The

  The second and third transmission lines 7 and 8 extend from the first transmission line 6 by branching in the second direction Y, respectively. The first branch part 17 where the second transmission line 7 branches and the second branch part 18 where the third transmission line 8 branches differ from each other in the extending direction (first direction X) of the first transmission line 6. In the present embodiment, the first branch portion 17 is provided in the first direction X1 with respect to the second branch portion 18. The direction of the second direction Y in which the second and third transmission lines 7 and 8 extend from the first transmission line 6 may be the same or opposite. In the present embodiment, the second transmission line 7 is the first branch portion 17. The third transmission line 8 extends from the second branch portion 18 to the other Y2 in the second direction.

  The first to third transmission lines 6, 7, and 8 are realized by a microstrip line, a coplanar line, a strip line, a waveguide, a dielectric waveguide, an image guide, a non-radiative dielectric line, and the like, respectively. The first to third transmission lines 6, 7, and 8 in the present embodiment are realized by microstrip lines, and each include a conductive line, a dielectric substrate 5, and a back electrode 9. . The conductive line is selected to have a line width of about 100 μm to 500 μm so that transmission loss of a high-frequency signal to be transmitted is reduced.

  The first phase shift circuit 11 has at least one first connection end, and has two first connection ends 21a and 21b in the present embodiment. In the first phase shift circuit 11, one first connection end 21 a is connected to the free end portion of the second transmission line 7 in the second direction Y 1. The second phase shift circuit 12 has at least one second connection end, and has two second connection ends 22a and 22b in the present embodiment. In the second phase shift circuit 12, one second connection end 22 a is connected to the free end portion of the other Y 2 in the second direction of the third transmission line 8. The first and second phase shift circuits 11 and 12 apply a voltage between the two first connection terminals 21a and 21b and between the second connection terminals 22a and 22b, respectively, to thereby reflect the reflected high-frequency signal. The phase can be adjusted. The first and second phase shift circuits 11 and 12 are composed of variable capacitance elements whose electric capacitance changes according to an applied voltage. The first and second phase shift circuits 11 and 12 are semiconductor elements such as varactor diodes, ferroelectric elements, piezoelectric elements, and MEMS (Micro Electrodes). This is realized by a voltage controlled variable capacitor including a mechanical system) element, and in this embodiment, realized by a varactor diode.

  The matching circuit 1 of the present embodiment includes a first voltage application circuit 23 that applies a voltage to the first phase shift circuit 11, a second voltage application circuit 24 that applies a voltage to the second phase shift circuit 12, and a first And a ground circuit 25 for supplying a reference potential GND for determining a voltage applied to the second phase shift circuits 11 and 12.

  The first voltage application circuit 23 is electrically connected to the other first connection end 21 b of the first phase shift circuit 11. The first voltage application circuit 23 is connected to the other first connection end 21b of the first phase shift circuit 11 and has a transmission line 23a extending in the second direction Y, and a radial provided in the middle of the transmission line 23a. And a stub 23b. The second voltage application circuit 24 is connected to the other second connection end 22b of the second phase shift circuit. The second voltage application circuit 24 has an end connected to the other second connection end 22b of the second phase shift circuit 12, a transmission line 24a extending in the second direction Y, and a radial provided in the middle of the transmission line 24a. And a stub 24b. The ground circuit 25 is provided in the middle of the transmission line 25a that extends in the second direction one Y1 from the third branch part 19 in the other X2 in the first direction than the second branch part 18 of the first transmission line 6 and the second direction. And a radial stub 25b. Each transmission line 23a, 24a, 25a has the same configuration as the first to third transmission lines 6, 7, 8 described above. Each radial stub 23b, 24b, 25b is formed in a fan shape, and the tip is connected to each transmission line 23a, 24a, 25a. Each radial stub 23b, 24b, 25b is selected in shape and size so that it appears to be a short circuit with respect to a high-frequency signal at the connection position in each transmission line 23a, 24a, 25a. As a result, leakage of high-frequency signals is suppressed, and transmission loss of the matching circuit 1 is reduced. In the radial stubs 23b and 24b, the connection positions in the transmission lines 23a and 24a are the reactance components obtained by combining the first phase shift circuit 11 and the first voltage application circuit 23, and the first phase shift circuit 12 and the second voltage application circuit. The reactance component including 24 is selected to be close to 0, and is provided to increase the amount of phase change when a voltage is applied to the first and second phase shift circuits 11 and 12. The radial stub 25b is selected so as to appear open to the high frequency signal at the connection position in the first transmission line 6. Note that low-pass filters may be provided in place of the radial stubs 23b, 24b, and 25b.

  The ground circuit 25 and the back electrode 9 may be connected by a conductive via that penetrates the dielectric substrate 5 in the third direction Z. The conductive via is formed by filling a through hole penetrating the dielectric substrate 5 in the third direction Z with a conductive material, and has a conductive property. The ground circuit 25 is equipotential with the back electrode 9 through the conductive via. In the present embodiment, the potential of the back electrode 9 is set to the reference potential GND, which is 0V. One first connection end 21a of the first phase shift circuit 11 and the other second connection end 22a of the second phase shift circuit 12 are connected to the ground circuit 25 via the first to third transmission lines 6, 7, 8 respectively. Is set to 0 V, which is the same as that of the back electrode 9.

Positive voltages (+ V ₁ , + V ₂ ) are applied to the first and second voltage application circuits 23 and 24 with respect to the reference potential GND (0 V), respectively. As a result, a voltage of + V ₁ is applied to the other first connection end 21 b of the first phase shift circuit 11, and a voltage of + V ₂ is applied to the other second connection end 22 b of the second phase shift circuit 12. The voltages supplied to the first and second voltage application circuits 23 and 24 may be supplied from a power source provided on the dielectric substrate 5, and electrode pads are formed at the ends of the transmission lines 23a and 24a. Then, the power may be supplied from a power source provided on a substrate different from the dielectric substrate 5 via bonding wires connected to each electrode pad.

The second transmission line 7 and the first phase shift circuit 11 constitute a first stub 33 that functions as an open stub provided in the first transmission line 6. The third transmission line 8 and the second phase shift circuit 12 constitute a second stub 34 that functions as an open stub provided in the first transmission line 6. That is, the first transmission line 6 is provided with two open stubs. The first and second phase shift circuits 11 and 12 can adjust the phase of the reflected electromagnetic wave by applying voltages (+ V ₁ , + V ₂ ), respectively. Therefore, by adjusting the voltage (+ V ₁ ) applied to the first phase shift circuit 11, the electrical length of the first stub 33 when the first stub 33 is reciprocated once can be adjusted. Similarly, by adjusting the voltage (+ V ₂ ) applied to the second phase shift circuit 12, the electrical length of the second stub 34 when the second stub 34 reciprocates once can be adjusted. The impedances of the first branch portion 17 where the second transmission line 7 branches and the second branch portion 18 where the third transmission line 8 branches depend on the electrical lengths of the first and second stubs 33 and 34, respectively. Therefore, by adjusting the electrical lengths of the first and second stubs 33 and 34, the impedance of the entire matching circuit 1 can be adjusted.

A first stub composed of the second transmission line 7, the first phase shift circuit 11 and the first voltage application circuit 23, and a second stub composed of the third transmission line 8, the second phase shift circuit 12 and the second voltage application circuit 24. Constitutes a double stub and forms a matching circuit for mismatching caused by the bonding wire 15. A part of the high-frequency signal input from the electronic component 2 to the matching circuit 1 is reflected by the bonding wire 15, the rest is input to the first transmission line 6 via the bonding wire 15, and a part thereof is the first branch portion. 17 and the second branch portion 18 are reflected. The high frequency signal reflected by the bonding wire 15 and the high frequency signal reflected by the first and second branch portions 17 and 18 are superimposed on each other. For example, by adjusting the voltages (+ V ₁ , + V ₂ ) applied to the first and second phase shift circuits 11 and 12 so that the phases of the superimposed high-frequency signals are different from each other by πrad, the high-frequency signals cancel each other. Thus, the reflected high frequency signal can be reduced.

  In the present embodiment, the bonding wire 15 that electrically connects the first transmission line 6 and the electronic component 2 within the range in which the amount of phase shift of the first and second phase shift circuits 11 and 12 is variable, and the matching circuit The bonding wire 15 and the first branch portion 17 are arranged so that there is a case where the reflection coefficient of the electromagnetic wave input from the electronic component 2 to the connection circuit 3 configured by 1 is reflected by the connection circuit 3 is 0. The line length between them and the line lengths of the second and third transmission lines 7 and 8 are selected.

  In the present embodiment, the line length between the first branch portion 17 and the second branch portion 18 is selected as λ / 8 + n · λ / 4 where λ is the wavelength of the high-frequency signal (the symbol “n” is Represents any natural number including 0).

  In the first transmission line 6 according to the present embodiment, a high-pass filter is provided between the connection part to which the bonding wire 15 is connected and the first branch part 17 and between the third branch part 19 and the output port P. Is further provided. The high-pass filter is realized by a configuration in which a thin insulating film formed of, for example, silicon nitride and silicon oxide is sandwiched between transmission lines, an interdigital capacitor, a ceramic capacitor, a single plate capacitor, a thin film capacitor, and the like. Is first electromagnetically coupled to a transmission line formed in the inner layer of the dielectric substrate 5, or is first transmitted to a dielectric waveguide inside the dielectric substrate 5 through a slot extending from the first transmission line 6 in the third direction Z. This is realized by connecting the line 6. Such a high-pass filter cuts off the DC voltage supplied by the first and second voltage application circuits 23 and 24 and allows the high-frequency signal output from the electronic component 2 to pass. By providing the high-pass filter, the voltage applied to the first and second phase shift circuits 11 and 12 by the first and second voltage application circuits 23 and 24 is connected to the matching circuit 1 across the high-pass filter. And it can prevent being applied to other circuits.

  FIG. 2 is a plan view showing the mounting portion 4. The matching circuit 1 of the present embodiment further includes a mounting unit 4. The mounting unit 4 is configured such that a high-frequency signal output from the electronic component 2 is efficiently output with low loss from the output port P of the matching circuit 1. The mounting portion 4 is formed on the surface of the dielectric substrate 5, the Z direction one side Z <b> 1 of the dielectric substrate 5, and has a conductive component placement table 14 on which the electronic component 2 is disposed, and the dielectric substrate. 5, on the surface of one side Z <b> 1 in the third direction, extending from the component placement table 14 toward the region where the first transmission line 6 is provided, and having a conductive protrusion 26 and the dielectric substrate 5. The back surface electrode 9 formed on the surface of the other side Z <b> 2 in the third direction and the conductive portion 27 that conducts the protruding portion 26 and the back surface electrode 9 are configured.

  The component placement table 14 is formed in a longitudinal plate shape extending in the second direction Y on the surface of the dielectric substrate 5 in the third direction one Z1. The component placement table 14 is disposed such that the center in the second direction Y overlaps the extension line of the first transmission line 6 and is disposed as close to the first transmission line 6 as possible. The width of the component placement table 14 in the second direction Y is a region protruding from the electronic component 2 in the second direction Y1 and the second direction Y2 when the electronic component 2 is disposed when viewed from the third direction Z1. It is selected wider than the electronic component 2 so that 29a and 29b are formed. The electronic component 2 is arranged near the end portion close to the first transmission line 6 in the component arrangement table 14 with the input / output terminal 16 overlapping the extension line of the first transmission line 6 when viewed from one side Z1 in the third direction. The As a result, the length of the bonding wire 15 can be made as short as possible. The length of the bonding wire 15 is designed to be about 300 μm to 700 μm, and the diameter is about 25 μm.

  The protruding portion 26 is formed on the surface of the dielectric substrate 5 in the third direction one Z1 so as to extend from the component placement table 14 toward the region where the first transmission line 6 is provided. The protrusion 26 has conductivity and is formed of the same material as that of the component placement table 14. The protruding portion 26 in the present embodiment is configured to include four protruding portions 28 extending from the component placement table 14 in the other first direction X2. Each projecting portion 28 is formed apart from the first transmission line 6 so as not to be connected to the first transmission line 6, and is arranged at intervals in the second direction Y. The four projecting portions 28 are arranged symmetrically with respect to the extension line of the first transmission line 6 when viewed from one side Z1 in the third direction. Of the four projecting portions 28, a pair of projecting portions 28 arranged on the inner side are referred to as first and second projecting portions 28a and 28b, respectively, and a pair of projecting portions 28 arranged on the outer side are respectively described. It describes as the 3rd and 4th protrusion part 28c, 28d.

  The conducting portion 27 is composed of one or more first conducting portions 27 a that electrically connect the component placement table 14 and the back electrode 9, and one or more that electrically connects each protruding portion 28 and the back electrode 9. 2nd conduction | electrical_connection part 27b is included. The first and second conducting portions 27a and 27b are each formed by filling a through hole penetrating the dielectric substrate 5 with a conductive material. In the present embodiment, the first conductive portions 27a are arranged on the entire component placement table 14 with a predetermined interval when viewed from one side Z1 in the third direction. The component placement table 14 is set to the same potential as the back electrode 9 through the first conduction part 27a. By providing the plurality of first conduction portions 27a, a local deviation from the reference potential GND of the component placement table 14 can be eliminated as quickly as possible.

  The second conduction portion 27 b is formed by filling a through hole penetrating the dielectric substrate 5 between each protruding portion 28 and the back electrode 9 with a conductive material. Each protruding portion 28 is set to the same potential as the back electrode 9 via the second conducting portion 27b. Since each protruding portion 28 is connected to the component placement table 14, even if the second conducting portion 27b is not provided, the protruding portion 28 is set to the same potential as the back electrode 9. However, by providing the second conducting portion 27b, the reference potential GND is provided. Deviation from can be resolved as quickly as possible.

  Back surface electrode 9, conductive lines constituting first to third transmission lines 6, 7, 8, component placement table 14, first and second voltage application circuits 23, 24, ground circuit 25, conduction via, The first and second conducting portions 27a and 27b are mainly made of conductive materials such as Cu (copper), Ag (silver), W (tungsten), Mo (molybdenum), Al (aluminum), Ni (nickel), and Au (gold), respectively. It is formed of a metal having properties. For example, through holes for the first and second conducting portions 27a and 27b are formed in the ceramic green sheet for the dielectric substrate 5 by a punching method using a die or punching or a processing method such as laser processing. The through holes for the second conductive portions 27a and 27b are filled with conductive paste for conductive vias by printing means such as a screen printing method, and the back electrode 9 and the first to third transmission lines 6, 7, 8 and the like. The metallized paste for printing is applied by printing and fired together with the ceramic green sheet for the dielectric substrate 5. The metallized paste is prepared by adding an organic binder, an organic solvent and, if necessary, a dispersant to the main component metal powder, and mixing and kneading them by a kneading means such as a ball mill, a three-roll mill, or a planetary mixer. Glass or ceramic powder may be added to match the sintering behavior of the ceramic green sheet or to increase the bonding strength with the dielectric substrate 5 after firing.

  The line width W1 in the second direction Y of the first transmission line 6 and the distance W3 between the first and second projecting portions 28a and 28b and the first transmission line 6 are the first transmission line 6 as a signal line, When viewed as a coplanar line with the first and second projecting portions 28a and 28b as the ground, the impedance viewed from the first transmission line 6 side includes the output impedance of the electronic component 2 including the bonding wire 15 (in this embodiment, 50Ω). The interval W3 is set so that the bonding wire 15, a ground wire 31a, which will be described later, and a ground wire 31b are parallel and shortest. Further, the line width W1 and the interval W3 of the first transmission line 6 also depend on the interval between the input / output pads composed of the input / output terminal 16 of the electronic component 2 and the ground terminals 32a and 32b.

  The width W2 in the first direction X of the first and second projecting portions 28a and 28b is such that the impedance including the bonding wire 15 and the matching circuit 1 matches the electronic component 2, and the input / output terminal 16 of the electronic component 2 Is set so as to reduce reflection of light. The width W2 in the first direction X of the first and second projecting portions is selected so as to sandwich at least the end portion of the first transmission line 6 near the component placement table 14 by the first and second projecting portions 28a and 28b. . The width W2 of the first and second protruding portions in the first direction X is preferably selected to be slightly larger than λ / 4 of the wavelength λ of the high-frequency signal output from the electronic component 2. For example, when the wavelength of the high frequency signal is 1500 μm, the width W2 of the first and second protruding portions is selected to be 410 μm.

  Further, the interval W4 between the first protruding portion 28a and the third protruding portion 28c, and the interval W4 between the second protruding portion 28b and the fourth protruding portion 28d are impedances including the bonding wire 15 and the matching circuit 1. It is set so as to match with the electronic component 2 and to reduce reflection at the input / output terminal 16 of the electronic component 2, and is selected to be, for example, about λ / 8 or more and less than λ / 4. In the present embodiment, in the second direction Y, the pair of third and fourth projecting portions 28c and 28d are provided outside the first and second projecting portions 28a and 28b, but a plurality of pairs of projecting portions 28 are provided. Further, an interval between the projecting portions 28 in this case is set similarly to the interval W4.

  The width W5 in the first direction X of the third and fourth protruding portions 28c and 28d is such that the impedance including the bonding wire 15 and the matching circuit 1 is matched with the electronic component 2, and the input / output terminal 16 of the electronic component 2 Is set so as to reduce reflection of light. The width W5 of the third and fourth projecting portions 28c, 28d is selected to be, for example, about λ / 4. For example, when the wavelength of the high frequency signal is 1500 μm, the width W5 of the third and fourth projecting portions 28c and 28d is selected to be 380 μm.

  In the present embodiment, the electronic component 2 has a pair of ground terminals 32a and 32b to which a reference potential GND is applied. The ground terminals 32a and 32b are provided on the surface of the electronic component 2 in the first direction X1 with the input / output terminal 16 interposed therebetween. The input / output terminal 16 and the pair of ground terminals 32a and 32b are provided at end portions near the first transmission line 6 in a state where the electronic component 2 is disposed on the component placement table 14, respectively. One ground terminal 32a is provided on an extension line of the first projecting portion 28a when viewed from the first direction X1. The other ground terminal 32b is provided on an extension line of the second projecting portion 28b when viewed from one side Z1 in the third direction.

  One ground terminal 32a and the first protruding portion 28a are electrically connected by a ground wire 31a. The other ground terminal 32b and the second projecting portion 28b are electrically connected by a ground wire 31b. One ground wire 31a and the other ground wire 31b are realized by bonding wires having the same configuration as the bonding wire 15 in the present embodiment.

According to the matching circuit 1 of the present embodiment described above, the first stub 33 functioning as a stub by the second transmission line 7 and the first phase shift circuit 11, the third transmission line 8 and the second phase shift circuit 12. Thus, a second stub 34 functioning as a stub is provided on the first transmission line 6. As described above, the electrical length of the first stub 33 can be adjusted by adjusting the voltage (+ V ₁ ) applied to the first phase shift circuit 11, and the voltage applied to the second phase shift circuit 12 ( By adjusting + V ₂ ), the electrical length of the second stub 34 can be adjusted. The impedances of the first branch portion 17 where the second transmission line 7 branches and the second branch portion 18 where the third transmission line 8 branches depend on the electrical lengths of the first and second stubs 33 and 34, respectively. Therefore, by adjusting the electrical lengths of the first and second stubs 33 and 34, the impedance of the entire matching circuit 1 can be adjusted. As a result, even if variations in the manufacturing process occur in the shapes such as the lengths and line widths of the first to third transmission lines 6, 7, and 8, they are applied to the first and second phase shift circuits 11 and 12. By adjusting the voltages (+ V ₁ , + V ₂ ), the impedance of the entire matching circuit 1 can be adjusted as designed.

  Furthermore, the impedance of the connection circuit 3 including the bonding wire 15 and the matching circuit 1 depends on the mounting state of the electronic component 2 and the connection state of the bonding wire 15 such as the length and arrangement of the bonding wire 15. Even when the electronic component 2 is mounted in this way and the electronic component 2 is connected by the bonding wire 15, when the bonding wire 15 and the matching circuit 1 are viewed from the electronic component 2 by adjusting the impedance of the matching circuit 1. Can be adjusted. For example, by adjusting the voltage applied to the first and second phase shift circuits 11 and 12 so as to match the impedance between the connection circuit 3 including the bonding wire 15 and the matching circuit 1 and the electronic component 2, The power output from the component can be prevented from being reflected by the matching circuit, and the insertion loss at the connection portion connecting the electronic components can be minimized. Further, by adjusting the impedance of the matching circuit, the electronic component 2 can be connected to the designed load and used, and the characteristics as designed of the electronic component 2 can be obtained. For example, when an oscillation element having an output impedance of 50Ω is used as the electronic component 2, a stable oscillation frequency, oscillation output, and phase noise as designed can be obtained by adjusting the impedance of the connection circuit 3 to 50Ω.

In the present invention, impedance matching is achieved by adjusting the magnitude of the voltage applied to the first and second phase shift circuits (+ V ₁ , + V ₂ ). Compared with this technique, impedance matching can be achieved with higher accuracy.

  In the second conventional technique, the capacitance of the varactor diode connected in parallel with the transmission line is adjusted. Therefore, even if the applied voltage of the varactor diode is changed, the reflection coefficient on the complex plane is only in one direction. In the present invention, the reflection coefficient on the complex plane can be changed in any direction by adjusting the electrical lengths of the two first and second stubs 33 and 34, respectively. It is possible to adjust so as to match the deviation of the impedance.

Furthermore, in the matching circuit 1 of the present embodiment, the bonding wire that electrically connects the first transmission line 6 and the electronic component 2 within a range in which the phase shift amounts of the first and second phase shift circuits 11 and 12 are variable. 15 and the bonding wire 15 so that the reflection coefficient of the electromagnetic wave input from the electronic component 2 to the connection circuit 3 constituted by the matching circuit 1 is reflected by the connection circuit 3 may be zero. The line length between the one branch parts 17 and the line lengths of the second and third transmission lines 7 and 8 are selected. Usually, since the range of the phase shift amount that can be adjusted by the voltages (+ V ₁ , + V ₂ ) applied to the first and second phase shift circuits 11 and 12 is limited, the first to third transmission lines 6 and 7 , 8 is set to an arbitrary length, the reflection coefficient reflected by the connection circuit of electromagnetic waves input from the electronic component 2 to the connection circuit 3 may not be adjusted to zero. In the present embodiment, the reflection coefficient of the connection circuit 3 becomes 0 within the range of the phase shift amount that can be adjusted by the voltages (+ V ₁ , + V ₂ ) applied to the first and second phase shift circuits 11 and 12. Since the line length between the bonding wire 15 and the first branch part 17 and the line lengths of the second and third transmission lines 7 and 8 are selected so as to exist, the electronic component 2 is mounted and the electronic component 2 And the matching circuit 1 are electrically connected via the bonding wire 15, and then the electronic components 2 are adjusted by adjusting the voltages (+ V ₁ , + V ₂ ) applied to the first and second phase shift circuits 11, 12. Can be prevented from being reflected by the connection circuit 3. As a result, the insertion loss at the connecting portion for connecting the electronic component 2 can be minimized, and the electronic component 2 can be used by being connected to the designed load. Obtainable.

In particular, in the present embodiment, the line length between the first branch portion 17 and the second branch portion 18 is selected to be approximately λ / 8 + n · λ / 4, where λ is the wavelength of the high-frequency signal. For example, when the line length between the first branch part 17 and the second branch part 18 approaches n · λ / 2, the change in the impedance of the matching circuit 1 with respect to the frequency of the high-frequency signal increases, and (2 · n + 1) When approaching λ / 4, the range of impedance that can be adjusted is reduced by adjusting the voltages (+ V ₁ , + V ₂ ) applied to the first and second phase shift circuits 11, 12, but approximately λ / 8 + n By setting λ / 4, the change in impedance of the matching circuit 1 with respect to the frequency of the high-frequency signal is reduced, and the voltages (+ V ₁ , + V ₂ ) applied to the first and second phase shift circuits 11 and 12 are reduced. By adjusting, the adjustable impedance range can be increased.

  Further, according to the matching circuit 1 of the present embodiment, the protruding portion 26 and the bonding wire 15 are electromagnetically coupled to form a transmission line. If the protruding portion 26 is not provided, the transmission mode is coupled to the parallel plate mode formed by the component placement table 14 and the back electrode 9, resulting in leakage and an increase in transmission loss. By providing the protrusion 26, transmission in the parallel plate mode can be suppressed and transmission loss can be suppressed, so that a high-frequency signal can be transmitted efficiently. As a result, transmission loss of high-frequency signals can be reduced. Further, as another embodiment of the present invention, a concave portion may be formed by scoring the surface portion of the dielectric substrate 5 in the first direction Z1 in the third direction, and the component placement table 14 may be arranged in the concave portion. Thereby, the length of the bonding wire 15 can be shortened.

  Further, according to the matching circuit 1 of the present embodiment, the first and second projecting portions 28 a and 28 b constituting the projecting portion 26 are provided apart from each other in the second direction Y, and the component arrangement of the first transmission line 6 is performed. It is formed to extend from the component placement table 14 to a position sandwiching the end near the table 14. Therefore, when the bonding wire 15 connected to the input / output terminal 16 of the electronic component 2 is connected to the end portion of the first transmission line 6 near the component placement table 14, the bonding wire 15 has the first and It is provided along the 2nd protrusion part 28a, 28b. As a result, the entire bonding wire 15 is electromagnetically coupled to the protruding portion 26 to form a pseudo coplanar transmission line, and as described above, a high-frequency signal can be efficiently transmitted by the bonding wire 15. Signal transmission loss can be reduced. In particular, since the first and second projecting portions 28a and 28b are formed in the shape described above, transmission loss of high frequency signals can be reduced.

  Furthermore, according to the matching circuit 1 of the present embodiment, a plurality of protruding portions 28 are formed in addition to the first and second protruding portions 28a and 28b. In addition to the first and second projecting portions 28a and 28b and the ground wires 31a and 31b, a plurality of projecting portions 28 and the bonding wire 15 constitute a transmission line, and the bonding wire 15 efficiently provides a high-frequency signal. Can be transmitted, and transmission loss of high-frequency signals can be reduced. In particular, since the third and fourth projecting portions 28c and 28d are formed in the shape described above, transmission loss of high-frequency signals can be reduced.

  Further, since a pair of ground wires 31 a and 31 b are provided along the bonding wire 15, the transmission line is formed by the ground wires 31 a and 31 b and the bonding wire 15 in addition to the first and second protruding portions 28 a and 28 b. The high-frequency signal can be efficiently transmitted by the bonding wire 15, and the transmission loss of the high-frequency signal can be reduced.

  FIG. 3 is a schematic diagram showing a configuration of the transmitter 40 according to the embodiment of the present invention. The transmitter 40 includes the matching circuit 1 of the embodiment shown in FIG. 1 described above, a high frequency oscillator 41, a transmission line 42, and a transmitting antenna 43. The high-frequency oscillator 41 includes a Gunn oscillator that uses a Gunn diode, an Impat oscillator that uses an Impat diode, or an MMIC that functions as an oscillator that uses a transistor such as an FET (Field Effect Transistor). appear. The transmission line 42 includes a microstrip line, a strip line, a coplanar line, a coplanar line with a ground, a slot line, a waveguide, a dielectric waveguide, a bonding wire, and the like. A first end 42 a of the transmission line 42 in the transmission direction of the high frequency signal is connected to the high frequency oscillator 41, and a second end 42 b of the transmission line 42 in the transmission direction of the high frequency signal is connected to the transmitting antenna 43. The transmitting antenna 43 is realized by a patch antenna or a horn antenna. The transmission direction of the high frequency signal is the propagation direction of the electromagnetic wave.

  In the matching circuit 1, the first transmission line 6 is inserted into the transmission line 42 so that the high-frequency signal passes. More specifically, the transmission line 42 includes a transmission line corresponding to the bonding wire 15 that electrically connects the end of the first transmission line 6 in the first direction X1 and the high-frequency oscillator 41; The transmission line 6 includes a transmission line that electrically connects the end of the other X2 in the first direction of the transmission line 6 and the transmitting antenna 43. A high frequency oscillator 41 corresponding to the electronic component 2 is arranged on the component arrangement table 14.

  A high-frequency signal generated by the high-frequency oscillator 41 passes through the transmission line 42 and the matching circuit 1, is given to the transmitting antenna 43, and is radiated as a radio wave from the transmitting antenna 43. As described above, since the matching circuit 1 is inserted into the transmission line 42, for example, there are variations in the length and shape of bonding wires and bumps for connecting the high-frequency oscillator 41, the wiring width of the transmission line 42, and the like. However, it is possible to match the impedance with the high-frequency oscillator 41 by adjusting the impedance of the matching circuit 1. As a result, the transmitter 40 having stable oscillation characteristics and high transmission output can be realized because the insertion loss is suppressed to a small value.

  FIG. 4 is a schematic diagram illustrating a configuration of the receiver 50 according to the embodiment of this invention. The same configurations as those of the transmitter 40 of the above-described embodiment shown in FIG. 3 are denoted by the same reference numerals, and the description thereof may be omitted.

  The receiver 50 includes the matching circuit 1, the high frequency detector 51, the transmission line 42, and the receiving antenna 53 of the above-described embodiment. The high frequency detector 51 is realized by, for example, a Schottky barrier diode detector, a video detector, or an MMIC that functions as a mixer.

  The first end 42 a of the transmission line 42 in the transmission direction of the high frequency signal is connected to the high frequency detector 51, and the second end 42 b of the transmission line 42 in the transmission direction of the high frequency signal is connected to the receiving antenna 53. . The receiving antenna 53 is realized by a planar antenna such as a patch antenna, a horn antenna, a rod antenna, or the like.

  In the matching circuit 1, the first transmission line 6 is inserted into the transmission line 42 so that the high-frequency signal passes through the matching circuit 1. More specifically, the transmission line 42 is a transmission line corresponding to the above-described bonding wire 15 that electrically connects the end of the first transmission line 6 in the first direction X1 and the high-frequency detector 51; The first transmission line 6 includes a transmission line that electrically connects the end portion of the other X2 in the first direction and the receiving antenna 53. The high frequency detector 51 corresponding to the electronic component 2 is arranged on the component arrangement table 14. When a radio wave coming from the outside is captured by the reception antenna 53, the reception antenna 53 gives a high frequency signal based on the radio wave to the transmission line 42, passes through the matching circuit 1, and the high frequency signal received by the high frequency detector 51 is received. Given. The high frequency detector 51 detects a high frequency signal and detects information included in the high frequency signal. In the receiver 50, the high-frequency signal captured by the receiving antenna 53 is transmitted to the transmission line 42 and detected by the high-frequency detector 51.

  As described above, since the matching circuit 1 is inserted into the transmission line 42, for example, variations in the length and shape of bonding wires and bumps for connecting the high frequency detector 51, the wiring width of the transmission line 42, and the like occur. Even so, it is possible to match the impedance with the high-frequency detector 51 by adjusting the impedance of the matching circuit 1. Accordingly, it is possible to realize the receiver 50 having a stable detection characteristic and a high detection output since the insertion loss is suppressed to be small.

  FIG. 5 is a schematic diagram illustrating a configuration of a radar apparatus 70 including the transceiver 60 according to the embodiment of this invention. In the radar apparatus 70, the same reference numerals are given to the same configurations as those of the transmitter 40 and the receiver 50 of the above-described embodiment shown in FIGS. 3 and 4, and the description thereof may be omitted. The radar apparatus 70 includes a transceiver 60 and a distance detector 71.

  The transceiver 60 includes the matching circuit 1, the high frequency oscillator 41, the fourth to eighth transmission lines 61, 62, 63, 64, 65, the branching unit 66, the branching unit 67, A transmission / reception antenna 68 and a mixer 69 are included. The transmission / reception antenna 68 is realized by a patch antenna or a horn antenna. The fourth to eighth transmission lines 61, 62, 63, 64, 65 have the same configuration as the transmission line 42 described above.

  The first end 61a of the fourth transmission line 61 in the high-frequency signal transmission direction is connected to the high-frequency oscillator 41, and the second end 61b of the fourth transmission line 61 in the high-frequency signal transmission direction is connected to the branching device 66. Is done. In the matching circuit 1, the first transmission line 6 is inserted into the fourth transmission line 61 so that the high-frequency signal passes through the matching circuit 1. More specifically, the fourth transmission line 61 includes a transmission line corresponding to the above-described bonding wire 15 that electrically connects the end of the first transmission line 6 in the first direction X1 and the high-frequency oscillator 41. The first transmission line 6 includes a transmission line that electrically connects the end of the other X2 in the first direction X2 and the branching device 66. A high frequency oscillator 41 corresponding to the electronic component 2 is arranged on the component arrangement table 14.

  The branching device (switching device) 66 has first, second, and third terminals 66a, 66b, 66c, and a high-frequency signal applied to the first terminal 66a is selectively applied to the second terminal 66b and the third terminal 66c. Output to. The branching device 66 is realized by, for example, a high frequency switching element. The branching device 66 is supplied with a control signal from a control unit (not shown), and selectively connects the first terminal 66a and the second terminal 66b or the first terminal 66a and the third terminal 66c based on the control signal. The radar device 70 is realized by a pulse radar. The controller connects the first terminal 66a and the second terminal 66b, outputs a pulsed high-frequency signal from the second terminal 66b, and then connects the first terminal 66a and the third terminal 66c to generate a high-frequency signal. A signal is output from the third terminal 66c. A first end 62a of the fifth transmission line 62 in the transmission direction of the high frequency signal is connected to the second terminal 66b. A first end portion 64a of the seventh transmission line 64 in the transmission direction of the high frequency signal is connected to the third terminal 66c. The radar apparatus 70 may be realized by FM-CW radar using a voltage-controlled oscillator as an oscillator.

  The duplexer 67 has fourth, fifth, and sixth terminals 67a, 67b, and 67c, outputs a high-frequency signal applied to the fourth terminal 67a to the fifth terminal 67b, and provides a high-frequency signal applied to the fifth terminal 67b. The signal is output to the sixth terminal 67c. A second end 62b of the fifth transmission line 62 in the high-frequency signal transmission direction is connected to the fourth terminal 67a. The fifth terminal 67b is connected to a first end 63a of the sixth transmission line 63 in the high-frequency signal transmission direction. A second end 63 b of the sixth transmission line 63 in the high-frequency signal transmission direction is connected to the transmission / reception antenna 68.

  The sixth terminal 67c is connected to the first end portion 65a of the eighth transmission line 65 in the transmission direction of the high frequency signal. The second end portion 64 b of the seventh transmission line 64 in the high-frequency signal transmission direction and the second end portion 65 b of the eighth transmission line 65 in the high-frequency signal transmission direction are connected to the mixer 69. The duplexer 67 is realized by a hybrid circuit. The hybrid circuit is realized by a directional coupler, a branch line, a magic T, a rat race, or the like.

  The high-frequency signal generated by the high-frequency oscillator 41 passes through the fourth transmission line 61 and the matching circuit 1 and passes through the branching device 66, the fifth transmission line 62, the branching filter 67, and the sixth transmission line 63. 68 and radiated as radio waves from the transmitting / receiving antenna 68. The high frequency signal generated by the high frequency oscillator 41 passes through the fourth transmission line 61 and the matching circuit 1 and is given as a local signal to the mixer 69 via the branching device 66 and the seventh transmission line 64.

  When a radio wave arriving from the outside is received by the transmission / reception antenna 68, the transmission / reception antenna 68 gives a high-frequency signal based on the radio wave to the sixth transmission line 63 and to the mixer 69 via the duplexer 67 and the eighth transmission line 65. It is done.

  The mixer 69 mixes the high frequency signals supplied from the seventh and eighth transmission lines 64 and 65 and outputs an intermediate frequency signal. The intermediate frequency signal output from the mixer 69 is given to the distance detector 71.

  The distance detector 71 includes the high-frequency detector 51 described above, and is based on the intermediate frequency signal obtained by receiving the radio wave (echo) radiated from the transmitter / receiver 60 and reflected by the measurement object, Calculate the distance to the measurement object. The distance detector 71 is realized by a microcomputer, for example.

  In the transmitter / receiver 60, the matching circuit 1 is inserted into the fourth transmission line 61 so that a high-frequency signal passes through the matching circuit 1, so that, for example, even if variations in wiring width occur, the matching circuit 1 By adjusting the impedance, impedance matching with the high frequency oscillator 41 can be achieved. As a result, for example, the transmitter / receiver 60 having a stable oscillation characteristic and a high transmission output can be realized because the insertion loss is suppressed to be small, and also has a stable detection characteristic and the insertion loss is suppressed to be small. Therefore, the transmitter / receiver 60 having a high detection output can be realized, and the reliability of the intermediate frequency signal generated by the mixer 69 can be improved, for example.

  In the radar apparatus 70, based on the intermediate frequency signal from the transmitter / receiver 60, the distance detector detects the distance from the transmitter / receiver 60 to the detection target, for example, the distance from the transmission / reception antenna 68 to the detection target. The distance to the detection object can be accurately detected.

  The branching unit 66 may be realized by a hybrid circuit such as a directional coupler or a power divider. In this case, the high-frequency signal supplied to the first terminal 67a is branched to the second terminal 66b and the third terminal 66c. Is output. In this case, the power of the radio wave output from the transmission / reception antenna 68 is lower than that of the configuration described above, but the control of the apparatus is simplified because it is not necessary to control the branching device 66.

  In the present embodiment, the matching circuit 1 is inserted into the fourth transmission line 61, but the matching circuit 1 in still another embodiment of the present invention is at least one of the fourth to eighth transmission lines 61 to 65. For example, the high-frequency signal may be inserted so as to pass through the matching circuit 1. Even if it is such a structure, the same effect can be achieved.

  In still another embodiment of the present invention, the duplexer 67 may be realized by a circulator or a high frequency switching element, and even with such a configuration, the same effect can be achieved. it can.

  FIG. 6 is a schematic diagram showing a configuration of a radar apparatus 86 including a transceiver 85 according to another embodiment of the present invention. In the radar apparatus 86, the same reference numerals are given to the same configurations as those of the transmitter 40 and the receiver 50 of the above-described embodiment shown in FIGS. 3 and 4, and the description thereof may be omitted. The radar apparatus 86 includes a transceiver 85 and a distance detector 71.

  The transceiver 85 includes the matching circuit 1 according to the above-described embodiment, the high-frequency oscillator 41, the fourth to seventh transmission lines 61, 62, 63, and 64, the branching unit 66, the transmitting antenna 43, and the receiving unit. An antenna 53 and a mixer 69 are included. The transmitting antenna 43 and the receiving antenna 53 are realized by a patch antenna or a horn antenna. The fourth to seventh transmission lines 61, 62, 63, 64 have the same configuration as the transmission line 42 described above.

  The first end 61a of the fourth transmission line 61 in the high-frequency signal transmission direction is connected to the high-frequency oscillator 41, and the second end 61b of the fourth transmission line 61 in the high-frequency signal transmission direction is connected to the branching device 66. Is done. In the matching circuit 1, the first transmission line 6 is inserted into the fourth transmission line 61 so that the high-frequency signal passes through the matching circuit 1.

  The branching device (switching device) 66 has first, second, and third terminals 66a, 66b, 66c, and a high-frequency signal applied to the first terminal 66a is selectively applied to the second terminal 66b and the third terminal 66c. Output to. The branching device 66 is realized by, for example, a high frequency switching element. The branching device 66 is supplied with a control signal from a control unit (not shown), and selectively connects the first terminal 66a and the second terminal 66b or the first terminal 66a and the third terminal 66c based on the control signal. The radar device 86 is realized by a pulse radar. The controller connects the first terminal 66a and the second terminal 66b, outputs a pulsed high-frequency signal from the second terminal 66b, and then connects the first terminal 66a and the third terminal 66c to generate a high-frequency signal. A signal is output from the third terminal 66c. A first end 62a of the fifth transmission line 62 in the transmission direction of the high frequency signal is connected to the second terminal 66b. A first end portion 64a of the seventh transmission line 64 in the transmission direction of the high frequency signal is connected to the third terminal 66c. The radar device 86 may be realized by FM-CW radar using a voltage-controlled oscillator as an oscillator.

  The second end 62 b of the fifth transmission line 62 in the transmission direction of the high frequency signal is connected to the transmission antenna 43.

  The receiving antenna 53 and the mixer 69 are connected by a sixth transmission line 63. The second end portion 64 b of the seventh transmission line 64 in the transmission direction of the high frequency signal is connected to the mixer 69.

  The high-frequency signal generated by the high-frequency oscillator 41 passes through the fourth transmission line 61 and the matching circuit 1, is given to the transmitting antenna 43 through the branching device 66 and the fifth transmission line 62, and is transmitted from the transmitting antenna 43 to the radio wave. Is emitted as. The high frequency signal generated by the high frequency oscillator 41 passes through the fourth transmission line 61 and the matching circuit 1 and is given as a local signal to the mixer 69 via the branching device 66 and the seventh transmission line 64.

  When the reception antenna 53 receives a radio wave coming from the outside, the reception antenna 53 gives a high-frequency signal based on the radio wave to the mixer 69 via the sixth transmission line 63.

  The mixer 69 mixes the high frequency signals supplied from the sixth and seventh transmission lines 63 and 64 and outputs an intermediate frequency signal. The intermediate frequency signal output from the mixer 69 is given to the distance detector 71.

  The distance detector 71 includes the high-frequency detector 51 described above, and is based on the intermediate frequency signal obtained by receiving the radio wave (echo) radiated from the transmitter / receiver 85 and reflected by the measurement object, Calculate the distance to the measurement object. The distance detector 71 is realized by a microcomputer, for example.

  In the transceiver 85, the matching circuit 1 is inserted into the fourth transmission line 61 by inserting the matching circuit 1 into the fourth transmission line 61 so that the high-frequency signal passes through the matching circuit 1. Thus, even if, for example, variations in wiring width occur, impedance matching with the high-frequency oscillator 41 can be achieved by adjusting the impedance of the matching circuit 1. As a result, for example, the transmitter / receiver 85 having a stable oscillation characteristic and a high transmission output can be realized because the insertion loss is suppressed to a small level, and also has a stable detection characteristic and a small insertion loss. Therefore, the transmitter / receiver 85 having a high detection output can be realized, and, for example, the reliability of the intermediate frequency signal generated by the mixer 69 can be improved.

  In the radar device 86, based on the intermediate frequency signal from the transmitter / receiver 85, the distance detector is a distance from the transmitter / receiver 85 to the detection target, for example, the distance between the transmitting and receiving antennas 43 and 53 and the detection target. Therefore, the distance to the detection target can be accurately detected.

  The branching unit 66 may be realized by a hybrid circuit such as a directional coupler or a power divider. In this case, the high-frequency signal supplied to the fifth transmission line 62 branches to the second terminal 66b and the third terminal 66c. Is output. In this case, the power of the radio wave output from the transmitting antenna 43 is lower than that of the configuration described above, but the control of the apparatus is simplified because it is not necessary to control the branching device 66.

  In the present embodiment, the matching circuit 1 is inserted into the fourth transmission line 61. However, in still another embodiment of the present invention, the matching circuit 1 is at least one of the fourth to seventh transmission lines 61 to 64. Alternatively, the high-frequency signal may be inserted so as to pass through the matching circuit 1. Even if it is such a structure, the same effect can be achieved.

1 is a perspective view showing a matching circuit 1 according to an embodiment of the present invention. FIG. 6 is a plan view showing a mounting unit 4. It is a schematic diagram which shows the structure of the transmitter 40 of one Embodiment of this invention. It is a schematic diagram which shows the structure of the receiver 50 of one Embodiment of this invention. It is a schematic diagram which shows the structure of the radar apparatus 70 provided with the transmitter / receiver 60 of one Embodiment of this invention. It is a schematic diagram which shows the structure of the radar apparatus 86 provided with the transmitter / receiver 85 of other embodiment of this invention.

Explanation of symbols

DESCRIPTION OF SYMBOLS 1 Matching circuit 2 Electronic component 3 Connection circuit 4 Mounting part 5 Dielectric board 6 1st transmission line 7 2nd transmission line 8 3rd transmission line 9 Back electrode 11 1st phase shift circuit 12 2nd phase shift circuit 14 Component placement stand 23 1st voltage application circuit 23a, 24a, 25a Transmission line 23b, 24b, 25b Radial stub 24 2nd voltage application circuit 25 Ground circuit 26 Protrusion part 27 Conduction part 40 Transmitter 41 High frequency oscillator 42 Transmission line 43 Transmission antenna 50 Reception Unit 51 High Frequency Detector 53 Reception Antenna 60 Transmitter / Receiver 66 Branching Unit 67 Divider 68 Transmit / Receive Antenna 69 Mixer 70 Radar Device 71 Distance Detector 85 Transceiver 86 Radar Device

Claims (9)

Branches from different sites, the first branch portion and have a second branch portion, the line length between the first branch portion and the second branch portion, when the wavelength of an electromagnetic wave transmitting and lambda, a first transmission line that is λ / 8 + n · λ / 4 (the symbol “n” represents an arbitrary natural number including 0) ;
A first end connected to the first branch of the first transmission line ; and a second end spaced from the first branch, the first branch of the first transmission line. A second transmission line branching out from and extending;
A first shift end having at least one first connection end, the first connection end being connected to the second end of the second transmission line, and capable of adjusting a phase of an electromagnetic wave reflected by applying a voltage; Phase circuit,
A second end of the first transmission line; a third end connected to the second branch of the first transmission line ; and a fourth end spaced from the second branch. A third transmission line extending from and branching from
A second transition having at least one second connection end, the second connection end being connected to the fourth end of the third transmission line, and capable of adjusting a phase of an electromagnetic wave reflected by applying a voltage; A matching circuit comprising a phase circuit. A matching circuit according to claim 1;
A connection circuit that electrically connects the first transmission line and the electronic component ;
When an electromagnetic wave is input from the electronic component, the reflection coefficient reflected by the connection circuit may be 0 in a range where the amount of phase shift of the first and second phase shift circuits is variable. connection circuit, characterized in that the line length and line length of the second and third transmission line between the and the connector first branch site is selected. A matching circuit according to claim 1;
A substrate having the first to third transmission lines and the first and second phase shift circuits, and having electrical insulation;
A component placement part formed on one surface of the substrate, having electrical conductivity, on which an electronic component is placed;
A connection body for electrically connecting the first transmission line and the electronic component;
On the one surface, a projecting portion that is formed to extend along the connection body from the component placement portion toward the region where the first transmission line is provided, and has conductivity,
A back electrode formed on the other surface of the substrate;
Including a conductive portion for conducting the protruding portion and the back electrode ;
The projecting portion, the said first transmission line to sandwich the end portion of the component placement side, connection circuit and having a first projecting portion and a second projecting portion away from each other. 4. The connection circuit according to claim 3, wherein the projecting portion further includes a third projecting portion and a fourth projecting portion that are spaced apart from each other and sandwich the first projecting portion and the second projecting portion. A high-frequency oscillator that generates a high-frequency signal;
A transmission line connected to the high-frequency oscillator and transmitting a high-frequency signal from the high-frequency oscillator;
The matching circuit according to claim 1 , wherein the first transmission line is inserted into the transmission line;
A transmitter comprising: an antenna connected to the transmission line and radiating a high frequency signal. An antenna that captures high-frequency signals;
A transmission line connected to the antenna and transmitting a high-frequency signal captured by the antenna;
The matching circuit according to claim 1 , wherein the first transmission line is inserted into the transmission line;
And a high-frequency detector connected to the transmission line and detecting a high-frequency signal transmitted to the transmission line. A high-frequency oscillator that generates a high-frequency signal;
A fourth transmission line connected to the high-frequency oscillator for transmitting a high-frequency signal;
The first terminal is connected to the fourth transmission line, and a high-frequency signal applied to the first terminal is selectively applied to the second terminal or the third terminal. An output branching device;
A fifth transmission line connected to the second terminal and transmitting a high-frequency signal applied from the second terminal;
A fourth, fifth, and sixth terminal that outputs a high-frequency signal to the fourth terminal via the fifth transmission line, and outputs a high-frequency signal to the fifth terminal; A duplexer that outputs to the sixth terminal;
A sixth transmission line connected to the fifth terminal for transmitting a high-frequency signal output from the fifth terminal and transmitting a high-frequency signal to the fifth terminal;
An antenna connected to the sixth transmission line for radiating and capturing high-frequency signals;
A seventh transmission line connected to the third terminal and transmitting a high-frequency signal output from the third terminal;
An eighth transmission line connected to the sixth terminal and transmitting a high-frequency signal output from the sixth terminal;
A mixer that is connected to the seventh and eighth transmission lines, mixes high-frequency signals given from the seventh and eighth transmission lines, and outputs an intermediate frequency signal;
The transceiver including the matching circuit according to claim 1 , wherein the first transmission line is inserted into at least one of the fourth to eighth transmission lines. A high-frequency oscillator that generates a high-frequency signal;
A fourth transmission line connected to the high-frequency oscillator for transmitting a high-frequency signal;
The first terminal is connected to the fourth transmission line, and a high-frequency signal applied to the first terminal is selectively applied to the second terminal or the third terminal. An output branching device;
A fifth transmission line connected to the second terminal and transmitting a high-frequency signal applied from the second terminal;
A transmitting antenna connected to the fifth transmission line and emitting a high-frequency signal;
A receiving antenna for capturing high-frequency signals;
A sixth transmission line connected to the receiving antenna and transmitting the captured high-frequency signal;
A seventh transmission line connected to the third terminal and transmitting a high-frequency signal output from the third terminal;
A mixer that is connected to the sixth and seventh transmission lines, mixes high-frequency signals given from the sixth and seventh transmission lines, and outputs an intermediate frequency signal;
The transceiver including the matching circuit according to claim 1 , wherein the first transmission line is inserted into at least one of the fourth to seventh transmission lines. The transceiver according to claim 7 or 8 ,
A radar apparatus comprising: a distance detector that detects a distance from the transceiver to a detection target based on an intermediate frequency signal from the transceiver.

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