JP2770286B2 - Vibration noise control device - Google Patents

Description

DETAILED DESCRIPTION OF THE INVENTION

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a vibration noise control apparatus, more specifically, to actively control periodic or pseudo-periodic vibration noise generated from a rotating body or the like to reduce the vibration noise. The present invention relates to a vibration noise control device that can be used.

[0002]

2. Description of the Related Art In recent years, adaptive digital filters (Adaptiv
e Digital Filter: An active vibration noise control device that attenuates the vibration noise generated from the vibration noise source using the "ADF" to reduce the vibration noise has been actively developed in various fields. Have been.

[0003] Among these various types of active vibration noise control devices, a vibration noise control device suitable for reducing vibration noise having periodicity or pseudo-periodicity generated from a vehicle of an automobile or the like is related to driving of a power plant. Is input to the adaptive control circuit, and a predetermined pulse signal (trigger signal) having
The present applicant has already proposed a device designed to reduce the vibration noise by updating the filter coefficient of the first filter means composed of F and performing adaptive control (Japanese Patent Application No. 4-88075). issue).

However, in the above-mentioned vibration noise control apparatus, although the pulse signal is directly input to the adaptive control circuit, a complicated product-sum operation is reduced, and the convergence of the adaptive control can be improved to some extent. Since the number of generated sampling pulses within the generation period of the pulse signal (trigger signal) is the tap length of the ADF, the ADF having a tap length that can correspond to any generation period of the pulse signal (trigger signal) is used. Required. Further, depending on the vibration noise period, the tap length becomes long and the product-sum operation takes time, resulting in a disadvantage that the convergence speed of the adaptive control is reduced.

Therefore, as a measure for solving such a drawback, the applicant of the present invention generates a sinusoidal wave of a single period for the vibration noise period peculiar to each component of the vibration noise source, and converts the sinusoidal wave to the ADF. A vibration and noise control device for inputting has been proposed (Japanese Patent Application No. 5-037458).

In the vibration noise control device, a finite-length impulse response (FiniteImpulse Response:
An FIR) type Wiener filter having a tap number of “2” (hereinafter referred to as “W filter”) is used, and a rotation signal of the rotating body is converted into a pulse signal at every predetermined minute rotation angle (for example, at every 3.6 °). Detected. Then, for example, a sine wave for one cycle is generated for each rotation of the rotator, and the sine wave is input to the first filter means to perform adaptive control. But it is possible,
It is considered that the time required for the product-sum operation can be reduced.

[0007]

However, according to the results of subsequent simulations by the present applicant, in the above-described prior art, when adaptive control is performed using the above-described two-tap W filter, one cycle per one cycle is performed. If the number of generated pulse signals, that is, the number of generated divided signals is excessively increased, a new problem arises in that the convergence of adaptive control deteriorates when the phase delay of the system is taken into consideration.

That is, the phase and amplitude of the W filter can be arbitrarily changed by inputting a sine wave, and when the input signal S (n) is discretely displayed, the expression (1 ') is obtained.

[0009]

(Equation 1) Here, for the sake of convenience, if Im indicating the imaginary part is omitted, the input signal S (n) is represented by Expression (2 ′).

[0010]

(Equation 2) n is a discrete time signal. K represents k = (2π / N), and N represents the number of divided signals generated. Further, an input signal S ′ having a phase delay φ with respect to the input signal S (n).
(N) is represented by equation (3 ').

[0011]

(Equation 3) Since this input signal S '(n) is adaptively controlled by the W filter and canceled out, if the first filter coefficient of the W filter is T (1) and the second filter coefficient is T (2), The input signal S '(n) is represented by equation (4').

S ′ (n) = T (1) · S (n) + T (2) · S (n−1) (4 ′) Therefore, the equations (2 ′) and (3 ′) are expressed by the following equations. By substituting into (4 '), equation (5') is obtained, and equation (6 ') is derived from equation (5').

[0013]

(Equation 4)

[0014]

(Equation 5) The above equation (6 ′) indicates that the first and second filter coefficients T (1), T (2) and k (= (2π /) of the W filter when the input signal S (n) has a phase delay φ. N)). Then, the amplitude condition of the control signal generated by the first filter coefficient T (1) and the second filter coefficient T (2) forms an elliptical locus on the T plane as shown in Expression (7 '). , And the phase condition is, as shown in equation (8 '),
Form a linear trajectory.

(T (1) + T (2) cos K) ² + T (2) ² sin ² K = 1 (7 ′) tan φ = −T (2) sin K / (T (1) + T ( 2) cos K) (8 ') Therefore, the first and second filter coefficients T (1), T (1')
(2) is obtained by solving the above equations (7 ') and (8') for T (1) and T (2).
And equation (10 ').

T (1) = cos φ + (sin φ / tan k) (9 ′) T (2) = − (sin φ / sin k) (10 ′) By the way, the number of divided signals N N when the number is extremely large
Since it can be approximated as → ∞, k is approximated as k → 0. Therefore, when the phase delay φ is not “0”, that is, when the phase delay φ occurs, the first and second filter coefficients T (1) and T (2) are calculated by the equations (11 ′) and (11 ′). 1
2 ').

When 0 <φ <π, [T (1), T (2)] = [+ ∞, −∞] (11 ′) When −π <φ <0, [T (1) , T (2)] = [− ∞, + ∞] (12 ′) On the other hand, when Equations (7 ′) and (8 ′) are approximated to k → 0, the amplitude condition becomes Equation (13 ′). The phase condition is given by equation (14 ').

T (2) = ± 1−T (1) (13 ′) φ = 0, ± π (14 ′) Therefore, the first filter is obtained from equations (13 ′) and (14 ′). FIG. 14 shows the relationship between the coefficient T (1) and the second filter coefficient T (2).

As is apparent from FIG. 14, 0 ≦ T
When (1) ≦ 1, the phase delay φ is always “0” on T (2) = 1−T (1), and the input signal S (n) does not undergo any phase shift. When −1 ≦ T (1) ≦ 0, the phase delay φ always becomes “± π” on T (2) = − 1−T (1). However, the phase lag φ
When the phase lag occurs even slightly from “0” or “± π”, the first and second filter coefficients T (1) and T (2)
It becomes infinite in the quadrant or the fourth quadrant and diverges.

This means that it becomes difficult to converge the first and second filter coefficients T (1) and T (2) even if a slight phase delay occurs when the number N of the divided signals increases. Means

That is, in a real system such as a case where vibration noise control is actively performed on a vehicle such as an automobile, there is a phase delay φ caused by the vibration noise transmission system from the adaptive control circuit to the error sensor. , A phase delay φ with respect to the input signal always occurs. On the other hand, in the prior art by the present applicant, since a desired sine wave is obtained in accordance with a large number of pulse signals generated at every predetermined minute rotation angle of the engine, the number N of divided signals generated is extremely small. In many cases (for example, 100), considering the above-mentioned phase delay φ, the convergence becomes poor, and a new problem arises in that it becomes difficult to adaptively control the system.

SUMMARY OF THE INVENTION The present invention has been made in view of the above problems, and has as its object to provide a vibration and noise control device capable of reducing the calculation load and converging in a shorter time.

[0023]

In order to achieve the above object, the present invention provides a vibration noise source having at least a rotating body that generates periodic or pseudo-periodic vibration noise.
First filter means including an adaptive digital filter for outputting a control signal for controlling the vibration noise source, drive signal generation means for converting the control signal into a drive signal, and drive generated by the drive signal generation means Error signal detection means for detecting an error signal between the signal and the vibration noise signal from the vibration noise source; and a transmission characteristic of a vibration noise transmission path formed between the drive signal generation means and the error signal detection means. A second filter for expressing the error signal based on a detection result of the error signal detector, a reference signal output from the second filter, and a filter coefficient of the first filter. And a control signal updating means for updating the filter coefficient of the first filter means. A drive cycle signal detecting means for detecting a drive cycle signal corresponding to a noise cycle for each predetermined rotation angle of the rotating body; and a plurality of divided signals between generation cycles of the drive cycle signal detected by the drive cycle signal detection means. Generating a reference signal consisting of a sine wave of a single cycle in accordance with the generation timing of the divided signal generated by the divided signal generating means, and inputting the reference signal to the first filter means Reference signal generating means for performing
In the adaptive digital filter of the filter means, the number of taps is composed of two taps, and the number N of divided signals generated by the divided signal generating means is 3 ≦ N ≦ 7 (where N is a real number). It is characterized by being set in a range.

Preferably, the number N of divided signals generated by the divided signal generating means is set to "4".

Further, a sampling period generation for generating a sampling period governing a series of operations for outputting and updating the filter coefficient of the first filter means based on a driving frequency of the control means for controlling the rotating body. Means for determining the delay period of the adaptive digital filter based on the generation cycle of the drive cycle signal detected by the drive cycle signal detection means and the sampling cycle, and generating the pulse signal. A delay period changing unit that changes the delay period in accordance with the change in the generation period when the period is changed, and when the delay period is changed by the delay period changing unit, the delay period is changed to the changed delay period. Filter coefficient changing means for forcibly changing the filter coefficient of the adaptive digital filter based on the Also preferably characterized.

Further, according to the present invention, there is provided a vibration noise source having at least a rotating body that generates periodic or pseudo-periodic vibration noise, instead of the vibration noise control device. First filter means having an adaptive digital filter for outputting a signal; drive signal generation means for converting the control signal into a drive signal; drive signal generated by the drive signal generation means; Error signal detection means for detecting an error signal from the vibration noise signal; second filter means for expressing a transmission characteristic of a vibration noise transmission path formed between the drive signal generation means and the error signal detection means; Based on the detection result of the error signal detection means, the reference signal output from the second filter means, and the filter coefficient of the first filter means. A control signal updating means for updating a filter coefficient of said first filter means so as to obtain a value. A driving cycle signal corresponding to a vibration noise cycle specific to a component of said vibration noise source. And a division for generating a large number of divided signals for dividing a generation cycle of the drive cycle signal detected by the drive cycle signal detection for each predetermined minute angle. Signal generation means, and reference signal storage means for storing a reference signal to be output to the first filter means in accordance with the generation timing of the divided signal, wherein the adaptive digital filter of the first filter means The number of taps is two taps, and the reference signal storage means stores a single cycle sine wave corresponding to the vibration noise period of the vibration noise source. Means, and a delayed sine wave storage means for storing a delayed sine wave having a predetermined delay period M with respect to the sine wave stored by the sine wave storage means, and the predetermined delay period M is 1/3 It is still more preferable that the ratio is set in the range of ≧ M ≧ 1/7 (where M is a real number).

Further, preferably, the predetermined delay period M
Is set to “１ ／”.

In addition, a sampling period for controlling a series of operations for outputting and updating the filter coefficient of the first filter means is generated based on a driving frequency of the control means for controlling the rotating body. It is also preferable to have a means.

Further, a series of operations for outputting and updating the filter coefficient of the first filter means may be executed in synchronization with the generation of the divided signal.

Further, according to the present invention, the second filter means includes a transfer characteristic storing means for storing a phase / amplitude transfer characteristic of the vibration noise transmission path, and a generation interval of the divided signal generated by the divided signal generating means. The phase / amplitude transfer characteristic stored in the transfer characteristic storage means is read out according to

[0031]

The amplitude condition and the phase condition of the adaptive digital filter (ADF) having the number of taps of "2" are calculated by the equations (7 ') and (7'), respectively, as described in the section of [Problem to be Solved by the Invention]. (8 ').

(T (1) + T (2) cos K) ² + T (2) ² sin ² K = 1 (7 ′) tan φ = −T (2) sin K / (T (1) + T ( 2) cos K) (8 ′) Here, k is k = (2π / N), and N is the number N of divided signals generated within the vibration noise period.

FIG. 13 is a graph showing the number N of divided signals, the equal-amplitude ellipse and the equal-phase straight line (the phase delay φ is φ = 0, ± π / 4, ±
FIG. 3 is a diagram showing a relationship with (π / 2, ± π3 / 4, ± π). The horizontal axis is the first filter coefficient T (1) of the ADF,
The vertical axis is the second filter coefficient T (2). FIG.
13A shows the case where the number of occurrences N is "4", FIG. 13B shows the case where the number of occurrences N is "8", and FIG. 13C shows the case where the number of occurrences N is "16".

As is apparent from FIG. 13, the locus of the equal-amplitude ellipse is a perfect circle when the number N of occurrences is "4".
When the number N of occurrences is "4" or more, ellipses having a long axis in the second and fourth quadrants are formed, and as the number N of occurrences increases, the ratio between the major axis and the minor axis increases. Although not shown, when the number of occurrences N is equal to or less than "4", ellipses having a major axis are formed in the first quadrant and the third quadrant.

On the other hand, when the phase lag φ is “0” or “± π” and there is no phase lag φ, the equal phase straight line always has the first filter coefficient T.
(1), but when the number N of occurrences becomes greater than the boundary of “4”, the other three equal-phase straight lines (φ =
± π / 4, ± π / 2, ± π3 / 4) approach the major axes of the ellipses formed in the second and fourth quadrants, and therefore, the reasons described in [Problems to be Solved by the Invention]. From (FIG. 14
Reference) It turns out that the convergence of adaptive control becomes difficult. Although illustration is omitted, if the number of occurrences N is less than "4", the equiphase straight line approaches the major axis of the ellipse formed in the first quadrant and the third quadrant. Become. That is, the number N of occurrences has an optimum range.

That is, according to the present invention, as described above, the number N of divided signals is set in the range of 3 ≦ N ≦ 7 (where N is a real number). Also, the filter coefficients can be converged in a short time. In particular, when the number of occurrences N is "4", the amplitude locus becomes a perfect circle,
Since the equiphase straight line when the phase delay φ occurs is also formed in each of the first to fourth quadrants on average, optimal control is performed.

Further, a single-cycle sine wave and a predetermined delay period M for the sine wave (the predetermined delay period M is 1/3 ≧ M ≧ 1 /
When a delayed sine wave having 7 (where M is a real number) (preferably 1/4) is input to the first filter means, the same operation as described above can be obtained. That is,
One of the two taps of the adaptive digital filter is updated with the reference signal output based on the sine wave, and the other tap is updated with the reference signal output based on the delayed sine wave. . In this manner, one cycle is minutely divided, and a sine wave and a delayed sine wave delayed by a predetermined delay cycle M are simultaneously output in accordance with the divided signal, thereby obtaining a sine wave value obtained by dividing the sine wave into four. Can be obtained.

Further, by generating a sampling cycle based on the driving frequency of the control means for controlling the rotating body, adaptive control can be executed at a fixed sampling cycle, and the filter coefficient of the first filter means can be controlled. Is performed in synchronization with the generation of the divided signal, so that adaptive control can be performed at a variable sampling period.

Further, by storing the transmission characteristics of the vibration noise transmission path in the transmission characteristic storage means, generation of the divided signal is achieved.
The transfer characteristics can be read according to the interval .

[0040]

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS An embodiment in which the vibration and noise control apparatus according to the present invention is applied to a vehicle such as an automobile will be described below in detail with reference to the drawings.

FIG. 1 is a diagram showing a state in which an engine as a vibration noise source that generates vibration noise having periodicity or pseudo-periodicity is mounted on a vehicle body.

In FIG. 1, reference numeral 1 denotes a four-cycle engine (hereinafter simply referred to as "engine") of a vehicle driving power plant having, for example, four in-line cylinders. The engine 1 includes an engine mount 2 and front wheels (driving wheels). ) 4 suspensions 5
And the support 7 of the exhaust pipe 6 are supported by the vehicle body 8.

Further, the engine mount 2 has an appropriate number of self-expandable engine mounts 2a as electromechanical conversion means capable of changing the vibration transmission characteristics, and an appropriate number of normal engine mounts which cannot change the vibration transmission characteristics. And an engine mount 2b.

The self-expandable engine mount 2a includes a voice coil motor (VCM), an actuator such as a piezoelectric element or a magnetostrictive element, and an electronic mount control unit (EMCU) according to the vibration of the engine.
The vibration of the engine is controlled by a signal from a motor (not shown). That is, the self-expandable engine mount 2a has a liquid chamber filled with liquid, and the vibration of the vibration source is transmitted to the vehicle body 8 by the actuator via the elastic rubber fixed to the vibration source (engine 1). Control

A vibration error sensor 9 is provided near the engine 2b. Further, in the vicinity of a flywheel fixed to a crankshaft (not shown) of the engine 1,
A rotation detection sensor such as a magnetic sensor is provided.

FIG. 2 is a system configuration diagram showing one embodiment (first embodiment) of the vibration noise control device according to the present invention.

That is, the vibration and noise control device includes a rotation detection sensor 1 for detecting a rotation signal X of the flywheel.
0 and an electronic control unit (hereinafter referred to as an “ECU”) that generates timing pulse signals Y ₁ and Y ₂ indicating the vibration noise period corresponding to each component of the engine by shaping the waveform of the output signal from the rotation detection sensor 10. 11) and the E
Timing pulse signals Y ₁ and Y ₂ output from the CU 11
DS capable of high-speed operation that performs adaptive control using a signal as a trigger signal
P (Digital Signal Processor) 12 and the DSP 12
A vibration noise transmission system 13 through which a control signal V (digital signal) output from the vibration signal passes, the vibration error sensor 9 into which the control signal V passing through the vibration noise transmission system 13 is input as a drive signal Z, An A / D converter 14 that converts an error signal (analog signal) ε output from the error sensor 9 into a digital signal and feeds it back to the DSP 12 is configured as a main part.

More specifically, the rotation detecting sensor 10 counts the number of ring gears of the flywheel, detects a pulse signal thereof, and supplies the pulse signal to the ECU 11. The means for detecting the rotation of the engine 1 is not limited to the means for counting and detecting the ring gear of the flywheel as described above, and the rotation signal of the crankshaft or camshaft is directly detected by an encoder or the like. However, when the rotation of the crankshaft is directly detected, there is a possibility that the rotation may fluctuate due to torsional vibration of the crankshaft or the like. While the rotation of the camshaft may fluctuate slightly due to elongation of the timing belt connecting the pulley, the flywheel fixed to the crankshaft has a large moment of inertia and a small rotation fluctuation. There is an advantage that a desired sampling frequency can be obtained relatively easily and with high accuracy.

The DSP 12 includes a plurality of types of adaptive control circuits (in this embodiment, two types of adaptive control circuits 15, 15) so that adaptive control can be performed in accordance with the vibration noise period peculiar to each component of the engine. ₁ , 15 ₂ ) are built-in. Further, the adaptive control circuits 15 ₁ and 15 ₂ generate reference signals U ₁ , U ₂ based on the generation cycle of the timing pulse signals Y ₁ and Y ₂ .
A reference signal generating circuit 16 _1, 16 ₂ for generating U _2, W filters 17 ₁ as FIR type ADF of the reference signal U _1, U ₂ the number of taps for filtering the "2", 1
7 ₂ (first filter means) and W filters 17 ₁ , 17
And LMS as an adaptive algorithm for processing for updating the _second filter coefficients (Least Mean Square) processor 18 _1, 18 ₂ (control signal updating means), transmission characteristic caused by the vibratory noise transmission system 13 Transfer characteristic correction means (hereinafter, referred to as "C filter") for correcting the phase amplitude change of
19 ₁ and 19 ₂ (second filter means).
The DSP 12 includes the first and second frequency dividing circuits 2
0 _1, 20 ₂ by the timing pulse signals Y _1, Y ₂ of the variable sampling pulse P generated by 4 dividing the generation cycle
Driven by sr (divided signal).

More specifically, the reference signal generation circuit 1
6 ₁ and 16 ₂ generate sine wave values corresponding to vibration noise characteristics specific to each component of the engine such as a valve train, a crankshaft, and a combustion chamber, which are vibration noise sources, and convert the sine wave values to W Input to filters 17 ₁ and 17 ₂ . In the present embodiment, a reference signal U ₁ (1) as a sine wave value suitable for controlling a vibration component (primary vibration component) of a piston system or the like that generates a regular vibration noise characteristic in synchronization with the rotation of the engine. Next reference signal),
A reference signal U ₂ (secondary reference signal) as a sine wave value suitable for controlling a vibration component (secondary vibration component) of an explosion pressure (excitation force) that generates irregular vibration noise characteristics according to a combustion state. )
Are generated. That is, the reference signal creation circuit 16
_1, as shown in FIG. 3 (a) (b), the first frequency divider 20 ₁ generation period of the timing pulse signal Y ₁ 4
The variable sampling pulse Psr generated by frequency division is input. A sine wave value corresponding to the input signal of the variable sampling pulse Psr is stored in advance in the reference signal creation circuit 16 ₁ , and one cycle of the flywheel corresponding to one cycle of the primary vibration component makes one cycle. A minute sine wave value, that is, four digital sine wave values are output. Also,
Wherein a substantially same for reference signal generating circuit 16 _2,
As shown in FIG. 3 (c) (d), the variable sampling pulse Psr the generation period of the timing pulse signal Y ₂ are generated by 4 divided by the second frequency divider 20 ₂ is inputted.
Then, a sine wave value for one cycle is digitally output every 0.5 rotations of the flywheel corresponding to one cycle of the secondary vibration component. Therefore, when the flywheel makes one rotation, a sine wave value for two cycles, ie, 8 Digital sine wave values are output.

As described above, by introducing the concept of the vibration order as described above and performing adaptive control by dividing the vibration order components into a plurality of types, it is possible to more effectively reduce the vibration noise. That is, the primary vibration order component relates to a vibration component generated regularly, such as rotation of the crankshaft. By individually performing adaptive control only on the primary vibration order component, the primary vibration order component is caused by inertia force such as engine rotation. Vibration noise generated as a result can be efficiently reduced. Also,
One explosion stroke is performed per cylinder during two revolutions of the crankshaft. Therefore, in the case of a four-cylinder engine, there are four explosion strokes during two revolutions of the crankshaft. Indicates the vibration component related to the explosion pressure. Then, by dividing the secondary vibration order component related to the explosion pressure having the irregular vibration noise characteristic into the primary vibration order component having the regular vibration noise characteristic and performing the adaptive control, the vibration noise can be further reduced. It can be reduced effectively.

Thus, the vibration noise transmission system 13 has the structure shown in FIG.
As shown in FIG. 5, a variable low-pass filter 21 (cutoff frequency Fc; Fc = Fsr / 2) for filtering a predetermined high frequency included in the control signal V according to the engine speed, and the control signal V filtered by the variable low-pass filter 21 ′ To an analog signal, a fixed low-pass filter 23 (cutoff frequency Fc; Fc = Fs / 2) for smoothing the output signal (rectangular signal) of the D / A converter 22, An amplifier 24 and the above-described self-expandable engine mount 2a are provided. The vibration frequency transmission system 13, the vibration error sensor 9, and the A / D converter 14 are driven by a third frequency dividing circuit 25 to drive the ECU 11 at a drive frequency (for example, 20 MHz).
z) divided by a fixed sampling frequency (for example, 10 KHz) Fs (fixed sampling pulse P)
The drive is controlled by s).

As shown in FIG. 4, the C filter 19 is an adaptive digital filter 28 having two taps.
(Hereinafter referred to as “identification filter”) filter coefficient C
(1) and C (2) are identified in advance according to the variable sampling pulse Psr generated according to the engine speed, and the identified filter coefficients C (1) and C (2) are tabulated and stored. I have.

More specifically, the variable sampling pulse Psr generated according to the engine speed is identified by the identification filter 28.
And input to the variable low-pass filter 21. The output signal from the identification filter 28 is input to an adder 30 after a predetermined high-frequency is cut off by an identification variable low-pass filter (cutoff frequency Fc; Fc = Fsr / 2) 29. That is, the high frequency of the output signal from the identification filter 28 is cut off by the identification variable low-pass filter 21 to obtain a desired sine wave, and the sine wave is input to the adder 30.

On the other hand, a variable low-pass filter for compensation (cut-off frequency Fc; Fc = Fsr / 2) 31 is provided between the variable low-pass filter 21 and the D / A converter 22 to identify the transfer characteristic of the vibration noise transmission system 13. Is interposed.
This is because the variable identification low-pass filter 29 described above is interposed between the identification filter 28 and the adder 30.
It is interposed to compensate for the transmission system of the system due to the insertion of the variable low-pass filter 29 for identification. The output signal from the variable low-pass filter 21 is passed through a compensating variable low-pass filter 31, a D / A converter 22, a fixed low-pass filter 23, an amplifier 24, and a self-stretchable engine mount 2a. Is input to Then, the adder 30 cancels out the output signal from the self-expandable engine mount 2a and the output signal from the identification variable low-pass filter 29.
Is output to the LMS processing unit 32, and the cancellation signal η
The filter coefficients C (1) and C (2) of the identification filter are identified so that the square η ² of “0” becomes “0”. The cutoff frequencies Fc of the variable low-pass filter 21, the variable low-pass filter 29 for identification, and the variable low-pass filter 31 for compensation are updated in accordance with each variable sampling frequency Fsr that can be generated by engine rotation, and the filter for identification. The filter coefficients C (1) and C (2) are also sequentially updated according to each of the variable sampling frequencies Fsr, and the filter coefficients C (1) and C (2) identified according to each of the variable sampling frequencies Fsr are stored in a table. And stored in the C filter 19.

As shown in FIG. 2, the ECU 11 receives the rotation signal X detected by the rotation detecting sensor 10 from the vibration and noise control apparatus having the above-described configuration. Timing pulse signals Y ₁ , Y ₂ according to the vibration noise period specific to the component
Are the reference signal generation circuits 16 ₁ and 16 ₂ and the C filter 1
It is input to 9 ₁ and 19 ₂ . Meanwhile, the timing pulse signal in the first and second divider circuits 20 _1, 20 ₂ Y _1, Y ₂
Is generated based on the detection timing of the rotation detection sensor 10, and the variable sampling pulse Psr is input to the reference signal generation circuits 16 ₁ and 16 ₂ . Each time the variable sampling pulse Psr is input to the reference signal generation circuits 16 ₁ and 16 ₂ , a predetermined sine wave value is sequentially output. In other words, the reference signal generation circuit 16 ₁ outputs a primary reference signal U ₁ suitable for controlling the primary vibration order component, and the reference signal generation circuit 16 ₂ outputs the primary reference signal U ₁ suitable for controlling the secondary vibration order component.
Next reference signal U ₂ is output.

Next, the primary and secondary reference signals U ₁ , U
₂ is filtered by each of the W filters 17 _1, 17 ₂ is outputted as the control signal V _1, V _2, the control signals V _1, V ₂ are added by the adder 26, generated is the sum The control signal V is converted into a drive signal Z by the vibration noise transmission system 13 and input to the vibration error sensor 9. Further, the vibration noise control system 13 is driven and controlled by a fixed sampling pulse Ps generated by dividing the driving frequency (for example, 20 MHz) of the ECU 11 by the third frequency dividing circuit 25. Specifically, the control signal V is first input to the variable low-pass filter 21 updated according to the generation cycle (variable sampling frequency τ (= 1 / Fsr)) of the variable sampling pulse Psr. In other words, when digital signal processing is performed using the variable sampling pulse Psr generated based on the engine speed, harmonic frequencies other than the signal to be controlled are generated due to the characteristics of the system. Need to shut off. However, since the cutoff frequency Fc is set to about (1/2) of the normal band frequency, the engine speed is, for example, 600 rpm (1).
The cutoff frequency when the frequency of the next vibration is 10 Hz is 20 Hz, whereas the cutoff frequency when the engine speed is 6000 rpm is 200 Hz, for example. Can not do it. For this reason, the cutoff frequency Fc of the control signal V is updated according to the generation cycle (variable sampling frequency τ) of the variable sampling pulse Psr determined according to the engine speed.

Next, the control signal V '(digital signal) that has passed through the variable low-pass filter 21 is D / A
After being converted into an analog signal by the converter 22, the signal is smoothed by a fixed low-pass filter 23 having a predetermined cut-off frequency Fc (= Fs / 2), and is passed through an amplifier 24 and a self-expandable engine mount 2a to generate a vibration error as a drive signal Z. Input to the sensor 9.

On the other hand, a vibration noise signal D from the engine 1, which is a vibration noise source, is also input to the vibration error sensor 9,
The drive signal Z and the vibration noise signal D are canceled by the vibration error sensor 9, and an error signal ε is output from the vibration error sensor 9. Then, the error signal (analog signal) ε is converted into a digital signal by the A / D converter 14 (error signal ε ′) and input to the LMS processing units 18 ₁ and 18 ₂ . Then, in the LMS processing units 18 ₁ and 18 ₂ , the transmission characteristics of the vibration noise transmission system 13 previously identified and stored in the C filters 19 ₁ and 19 ₂ , that is, the reference signals R ₁ and R ₂ The error signal ε ′ and the reference signals U ₁ , U ₂ and W
Filter 17 _1, 17 ₂ of W filter 17 on the basis of the current filter coefficients _1, 17 ₂ of the filter coefficients are updated,
New control signals V ₁ and V ₂ are output from the W filters 17 ₁ and 17 ₂ , and adaptive control of vibration noise is executed.

FIG. 5 shows a comparative example (variable sampling pulse Psr per cycle, that is, the number N of divided signals generated: N) of the convergence from the start of the adaptive control of the first embodiment.
100), the horizontal axis represents time [sec], and the vertical axis represents amplitude. In the figure, the solid line is the first embodiment, and the broken line is the comparative example. The phase delay φ of the vibration noise transmission system 13 is 0.05 [sec] in time conversion. FIG. 5B shows a case where the adaptive control is not performed, and FIG. 5A shows a temporal change of the amplitude after the start of the adaptive control.

As apparent from FIG. 5 (a), in the comparative example, although the amplitude attenuates to a certain extent about 0.2 seconds after the start of the adaptive control, the waveform attenuates after 0.2 seconds elapses. On the other hand, in the first embodiment, 0.
After 2 seconds elapse, it attenuates more rapidly, and after 0.6 seconds elapses, the amplitude becomes almost “0”, indicating that the sample has higher convergence than the comparative example.

As described above, in the above vibration noise control apparatus, the reference signal U output from the reference signal generation circuit 16 is a sine wave value obtained by dividing the vibration noise of one cycle of the vibration order component to be controlled into four. , Convergence deterioration due to the phase delay φ can be avoided.

FIG. 6 is a system configuration diagram schematically showing a vibration noise control device according to a second embodiment. In the second embodiment, updating and output of filter coefficients of W filters 17 ₁ and 17 ₂ are performed. A series of operations to be performed is governed by the fixed sampling frequency Fs.

That is, in the second embodiment, E
The drive frequency of the CU 11 (for example, 20 MHz) is adaptively controlled based on a fixed sampling pulse Ps (the sampling frequency Fs is 1 KHz, for example) generated by dividing the frequency by the frequency dividing circuit 33.

More specifically, as in the first embodiment, the rotation signal X detected by the rotation detection sensor 10 is supplied to the ECU.
The ECU 11 outputs timing pulse signals Y ₁ and Y ₂ corresponding to the vibration and noise periods specific to each component of the engine to the reference signal generation circuits 16 ₁ and 16 ₂ and the C filters 19 ₁ and 19 ₂ . Is entered. On the other hand, the driving frequency (for example, 20 MHz) of the ECU 11 is divided by the frequency dividing circuit 33 to generate a fixed sampling pulse Ps, and the fixed sampling pulse Ps is used as the reference signal generating circuit 16 ₁ , 1
6 ₂ and C filters 19 ₁ and 19 ₂ .

The reference signal generating circuits 16 ₁ and 16 _{2 use} the W filter 1 in accordance with the generation cycle of the timing pulse signal Y.
W filters 17 ₁ , 17 2 indicating the delay period between the first filter coefficient T (1) and the second filter coefficient T (2) of 7 ₁ , 17 ₂
The order m of ₂ is calculated. For example, when adaptive control is performed at a sampling frequency of 1 kHz when the generation frequency F of the timing pulse signal Y is 10 Hz, 100 sampling pulses Ps are detected during the generation cycle of the timing pulse signal Y. Therefore, at this time, the delay period of the W filter, that is, the order m of the W filter 17 is set to “25” in order to perform processing by the 2-tap W filter 17 using a desired sine wave value. Further, when adaptive control is performed at a sampling frequency of 1 KHz when the generation frequency F of the timing pulse signal Y is 50 Hz, 20 sampling pulses Ps are detected during the generation cycle of the timing pulse signal Y. Therefore, at this time, the delay period of the W filter 17, that is, the order m of the W filter 17 is set to "5" in order to perform the processing by the two-tap W filter 17. Thus, the reference signal generation circuits 16 ₁ and 16 ₂
In this case, the order m for processing by the two-tap W filter 17 is appropriately calculated according to the generation frequency F of the timing pulse signal Y.

Next, the primary and secondary reference signals U ₁ , U
_2, the control signals V _1, V ₂ are filtered by the W filters 17 _1, 17 ₂ each is output, the control signals V
₁ and V ₂ are added by an adder 26, and the control signal V generated by the addition is converted into an analog signal by a D / A converter 22, and then fixed low-pass filter 23 and amplifier 2
The drive signal Z is converted into a drive signal Z via the self-contracting engine mount 2 a and the vibration error sensor 9.

On the other hand, a vibration noise signal D from the engine 1 which is a vibration noise source is also input to the vibration error sensor 9,
The drive signal Z and the vibration noise signal D are canceled by the vibration error sensor 9, and an error signal ε is output from the vibration error sensor 9. Then, the error signal (analog signal) ε is converted into a digital signal by the A / D converter 14 (error signal ε ′) and input to the LMS processing units 18 ₁ and 18 ₂ . Then, in the LMS processing units 18 ₁ and 18 ₂ , the C filter 1
The transmission characteristics of the vibration and noise transmission system 13 stored in 9 ₁ and 19 ₂ , that is, the current values of the reference signals R ₁ and R ₂ , the error signal ε ′, the reference signals U ₁ and U _2, and the W filters 17 ₁ and 17 ₂ The filter coefficients of the W filters 17 ₁ and 17 ₂ are updated based on the filter coefficients of the above, new control signals V ₁ and V ₂ are output from the W filters 17 ₁ and 17 _2, and the adaptive control of the vibration noise is executed. You.

As described above, the LMS processing sections 18 ₁ and 18 ₂ are driven in synchronization with the generation of the fixed sampling pulse Ps, and the first filter coefficients T of the W filters 17 ₁ and 17 ₂ are set.
(1) and the coefficient update of the second filter coefficient T (2) are successively performed, but the engine speed suddenly changes and the W filter 17 ₁ ,
When the order m of 17 ₂ is changed, the W filters 17 ₁ , 1
Discontinuity occurs and the control signal V _1, V ₂ 7 ₂ of the filter coefficient update is updated based on the last updated values, there is a possibility that hinder the reduction of vibrations and noises. Therefore, in this embodiment,
When the order m of the W filters 17 ₁ and 17 ₂ is changed due to a sudden change in the engine speed, the filter coefficient of the W filter 17 is forcibly changed so that a discontinuous portion does not occur in the control signals V ₁ and V _2. doing. Hereinafter, a procedure for setting the filter coefficients T (1) and T (2) of the W filter 17 will be described in detail.

FIG. 7 is a flowchart showing the procedure for changing the filter coefficient. This program is executed in the DSP 12 in synchronization with the generation of the timing pulse.

First, in step S1, the rotation detection sensor 1
0, the engine rotation is detected, and the timing pulse Y
Is calculated.

Next, the F table is searched, and the order m of the W filter 17 corresponding to the generated frequency F is calculated (step S2). As shown in FIG. 8, specifically, the F table includes generated frequencies F ₀ , F ₁ , F ₂ ,..., Fn−1, and Fn.
Table values m (0), m (1),.
(n) is given, and the order m of the W filter 17 is
It is read by searching the table.

Next, the process proceeds to step S3, where the order m (n) of the W filter 17 at the time of generation of the current timing pulse is m (n).
-1) is determined, and if the previous order m (n) is equal to the current order m (n-1), the program is terminated as it is, while the previous order m (n) is compared with the current order m (n). If the order m (n-1) is different, the process proceeds to step S4, where the filter coefficients T (1) and T (2) are changed, and the program ends.

That is, the filter coefficient T of the W filter
The control signal Y obtained by multiplying (1) and T (2) with the reference signals U ₁ and U ₂ is given by Expression (1).

[0075]

(Equation 6) Therefore, the change of the phase and the amplitude by the W filter 17 is represented by the equation (2).

[0076]

(Equation 7) If the above equation (2) represents the current phase / amplitude, the phase / amplitude at the time of the last generation of the timing pulse can be expressed by equation (3).

[0077]

(Equation 8) When the order of the W filter 17 is changed from the previous value m ′ to the current value m, Expressions (2) and (3) must be equal, and therefore Expressions (4) and (5) ) Holds.

[0078]

(Equation 9)

[0079]

(Equation 10) Therefore, the filter coefficients T (1) and T (2) of the W filter 17 are obtained from Expressions (6) and (7) from Expressions (4) and (5).

[0080]

[Equation 11]

[0081]

(Equation 12) In this manner, desired filter coefficients T (1) and T (2) can be obtained even when the engine speed fluctuates and the order of the W filter 17 is changed from m 'to m in the case of fixed sampling.
The occurrence of discontinuity in the control signal V can be avoided.

The filter coefficients T (1), T (2)
In the calculation of, the calculation load of the triangular relation is large, so (2π (F / Fs) m) and (2π (F / Fs)
m ′) and the like, and a trigonometric function table such as a sine table or a tan table in which function values corresponding to the variables are stored in a storage unit, and stored as necessary. It is also preferable to read out a desired function value from these trigonometric function tables, or to calculate by an interpolation method.

In the above embodiment, the case where the number of generated divided signals is "4" has been described. However, although the controllability is slightly inferior to the case where N = 4, 3≤N≤7 (N is a real number). If so, the ratio between the major axis and the minor axis of the equal-amplitude ellipse does not become so large and good convergence can be obtained, so that the desired effect can be obtained sufficiently.

FIG. 9 is a system configuration diagram showing a third embodiment of the vibration and noise control apparatus, and includes adaptive control circuits 34 ₁ , 3.
4 _2, reference signal U variable sampling pulse Psr generated every predetermined minute angle of rotation of the engine 1 (divided signal) corresponding to the variable sampling pulse Psr is supplied
₁ , U ₂ and reference signal storage means (hereinafter referred to as “R table”) 35 ₁ , 3 for outputting basic reference signals R ₁ ′, R ₂ ′.
5 _2, phase amplitude characteristic storage means for storing the phase amplitude characteristic of the vibration noise transmission system 13 (hereinafter, referred to as "C Table")
36 ₁ , 36 ₂ , amplifiers 38 ₁ , 38 ₂ for amplifying the amplitudes of the basic reference signals R ₁ ′, R ₂ ′ output from the R tables 35 ₁ , 35 ₂ with predetermined gain variables, and a W filter 37 ₁ ,
And a LMS processor 39 _1, 39 ₂ for performing arithmetic processing for updating the 37 _second filter coefficients.

More specifically, as shown in FIG. 10, a single-cycle sine wave and a π / 2
Is digitally stored at every minute angle corresponding to the generation timing of the variable sampling pulse Psr, for example, at every 3.6 °. For example, when the primary vibration component of the engine is to be controlled, addresses 0, 1,..., 99 in the order of one rotation of the flywheel corresponding to one cycle of the primary vibration component. 100 variable sampling pulses Psr are input at intervals, and a sine value and a delayed sine value corresponding to the variable sampling pulse Psr are output using the input timing of the variable sampling pulse Psr as a read pointer.

As shown in FIG. 11, the C table 36 stores a shift amount Δ indicating a phase delay φ with respect to the reference signal U.
A ΔP table 40 storing P and a Δa table 41 storing a gain variable Δa of the basic reference signal R ′ output from the R table 35 are stored. That is, the shift amount ΔP and the gain variable Δa according to the read pointer (indicated by the arrow A in the figure) of the sine wave and the delayed sine wave determined according to the input of the variable sampling pulse Psr are identified in advance according to the system. By searching the C table 36, the phase delay ΔP and the gain variable Δa corresponding to the read pointer are read.

That is, since the reference signal U ₁ is a sine wave and the reference signal U ₂ is a delayed sine wave, the phase amplitude information (shift amount ΔP and gain amount) of the read pointer A corresponding to the generation timing of the variable sampling pulse Psr. Δa) is determined by searching the C table 36. Therefore, without the need for complicated arithmetic processing,
Each time the variable sampling pulse Psr is input, a set of sine values U (1), delayed sine values (2), and Reference signal R
(1) and R (2) are uniquely determined.

In the vibration and noise control device thus configured, the variable sampling pulse Psr
From 50, the data is input to the R table 35 and the C table 36. Then, in synchronization with the input of the variable sampling pulse Psr, a sine value and a delayed sine value corresponding to a read pointer (indicated by an arrow A in the figure) are read, and the sine wave value and the delayed sine wave value are referred to as a reference signal U (1 ) And U (2) are input to the W filter 37. On the other hand, in the C table 36, every time the variable sampling pulse Psr is input,
The corresponding read pointer shift amount ΔP and gain variable Δa are read. The shift amount ΔP is input to the R table 35, and the sine value and the delayed sine value shifted by the shift amount ΔP are used as the basic reference signals R ′ (1) and R ′.
The data is output from the R table 35 as (2) and supplied to the amplifier 38. Then, the amplifier 38 amplifies the amplitudes of the basic reference signals R (1) and R (2) by the gain variable Δa to create reference signals R (1) and R (2), and inputs the signals to the LMS processing unit 39.

Next, in the LMS processing section 39, the first filter of the W filter 37 is obtained based on the equations (8) and (9).
And the second filter coefficients T (1) and T (2) are updated.

[0090]

(Equation 13)

[0091]

[Equation 14] Here, T (1) (i + 1) and T (2) (i + 1) are new filter coefficient values of the first and second filter coefficients T (1) and T (2), and T (1) (i). And T (2) (i) are the current filter coefficient values of the first and second filter coefficients T (1), T (2). μ is a step size parameter that regulates the coefficient update correction amount each time, and is set in advance to a predetermined value according to the control target.

Next, the coefficient updating unit 42 of the W filter 37
The filter coefficient of the W filter is updated by the
The current filter coefficients T (1), T
(2) is multiplied by the reference signals U (1) and U (2) to output a control signal V.

Then, as shown in FIG. 9, the control signal V is sampled by the D / A converter 22 using the variable sampling pulse (Psr) output from the ECU 11 as a trigger, converted into an analog signal, and then converted to an analog signal. , An amplifier 24 and a self-expandable engine mount 2a, and is input to the vibration error sensor 9 as a drive signal Z. On the other hand, a vibration noise signal D from the engine 1, which is a vibration noise source, is input to the vibration error sensor 9, and the driving signal Z and the vibration noise signal D are canceled by the vibration error sensor 9, and the error signal ε is reduced. Output from the vibration error sensor 9. The error signal ε is D
Like the A / A converter 24, the variable sampling pulse Psr output from the ECU 11
Sampled by the D converter 19, the LMS processing unit 3
The filter coefficients are input to 9 ₁ and 39 ₂ , and the filter coefficient of the W filter 37 is updated as in the first and second embodiments.

As described above, in the third embodiment,
Since the sine wave and the delayed sine wave having a phase delay of π / 2 with respect to the sine wave are simultaneously output, a sine wave and a cosine wave delayed by １ ／ period from the sine wave are output. As a result, substantially the same result can be obtained as in the first and second embodiments when the number of generated divided signals is set to “4”.

Further, since the reference signal U is a sine wave, there is no need for a higher-order frequency characteristic relating to the transfer characteristic of the system or a filter having a long tap length. Therefore, the transfer characteristic of the system is previously determined using many storage elements. There is no need to store the information, and the phase and amplitude can be corrected by storing the transfer characteristics of the system identified in advance and reading the data appropriately according to the engine speed and the like, thereby simplifying the device. And the convergence speed can be improved.

FIG. 12 shows the convergence after the start of the adaptive control of the third embodiment in comparison with the first embodiment. The horizontal axis represents time [sec], and the vertical axis represents the time. Indicates amplitude. In the figure, the two-dot chain line is the third embodiment, and the solid line is the first embodiment. The phase delay φ of the amplitude noise transmission system 13 is 0.05 [sec] in time conversion. FIG. 12B shows a case where the adaptive control is not performed, and FIG. 12A shows a temporal change of the amplitude after the start of the adaptive control.

As is apparent from FIG. 12A, the third embodiment has a higher convergence than the first embodiment. This is because the first embodiment generates a reference signal based on a sine wave value read out by simply dividing one period of the vibration noise period into four, whereas the third embodiment generates the vibration noise This is because a sine wave value and a delayed sine wave value obtained by dividing one cycle of the cycle by 100 are sequentially read out to generate the reference signal, so that it is possible to perform finer control.

In the third embodiment, the predetermined delay period M is set to 1/4, but 1/3 ≧ M ≧ 1/7
Within the range of (M is a real number), the desired effect can be obtained sufficiently for the same reason as described in the first and second embodiments.

In the third embodiment, the sampling frequency is variable.
The adaptive control can be similarly performed by using a predetermined frequency obtained by dividing the drive frequency of U50 (for example, 20 MHz) as the sampling frequency. In this case, since the generation cycle of the timing pulse signal Y varies according to the engine speed, when the generation cycle of the sampling pulse is shorter than the generation cycle of the timing pulse signal Y, the same sine wave value,
By reading the shift amount ΔP and the gain variable Δa several times, it is possible to perform the same processing as in the case of obtaining a sine wave value, a shift amount, and a gain variable by variable sampling.

The present invention is not limited to the above embodiment, but can be modified without departing from the scope of the invention. For example, in the above embodiment, a self-expandable engine mount with a built-in actuator is used as the electromechanical conversion means. However, it is needless to say that the present invention can be similarly applied to the case of controlling noise with a speaker or the like. Nor. Further, in the above embodiment, the adaptive control is performed with the two vibration orders of the primary vibration order and the secondary vibration order as the control objects, but the convergence is similarly good when the three or more vibration orders are the control objects. It goes without saying that adaptive control can be executed.

[0101]

According to the present invention described in detail above, the present invention relates to a control signal for controlling a vibration noise source for a vibration noise source having at least a rotating body which generates vibration noise having periodicity or pseudo-periodicity. First filter means provided with an adaptive digital filter for outputting the control signal, drive signal generation means for converting the control signal into a drive signal, drive signal generated by the drive signal generation means, and vibration from the vibration noise source Error signal detection means for detecting an error signal with respect to the noise signal; second filter means for expressing a transmission characteristic of a vibration noise transmission path formed between the drive signal generation means and the error signal detection means; The error signal has a minimum value based on a detection result of the error signal detection means, a reference signal output from the second filter means, and a filter coefficient of the first filter means. And a control signal updating means for updating a filter coefficient of the first filter means, wherein a driving cycle signal corresponding to a vibration noise cycle peculiar to a component of the vibration noise source is transmitted to the rotating body. A driving cycle signal detecting means for detecting at every predetermined rotation angle; a dividing signal generating means for generating a plurality of divided signals during a generation cycle of the driving cycle signal detected by the driving cycle signal detecting means; Reference signal generating means for generating a reference signal consisting of a single-cycle sine wave in accordance with the generation timing of the divided signal generated by the means, and inputting the reference signal to the first filter means; The adaptive digital filter of the filter means has a tap number of 2 taps, and the number N of divided signals generated by the divided signal generating means is 3 ≦ N ≦ 7. However, N is the range of a real number) (preferably, since N = 4) is set, even if the phase delay φ caused by vibration noise transmission system occurs,
The filter coefficients can be converged in a short time without divergence, and desired reduction in vibration noise can be achieved.

Further, a sampling period for controlling a series of operations for outputting and updating the filter coefficient of the first filter means is generated based on a driving frequency of the control means for controlling the rotating body. Means for determining the delay period of the adaptive digital filter based on the generation cycle of the drive cycle signal detected by the drive cycle signal detection means and the sampling cycle, and generating the pulse signal. A delay period changing unit that changes the delay period in accordance with the change in the generation period when the period is changed, and when the delay period is changed by the delay period changing unit, the delay period is changed to the changed delay period. Having filter coefficient changing means for forcibly changing the filter coefficient of the adaptive digital filter based on the Ri, even if the sampling period to the fixing can avoid discontinuity occurs in the control signal, unwanted vibration noise component nor control effect is deteriorated without occur.

Further, in accordance with the present invention, in place of the above-mentioned vibration noise control device, a drive period signal for detecting a drive period signal corresponding to a vibration noise period peculiar to the component of the vibration noise source at every predetermined angle of the rotating body is provided. Signal detection means, divided signal generation means for generating a large number of divided signals for dividing the generation cycle of the drive cycle signal detected by the drive cycle signal detection means for each predetermined minute angle, and according to the generation timing of the divided signal Reference signal storage means for storing a reference signal to be output to the first filter means, wherein the adaptive digital filter of the first filter means has two taps, A signal storage means for storing a single-cycle sine wave corresponding to the vibration noise cycle of the vibration noise source; and a sine wave stored by the sine wave storage means. Delay sine wave storage means for storing a delay sine wave having a constant delay period M, and the predetermined delay period M is in the range of 1/3 ≧ M ≧ 1/7 (where M is a real number) Preferably, M = 1/4), so that the same operation as when the above-described one period of the vibration noise period is divided into four is obtained. Therefore, as described above, adaptive control with excellent convergence can be performed. Can be performed. In particular, in this case, since the divided signal is detected at each minute angle, finer control can be performed as compared to a case where one vibration noise period is simply divided into four, and adaptive control with more excellent convergence can be performed. It can be carried out.

Further, according to the present invention, the second filter means includes a transfer characteristic storing means for storing a phase / amplitude transfer characteristic of a vibration noise transmission path, and a generation interval of the divided signal generated by the divided signal generating means. By reading the phase / amplitude transfer characteristic stored in the transfer characteristic storage means in accordance with the above, it is not necessary to identify the phase / amplitude transfer characteristic by previously storing higher-order frequency characteristics, and This can be performed without requiring complicated arithmetic processing. That is, the reference signal output from the second filter means can be obtained easily and quickly according to the vibration noise period, and highly accurate adaptive control can be performed.

[Brief description of the drawings]

FIG. 1 is a diagram showing a state in which an engine is mounted on a vehicle body.

FIG. 2 is an overall configuration diagram showing one embodiment (first embodiment) of the vibration noise control device according to the present invention.

FIG. 3 is a diagram illustrating a relationship between an input signal of a variable sampling pulse and an output signal of a sine value.

FIG. 4 is a block circuit diagram showing a procedure for identifying a transmission characteristic of a vibration transmission system.

FIG. 5 is a diagram illustrating convergence of adaptive control according to the first embodiment together with a comparative example.

FIG. 6 is an overall configuration diagram showing a second embodiment of the vibration noise control device according to the present invention.

FIG. 7 is a flowchart showing a procedure for calculating a filter coefficient of a W filter when the engine speed changes rapidly.

FIG. 8 is an F table for calculating an optimal order of a W filter.

FIG. 9 is an overall configuration diagram showing a third embodiment of the vibration noise control device according to the present invention.

FIG. 10 is a diagram showing a sine wave and a delayed sine wave stored in a reference signal storage unit.

FIG. 11 is a block diagram showing details of a main part of the third embodiment.

FIG. 12 is a diagram showing the convergence of adaptive control of the third embodiment together with the first embodiment.

FIG. 13 is a diagram for explaining the grounds for limiting the numerical value of the number N of generated divided signals.

FIG. 14 is a diagram for explaining a problem of the prior art.

[Explanation of symbols]

Reference Signs List 1 internal combustion engine (vibration noise source) 9 vibration error sensor (error signal detecting means) 11 ECU (drive cycle signal detecting means) 12 DSP (delay period determining means, delay period changing means,
Filter coefficient changing means) 16 reference signal creation circuit (reference signal creation means) 17 ₁ , 17 ₂ W filter (first filter means) 19 ₁ , 19 ₂ C filter (second filter means) 201 ₁ first part Frequency dividing circuit (divided signal generating means) 20 ₂ Second frequency dividing circuit (divided signal generating means) 25 Third frequency dividing circuit (sampling period generating means) 33 Frequency dividing circuit (sampling period generating means) 35 ₁ , 35 ₂ R table (reference signal storage means) 36 ₁ , 36 ₂ C table (second filter means) 50 ECU (drive cycle signal detection means, divided signal generation means)

──────────────────────────────────────────────────続 き Continued on the front page (51) Int.Cl. ⁶ Identification code FI H03H 21/00 H03H 21/00

Claims (8)

(57) [Claims] An adaptive digital filter for outputting a control signal for controlling a vibration noise source to a vibration noise source having at least a rotating body that generates vibration noise having periodicity or pseudo-periodicity. Filter means, a drive signal generation means for converting the control signal into a drive signal, and an error signal detection for detecting an error signal between the drive signal generated by the drive signal generation means and the vibration noise signal from the vibration noise source Means for expressing a transmission characteristic of a vibration noise transmission path formed between the drive signal generation means and the error signal detection means.
Filter means, based on a detection result of the error signal detection means, a reference signal output from the second filter means, and a filter coefficient of the first filter means, so that the error signal has a minimum value. A vibration signal control device for updating a filter coefficient of the first filter device, wherein a driving cycle signal corresponding to a vibration noise period specific to a component of the vibration noise source is provided to a predetermined position of the rotating body. Drive cycle signal detection means for detecting each rotation angle, division signal generation means for generating a plurality of divided signals during a generation cycle of the drive cycle signal detected by the drive cycle signal detection means, and division signal generation means A reference signal consisting of a sinusoidal wave of a single cycle in accordance with the generation timing of the divided signal generated by the reference signal, and inputting the reference signal to the first filter means And a forming means, the adaptive digital filter of said first filter means,
The number of taps is made up of two taps, and the number N of divided signals generated by the divided signal generating means is set in the range of 3 ≦ N ≦ 7 (where N is a real number). Vibration noise control device. 2. The vibration noise control device according to claim 1, wherein the number N of divided signals generated by said divided signal generating means is set to “4”. 3. A sampling period generation for generating a sampling period that governs a series of operations for outputting and updating a filter coefficient of the first filter unit based on a driving frequency of a control unit that controls the rotating body. Means,
A delay period determining unit that determines a delay period of the adaptive digital filter based on a generation period of the drive period signal detected by the drive period signal detection unit and the sampling period; and a generation period of the drive period signal. Has a delay period changing means for changing the delay period in accordance with the change of the occurrence cycle, and when the delay period is changed by the delay period changing means, based on the changed delay period. 3. The vibration noise control device according to claim 1, further comprising a filter coefficient changing unit for forcibly changing a filter coefficient of the adaptive digital filter. 4. An adaptive digital filter for outputting a control signal for controlling a vibration noise source to a vibration noise source having at least a rotating body that generates vibration noise having periodicity or pseudo-periodicity. Filter means, a drive signal generation means for converting the control signal into a drive signal, and an error signal detection for detecting an error signal between the drive signal generated by the drive signal generation means and the vibration noise signal from the vibration noise source Means for expressing a transmission characteristic of a vibration noise transmission path formed between the drive signal generation means and the error signal detection means.
Filter means, based on a detection result of the error signal detection means, a reference signal output from the second filter means, and a filter coefficient of the first filter means, so that the error signal has a minimum value. A vibration signal control device for updating a filter coefficient of the first filter device, wherein a driving cycle signal corresponding to a vibration noise period specific to a component of the vibration noise source is provided to a predetermined position of the rotating body. Drive cycle signal detection means for detecting each angle, divided signal generation means for generating a number of divided signals for dividing the generation cycle of the drive cycle signal detected by the drive cycle signal detection means for each predetermined minute angle; Reference signal storage means for storing a reference signal to be output to the first filter means according to the generation timing of the divided signal. Type digital filter,
The number of taps is two, and the reference signal storage means stores a sine wave of a single cycle corresponding to the vibration noise period of the vibration noise source; and the sine wave storage means And a delay sine wave storage means for storing a delay sine wave having a predetermined delay period M with respect to the sine wave stored in accordance with the following formula, and the predetermined delay period M is: 1/3 ≧ M ≧ 1/7 (provided that , M is a real number). 5. The vibration noise control device according to claim 4, wherein the predetermined delay period M is set to “１ ／”. 6. A sampling cycle creation for creating a sampling cycle that governs a series of operations for outputting and updating filter coefficients of the first filter means based on a driving frequency of the control means for controlling the rotating body. The vibration and noise control device according to claim 4 or 5, further comprising means. 7. The method according to claim 1, wherein a series of operations for outputting and updating filter coefficients of said first filter means are executed in synchronization with generation of said divided signal. The vibration and noise control device according to claim 4. 8. The transmission apparatus according to claim 1, wherein said second filter means includes a transfer characteristic storing means for storing a phase and amplitude transfer characteristic of the vibration noise transmission path, and said transmission means stores the transmission signal in accordance with an interval of generation of the divided signal generated by said divided signal generation means. The vibration and noise control device according to claim 1 , wherein the phase and amplitude transmission characteristics stored in the characteristic storage unit are selected and output .