JP2007110256A - Phased-array antenna - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To provide a phased-array antenna including variable phase shifters each configured by using a variable dielectric constant dielectric whose dielectric constant varies with an applied voltage for adopting a configuration of independently controlling a phase shift amount by the variable phase shifters grouped into right tilt and left tilt groups that eliminates the need for a DC block element being a cause to mismatching and provides a beam shape less deformed at beam tilting. <P>SOLUTION: The phased-array antenna includes a feeding phase shift unit 130 with a lamination structure formed by laminating at least a ground conductor layer 117, an insulator layer 118, a main conductor layer 119, a variable dielectric constant dielectric layer 120 and a sub conductor layer 121 in this order, and the feeding phase shift unit 130 is provided with propagation characteristic variable lines 105 located on the sub conductor layer in a region planarly overlapped on lines on the main conductor layers. Application of a bias voltage between the main conductor layer and the sub conductor layer changes the dielectric constant of the variable dielectric constant dielectric of the variable propagation characteristic lines to control the propagation characteristic. Thus, the need for the DC block element having conventionally been inserted in series with feeder lines can be eliminated. <P>COPYRIGHT: (C)2007,JPO&INPIT

Description

The present invention relates to a phased array antenna.
More specifically, in a phased array antenna having a variable phase shifter configured using a variable dielectric constant dielectric whose dielectric constant changes depending on an applied electric field, the beam shape is less distorted even during beam tilt, and high directivity gain TECHNICAL FIELD OF THE INVENTION

  As a conventional phased array antenna having a variable phase shifter configured using a variable dielectric constant dielectric whose dielectric constant changes depending on the applied electric field, the variable phase shifter is divided into two groups for right side tilt and left side tilt. By controlling these phase shift amounts independently of each other, it is possible to suppress power variation and phase shift variation distributed to each antenna element, and thus maintain a high directivity gain without destroying a sharp beam shape even during beam tilt. There are some (see, for example, FIG. 4 of Patent Document 1).

  In addition, as a structure of a conventional phased array antenna having a variable phase shifter configured using a variable dielectric constant dielectric whose dielectric constant changes depending on an applied electric field, for example, support insulation of an open-ended line in the variable phase shifter A variable dielectric constant dielectric is used as a body to form a propagation characteristic variable line, and a voltage is applied between the propagation characteristic variable line conductor and the ground conductor to change the propagation characteristic of the propagation characteristic variable line to change the transmission characteristic. Some control the amount of phase shift of the phase shifter (see, for example, Patent Document 2).

  Furthermore, the variable phase shifter area has a two-layer microstrip line structure, and a variable dielectric constant dielectric is used as a support insulator for one layer, so that a propagation characteristic variable line is formed, and between the line conductors of both layers is formed. Connected by holes (see Embodiment 1 of Patent Document 1 and FIG. 1), or connected between line conductors of both layers by electromagnetic coupling (see Embodiment 2 of Patent Document 1 and FIG. 2), There is a type that controls the amount of phase shift of a variable phase shifter by changing the propagation characteristic of the propagation characteristic variable line by applying a voltage between the propagation characteristic variable line conductor and the ground conductor.

Here, the conventional phased array antenna will be described with reference to the drawings.
FIG. 3 is a diagram showing an example of a dielectric constant change characteristic when a variable dielectric constant dielectric is applied with an electric field, and FIG. 4 is a perspective view of a variable phase shifter using the variable dielectric constant dielectric.

  In general, a variable dielectric constant dielectric such as a ferroelectric has a property that the dielectric constant changes depending on an electric field applied as shown in FIG. 3, and a variable phase shifter is configured using the variable dielectric constant dielectric. For example, as shown in FIG. 4, a hybrid coupler 404 having an input / output line 403 in a microstrip line structure in which a waveguide conductor is laminated on a waveguide insulator 402 on a waveguide ground conductor 401. And an open-ended line 405 having the same length is connected to a pair of isolation ports of the hybrid coupler 404, and a variable dielectric constant dielectric is used only for the waveguide insulator 406 of the open-ended line. good.

  Here, by applying a bias voltage between the waveguide conductors 403 to 405 and the ground conductor 401 of the variable phase shifter 400, an electric field (quasi-TEM mode) and a bias generated by high-frequency power propagating through the microstrip line are applied. Since the direction of the electric field generated by the voltage (TEM mode) is substantially parallel, the open-ended line 405 functions as a propagation characteristic variable line 405 capable of controlling the propagation characteristic of the high-frequency power propagating by the bias voltage.

  The bias voltage to the variable dielectric constant dielectric 406 is a continuous conductor in which all of the waveguide conductors 403 to 405 constituting the variable phase shifter 400 are connected in a direct current manner. It is sufficient to input from any position.

  Here, the waveguide insulator in the region where the input / output line 403 and the hybrid coupler 404 are formed is a normal insulator whose dielectric constant does not change due to the applied electric field. Functions as a fixed line.

  In the variable phase shifter 400 configured as described above, a high frequency signal input from one input / output line 403a of the input / output line 403 is output to the two propagation characteristic variable lines 405 through the hybrid coupler 404, and two propagation characteristics are obtained. The high-frequency signal reflected at the open end of the variable line 405 receives a propagation phase delay reflecting the applied bias voltage and is re-input to the hybrid coupler 404, and the high-frequency signal passing through the hybrid coupler 404 is the other input / output line 403b. Are combined and output.

  In addition, when a high frequency signal is input from the other input / output line 403b, the high frequency signal is output to the one input / output line 403a with the same propagation phase delay just by reversing the input / output.

  Since the propagation characteristic variable line 405 is also connected to the input / output line 403 via the hybrid coupler 404 in a DC manner, even when a plurality of variable phase shifters 400 are connected in series with each other, the connection is possible. By applying a bias voltage to an arbitrary position on a continuous waveguide conductor of a plurality of variable phase shifters, the same bias voltage is simultaneously applied to all the variable phase shifters, so that the configuration of the bias circuit is simple. A variable phase shifter can be realized.

Next, the principle of the phased array antenna using the variable phase shifter will be described below.
FIG. 5 shows the principle of a phased array antenna using the above-described variable phase shifter.
The operation when this antenna is used for reception will be described below.
W1 to W4 represent wavefronts of incoming waves, and each wavefront receives a phase shift (propagation phase delay) of Φ while propagating in space from W1 to W2, W2 to W3, and W3 to W4.

  Now, paying attention to the wavefront W1, the signal component received by the antenna element 501 is not subjected to phase shift in the space, and passes through the three variable phase shifters 505, 506, and 507 in the feed phase shift section 500. The phase is shifted by Φ and reaches the power supply terminal 509 with a total phase shift amount of 3Φ.

  The signal component received by the antenna element 502 undergoes a phase shift of Φ while propagating in the space from the position W1 to the position W2, and the two variable phase shifters 506 and 507 are provided in the feed phase shift unit 500. The phase shifts by Φ by passing, and reaches the power supply terminal 509 with a total phase shift amount of 3Φ.

  The signal component received by the antenna element 503 undergoes a phase shift of 2Φ while propagating from W1 to W3 in the space, and passes through one variable phase shifter 508 in the power feeding phase shifter 500. The phase shift of Φ is received, and the power supply terminal 509 is reached with a total phase shift amount of 3Φ.

  Further, the signal component received by the antenna element 504 undergoes a phase shift of 3Φ while propagating in the space from the position W1 to the position W4, and therefore, one variable phase shifter does not pass through the feed phase shifter 500. The power supply terminal 509 is reached with a total phase shift amount of 3Φ without being subjected to phase shift.

  That is, the above-mentioned phased array antenna has a function of synthesizing incoming radio waves having the wavefront W1 in phase at the feeding terminal 509, and thus as an antenna that forms a main beam (directivity) in the arrival direction indicated by Θ in the figure. Operate.

  Since the phase shifters 505 to 508 in the power feeding phase shifter 500 are all variable phase shifters having the same characteristics, the same phase shift amount can be obtained with respect to the same control voltage value. In contrast, since it has one main beam and the feeding circuit unit 500 is formed of continuous conductors connected in a DC manner, the direction of the main beam can be changed by one bias voltage 510. .

As can be seen from FIG. 5, the main beam direction Θ is determined from the phase shift amount Φ of the variable phase shifter and the antenna element spacing d.
Θ = arccos (Φ / d)
It is a relationship.

  Next, the electric power distributed to each antenna element by controlling the amount of phase shift independently by dividing the variable phase shifter into two groups for right side tilt and left side tilt while having the above-mentioned beam control principle. The phased array antenna of FIG. 4 of Patent Document 1 will be described with reference to the drawings as an example of a system that can suppress variations and phase shift variations and thus maintain a high directivity gain without losing a sharp beam shape even during beam tilt.

  FIG. 6 is a layout diagram of the variable phase shifter of the phased array antenna described in FIG. 4 of Patent Document 1. 600 is a feeding phase shift unit, 601 is a feeding terminal, and 602 (602a to 602d) is a variable for right tilt. A phase shifter group, 603 (603a to 603d) is a variable phase shifter group for left tilt, 604 is a bias voltage for right tilt, 605 is a bias voltage for left tilt, 606 (606a to 606d) is an antenna element, and 607 is A DC blocking element for passing a high-frequency signal and separating a right-side tilt bias voltage and a left-side tilt bias voltage, 608 is a high-frequency blocking element that applies a bias voltage to each variable phase shifter and blocks a high-frequency signal. is there.

  According to the principle of the phased array antenna shown in FIG. 5 described above, the variable phase shifters are arranged asymmetrically. However, according to this, the number of variable phase shifters provided between the feed terminal and each antenna element is determined. In addition, each variable phase shifter has passing loss due to dielectric loss, conductor loss, and reflection loss due to mismatching, resulting in variations in power distributed to each antenna element and phase shift. It was difficult to obtain a symmetrical beam shape.

  As a method for solving this, in the configuration of FIG. 4 of Patent Document 1 shown in FIG. 6, the variable phase shifters provided between the feeding terminal 601 and each antenna element 606 are of the same type and the same number for all paths. The arrangement of the variable phase shifters is symmetrical.

  For beam control, all variable phase shifters are divided into two groups, a right-side tilt variable phase shifter and a left-side tilt variable phase shifter, and each group is set with independent bias voltages 604 and 605. The control method is taken.

  As can be seen from FIG. 6, assuming that the phase shift amount of the right tilt variable phase shifter is ΦR and the phase shift amount of the left tilt variable phase shifter is ΦL, the wavefront W1 reaches the power supply terminal 601. The total amount of phase shift received in the space and in the power feeding phase shift unit 600 is

Components received by antenna element 606a:
0 × (ΦR−ΦL) [in space] + 3 × ΦR + 0 × ΦL [in the feeding phase shift section] = 3ΦR
Components received by antenna element 606b:
1 × (ΦR−ΦL) [in space] + 2 × ΦR + 1 × ΦL [in the feeding phase shift section] = 3ΦR
Components received by antenna element 606c:
2 × (ΦR−ΦL) [in space] + 1 × ΦR + 2 × ΦL [in the feeding phase shift section] = 3ΦR
Components received by antenna element 606d:
3 × (ΦR−ΦL) [in space] + 0 × ΦR + 3 × ΦL [in the feeding phase shift section] = 3ΦR
Since all are synthesized in the same phase of 3ΦR, as in the case of FIG.
Θ = arccos ((ΦR−ΦL) / d)
It is the relationship.

Next, the structure of the phased array antenna of Patent Document 2 and Patent Document 1 having the above principle will be described with reference to the drawings.
FIG. 7A is a plan view and a cross-sectional view of a phased array antenna having a multilayer structure described in Patent Document 2. FIG.
In FIG. 7 (a), the uppermost position in the drawing is a plan view showing the state of the antenna viewed from the radiation surface side. Hereinafter, AA in the plan view in order toward the lower side in the drawing. A cross-sectional view taken along line AA, a cross-sectional view taken along the line BB, and a cross-sectional view taken along the line C-C showing the state of the cross section when the antenna is cut along a line, a line BB, and a line CC.

  That is, the AA line sectional view, the BB line sectional view, and the CC line sectional view are obtained by dividing the sectional view of the active phased array antenna shown in FIG. It is a detailed representation.

  Further, the plan view is obtained by extracting only the area of the broken line portion 609 in FIG. 6, and the display direction of the plan view is a direction obtained by rotating FIG. 6 by 90 degrees in the clockwise direction.

  Further, the plan view includes patterns 704 and 705 corresponding to the hybrid coupler 404 and the propagation characteristic variable line 405 included in the phase shifter 602 illustrated in FIG. 6, and the direct current illustrated in FIG. 6. A pattern 706 corresponding to the blocking element 607 and a pattern 707 corresponding to the high frequency blocking element 608 shown in FIG. 6 are indicated by broken lines.

  In the plan view, reference numeral 708 denotes an antenna element, 709 denotes an input terminal, 710 denotes a bias terminal, 711 denotes a feed line pattern, 712 denotes a coupling window between the feed line pattern 711 and the antenna element 708, and these regions are Along with the area of the hybrid coupler 704, a propagation characteristic fixed line that does not change the propagation characteristic for high frequency even when a bias voltage is applied is formed.

  On the other hand, the AA line cross-sectional view, the BB line cross-sectional view, and the CC line cross-sectional view show the layer structure constituting the antenna and its member types (constituent members).

  In these AA line sectional view, BB line sectional view, and CC line sectional view, 713 to 716 constitute a planar waveguide structure for constituting an antenna portion, and 713 for antenna element support 714 is a conductor layer on which an antenna element is formed, 715 is an air layer for an insulator necessary for constructing a planar waveguide structure, and 716 is grounding necessary for constructing a planar waveguide structure. It is a conductor layer.

  Further, reference numerals 716 to 719 form a planar waveguide structure for constituting a feeding phase shift part, and reference numeral 716 denotes a ground conductor layer (shared with the antenna part) necessary for constituting the planar waveguide structure, 717. Is an air layer for an insulator necessary for constructing a planar waveguide structure, 718 is a conductor layer for forming each pattern of the feeding phase shift section, 719 is an insulating layer for supporting the feeding phase shift section pattern, and 720 is It is a variable dielectric constant dielectric for a propagation characteristic variable line.

  Note that the three conductor layers 714, 716, and 718 are independently displayed for each layer in FIG. 7B so that the pattern shape of each layer is easily understood.

  In the phased array antenna described in Patent Document 2 configured as described above, four layers 713 to 716 are used as shown in the AA line sectional view, the BB line sectional view, and the CC line sectional view. The first inverted type (also called suspended type) microstrip structure for the antenna part is composed of the second inverted type microstrip structure for the feeding phase shift part by four layers 716 to 719, and As shown in the plan view, the antenna element 708 (714 in the cross-sectional view) and the feed line pattern 711 (718 in the cross-sectional view) are formed on the ground conductor layer 716 shared by the antenna portion and the feed phase shift portion. The electromagnetic wave is coupled through a coupling window 712 (coupling window 721 in the cross-sectional view), and high-frequency power is transferred.

  Further, the bias voltage is applied between the bias terminal 710 formed on the conductor layer 718 and the ground conductor layer 716, thereby propagating via the high-frequency blocking element pattern 707 → feed line pattern 711 → hybrid coupler pattern 704. This is applied to the characteristic variable line 705.

  The direction of the electric field (quasi-TEM mode) generated by the high-frequency power propagating through the propagation characteristic variable line 705 and the electric field (TEM mode) generated by the bias voltage are substantially parallel. It is possible to control the propagation characteristics of the high-frequency power propagating through.

  FIG. 8A is a plan view and a cross-sectional view of a phased array antenna having a multilayer structure disclosed in Embodiment 1 of Patent Document 1. FIG.

  In FIG. 8 (a), the uppermost position in the drawing is a plan view showing the state of the antenna viewed from the radiation surface side. Hereinafter, AA in the plan view in order toward the lower side in the drawing. A cross-sectional view taken along line AA, a cross-sectional view taken along the line BB, and a cross-sectional view taken along the line C-C are shown.

  That is, the AA line cross-sectional view, the BB line cross-sectional view, and the CC line cross-sectional view include the structure of the antenna portion of the active phased array antenna shown in FIG. It is shown in more detail by dividing the section.

Here, the display area of the plan view is the same as that of FIG.
In the plan view, a hybrid coupler pattern 804, a propagation characteristic variable line pattern 805, a direct current blocking element pattern 806, and a high frequency blocking element pattern 807 are represented by broken lines.

  Further, in the plan view, 808 is an antenna element, 809 is an input terminal, 810 is a bias terminal, 811 is a feed line pattern, 812 is a coupling window between the feed line pattern 811 and the antenna element 808, and 813 is propagated with the feed line pattern 811. The through holes connecting to the characteristic variable line pattern 805 are represented, and these areas together with the area of the hybrid coupler 804 are propagation characteristic fixed lines that do not change the high frequency propagation characteristics even when a bias voltage is applied.

  On the other hand, the AA line cross-sectional view, the BB line cross-sectional view, and the CC line cross-sectional view show the layer structure and the components constituting the antenna.

  In the AA line sectional view, the BB line sectional view, and the CC line sectional view, 814 to 817 constitute a planar waveguide structure for constituting the antenna portion, and 814 is for supporting the antenna element. Insulator layer, 815 is a conductor layer for manufacturing an antenna element, 816 is an air layer for an insulator necessary for constructing a planar waveguide structure, and 817 is a ground conductor layer necessary for constructing a planar waveguide structure It is.

  819 to 821 constitute a planar waveguide structure for constructing a feeding phase shifter other than the propagation characteristic variable line, and 819 represents a conductor for producing each pattern of the feeding phase shifter other than the propagation characteristic variable line. A layer 820 is a dielectric layer for an insulator necessary for constructing a planar waveguide structure, and 821 is a ground conductor layer necessary for constructing the planar waveguide structure.

  Further, 821 to 823 constitute a planar waveguide structure for constructing a propagation characteristic variable line, and 821 represents a ground conductor layer (shared with a feeding phase shift section) necessary for constructing the planar waveguide structure, Reference numeral 822 denotes a variable dielectric constant dielectric layer necessary for constructing a planar waveguide structure, and 823 denotes a conductor layer for producing a propagation characteristic variable line.

  Reference numeral 818 denotes an intermediate layer (air layer) that connects the planar waveguide structure of the antenna section and the planar waveguide structure of the feeding phase shift section.

  Note that the five conductor layers 815, 817, 819, 821, and 823 are independently displayed for each layer in FIG. 8B so that the pattern shape of each layer can be easily understood.

  In the phased array antenna disclosed in Embodiment 1 of Patent Document 1 configured as described above, as shown in cross-sectional views 801 to 803, the first inverted for the antenna unit is formed by four layers 814 to 817. Type (also known as suspended type) microstrip structure has three layers 819 to 821, and the second microstrip structure for the feed phase shifting part other than the propagation characteristic variable line is further variable in propagation characteristics by three layers 821 to 823. A third microstrip structure for the line is configured, and, as shown in the plan view, an antenna element 808 (815 in the AA line sectional view) and a feed line pattern 811 (in the AA sectional view) 819) is electromagnetically coupled through a coupling window 812 (824 in the AA sectional view) formed on the ground conductor layer 817 of the antenna portion, The frequency power is transferred, and the feed line pattern 811 (819 in the AA line cross-sectional view) and the propagation characteristic variable line pattern 805 (823 in the CC line cross-sectional view) are the through holes 813 (BB line). In the cross-sectional view, they are connected through 825).

  Further, the bias voltage is applied between the bias terminal 810 fabricated on the conductor layer 819 and the ground conductor layer 821, thereby propagating via the high frequency blocking element pattern 807 → feeding line pattern 811 → hybrid coupler pattern 804. This is applied to the characteristic variable line 805.

  Since the direction of the electric field (quasi-TEM mode) generated by the high frequency power propagating through the propagation characteristic variable line 805 and the electric field (TEM mode) generated by the bias voltage are substantially parallel, the bias voltage causes the electric field on the propagation characteristic variable line 805 to be It is possible to control the propagation characteristics of the high-frequency power propagating through.

9A is a plan view and a cross-sectional view of a phased array antenna having a multilayer structure disclosed in Embodiment 2 of Patent Document 1. FIG.
In FIG. 9 (a), the uppermost position in the drawing is a plan view showing the state of the antenna viewed from the radiation surface side. Hereinafter, AA in the plan view in order toward the lower side in the drawing. A cross-sectional view taken along line AA, a cross-sectional view taken along the line BB, and a cross-sectional view taken along the line C-C showing the state of the cross section when the antenna is cut along a line, a line BB, and a line CC.

  That is, the AA line sectional view, the BB line sectional view, and the CC line sectional view are obtained by adding the structure of the antenna unit to the structure of the phase shifter shown in FIG. Each section is shown in more detail.

Here, the display area of the plan view is the same as that of FIG.
Further, in the plan view, a hybrid coupler pattern 904 and a propagation characteristic variable line pattern 905 are represented by broken lines.

  Further, in the plan view, 906 is an antenna element, 907 is an input terminal, 908 is a bias terminal, 909 is a feed line pattern, 910 is a coupling window between the feed line pattern 909 and the antenna element 906, and 911 corresponds to a DC blocking element. Reference numeral 912 denotes a coupling window for electromagnetically coupling the direct current blocking element pattern 911 and the propagation characteristic variable line pattern 905, and reference numeral 913 denotes a pattern corresponding to the high frequency blocking element. These regions are regions of the hybrid coupler 904. At the same time, the transmission line is a fixed propagation characteristic line that does not change the propagation characteristic for high frequencies even when a bias voltage is applied.

On the other hand, the AA line cross-sectional view, the BB line cross-sectional view, and the CC line cross-sectional view show the layer structure and the components constituting the antenna.
In the AA line sectional view, the BB line sectional view, and the CC line sectional view, 914 to 917 constitute a planar waveguide structure for constituting the antenna portion, and 914 is for supporting the antenna element. Insulator layer, 915 is a conductor layer for producing an antenna element, 916 is an air layer for an insulator necessary for constructing a planar waveguide structure, and 917 is a ground conductor layer necessary for constructing a planar waveguide structure It is.

  Also, reference numerals 919 to 921 form a planar waveguide structure for configuring a feeding phase shift section other than the propagation characteristic variable line, and 919 is a conductor for producing each pattern of the feeding phase shift section other than the propagation characteristic variable line. Reference numeral 920 denotes a dielectric layer for an insulator necessary for constructing the planar waveguide structure, and reference numeral 921 denotes a ground conductor layer necessary for constructing the planar waveguide structure.

  Furthermore, 921 to 923 constitute a planar waveguide structure for constructing a propagation characteristic variable line, and 921 represents a ground conductor layer necessary for constructing the planar waveguide structure (shared with the feeding phase shift section). , 922 is a variable dielectric constant dielectric layer necessary for constructing a planar waveguide structure, and 923 is a conductor layer for producing a propagation characteristic variable line.

  Reference numeral 918 denotes an intermediate layer (air layer) that connects the planar waveguide structure of the antenna section and the planar waveguide structure of the feeding phase shift section.

  Note that the five conductor layers 915, 917, 919, 921, and 923 are displayed independently for each layer in FIG. 9B so that the pattern shape of each layer is easily understood.

  In the phased array antenna disclosed in Embodiment 2 of Patent Document 1 configured as described above, as shown in the AA line sectional view, the BB line sectional view, and the CC line sectional view, 914 The first inverted type (also called suspended type) microstrip structure for the antenna unit is composed of the four layers of -917 to the second microstrip for the feed phase shifting unit other than the propagation characteristic variable line by the three layers of 919 to 921. In the strip structure, a third microstrip structure for a variable propagation characteristic line is configured by three layers 921 to 923. As shown in the plan view, the antenna element 906 (in the sectional view taken along the line AA) is shown. 915) and the feed line pattern 909 (919 in the AA sectional view) are a coupling window 910 (924 in the AA sectional view) formed on the ground conductor layer 917 of the antenna section. Are coupled in an electromagnetic field, and deliver high-frequency power. Further, the feed line pattern 909 (919 in the AA line sectional view) and the propagation characteristic variable line pattern 905 (923 in the CC line sectional view) are Corresponding to the DC blocking element through the coupling window 912 (926 in the cross-sectional view taken along the line B-B) formed on the ground conductor layer 921 (shared with the feeding phase shifter) necessary for constituting the planar waveguide structure. The pattern 911 (925 in the BB sectional view) and the propagation characteristic variable line pattern 905 (923 in the CC sectional view) are electromagnetically coupled, and a direct current (bias) which is a control voltage of the variable phase shifter. Voltage) and high-frequency power delivery.

  Further, the bias voltage is applied between the bias terminal 908 fabricated on the conductor layer 923 and the ground conductor layer 921, thereby being applied to the propagation characteristic variable line 905 via the high frequency blocking element pattern 913.

The direction of the electric field (quasi-TEM mode) generated by the high-frequency power propagating through the propagation characteristic variable line 905 and the electric field (TEM mode) generated by the bias voltage are substantially parallel. It is possible to control the propagation characteristics of the high-frequency power propagating through.
Japanese Unexamined Patent Publication No. 2004-23228 (FIGS. 1, 2, and 4) Japanese Unexamined Patent Publication No. 2000-236207 (FIGS. 1, 2 and 4)

  However, the configuration of the conventional phased array antenna has a problem that it is difficult to maintain a high directivity gain without losing the beam shape even at the time of beam tilt.

  That is, in the conventional phased array antenna, in order to realize a high directivity gain with a bilaterally symmetric beam shape, the variable phase shifter is connected to the variable phase shifter group for right side tilt and the left side tilt as shown in FIG. However, in order to separate the two bias voltages in a direct current manner, the embodiments of Patent Document 2 and Patent Document 1 are used. 1 requires a pattern for a DC blocking element on the feed line pattern, and in the feed phase shift part disclosed in Embodiment 2 of Patent Document 1, the feed line and the propagation characteristic variable line Therefore, a pattern for a DC blocking element that couples the two in an electromagnetic field is required.

  However, in these cases, mismatches in the DC blocking elements inserted many on the line propagating the high-frequency signal are accumulated, so that the high directivity is obtained even when the beam tilt amount is zero (the beam is in the front direction). Even if the feed phase shifter is designed to have a characteristic gain, it simply cancels the mismatch accumulation due to the DC blocking element by adding elements or optimizing the line parameters. If the accumulated state of matching changes, the canceled state of unmatched accumulation collapses, and therefore the beam shape collapses, making it difficult to maintain a high directivity gain.

  The present invention has been made in order to solve the above-described conventional problems, and in a phased array antenna having a variable phase shifter configured using a variable dielectric constant dielectric whose dielectric constant changes depending on an applied electric field, a high directivity is provided. In order to realize the performance gain, the variable phase shifter is divided into a variable phase shifter group for the right tilt and a variable phase shifter group for the left tilt as shown in FIG. In the case of the configuration, it is an object to provide a phased array antenna that eliminates the need for a DC blocking element that causes mismatching, and therefore has little collapse of the beam shape even at the time of beam tilt and can maintain a high directivity gain.

  In order to solve the conventional problem, a phased array antenna according to claim 1 of the present application includes a phased phase shifter configured using a variable dielectric constant dielectric whose dielectric constant changes according to an applied electric field. The array antenna includes a feed phase shift portion having a laminated structure formed by laminating at least a ground conductor layer, an insulator layer, a main conductor layer, a variable dielectric constant dielectric layer, and a sub conductor layer in this order. It is what.

  The phased array antenna according to claim 2 of the present application is the phased array antenna according to claim 1, wherein the feeding phase shift unit includes a propagation characteristic fixed line that does not change a propagation characteristic of the high frequency power, and a high frequency power. And a propagation characteristic variable line that varies the propagation characteristic.

  The phased array antenna according to a third aspect of the present invention is the phased array antenna according to the second aspect, wherein the fixed propagation characteristic line is the sub-conductor layer corresponding to a line provided on the main conductor layer. An electric field created by high-frequency power propagating through the line provided on the main conductor layer without having a line in the upper region is concentratedly propagated between the main conductor layer and the ground conductor layer, and the propagation characteristic variable line Has a line in a region on the sub conductor layer corresponding to the line provided on the main conductor layer, and generates an electric field generated by high frequency power propagating through the line provided on the main conductor layer. And the ground conductor layer and the main conductor layer and the sub-conductor layer are distributed and propagated, and the propagation characteristic fixed line and the propagation characteristic variable line are configured as continuous conductors on the main conductor layer. , Characterized by It is intended.

  The phased array antenna according to claim 4 of the present application is the phased array antenna according to claim 3, wherein the propagation characteristic variable line is applied by applying a bias voltage between the main conductor layer and the sub conductor layer. The variable dielectric constant dielectric of the variable dielectric constant dielectric layer is changed to control the propagation characteristics of the high frequency power.

  The phased array antenna according to claim 5 of the present application is the phased array antenna according to claim 1, wherein the variable dielectric constant dielectric layer is made of liquid crystal or a material containing liquid crystal. It is.

  The phased array antenna according to claim 6 of the present application is the phased array antenna according to claim 1, wherein the laminated structure is second on the side of the sub conductor layer opposite to the variable dielectric constant dielectric layer. The variable dielectric constant dielectric layer is held in a sealed space formed between the insulating layer and the second insulating layer.

  According to the present invention, in a phased array antenna having a variable phase shifter configured using a variable dielectric constant dielectric whose dielectric constant is changed by an applied electric field, a variable for right side tilt is realized in order to realize high directivity gain. When the phase shifter group and the left tilt variable phase shifter group are configured such that the amount of phase shift can be controlled independently of each other, the two bias voltages that cause mismatching are separated in a DC manner. It is possible to realize an antenna that eliminates the need for a DC blocking element, and thus can maintain a high directivity gain with little beam shape collapse even during beam tilt.

Embodiments of the phased array antenna of the present invention will be described below in detail with reference to the drawings.
(Embodiment 1)
First, the phased array antenna of the present invention will be described with respect to an embodiment in which a solid dielectric is used as the variable dielectric constant dielectric layer.

FIG. 1A is a plan view and a cross-sectional view of a phased array antenna according to Embodiment 1 of the present invention.
In FIG. 1 (a), the uppermost position in the drawing is a plan view showing the state of the antenna viewed from the radiation surface side. Hereinafter, AA in the plan view in order toward the lower side in the drawing. A cross-sectional view taken along line AA, a cross-sectional view taken along the line BB, and a cross-sectional view taken along the line C-C showing the state of the cross section when the antenna is cut along a line, a line BB, and a line CC.

Here, the plan view display area is the same as that of the conventional antenna shown in FIG.
Further, in the plan view, the hybrid coupler pattern 104 and the propagation characteristic variable line pattern 105 are represented by broken lines.

  Further, in the plan view, 106 is an antenna element, 107 is an input terminal, 108 is a bias terminal, 109 is a feed line pattern, 110 is a bias line, 111 is a bias voltage supply through hole, 112 is a land for through hole, and 113 is a feed. The coupling window for electromagnetically coupling the line pattern 109 and the antenna element 106 is represented, and these areas together with the hybrid coupler 104 area are fixed propagation characteristics that do not change the propagation characteristics for high frequencies even when a bias voltage is applied. It is a track.

On the other hand, the AA line cross-sectional view, the BB line cross-sectional view, and the CC line cross-sectional view show the layer structure and the components constituting the antenna.
In the AA line sectional view, the BB line sectional view, and the CC line sectional view, 114 to 117 constitute a planar waveguide structure for constituting the antenna portion, and 114 is for supporting the antenna element. Insulator layer, 115 is a conductor layer for producing an antenna element, 116 is an air layer as an insulator layer necessary for constructing a planar waveguide structure, and 117 is a ground conductor necessary for constructing a planar waveguide structure Is a layer.

  Reference numerals 117 to 123 form a planar waveguide structure for constituting the feeding phase shift section 130, and 117 denotes a ground conductor layer (shared with the antenna section) necessary for constructing the planar waveguide structure, 118. Is an air layer as an insulator layer necessary for constructing a planar waveguide structure, 119 is a main conductor layer for forming each pattern of a feeding phase shift section, and 120 is a variable dielectric constant dielectric layer for a propagation characteristic variable line , 121 is a sub conductor layer for producing a bias line for changing the electric field distribution state of the propagation characteristic variable line, 122 is an insulator layer for electromagnetically isolating the bias voltage supply circuit from the main conductor layer 119, and 123 is a bias. It is a conductor layer which produces the wiring pattern of a voltage supply circuit.

  Note that the five conductor layers 115, 117, 119, 121, and 123 are displayed independently for each layer in FIG. 1B so that the pattern shape of each layer can be easily understood.

  In the phased array antenna of the present embodiment configured as described above, the antenna has four layers 114 to 117 as shown in the AA line cross-sectional view, the BB line cross-sectional view, and the CC line cross-sectional view. In the first inverted type (also called suspended type) microstrip structure for the part, the second inverted type microstrip structure for the feeding phase shift part is configured by four layers 117 to 120. In the inverted microstrip structure 2, the sub conductor layer 121, the insulator layer 122, and the conductor layer 123 are disposed on the opposite side (lower side in the cross-sectional view) across the ground conductor layer 117 and the main conductor layer 119. It is an improved track with three additional layers.

  As described above, in the phased array antenna according to the first embodiment, at least the ground conductor layer 117, the insulator layer 118 which is an air layer, the main conductor layer 119, the variable dielectric constant dielectric layer 120, and the sub conductor layer 121 are provided. Feeding phase shifters 117 to 121 having a laminated structure formed by sequentially laminating are provided.

  In addition, as shown in the plan view of FIG. 1A, the antenna element 106 (115 in the AA line cross-sectional view) and the feed line pattern 109 (119 in the BB cross-sectional view) It is electromagnetically coupled through a coupling window 113 (coupling window 124 in the AA line cross-sectional view) formed on the ground conductor layer 117 shared by the phase-shifting portion, and high-frequency power is transferred. .

  Furthermore, the bias voltage is applied between the bias terminal 108 formed on the conductor layer 123, the main conductor layer 119, and the ground conductor layer 117 (the main conductor layer 119 and the ground conductor layer 117 have the same potential). This is applied to the bias line 110 via the through-hole land 112 to the bias voltage supply through-hole 111.

  As described above, in the phased array antenna according to the first embodiment, the feeding phase shifters 117 to 123 bias the propagation characteristic fixed lines 104 and 109 that propagate the high frequency power without changing the propagation characteristic, and the high frequency power. A variable propagation characteristic line 105 that propagates with propagation characteristics according to voltage is provided on the main conductor layer 119 with a continuous conductor, and a bias is formed on the sub conductor layer 121 in a region where the propagation characteristic fixed lines 104 and 109 are formed. A bias line 110 is provided on the sub conductor layer 121 in a region where the propagation characteristic variable line 105 is formed without the line.

  Here, the operation of the propagation characteristic fixed line and the propagation characteristic variable line will be described in more detail with reference to FIG. 1C in which the peripheral portion of the main conductor in the BB line sectional view and the CC line sectional view is enlarged. To do.

  FIG. 1C shows the electric field distribution of the high-frequency power propagating on the main conductor layer 119 in the BB line sectional view and the main conductor layer 119 and the sub-conductor layer 121 in the BB line sectional view.

  In FIG. 1C, 117 is a ground conductor layer, 118 is an air layer for an insulator, 120 is a variable dielectric constant dielectric layer, and 122 is an insulator layer.

  Reference numeral 125 denotes an electric field generated by the high-frequency power propagating on the main conductor layer in the BB line sectional view, and 126 propagates on the main conductor layer and the sub-conductor layer in the CC line sectional view. It shows the electric field created by high-frequency power.

  Here, as shown in FIG. 1C, a bias line is provided on the sub-conductor layer in a region overlapping the line provided on the main conductor layer in the region of the BB cross-sectional view. Therefore, the electric field lines coming out of the main conductor layer are concentrated and propagated between the main conductor layer and the ground conductor layer (there are few that pass through the variable dielectric constant dielectric layer).

  For this reason, when a bias voltage is applied to the phase shifter, an electric field due to the bias voltage is not generated in the variable dielectric constant dielectric layer around the main conductor layer, and thus the dielectric constant of the variable dielectric constant dielectric layer is Since it does not change and the propagation characteristics for high-frequency power propagating on the main conductor layer do not change, the main conductor in this region constitutes a propagation characteristic fixed line.

  On the other hand, as shown in FIG. 1C, a bias line is provided on the sub-conductor layer in a region overlapping the line provided on the main conductor layer in the region of the CC cross-sectional view. Therefore, the electric lines of force that emerge from the main conductor layer are distributed not only between the main conductor layer and the ground conductor layer but also between the main conductor layer and the sub conductor layer (many of them pass through the variable dielectric constant dielectric layer) and propagate. is doing.

  Therefore, when a bias voltage is applied to the phase shifter, an electric field due to the bias voltage is generated between the main conductor layer and the bias line. The electric field due to the bias voltage is distributed between the main conductor layer 119 and the sub-conductor layer. Therefore, the dielectric constant of the variable dielectric constant dielectric layer between the main conductor layer and the bias line changes, and the high frequency power propagates on the main conductor layer. Propagation characteristics change, and the main conductor layer in this region constitutes a propagation characteristic variable line.

  That is, in the phased array antenna according to the first embodiment, the dielectric constant of the variable dielectric constant dielectric layer of the propagation characteristic variable line is changed by changing the bias voltage applied between the main conductor layer and the sub conductor layer. It is configured to control the amount of phase shift by changing the propagation characteristic of the propagation characteristic variable line.

  In the fixed propagation line, since the variable dielectric constant dielectric layer exists between the main conductor layer and the sub conductor layer, the main conductor is not affected even if a bias voltage is applied between the ground conductor layer and the sub conductor layer. No DC voltage is applied between the layer and the sub conductor layer. For this reason, since the right tilt control voltage and the left tilt control voltage do not collide with each other through the main conductor layer, the DC blocking element is unnecessary.

  As described above, according to the phased array antenna of the first embodiment, the feeding phase shift portion is formed by laminating the ground conductor layer, the insulator layer, the main conductor layer, the variable dielectric constant dielectric layer, and the sub conductor layer in this order. Thus, the line through which the high-frequency power propagates can be insulated from the bias voltage without providing a DC blocking element on the line through which the high-frequency power propagates. Therefore, in order to achieve a high directivity gain, the variable phase shifter is divided into a variable phase shifter group for right tilt and a variable phase shifter group for left tilt, and the phase shift amount is controlled independently of each other. In this case, the accumulation of mismatch due to the DC blocking element is eliminated, so that it is possible to realize an antenna that can maintain a high directivity gain with little collapse of the beam shape even during beam tilt.

  In the plan view of FIG. 1A, the phased array antenna of the first embodiment is not provided with a line pattern corresponding to the high-frequency blocking element shown in Patent Document 2 and Patent Document 1, but this is a bias. Since most of the high-frequency current flowing on the line 110 is concentrated on the surface facing the main conductor layer 119 side, as shown in FIG. 1, by adopting a laminated structure in which power is supplied from the side opposite to the main conductor layer 119 side, This is because the high-frequency blocking element can be omitted.

In the first embodiment, a ferroelectric material such as BaTiO ₃ or BaSrTiO ₃ —MgO can be used as the variable dielectric constant dielectric layer, and a thermosetting epoxy as well as an air layer as the insulator layer. Resin, urethane resin, xylene resin, UV curable acrylic resin, epoxy resin, phenol resin, polytetrafluoroethylene (PTFE), liquid crystal polymer, resin such as polyimide, polyamide, epoxy, or their composite materials, glass and ceramics Needless to say, a layer made of a photopolymerizable polymer, a thermopolymerizable polymer, or the like can be used.

(Embodiment 2)
Next, with respect to the phased array antenna of the present invention, an embodiment in which a liquid such as a liquid crystal is used as the variable dielectric constant dielectric layer will be described.

FIG. 2A is a plan view and a cross-sectional view of a phased array antenna according to Embodiment 2 of the present invention.
In FIG. 2 (a), the uppermost position in the drawing is a plan view showing the state of the antenna viewed from the radiation surface side. Hereinafter, AA in the plan view in order toward the lower side in the drawing. A cross-sectional view taken along line AA, a cross-sectional view taken along the line BB, and a cross-sectional view taken along the line C-C showing the state of the cross section when the antenna is cut along a line, a line BB, and a line CC.

Here, the display area of the plan view is the same as that of FIG. 7 showing a conventional antenna.
In the plan view, a hybrid coupler pattern 204 and a propagation characteristic variable line pattern 205 are indicated by broken lines.
Furthermore, each element 206 to 213 in the plan view is the same as that in FIG. 1 of the first embodiment.

  On the other hand, the AA line cross-sectional view, the BB line cross-sectional view, and the CC line cross-sectional view show the layer structure and the components constituting the antenna.

  In AA line cross-sectional view, BB line cross-sectional view, and CC line cross-sectional view, 214 to 217 constitute a planar waveguide structure for constituting an antenna portion. 1 in FIG.

  Reference numerals 217 to 223 form a planar waveguide structure for constituting the feeding phase shift section 230, and reference numeral 217 denotes a ground conductor layer (shared with the antenna section) necessary for constructing the planar waveguide structure. Is an insulator layer necessary for constructing a planar waveguide structure, 219 is a main conductor layer for forming each pattern of the feeding phase shift section, 220 is a variable dielectric constant dielectric layer for a propagation characteristic variable line, and 221 is a propagation A sub-conductor layer for producing a bias line for changing the electric field distribution state of the variable characteristic line, 222 is an insulator layer for electromagnetically isolating the bias voltage supply circuit from the main conductor layer 219, and 223 is a bias voltage supply circuit It is a conductor layer for producing a wiring pattern.

Here, in the second embodiment, a case where a liquid such as liquid crystal is used as the variable dielectric constant dielectric layer 220 is shown. The two insulator layers 218 and 222 have the end portions of the insulator layers 218 and 222 as the end portions. It is connected by a spacer 240 made of the same material, and forms a box shape that surrounds and holds the liquid at the antenna end as shown in the AA line cross-sectional view, the BB line cross-sectional view, and the CC line cross-sectional view. Thus, the variable dielectric constant dielectric layer 220 which is a liquid such as liquid crystal is stably held (accommodated) in a sealed space 250 inside the box-shaped insulator layer.
Further, since the main conductor layer 219 cannot be formed on the liquid, it is formed on the surface of the insulator layer 218.

  The five conductor layers 215, 217, 219, 221, and 223 are the same as those in the first embodiment, and the pattern shape of each layer is the same as that in FIG.

  In the phased array antenna of the present embodiment configured as described above, the antenna has four layers 214 to 217 as shown in the AA line sectional view, the BB line sectional view, and the CC line sectional view. In the first inverted type (also called suspended type) microstrip structure for the part, the second inverted type microstrip structure for the feeding phase shift part is configured by four layers 217 to 220. In the inverted microstrip structure 2, the sub conductor layer 221, the insulator layer 222, and the conductor are arranged on the opposite side (the lower side in the sectional view taken along the line CC) across the ground conductor layer 217 and the main conductor layer 219. It is an improved type line in which three layers with the layer 223 are added.

  Here, the operation of the propagation characteristic fixed line and the propagation characteristic variable line will be described in more detail with reference to FIG. 2B in which the peripheral portion of the main conductor in the BB line sectional view and the CC line sectional view is enlarged. To do.

  FIG. 2B shows the electric field distribution of the high-frequency power propagating on the main conductor layer 219 of the BB line cross-sectional view and the main conductor layer 219 and the sub-conductor layer 221 of the CC line cross-sectional view.

  In FIG. 2B, reference numeral 217 denotes a ground conductor layer, 218 denotes an insulator layer, 220 denotes a variable dielectric constant dielectric layer, and 222 denotes an insulator layer.

  Further, reference numeral 225 denotes an electric field generated by high-frequency power propagating on the main conductor layer 219 in the sectional view taken along the line B-B, and reference numeral 226 denotes the main conductor layer 219 and the sub conductor layer 221 in the sectional view taken along the line C-C. It shows the electric field created by the high-frequency power propagating through.

  Here, as shown in FIG. 2B, a bias line is provided on the sub-conductor layer in a region overlapping the line provided on the main conductor layer in the region of the sectional view taken along the line BB. Therefore, the electric lines of force that emerge from the main conductor layer are concentrated and propagated between the main conductor layer and the ground conductor layer (there are few that pass through the variable dielectric constant dielectric).

  That is, when a bias voltage is applied to the phase shifter, an electric field due to the bias voltage is not generated in the variable dielectric constant dielectric layer around the main conductor layer, and thus the dielectric constant of the variable dielectric constant dielectric layer changes. In addition, since the propagation characteristics for high-frequency power propagating on the main conductor layer do not change, the main conductor layer in this region is a propagation characteristic fixed line.

  On the other hand, as shown in FIG. 2B, a bias line is provided on the sub-conductor layer in a region overlapping with the line provided on the main conductor layer in the region of the CC cross-sectional view. As a result, the electric field lines coming out of the main conductor layer are distributed not only between the main conductor layer and the ground conductor layer but also between the main conductor layer and the sub conductor layer (many passes through the variable dielectric constant dielectric) and propagates. is doing.

  That is, when a bias voltage is applied to the phase shifter, an electric field due to the bias voltage is generated between the main conductor layer and the bias line, but the electric field due to this bias voltage is distributed between the main conductor layer 219 and the sub conductor layer. Therefore, the dielectric constant of the variable dielectric constant dielectric layer between the main conductor layer and the bias line changes, and the propagation characteristic for the high frequency power propagating on the main conductor layer changes. The main conductor layer in this region is a variable propagation characteristic line.

  That is, in the phased array antenna of the second embodiment, as in the first embodiment, by changing the bias voltage applied between the main conductor layer and the sub conductor layer, the variable dielectric constant dielectric of the propagation characteristic variable line is changed. The phase shift amount is controlled by changing the dielectric constant and changing the propagation characteristic of the variable propagation characteristic line.

  In addition, since the propagation characteristic fixed line has a structure in which a variable dielectric constant dielectric layer is interposed between the main conductor layer and the sub conductor layer, even if a bias voltage is applied to the sub conductor layer, the main conductor layer is not affected. Does not apply a direct bias voltage. For this reason, since the right tilt control voltage and the left tilt control voltage do not collide with each other through the main conductor layer, the DC blocking element is unnecessary.

  As described above, according to the second embodiment, as in the first embodiment, the power feeding phase shifting portion is divided into the ground conductor layer, the insulator layer, the main conductor layer, the variable dielectric constant dielectric layer, and the sub conductor layer. Since the laminated structure is formed by laminating in this order, it is possible to insulate the bias voltage from the line through which the high frequency power propagates without providing a DC blocking element on the line through which the high frequency power propagates. Therefore, in order to achieve high directivity gain, the variable phase shifter is divided into a variable phase shifter group for right tilt and a variable phase shifter group for left tilt, and the phase shift amount is controlled independently of each other. In this case, it is possible to realize a phased array antenna capable of maintaining a high directivity gain with less misalignment of the beam shape even when the beam is tilted.

  Further, according to the second embodiment, since the liquid crystal is used as the variable dielectric constant dielectric layer, it is possible to realize a phased array antenna in which the dielectric constant of the variable dielectric constant dielectric layer can be easily changed. It becomes.

  In the second embodiment, nematic liquid crystal, smectic liquid crystal, cholesteric liquid crystal, discotic liquid crystal, ferroelectric liquid crystal, or a composite material of liquid crystal and resin is used as the liquid variable dielectric constant dielectric layer. It goes without saying that it is possible.

Further, a separate insulator layer 218, 222 and spacer 240 are connected to form a box-shaped insulator layer having a space 250 for accommodating the variable dielectric constant dielectric layer 220 therein. The liquid variable dielectric constant dielectric layer 220 may be integrally formed as long as it can be stably held.
Furthermore, any other structure may be adopted as long as the liquid variable dielectric constant dielectric layer 220 can be stably held.

  Furthermore, it goes without saying that the box-shaped variable dielectric constant dielectric layer in which the liquid crystal in the second embodiment is stably held can be used as the variable dielectric constant dielectric layer in the first embodiment. The main advantage is that air with extremely low dielectric loss can be used as the insulator layer of the main conductor line, and that liquid crystal can be used as the variable dielectric constant dielectric, thereby expanding the selection range of the variable dielectric constant dielectric material. Needless to say.

  Further, in the first embodiment and the second embodiment, the line shape of the main conductor layer and the sub conductor layer in the propagation characteristic variable line portion is a linear resonant line shape having a length of ½ wavelength or an integral multiple thereof, Further, it is needless to say that the variable propagation characteristics can be obtained in the ring-shaped or disk-shaped resonant line shape as well.

  In the second embodiment, buffer layers may be provided on the surfaces of both conductor layers in order to prevent the conductor metals of the main conductor line layer and the sub conductor layer from directly touching the liquid crystal.

  As described above, the present invention provides a variable phase shift antenna for realizing a high directivity gain in a phased array antenna having a variable phase shifter configured using a variable dielectric constant dielectric whose dielectric constant varies with an applied electric field. DC blocking element that causes mismatch when phase shifter is divided into variable phase shifter group for right tilt and variable phase shifter group for left tilt to control phase shift amount independently of each other Therefore, it is possible to realize an antenna that can maintain a high directivity gain with little collapse of the beam shape even when the beam is tilted, and is useful as an on-vehicle radar or satellite communication antenna.

Plan view and sectional view of phased array antenna according to Embodiment 1 of the present invention Plan view of each conductor layer of phased array antenna according to Embodiment 1 of the present invention Electric field distribution diagram near main conductor layer and sub-conductor layer of phased array antenna in Embodiment 1 of the present invention Plan view and sectional view of phased array antenna in embodiment 2 of the present invention Electric field distribution diagram in the vicinity of the main conductor layer and the sub conductor layer of the phased array antenna according to the second embodiment of the present invention Diagram showing examples of characteristics of variable dielectric constant dielectric Diagram showing the principle of phase shifter Diagram showing the principle of phased array antenna Diagram showing phase shifter arrangement of high gain phased array antenna Plan view and sectional view of conventional phased array antenna shown in Patent Document 2 The top view of each conductor layer of the conventional phased array antenna shown by patent document 2 A plan view and a sectional view of a conventional phased array antenna shown in claim 1 of Patent Document 1 The top view of each conductor layer of the conventional phased array antenna shown by Claim 1 of patent document 1 Plan view and sectional view of conventional phased array antenna shown in claim 2 of Patent Document 1 The top view of each conductor layer of the conventional phased array antenna shown in Claim 2 of patent document 1

Explanation of symbols

104 Hybrid coupler 105 Propagation characteristic variable line 106 Antenna element 107 Input terminal 108 Bias terminal 109 Feed line 110 Bias line 111 Bias voltage supply through hole 112 Through hole land 113 Coupling window 114 Insulator layer 115 Conductor layer 116 Air for insulator Layer 117 Ground conductor layer 118 Air layer for insulator 119 Main conductor layer 120 Variable dielectric constant dielectric layer 121 Sub-conductor layer 122 Insulator layer 123 Conductor layer 124 Binding window 125 Electric field generated by high-frequency power propagating on the main conductor layer 126 Electric field 130 generated by high-frequency power propagating on the main conductor layer and the sub conductor layer Feeding phase shifter 204 Hybrid coupler 205 Propagation characteristic variable line 206 Antenna element 207 Input terminal 208 Bias terminal 209 Feed line 210 Bias line 211 Bias voltage supply Through-hole 212 Through-hole land 213 Coupling window 214 Insulator layer 215 Conductor layer 216 Insulator air layer 217 Ground conductor layer 218 Insulator layer 219 Main conductor layer 220 Variable dielectric constant dielectric layer 221 Sub-conductor layer 222 Insulator layer 223 Conductor layer 224 Coupling window 225 Electric field 226 generated by high-frequency power propagating on the main conductor layer Electric field 230 generated by high-frequency power propagating on the main conductor layer and the sub-conductor layer 230 Feeding phase shifter 240 Spacer 250 Space 401 Waveguide grounding Conductor 402 Insulator for waveguide 403 Input / output line 404 Hybrid coupler 405 Open-ended line 406 Insulator for open-ended line waveguide 500 Feeding phase shift sections 501 to 504 Antenna elements 505 to 508 Variable phase shifter 509 Feeding terminal 510 Bias Voltage 600 Feeding phase shifter 601 Feeding terminal 602 Variable for right side tilt Phaser group 603 Left-side tilt variable phase shifter group 604 Right-side tilt bias voltage 605 Left-side tilt bias voltage 606 Antenna element 607 DC blocking element 608 High-frequency blocking element 609 FIG. 1, FIG. 2, FIG. 7, FIG. 9 704 Hybrid coupler 705 Propagation characteristic variable line 706 DC blocking element 707 High frequency blocking element 708 Antenna element 709 Input terminal 710 Bias terminal 711 Feed line 712 Insulating layer 714 Insulator layer 714 Conductor layer 715 Insulator air layer 716 Ground conductor layer 717 Insulator air layer 718 Conductor layer 719 Insulator layer 720 Variable dielectric constant dielectric 721 Coupling window 804 Hybrid coupler 805 Propagation characteristic variable line 806 DC blocking element 807 High frequency blocking element 808 Antenna element 809 Input terminal 810 Ba Iias terminal 811 Feed line 812 Coupling window 813 Through hole 814 Insulator layer 815 Conductor layer 816 Insulator air layer 817 Ground conductor layer 818 Air layer 819 Conductor layer 820 Insulator dielectric layer 821 Ground conductor layer 822 Variable dielectric Dielectric layer 823 Conductor layer 824 Coupling window 825 Through hole 904 Hybrid coupler 905 Propagation characteristic variable line 906 Antenna element 907 Input terminal 908 Bias terminal 909 Feed line 910 Coupling window 911 DC blocking element 912 Coupling window 913 High frequency blocking element 914 Insulator Layer 915 Conductor layer 916 Insulator air layer 917 Ground conductor layer 918 Air layer 919 Conductor layer 920 Dielectric layer 921 Ground conductor layer 922 Variable dielectric constant dielectric layer 923 Conductor layer 924 Coupling window 925 DC blocking element 926 Coupling window

Claims (6)

In a phased array antenna having a variable phase shifter configured using a variable dielectric constant dielectric whose dielectric constant is changed by an applied electric field,
Provided with a feeding phase shifter having a laminated structure formed by laminating at least a ground conductor layer, an insulator layer, a main conductor layer, a variable dielectric constant dielectric layer, and a sub conductor layer in this order,
A phased array antenna characterized by that. The phased array antenna according to claim 1,
The feeding phase shifter is
Propagation characteristics fixed line that does not change the propagation characteristics of high-frequency power,
It has a propagation characteristic variable line that varies the propagation characteristic of high-frequency power,
A phased array antenna characterized by that. The phased array antenna according to claim 2,
The propagation characteristic fixed line is:
An electric field created by high-frequency power propagating through a line provided on the main conductor layer without having a line in a region on the sub-conductor layer corresponding to the line provided on the main conductor layer, and the main conductor layer Concentrated propagation between the ground conductor layers,
The propagation characteristic variable line is:
An electric field generated by high-frequency power having a line in a region on the sub conductor layer corresponding to the line provided on the main conductor layer and propagating through the line provided on the main conductor layer, Distributed and propagated between the ground conductor layer and the main conductor layer and the sub conductor layer,
On the main conductor layer, the propagation characteristic fixed line and the propagation characteristic variable line are configured as continuous conductors,
A phased array antenna characterized by that. The phased array antenna according to claim 3,
The propagation characteristic variable line is:
By applying a bias voltage between the main conductor layer and the sub-conductor layer, the dielectric constant of the variable dielectric constant dielectric constituting the variable dielectric constant dielectric layer is changed, and the propagation characteristics of high frequency power are controlled.
A phased array antenna characterized by that. The phased array antenna according to claim 1,
The variable dielectric constant dielectric layer is made of liquid crystal or a material containing liquid crystal,
A phased array antenna characterized by that. The phased array antenna according to claim 1,
The laminated structure has a second insulating layer on the side of the sub conductor layer opposite to the variable dielectric constant dielectric layer,
The variable dielectric constant dielectric layer is held in a sealed space formed between the insulating layer and the second insulating layer;
A phased array antenna characterized by that.

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