JP2002261738A - Wireless packet communication method and apparatus - Google Patents

Abstract

PROBLEM TO BE SOLVED: To provide a wire packet communication method and apparatus which supports data speeds for audio, video and computer graphics. SOLUTION: An automatic repeat request(ARQ) operation can be realized in wireless communication, by (2401) transmitting a plurality of data packets in a superpacket and (2430) responding, using an acknowledgement packet indicating which packet in the superpacket is repeat-requested.

Description

DETAILED DESCRIPTION OF THE INVENTION

[0001]

The present invention relates generally to wireless communications, and more particularly, to wireless communications using channel coding, multiple data rates, multiple modulation and channel coding schemes, or automatic repeat request (ARQ).

[0002]

2. Description of the Related Art IEEE 802.15 task group 3
Is a high-speed wireless personal area network (WPA)
The requirements in (N) are outlined. For example, different data rates should be used to support audio, video, and computer graphics.

[0003]

The present invention provides a WPAN that supports data rates for audio, video, and computer graphics.

[0004]

SUMMARY OF THE INVENTION The present invention advantageously employs probe, listen, and select techniques to select from the available frequency spectrum a frequency band having communication quality suitable for communication at a desired data rate. I do. Probe packets are transmitted at various frequencies during a defined time period and frequency channel quality information is obtained from those probe packets. This quality information is used to select a desired frequency band. The communication quality of the selected band may also be used as a basis for selecting from among a plurality of available modulation and coding combinations used in the communication operation. Further in accordance with the present invention, an ARQ operation may be performed by sending a plurality of data packets in a superpacket and responding with an ARQ acknowledgment packet indicating which of the superpackets requires retransmission. . Furthermore, according to the present invention,
Data encoding algorithms can be used to generate redundant (overhead) bits from the original data bits, and if redundant bits are needed, the original data bits and the redundant bits can be sent in separate transmissions. At the receiver, the original data bits can be determined from the received redundant bits, or the received data bits are combined with the received redundant bits and decoded together to generate the original data bits. Can be.

[0005]

DETAILED DESCRIPTION OF THE INVENTION The present invention relates to an IEEE P80 for a wireless personal area network (WPAN).
2.15 Working Group reference document, a review of the requirements in a high-speed wireless personal area network (WPAN) system, the contents of which are incorporated herein by reference, "May 11, 2000," TG3 standard definition (TG3-Criteria
-Definitions), which provides the best solution in terms of complexity versus performance, IEEE 80
2.15 Includes PHY layer solution for task group 3. The required data rates to be supported by the high-speed WPAN according to the present invention are specified in the above-mentioned reference document. Data rate in audio is 128k
bps to 1450 kbps, 2.5 Mbps to 18 Mbps for video, and 15,38 Mbps for computer graphics. The present invention provides a two-mode or three-mode system in the 2.4 GHz band for a wide range of required data rates and to obtain a cost-effective solution covering all data rates. Available modes include: (1) Mode 1 is a conventional Bluetooth 1.0 system, which provides a data rate of 1 Mbp. (2) Mode 2 uses the same frequency hopping (FH) pattern as Bluetooth, but uses QAM modulation that gives a data rate of 3.9 Mbps. (3) Mode 3 consists of probe, listening, and selection (PL
S) Using technology, 2.402 GHz to 2.483
A good 22 MHz band in the ISM of GHz is selected, and direct spread spectrum (direct sequence) is selected.
(nice spread spectrum DSSS)
To transmit up to 44 Mbps.

FIG. 1 summarizes examples of system parameters according to the present invention. A wireless transceiver device according to the present invention may support any combination of the above modes of operation. Examples of those devices are Mode 1 + Mode 2 capable devices that cover audio and Internet streaming data rates up to 2.5 Mbps,
And a device capable of processing mode 1 + mode 3, which covers DVD high quality game applications up to 38 Mbps. FIG. 2 schematically shows these typical configurations.

Mode 1 in the proposed system is:
Conventional Bluetooth operation, which is the specification of the Bluetooth system of July 26, 1999, version 1.0A ( Specification of th
e Bluetooth System , Versi
on 1.0A).

FIG. 3 summarizes the parameters in mode 2 and compares it to mode 1. A typical symbol rate in mode 2 is 0.65 Msymbols /
sec (other speeds are available) and 16QA
2.6 Mbits for M (16-level quadrature amplitude modulation)
/ Sec, and a bit rate of 3.9 Mbits / sec for 64QAM (64-level quadrature amplitude modulation). The transmission spectrum mask in mode 2 can be, for example, the same as Bluetooth, as shown in FIG. In FIG. 4, the transmitter transmits on channel M, and the power of adjacent channels is measured on channel N. The spectral mask of FIG.
= 0.54 raised cosine filter (raised cos)
Inefilter) and a 0.6 dB 3 dB bandwidth for mode 2 symbol rate.

Operation 1 in mode 1 and mode 2
In one example, the Bluetooth master and slave first synchronize with each other and communicate using mode 1,
Next, mode 2 is entered by negotiation. FIG.
The master and slave show typical transitions into and out of mode 2. Entry into and exit from mode 2 can be negotiated between master and slave.

The structure of a representative frame format for transmission from master to slave and from slave to master in mode 2 is similar to that in mode 1 and is shown in FIG. 6A. In one example,
The preamble is a pattern (1 + j) * {1, -1,
1, -1,1, -1,1, -1, -1,1, -1,1, -1,
1, -1, 1, -1, 1, -1, 1, -1},
This assists the receiver in initial timing acquisition. This preamble is followed by a 64-bit Bluetooth synchronization word transmitted using quadrature phase shift keying (QPSK), which means transmission of 32 symbols in mode 2. This sync word is followed by a 54 bit Bluetooth header transmitted using QPSK, which means 27 symbols in mode 2. 16 / 64Q
The earliest configuration in AM is (constellaratio
n) is the preamble, as shown in FIG.
Used for transmission of sync word and header.
The header is followed by a payload of 1 slot or up to 5 slots, similar to Bluetooth. The maximum number of bits in the payload is therefore 7120 bits for 16QAM and 1068 for 64QAM.
0 bits.

The master has the same piconet, with one slave in mode 2 and another in mode 1, as shown in the exemplary WPAN of FIG.
net). The timing diagram of FIG. 8 illustrates the Bluetooth SCO HV1 link between Master M and Slave S ₁ and S ₃ (ie,
Shows an example for mode 1), in this case, the slave S ₂ is communicating with the master and mode 2 (see also FIG. 7).

FIG. 9 is a block diagram of an exemplary receiver algorithm for acquisition and packet reception in mode 2, and FIG. 10 is a block diagram of an exemplary receiver supporting mode 2. It is shown. Figure 1
At zero, the A / D converter may sample the incoming symbol at, for example, two samples / symbol, meaning a sampling rate of 1.3 MHz. FIG. 11 shows a block diagram of a representative transmitter supporting mode 2.
Some blocks may be shared by the transmitter (FIG. 11) and the receiver (FIG. 10) to reduce the overall cost of the transceiver in mode 2. Similarly, some blocks of mode 2 transmitter and mode 2 receiver can also be used for mode 1, thereby reducing the overall cost of transceiver implementation for the mode 1 + mode 2 combination. Can be reduced.

In the example 101 of FIG. 10, in order to improve the packet error rate in the presence of an automatic repeat request (ARQ), a convolution (rate = 1/2, K = 5) is performed.
(volume) code. Upon detecting an incorrect packet CRC at 102, the transmitter may:
Send parity bit in retransmission. The receiver combines the received data between multiple packets with a Viterbi decoder to improve the overall performance of the receiver. FIG.
A shows a flow diagram of a representative scheme.

In the example of FIG. 12A, the original data bits and the corresponding CRC bits are encoded (eg, using convolutional coding) at 120 and are generated by the original data bits and the corresponding CRC bits + encoding algorithm. Generate an encoded result that includes encoded parity bits (redundant overhead bits). After the encoding operation at 120, at 121 only the original data bits and the corresponding CRC bits are first transmitted. If the CRC is not correctly checked at the receiver, 122
Requires retransmission. In response to the retransmission request, the parity bits associated with the previously transmitted data bits are transmitted at 123. At the receiver, the received parity bits are mapped into the corresponding data and CRC bits at 125 using conventional techniques. If the CRC of the data bits generated at 125 is correct at 124, these data bits are then sent to a higher layer.
If the CRC is not checked as correct at 124, the received parity bits are combined with the associated data bits + CRC bits (previously received at 121) and undergo Viterbi decoding at 126. Thereafter, at 127, if the data bits generated by the Viterbi decoding algorithm and the corresponding CRC bits produce a correct CRC result, these decoding bits are sent to a higher layer. Otherwise, the data bits received at 121 are discarded and at 128 a retransmission of those data bits is required.

Next, at 129, the original data bits and the corresponding CRC bits are retransmitted, and if the CRC check is correct, the data bits are sent to a higher layer. Otherwise, the retransmitted data bits + CRC bits are combined with parity bits (previously received at 123) and undergo Viterbi decoding at 1200. If the data bits generated by the Viterbi decoding algorithm and the corresponding CRC bits at 1200 generate the correct CRC result at 1201, those data bits are sent to a higher layer. Otherwise, the parity bits transmitted at 123 are discarded and a retransmission of the parity bits is requested at 1202. Thereafter, the operations generally shown in the flow through 123 through 1202 of FIG. 12A may be repeated until the CRC for the data bits is checked as correct or a predetermined timeout occurs. .

FIG. 12B schematically illustrates relevant portions of an exemplary transceiver embodiment that may perform the receiver operations described above in connection with FIG. 12A. For example, incoming packet data, including the received version of the original data bits and the corresponding CRC bits, is buffered at 1204 and applied to a CRC decoder 1205. In response to the CRC decoding operation, the controller 1206 generates a negative acknowledgment (NAK) or an acknowledgment (ACK) in the form of an ARQ packet for transmission to the other side. If the CRC is checked for correctness (ACK), the controller 1206 notifies the buffer 1204 and sends the buffered data to a higher layer. On the other hand, if CR
If C is not checked for correctness (NAK), in response to the negative acknowledgment, the other side sends parity bits, which are input to controller 1206 and
04 is buffered. Controller 1206 maps the received parity bits into corresponding data bits and CRC bits. The result of this mapping is applied to CRC decoder 1205 and if CRC
Is correct, the data bits are 1207
, Is sent to a higher layer.

If the CRC resulting from the mapping is not checked to be correct, the controller 1206 notifies the Viterbi decoder 1203, loads the parity bits and data (including CRC) bits from the buffer, and performs Viterbi decoding. The data (including CRC) bit output obtained from the Viterbi decoder 1203 to 1208 is
It is input to the CRC decoder 1205. If the CRC of the Viterbi decoded data bits is checked as correct, the controller 1206 instructs the Viterbi decoder to send the Viterbi decoded data bits at 1209 to a higher layer. on the other hand,
If the CRC of the Viterbi decoded data bits
Is not checked as correct, the controller 1206
Outputs another negative acknowledgment, and the other side responds by retransmitting the original data (including CRC) bits (12 in FIG. 12A).
9), which overwrite previously received data (including CRC) bits in buffer 1204. If the CRC of these newly received data bits is not checked for correctness, then controller 1206 may control the newly received data (including CRC) bits and the previously received parity bits (still in buffer 1204). Is transmitted. If this Viterbi decoding is the correct CR
If C does not occur, controller 1206 can output another NAK, in response to which the parity bit is retransmitted and input to controller 1206 and buffer 120
4 can be overwritten on the previous parity bit.

FIG. 12C schematically illustrates relevant portions of a transceiver embodiment that can perform the transceiver operations shown in FIG. 12A. In FIG. 12C, an encoder 1210 (eg, a convolutional encoder) encodes uncoded data and stores the data (including CRC) bits and corresponding parity bits in a buffer 1213. The pointer 1217 driven by the counter 1211 points to the selected entry 1215 in the buffer 1213. Selected entry 12
The fifteen data (including CRC) and parity bits are applied to a selector 1214 controlled by a flip-flop 1212. The data (including CRC) bit of entry 1215 is selected as the first outgoing packet. If a negative acknowledgment (NAK) is received, flip-flop 1212 switches, thereby selecting the parity bit of entry 1215 as the next outgoing packet. In all additional negative acknowledgments received,
The data (including CRC) bit and parity bit of the entry 1215 are changed to 1214 by the flip-flop 1212 switching operation in response to the received negative acknowledgment.
Are alternately selected. When an acknowledgment (ACK) is received, flip-flop 1212 is cleared and counter 1211 is incremented, causing the pointer to move to connect another entry in buffer 1213 to selector 1214. select.
Of course, the counter 1211 may be incremented in response to a predetermined timeout condition.

The representative simulation results shown in FIG. 13 compare the throughput of Bluetooth (131) with the throughput of Mode 2 (132, 133). This simulation assumes that at each hopping frequency the single path is independent of Rayleigh fading. This is a good model of mode 2 as the exponentially decaying channel model specified in the above-mentioned reference document. The x axis is
The average E _b / of the channel over all hopping frequencies
N ₀ . In 16QAM (132), mode 2 achieves a throughput of 2.6x Bluetooth, and in 64QAM (133), mode 2 is:
Achieve 3.9x Bluetooth throughput. E
The _b N ₀ or other available channel quality information, a modulation scheme that provides the highest throughput may be selected.

FIG. 14A, FIG. 14D, and FIG.
9 shows typical system parameters in mode 3.
The symbol rate in these parameters is (IEEE8
Same as 02.11 (b)) 11Msymbol / sec
And the spreading parameter is 11 Mchip / sec in these examples. Figure 1
4B shows an example of further parameters, where the spreading parameter is 18 Mchip / sec and the symbol rate is 1
8 Msymbol / sec. The transmission spectrum mask in mode 3 can be the same as in IEEE 802.11 (b), as shown in FIG. At a symbol rate of 11 Msymbol / sec, this spectral mask allows a modest cost filter. This spectrum mask has, for example, ∀ = 0.
It can be realized by a 22 raised cosine filter. In one example, the master and the slave may start communicating in mode 1. If both devices agree to switch to mode 3, the probe, listen, and select (PLS) protocols for frequency band selection are invoked. In one exemplary embodiment, the protocol is
Allows selection (for mode 3 transmission) of the best contiguous 22 MHz band within the entire 79 MHz range. this is,
Provides frequency diversity gain. FIG. 16 shows representative simulation results of the packet error rate (PER) in an IEEE 802.15.3 exponential channel model specified for a delay spread of 25 ns in the aforementioned reference document. The result of this simulation (using uncoded QPSK) is the PLS according to the invention.
Are compared with the performance without PLS (162). The 25 ns delay spread provides 3 frequency diversity for PLS technology on the 79 MHz ISM band. This is P
This results in a performance gain of about 15 dB in LS.

A typical communication between transceivers using mode 1 and mode 3 may include the following steps:
Start transmission in mode 1 and use PLS to identify a good 22 MHz contiguous band; negotiate to enter mode 3; time T _{2 in} mode 3
After spending, returns to between mode 1 time T _1; master can communicate with any Bluetooth device during the time T ₁ in the mode 1; also, during the time T ₁ in the mode 1, good PLS may again be used to identify a continuous band of 22 MHz; the device will again negotiate to enter mode 3 now in a possibly different 22 MHz band (or the same band).

In the state transition diagram of FIG. 17, T ₁ = 25 ms
And an example where T ₂ = 225 ms is shown. These choices are 18 Mbps HDTV every 250 ms.
Allows transmission of six video frames of MPEG2 video. The master can communicate with some devices in mode 1 while communicating with other devices in mode 3, as shown in the exemplary WPAN of FIG.

FIG. 19A shows a representative timing diagram illustrating communication in mode 1 and mode 3.
The master and the slave have T ₂ = 22 in mode 3.
Communicate for 5 ms, while the remaining 25 ms is the best 2 for communicating with other slaves (eg, for 17.5 ms) and for the next transmission in mode 3.
Determine 2 MHz transmission (eg, during 7.5 ms)
Used for PLS. The time used for _PLS is also referred to herein as _TPLS .

FIG. 19B schematically illustrates an exemplary embodiment of a wireless communication transceiver according to the present invention. The transceiver of FIG. 19B supports mode 1 and mode 3 operation. The mode controller 195 provides a control signal 196 that controls the transition between mode 1 and mode 3 operation by selecting between a mode 1 transceiver (XCVR) section 197 and a mode 3 transceiver section 198. appear. The mode controller 195 communicates at 192 with the mode 1 transceiver section 197 and at 193 with the mode 3 transceiver section 198.

Since the Bluetooth (mode 1) transceiver 197 can hop at a maximum rate of 3200 hop / sec (each hop is on a 1 MHz band), this rate can be used for channel sounding. This means that the duration of each slot (from master to slave or from slave to master) is 312.5 microseconds. In some embodiments, a pseudo-random hopping pattern is used. The pattern is chosen such that the entire 79 MHz range is sampled at a sufficient rate (eg, in 5 MHz steps) to identify the best 22 MHz frequency band. By using this hopping pattern, the master can send short packets, also referred to herein as probe packets, in the format shown in FIG. 20, to the slave in mode 1 (Bluetooth). Note that the exemplary probe packet of FIG. 20 is the same as the Bluetooth ID packet. The slave estimates the channel quality based on, for example, the correlation of the access code (eg, Bluetooth synchronization word) of the received probe packet. It should be noted that special or dedicated probe packets are not necessary since the channel quality can also be estimated based on normal mode 1 traffic packets.

Referring to the example of FIG. 21A, after 16 probe packets (each period is 312.5 microseconds including turnaround time), the slave
Best continuous 22 MHz to use in mode 3
A decision is made on the band, and then the index of the lowest frequency of that band is sent to the master eight times using eight slots (each period being 312.5 microseconds). This index is a number from 1 to 57 (79 (ISM
Bandwidth of the band) −22 (bandwidth in mode 3) = 57)
And therefore requires a maximum of 6 bits. These six bits are repeated three times, so that each slave-to-master packet (FIG. 22), here also referred to as a select packet, totals 18 bits. This leaves 226 microseconds of turnaround time. The number n of packets from the master to the slave (eg, 16 in FIG. 21A) and the number k of packets from the slave to the master (eg, 8 in FIG. 21A) can be defined by the PLS protocol;
Or may be agreed during the initial handshake between master and slave. Also, the slave can send a probe packet to the master, so that the master can evaluate the channel from slave to master.

The channel condition of each 1 MHz band can be estimated, for example, by using the access code of the probe packet or the maximum value of the correlation of any known part. This gives a good estimate of the fading parameter amplitude in the 1 MHz channel. This information can then be used to select the best 22 MHz band.
For example, in each successive 22 MHz frequency band, if the j-th frequency band is represented by f (j), the quality parameter q _{f (j)} can be calculated as follows.

[0028]

(Equation 1) Where | α _i | is the magnitude of the fading parameter amplitude estimation (eg, correlation value) for the i-th frequency hop at f (j).

The maximum q _{f (j)} the frequency band f with (j)
Is adopted as the best band. As another example, the quality parameter qf _(j) may be calculated as follows in each successive 22 MHz band.

[0030]

[Number 2] _{q f (j) = min |} α i | Then, band f with the largest q _{f (j) (j)} is selected as the best band. As another example, the following quality parameters may be calculated for each successive 22 MHz band.

[0031]

(Equation 3)

The ratio A _{f (j) which is} larger than a predetermined threshold value
/ B results in f _(j), associated A _{f (j)} and B frequencies with a _{f (j)} band f (j) can be identified, the maximum q
_{One of the} identified frequency bands with _{f (j)} is taken as the best band. The threshold value can be determined empirically, for example, based on experiments on desired performance in expected channel conditions.

Consider the example of a PLS where n = 16 and k = 8. This indicates that the 79 MHz band should be sampled in 5 MHz steps. Therefore, the hopping pattern is given as follows.

[0034]

## EQU4 ## o = {0, 5, 10, 15, 20, 25, 3
0,35,40,45,50,55,60,65,7
0,75｝

The i-th PLS frequency hop is defined as follows: f (i) = (x + o (i)) mod (7
9); i = 1, 2,. . . , 16. Where x is PL
The index of the Bluetooth hopping frequency that occurs at the beginning of the S procedure, where x = 0,1,
2,. . . , 78. The index i is
It can be taken sequentially from the following pseudo-random sequence:

[0036]

P = {16,4,10,8,14,12,6
1,13,7,9,11,15,5,2,3｝ For different values of n and k, different pseudo-random sequences can be defined.

The eight transmissions from the slave to the master are performed, for example, in the first eight frequencies of the sequence f (i), ie, i = 0, 1, 2,. . . , 8, the frequency of f (i) can be used. The exemplary procedure described above can be summarized as follows. 1. The master sends a probe packet to the slave at the frequency determined by sequence f (i). The transmission frequency is given by (2402 + f (i)) MHz. 2. The slave estimates the quality of each channel. 3. After 16 probe packets from the master to the slave, the slave uses all the quality information it has accumulated to estimate the best 22 MHz band. 4. The slave sends a selection packet containing the index of the lowest frequency of the best 22 MHz band to the master. 5. The slave repeats step 4 a total of eight times. 6. Transmission starts in mode 3 using the selected 22 MHz band.

FIG. 23 shows IEEE 802.1 with exponential fading for 25 ns delay spread.
The results of an example PLS procedure applied to 5.3 channels are shown, where 79 MHz channels are sampled at 5 MHz intervals. As shown, a 5 MHz interval may identify a good 22 MHz contiguous band within the 79 MHz bandwidth. The 1, 5, 22, and 79 MHz parameters described above are, of course, only representative, and other values may be used as desired. As one example, the system may transmit data occupying all channels, hopping over channels of different bandwidths (eg, 22 MHz channels) rather than hopping over 1 MHz channels.

FIG. 21B schematically shows relevant portions of an exemplary embodiment of the mode controller of FIG. 19A. The embodiment of FIG. 21B includes a probe and selection controller 211 that outputs information indicating the frequency at which to transmit the probe and selection packets to the mode 1 transceiver section 197 and also controls the PLS operation described above. Depending on whether the probe or selection part is being performed,
Probe and select packets may also be provided to the mode 1 transceiver section 197. Band quality determiner 212 receives the conventionally available correlation values from mode 1 transceiver section 197,
Bandwidth information is then determined, and that information is provided to band selector 213 at 215. Band quality information 2
15 may include, for example, any of the quality parameters described above. Band selector 213 operates in response to quality information 215 and can select a preferred frequency band for mode 3 communication. For example, band selector 213 may use any of the band selection criteria described above. Band selector 21
3 determines, at 216, the index of the lowest frequency of the preferred frequency band in the probe and selection controller 21;
Output to 1. The probe and selection control device 211
Including the index received in the select packet that the device supplies to the mode 1 transceiver section 197, P
It is used for transmission to other transceivers involved in LS operation.

The mode controller of FIG. 21B also includes a frequency band mapper 214, which receives selected packets from other transceivers involved in PLS operation. The frequency band mapper extracts an index from the selected packet, and determines a selected 22 MHz frequency band from the index. The information indicating the selected frequency band is stored in the frequency band mapper 2
From 14 is output to the mode 3 transceiver section 198, after which mode 3 communication can begin.

FIG. 21C is a cross-sectional view of FIGS. 19B and 21B.
Fig. 3 shows representative operations that can be performed by a transceiver. 221
In the above, the aforementioned parameters n, k, T₁, T_Two, And
And T _PLSBut, for example, during the initial handshaking
Is determined. At 222, the transceiver determines that₁−
T_PLSOperates in mode 1 during the period. Then 223
In, the available bandwidth (band width)
BW), the n probe frequencies in
At each probe frequency.
Is sent. In 225, the probe packet
Is received and the corresponding frequency channel quality information (eg,
(The maximum correlation value). At 226, the frequency
Bandwidth quality information is generated using channel quality information
The band quality information is transmitted in mode 227 in mode 3 communication.
Used to select the preferred frequency band for
You. At 228, k selected packets are replaced with k
Each selected packet transmitted on a different frequency
Displays the selected frequency band. At 229
Means that mode 3 communication uses the selected frequency band and
Interval T_TwoDone during Period T_TwoAfter finishing, 222
Mode 1 communication is resumed and the above operation is repeated.
You.

FIG. 14C schematically illustrates relevant portions of another exemplary embodiment of the mode controller of FIG. 19B. FIG. 14C
In one embodiment, the modulation and coding mapper 14
1 is a band selector 213 (see FIG. 21B) to 142
Receiving band quality information associated with the 22 MHz band selected during the PLS procedure. Modulation and coding mapper 141 may convert the band quality information into any of the typical modulation and channel coding combinations shown in, for example, 1-22 in FIGS. 14A, 14B, 14D, and 14E. Map up. The mapper 141 provides, at 143, information indicating the selected modulation and channel coding combination to the mode 3 transceiver section 198. The mapping operation may be determined to maximize system throughput, for example, given band quality information for a selected band. In one exemplary embodiment, experimental simulation information similar to that shown in FIG. 13 above, eg, throughput versus bandwidth quality at different modulation schemes and at different coding rates, is selected by mapper 141. Can be used to select a combination of modulation scheme and coding rate that gives the highest throughput at a given bandwidth quality information for a given band.

Referring again to FIGS. 17 and 19A,
From the master to the slave, and conversely, in the time slot T ₂ assigned to the mode 3 (e.g. 225 ms), some packets may be sent. As shown in FIG. 24A, for example, a nominal packet size of 200 microseconds may be used. The master and slave may during their initial handshake, for example, agree that a certain number of packets should be sent in each direction. They may also agree (during the handshake) on the modulation scheme to be used in each direction.

In the example of one-way communication, if A
RQ (automatic retransmission request automatic repeater
If (t request) is used, the transmitting device may transmit, for example, a predetermined number of normal packets (also referred to herein as superpackets). The number of regular packets in the superpacket can be agreed upon at the time of initial handshaking. After receiving the predetermined number of regular packets, the coding device may send a short ARQ packet, for example, half the length of the regular packet. A guard interval (eg, 100 microseconds) may be placed before and after this ARQ packet. This ARQ packet serves as an acknowledgment of receipt of the normal packet. Packets that have not been checked for a correct CRC are indicated in the ARQ packet. In that case, the transmitter may send the requested packet again in a further superpacket. This procedure can be repeated until all packets have been exhausted or a timeout has occurred. FIG. 24A
Is representative in the case of one-way communication with or without ARQ from master to slave (explicitly shown) or from slave (not explicitly shown) to master Indicates the slot format.

As shown in the example of FIG. 24B, bi-directional mode 3 communication from master to slave and from slave to master can be handled in a similar manner. ARQ
And retransmission is optional. The retransmission is performed by an interfering device (such as a Bluetooth device).
Mode 3 performance in the presence of r) may be improved. Referring to FIG. 24A for one-way transmission with ARQ, an exemplary retransmission technique (shown in FIG. 24C) is as follows.

At 1.2401, the master sends to the slave a 100 with a CRC at the end of each packet.
Send a superpacket containing packets. 2. The slave uses the CRC to determine whether the packet was received without errors. 3. The slave transmits an ARQ packet having a 100-bit payload to the master (243 in FIG. 24C).
0, 2431). Each bit is a 1 if the packet was received without error, and a 0 if the packet was received with an error. CRC
Is added to the end of the ARQ packet. 4. If the master correctly receives the ARQ packet at 2404, the master retransmits the requested packet (if any) to the slave (24 in FIG. 24C).
05). If the master, at 2404,
If the Q packet is not received correctly, (a) the master sends a 100 μsec A
Send an RQ packet (see 2410 in FIG. 24C);
Find the ARQ packet of the slave. (B) The master then determines 2404 the slave A
Listen for RQ packets. (C) In 2404, the master (24 in FIG. 24C)
Receive the slave's ARQ packet (sent at 20) and resend at 2405 the requested packet, if any (see 2408), or 240
In 6 to T ₂ time slot is completed mode 1 communication is started, step (a) and (b) is repeated by the master. 5. Steps 2 through 4 until all packets are received correctly by the slave (see 2408), or until T ₂ time slots is completed, it is repeated. 6. If no T ₂ time slot is completed in Step 4 or Step 5 (see 2409), the master to the slave, and transmits a new packet.

[0047] If master, before the T ₂ time slots is completed, After completion send all of its packets, the master may communicate with other Bluetooth devices in a mode 1. For example, if MPEG2 at a rate of 18 Mbps is transmitting, six frames (250 ms of video) require 204.5 ms at a rate of 22 Mbps. If T ₁ + T ₂ = 250 ms and 10 m
If s is used for a retransmission request, and if 7.5 ms is used for PLS, this will force the master to use mode 1 Bluetooth communication for 28 ms.
Let it stay.

Retransmission in two-way communication (see FIG. 24B) can be performed in the same manner as the one-way communication described above. The ARQ request of the slave device may be piggybacked on the slave data packet, or an independent ARQ packet may be used.

FIG. 24D schematically illustrates relevant portions of an exemplary embodiment of a mode 3 transceiver that can implement the exemplary retransmission technique described above and shown in FIG. 24C.
In FIG. 24D, the input super packet data is C
Applied to RC decoder 242, which performs a CRC check on each packet of the superpacket. For a given packet, CRC decoder 242 may provide a bit, eg, a bit value of 1 if the packet's CRC is checked for correctness, and a bit value if the packet's CRC is not checked for correctness.
A bit value of 0 can be shifted into register 243. In this way, register 243 is loaded with the bit value for each packet of the superpacket.
The bit values contained in register 243 are input to logic 244, which determines the C of each received packet.
Determine if the RC has been checked as correct. If so, the logic output 248
Informs the buffer 241 loaded with the incoming superpacket data that the superpacket data may be sent to a higher layer. On the other hand, if logic 244
Determines that the CRC of one or more received packets was not checked as being correct, outputs logic 2
48 informs the buffer 241 to hold the super packet data.

The contents of register 243 are also provided to ARQ generator 245, which uses the contents of the register to fill the payload of the outgoing ARQ packet. When superpackets, including retransmitted packets, are received, those retransmitted packets are buffered into their appropriate superpacket locations in buffer 241 and CRC decoder 242 transmits For this purpose, a CRC check is performed, and the result of the CRC is supplied to the register 243.

The ARQ receiver 246 receives the incoming ARQ packet and, in response, prompts the ARQ generator 245 to send the appropriate ARQ packet, or to send the previously buffered (see 247) outgoing superpacket. Select the requested packet and retransmit it to the other side. Point-to-multipoint communication can be realized by time division multiplexing between a plurality of slaves. Prior to each time slot for each slave, there is a PLS slot between the master and the associated slave.

In one embodiment, each 200 μsec long packet in FIG. 24A includes a data bit (payload) and a 32-bit long CRC. This CRC is, for example, a polynomial D ³² + D ²⁶ + D <sup>23
+ D 22 + D 16 + D</sup> 12 + D 11 + D 10 + D 8 + D 7 + D 5 + D 4
This is a 32-bit sequence generated by using + D ² +1. This exemplary packet format is shown in FIG. 25A.

FIG. 25B shows a representative ARQ packet format according to the present invention. The ARQ packet format of FIG. 25B is generally similar to the packet format shown in FIG. 25A and includes the training sequence of FIG. The payload of the packet of FIG. 25B is protected by a repetition code. The size of the packet in FIG. 25B can be specified in its header, or the number of packets in the superpacket transmitted by the master multiplied by the repetition code rate, the number of CRC bits, and the number of training bits; Can be determined by the master based on the

A number of packets in FIG. 24A, whose numbers can be agreed upon during the initial handshake, are preceded by a training sequence for timing, automatic gain control, and capture of packet timing. Generally, 10
The training sequence precedes the packets. FIG.
Indicates a representative format of the training sequence. FIG.
7, includes a training sequence (see also FIG. 26) and CRC, schematically showing a part of a typical slot format of the above period T ₂ in mode 3.

The preamble of the training sequence shown in FIG. 26 has a pattern (1 + j) * [1, -1,1, -1,1,1,
-1,1, -1,1, -1, -1,1, -1,1, -1,1,1,
−1, 1, −1, 1, −1, 1, −1], which aids in the initial symbol timing acquisition by the receiver. The preamble in the example of FIG. 26 is followed by a 64-bit Bluetooth synchronization word transmitted using quadrature phase shift keying (QPSK), meaning 32 symbol transmission in mode 3. This sync word contains QPS
Followed by a header transmitted using K modulation. For the transmission of preamble, sync word and header, 16
The furthest constellation in QAM is used (see FIG. 6A). Still referring to FIG. 27, the header is followed by a payload such that the total time occupied by the packet is 200 microseconds. This payload is followed by a 32-bit CRC.

The above slot and packet formats are merely representative; for example, the packet length can be set to any desired length, and different sized polynomials may be used for the CRC. It should be understood that different sizes of training sequences can be used for the preamble, and the synchronization word and header can be of the desired size. It should also be understood that the slot and packet formats described above can be readily applied to two-way communication.

The above typical slot and packet formats are, for example, HDT at 18 Mbps.
Enables transmission of V MPEG2 video. For example, 2
Assume that 4 frames / sec are transmitted in MPEG2 video. That is, the master sends 100 packets, each carrying 200 μsec in length, carrying a 2184 symbol data payload to the slave. For example, assuming that 10 such packets are preceded by a training sequence of 81 symbols (FIG. 26) and that 16QAM with rate 1/2 coding is used, the transmission of 6 video frames would be 2
06.8 msec is required. Assuming an ARQ rate of 9% means that the total time required for 6 video frames is 225 msec.
FIG. 28 summarizes representative transmission parameters for transmitting HDTV MPEG2 video using mode 3.

The receiver algorithm for acquisition and packet reception in mode 3 is the same as in mode 2. FIG. 29 shows a representative block diagram of the mode 3 receiver algorithm. FIG. 30 schematically illustrates an exemplary receiver embodiment for mode 3. The demodulator of FIG. 30, shown generally at 301,
Channel estimation, equalization, and symbol-to-bit mapping may be performed.

FIG. 31 shows a representative transmitter for mode 3. The respective D / A converters 310 for the I and Q channels are, for example, 6 bits 44 MH
z. The transmitter and receiver of FIGS. 31 and 30 together can be used to form the exemplary mode 3 transceiver of FIG. 19B described above.

In one exemplary embodiment, FIG.
As shown in FIG. 32B and FIG.
K, 16QAM, and 8PSK (8 phase shift keying)
Can be used in mode 3. Referring to the example of QPSK in FIG. 32A, IEEE
A representative cover sequence S as used in 802.11 has been used to spread the transmitted symbols. FIG. 32A shows a bit-to-symbol mapping. Referring to the example of 8PSK in FIG. 32B,
A cover sequence S as used in IEEE 802.11 has been used to spread the transmitted symbols. FIG. 32B shows a bit-to-symbol mapping. Referring to the example of 16QAM in FIG. 33, a cover sequence (also referred to herein as a scrambling code) S as used in IEEE 802.11 is used to spread transmitted symbols. FIG. 33 shows a bit-to-symbol mapping. In the examples of FIGS. 32A and 33, S
_i represents the i-th member of the sequence S, which is 1 or 0. In some embodiments, no cover sequence is used, in which case the constellation associated with any value of S may be used.

The exponentially delayed Rayleigh channel shown in FIG. 34 is representative of the expected operating environment and can therefore be used to test performance. The complex amplitude of the impulse response of the channel in FIG. 34 is given by the following equation.

[0062]

(Equation 6)

This channel model requires equalization (at the output of the filter 305 of FIG. 30), which can be done in a variety of ways, two conventional examples of which are related to FIGS. 35 and 36. This will be described below. FIG.
FIG. 5 shows a section of a typical MMSE (Least Mean Square Error) equalizer. Equalizer section is MM
It includes an SE equalizer, followed by a DFE (decision feedback equalizer). The MMSE uses the least mean square error criterion and channel estimates to make a decision on all symbols by 35
Occurs at 0. The DFE subtracts all channel decisions obtained by the MMSE from the input signal and then 351
Then, a matched filter soft decision is generated for all symbols. These are then fed to a soft decision block, which generates, at 352, a bit level soft decision. These bit-level soft decisions are then provided to a turbo decoder 307 (see FIG. 30) or, in the case of an uncoded system, to a threshold device.

The exemplary MAP equalizer section of FIG. 36, given the received signal and channel estimates,
Maximize the aposteriori probability of transmitted symbols.
These symbol probabilities 360 are then converted 361 to bit probabilities by addition over the symbols. These bit probabilities 362 are then input to a turbo decoder or threshold device.

Video transmission generally requires a BER of 10 ⁻⁸ , and turbo coding is used to achieve this error rate. Parallel convolutional code (paraal
ll concatenated convolut
It is known that the ion code PCCC has an error floor of about 10 ^-7 , but a serial concatenated convolutional code (serial code).
ncatenatedconvolution cod
es SCCC) has no error floor and can satisfy BER requirements. The SCCC in FIG. 37 is conventional and was first published by Divsalar and Polarara at the International Symposium on Turbo Codes and Applications in Brest, France, September 1997, Proceedings Int.
electronic Symposium of T
urbo Codes and Applicatio
ns), pp. 80-87, "Serial and Hybrid Connected Codes and Their Applications (Serial
and Hybrid Concatenated
Codes with Application), which is hereby incorporated by reference.
The contents will be incorporated into the present application.

FIGS. 38 to 44 show typical results of the Monte Carlo simulation for mode 3. FIG. In all simulations, 409
A frame size with six information bits was used. FIGS. 38 and 39 show FER and BER in the AWGN channel. FIG. 40 and FIG. 41 show FER and BER in an IEEE 802.15.3 multipath channel without fading. FIGS. 42 and 43 show IEEE 802.1 with fading.
5.3 shows FER and BER in a multipath channel. FIG. 44 shows FER in a single-path Rayleigh fading channel.

Due to typical transceiver size constraints, a single antenna is desirable for transmission and reception according to the present invention. However, it is also possible to use two antennas for transmit and receive diversity.
Simple schemes such as switch diversity can be easily incorporated into the transceiver device provided by the present invention, while still being transparent to other devices (eg, in a Bluetooth piconet). The modulation technique described above uses space-time coding (space
It is also applicable to more complex transmit diversity, such as time coding, beamforming, and so on.

The above-described modulation scheme of the present invention also provides a parallel concatenated trellis coded modulation.
catenated trellis coded m
Odulation PCTCM) and serially concatenated trellis coded modulation
native trellis coded modul
It allows for more complex coding schemes, such as SCTCM. Also, lower complexity trellis codes (which may perform better than the turbo coding of FIG. 37) can be easily incorporated into transceiver devices according to the present invention.

As mentioned above, FIG. 10 (receiver) and FIG. 11 (transmitter) show a representative transceiver in mode 2. Many components of the mode 2 receiver, such as the front end filter 105, LNA 106, RF / IF converter 107, and SAW filter 108, can be shared with mode 1. The baseband of the mode 2 receiver is filtering, AGC, timing acquisition, channel estimation, Q
Requires additional logic (beyond mode 1) to accept AM demodulation and Viterbi decoding in the case of ARQ. In one embodiment, the number of special gates for this additional logic is about 10,000
Become a gate.

As described above, FIG. 30 (receiver) and FIG. 31 (transmitter) show a representative transceiver in mode 3. Many components of the mode 3 receiver, such as front end filter 308, LNA 306, and RF / IF
Converter 302 may be shared with mode 1. Mode 1+
Mode 3 implementations require additional SAW filters beyond mode 1 implementations because the bandwidth of mode 3 is greater than mode 1. The baseband of a mode 3 receiver requires additional logic (beyond mode 1) for AGC, timing acquisition, channel estimation, QAM demodulation, equalization, and turbo decoding. In one embodiment, the number of special gates for this additional logic is about one.
It becomes 00,000 gates.

It will be apparent to those skilled in the art that embodiments of the exemplary transceiver according to the present invention may be implemented, for example, in a conventional Bluetooth MAC by making appropriate hardware and / or software modifications. . The above-mentioned, representative advantages provided by the present invention are listed below.

Interoperability with Bluetooth
T : The high-speed WPAN piconet according to the present invention can accommodate several mode 1 (Bluetooth) and mode 2 or mode 3 devices simultaneously. High throughput : In mode 3, the high speed WPAN according to the invention supports 6 simultaneous connections, each with a data rate of 20 Mbps, giving a total throughput of 6 × 20 = 120 Mbps over the 2.4 GHz ISM band. . In mode 2, the high speed WPAN supports the same number of connections as Bluetooth, each having a data rate of up to 4 Mbps. Co - existence : Bluetooth throughput around a typical WPAN according to the present invention is reduced by only 10%. The PLS technology means that the reduction in the throughput of IEEE 802.11 near the WPAN according to the present invention is 0%. This is because PLS selects different frequency bands. Resistance to jamming : PLS technology helps avoid jamming from microwave, Bluetooth, and IEEE 802.11, so PLS technology is robust to jamming. Low sensitivity level : typical sensitivity level in mode 2 is -78 dBm, and in mode 3 -69 d
Bm. Low power consumption : the estimated power consumption of mode 2 in 2001 is 25 mW on average for reception and 15 mW on transmission, and the estimated power consumption of mode 3 in 2001 is 95 mW on reception and 60 mW on transmission. . In the above, the representative examples of the present invention have been described in detail.
This does not limit the scope of the invention, which may be embodied by various embodiments.

This application is a pending US patent provisional application of the same time:
35U. S. C. Claiming priority under 119 (e) (1): Provisional Application No. 60/2, June 9, 2000
No. 10,851; Provisional Application No. 60, Jul. 5, 2000
Nos./215,953; provisional applications 60 / 216,290 and 60 / 216,436, filed July 6, 2000;
No. 60 / 216,291, No. 60 / 216,292
Nos. 60 / 216,413 and 60/21
No. 6,433; Provisional Application No. 60, Jul. 11, 2000
Nos./217,269, 60 / 217,272, and 60 / 217,277; Provisional Application No. 60 / 228,860, filed Aug. 29, 2000. All of the above provisional applications are hereby incorporated herein by reference. This application is related to the following contemporaneous applications filed concurrently with this application: the specification numbers are TI-31284 and TI-31285, each titled "Wireless Communications Using Efficient Channel Coding ( Wir
eless Communications with
Efficient Channel Codin
g) "and" Wireless communication using frequency band selection (Wi
releaseCommunications with
Frequency Band Selection
n) ".

[Brief description of the drawings]

FIG. 1 shows representative parameters of a WPAN according to the invention in table form.

FIG. 2 schematically shows a representative configuration of a WPAN transceiver device according to the present invention.

FIG. 3 shows, in tabular form, exemplary parameters associated with first and second modes of operation of a WPAN transceiver according to the present invention.

FIG. 4 shows, in table form, a transmit spectrum mask associated with the mode of operation shown in FIG. 3;

5 is a state transition diagram illustrating exemplary transitions of the transceiver device between the operating modes shown in FIG.

FIG. 6A schematically illustrates an exemplary frame format in Mode 2 transmission according to the present invention, and B is a representative 16QAM constellation that may be used in Mode 2 selected symbol transmission in accordance with the present invention. Graphically display constellation points.

FIG. 7 schematically illustrates the operation of an exemplary WPAN according to the present invention.

FIG. 8 is an exemplary timing diagram for communication in the WPAN of FIG. 7;

FIG. 9 schematically illustrates an exemplary acquisition and packet reception algorithm in a mode 2 receiver according to the present invention.

FIG. 10 schematically illustrates an exemplary embodiment of a mode 2 receiver capable of performing the algorithm of FIG. 9;

FIG. 11 schematically illustrates an exemplary embodiment of a mode 2 transmitter according to the present invention.

FIG. 12A illustrates an exemplary transmit encoding operation and receive decoding operation according to the present invention.

FIG. 12B schematically illustrates relevant portions of an exemplary transceiver embodiment capable of performing the receiving operations shown in A.

FIG. 12C schematically illustrates relevant portions of an exemplary transceiver embodiment capable of performing the receive operations illustrated in A.

FIG. 13 shows a representative simulation result obtained using a conventional Bluetooth operation (131) and 16Q
A graphical comparison is made between representative simulation results obtained using the mode 2 operation of the present invention with AM (132) and 64QAM (133).

FIG. 14A operates in mode 3 according to the present invention;
Representative parameters associated with a WPAN transceiver are shown in table form.

FIG. 14B operates in mode 3 according to the invention;
Representative parameters associated with a WPAN transceiver are shown in table form.

FIG. 14C illustrates portions of an exemplary embodiment of the mode controller of B.

FIG. 14D operates in mode 3 according to the invention;
Representative parameters associated with a WPAN transceiver are shown in table form.

FIG. 14E operates in mode 3 according to the invention;
Representative parameters associated with a WPAN transceiver are shown in table form.

FIG. 15 shows, in table form, a transmit spectrum mask that may be used by a mode 3 transceiver according to the present invention.

FIG. 16 graphically compares the mode 3 performance with PLS according to the invention and the mode 3 performance without PLS according to the invention.

FIG. 17 shows mode 1 of the transceiver device according to the present invention.
FIG. 9 is a state transition diagram showing a representative transition between the mode and a mode 3;

FIG. 18 schematically illustrates the operation of an exemplary WPAN according to the present invention.

FIG. 19A shows the representative state transition of FIG.
FIG. 4 is a timing chart showing typical operations that can be performed in the state, and FIG.
1 schematically illustrates an exemplary embodiment of a transceiver that supports.

FIG. 20 schematically illustrates an exemplary format of a probe packet according to the present invention.

FIG. 21A shows an example of the PLS portion of FIG. 19A in detail.

FIG. 21B schematically illustrates relevant portions of an exemplary embodiment of the mode controller of FIG. 19B.

FIG. 21C illustrates exemplary operations that may be performed by the mode controller of FIGS. 19B and 21B.

FIG. 22 schematically illustrates an exemplary format of a selected packet according to the present invention.

FIG. 23 graphically illustrates the results of a representative PLS sampling obtained according to the present invention.

FIG. 24A schematically illustrates an exemplary time slot format in mode 3 communication according to the present invention.

FIG. 24B schematically illustrates an exemplary time slot format in mode 3 communication according to the present invention.

FIG. 24C shows an exemplary operation of the retransmission technique according to the present invention.

FIG. 24D illustrates relevant portions of an exemplary transceiver embodiment that may perform the operations illustrated in C.

FIG. 25A shows an exemplary packet format used with the time slot format of FIG. 24A, and B shows an exemplary ARQ packet format according to the present invention.

FIG. 26 schematically illustrates an exemplary format of a training sequence that may be used with the packet format of FIG. 25A.

FIG. 27 shows details of the slot format part of FIG. 24A.

FIG. 28 shows, in table form, exemplary transmission parameters that may be used for video transmission using mode 3 according to the present invention.

FIG. 29 schematically illustrates an exemplary capture and packet reception algorithm in mode 3 operation according to the present invention.

FIG. 30 schematically illustrates an exemplary embodiment of a mode 3 receiver according to the present invention, capable of performing the algorithm of FIG. 29.

FIG. 31 schematically illustrates an exemplary embodiment of a mode 3 transmitter according to the present invention.

FIGS. 32A and 32B schematically illustrate exemplary bit-to-symbol mappings that may be used in mode 3 operation.

FIG. 33 schematically illustrates another exemplary bit-to-symbol mapping that may be used in mode 3 operation.

FIG. 34 graphically illustrates a typical channel impulse response encountered by a transceiver according to the present invention.

FIG. 35 schematically illustrates an exemplary embodiment of an equalizer section that may be used to perform the equalization of the channel model of FIG. 34.

FIG. 36 schematically illustrates another exemplary equalizer section that may be used to equalize the channel model of FIG. 34.

FIG. 37 schematically illustrates an exemplary turbocoder used with mode 3 operation according to the present invention.

FIG. 38 graphically illustrates the results of an exemplary simulation for mode 3 operation in a communication channel.

FIG. 39 graphically illustrates the results of an exemplary simulation for mode 3 operation in a communication channel.

FIG. 40 graphically illustrates the results of an exemplary simulation for mode 3 operation in a communication channel.

FIG. 41 graphically illustrates the results of an exemplary simulation for mode 3 operation in a communication channel.

FIG. 42 graphically illustrates the results of an exemplary simulation for mode 3 operation in a communication channel.

FIG. 43 graphically illustrates the results of an exemplary simulation for mode 3 operation in a communication channel.

FIG. 44 graphically illustrates the results of an exemplary simulation for mode 3 operation in a communication channel.

[Explanation of symbols]

 1203 Viterbi decoder 1206 Controller 1210 Encoder 1213 Buffer 1214 Selector

 ──────────────────────────────────────────────────の Continued on the front page (72) Inventor Mohammed Nafi United States Texas, Richardson, Buckingham Road 530, Apartment 121 (72) Inventor Anand Ge, Davak United States Texas, Plano, Kendall Drive 8625 F-term (reference 5K004 AA01 AA08 BA02 JA02 JB01 5K014 AA01 FA03 GA01 HA06 5K022 EE04 EE22 EE31 5K033 CB04 CC01 DA17

Claims (18)

[Claims] 1. A method of performing wireless packet communication between wireless packet communication transceivers, the method comprising: a first wireless packet communication transceiver transmitting a super packet including a plurality of packets to a second wireless packet communication via a wireless communication link;
Transmitting to a wireless packet communication transceiver, wherein the second transceiver is responsive to the transmission of the superpacket via the wireless communication link, a plurality of bits each corresponding to the packet of the superpacket; Transmitting an acknowledgment packet having a payload comprising the plurality of bits to the first transceiver, the bit value indicating whether retransmission of the respective corresponding packet is required. Method. 2. The method of claim 1, wherein the first transceiver determines from the payload of the acknowledgment packet whether any packets of the superpacket are to be retransmitted, and wherein the first transceiver determines from the acknowledgment packet The method of claim 1, comprising retransmitting a packet determined to require retransmission in another superpacket. 3. In response to the transmission of the another super packet, the second transceiver transmits a plurality of bits over the wireless communication link, each bit corresponding to the packet of the another super packet. Transmitting another acknowledgment packet having a payload comprising the plurality of bits to the first transceiver, wherein a bit value indicates whether retransmission of the respective corresponding packet is required. 3. The method according to 2. 4. The method of claim 1, further comprising the step of the second transceiver using an error detection procedure to detect whether retransmission of any of the superpackets is required. Or the method of claim 3. 5. The method of claim 4, wherein said using comprises using a cyclic redundancy code to determine whether retransmission of any of the superpackets is required. 6. If the first transceiver determines that the acknowledgment packet has not been correctly received and that a period for receiving the acknowledgment packet has not expired, The method of claim 1, comprising transmitting one packet requesting transmission of the acknowledgment packet by the second transceiver over the wireless communication link. 7. The step of the first transceiver transmitting the packet requesting transmission of the acknowledgment packet is repeated until one of the correct reception of the acknowledgment packet and the end of the feedback occurs. The method of claim 6, comprising a step. 8. The method according to claim 1, wherein the packet of the super packet includes one of audio information, video information, and computer graphics information. 9. The method according to claim 1, wherein the payload bits are repetitively coded in the acknowledgment packet. 10. A wireless packet communication device, comprising: an input for receiving a super packet including a plurality of packets from another wireless packet communication device via a wireless communication link; and an acknowledgment generator coupled to the input. In response to the superpacket, a plurality of bits each corresponding to the packet of the superpacket, the bit value of which indicates whether retransmission of the respective corresponding packet is required; Generating an acknowledgment packet having a payload including a plurality of bits, the acknowledgment generator; and an output coupled to the acknowledgment generator, outputting the acknowledgment packet and via the wireless communication link, And transmitting the output to another wireless packet communication device. 11. An error detector coupled to the input,
Determining whether any of the packets of the superpacket were not correctly received, wherein the error detector is coupled to the acknowledgment generator and to the acknowledgment generator, 11. The system of claim 10, further comprising providing information indicating the packet.
An apparatus according to claim 1. 12. A register coupled between the error detector and the acknowledgment notification, the register receiving the information from the error detector and supplying the information to the acknowledgment generator. An apparatus according to claim 10 or claim 11. 13. The apparatus of claim 12, wherein said acknowledgment generator inserts information received from said register into said payload of said acknowledgment packet. 14. The apparatus according to claim 10, wherein the packet of the super packet includes one of audio information, video information, and computer graphics information. 15. The apparatus according to claim 10, wherein the payload bits are repeatedly coded in the acknowledgment packet. 16. A wireless packet communication device, comprising: an output for providing a super packet including a plurality of packets for transmission over a wireless communication link to another wireless packet communication device; Through a plurality of bits each corresponding to the packet of the superpacket, the bit value of which indicates whether retransmission of the respective corresponding packet is required,
An input for receiving an acknowledgment packet having a payload comprising the plurality of bits, and an acknowledgment receiver coupled to the input, wherein in response to the payload of the acknowledgment packet, the The acknowledgment receiver selecting a packet to be retransmitted indicated by a payload from the previously transmitted superpacket. 17. The apparatus of claim 16, wherein the packet of the superpacket includes one of audio information, video information, and computer graphics information. 18. The apparatus of claim 16, wherein the payload bits are repetitively coded in the acknowledgment packet.