JP2001016286A - Receiver and communication unit - Google Patents

Abstract

PROBLEM TO BE SOLVED: To change an operating state so as to reduce the power consumption is response to, e.g. the presence/absence of a disturbing radio wave or the like. SOLUTION: In this receiver, an operating state of a low noise amplifier 21a, a mixer 23a, a receiver side variable amplifier circuit 26a, and a QPSK demodulation circuit 27a in a reception system circuit 2 is changed depending on communication factors including at least any of presence of a transmission operation, presence of a disturbing radio wave and a signal level of a received signal. In this case, the operating state of each section of the reception system circuit 2 is decided depending on contents of a circuit setting table 61 and a gain correction table 62. The contents of the circuit setting table 61 and the gain correction table 62 can be revised externally.

Description

DETAILED DESCRIPTION OF THE INVENTION

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention
The present invention relates to a receiving device and a communication device applied to a (Code Division Multiple Access) type mobile phone or the like.

[0002]

2. Description of the Related Art In recent years, there has been an increasing demand for portable telephones as communication equipment. At first, an analog type mobile phone was developed, but recently, a digital type research and development has also been conducted. Note that digital systems include, for example, TDMA (Time Division Multiple Acces).
s: time division multiple access) system and CDMA system.

FIG. 14 shows a circuit configuration example of a high-frequency stage of a general portable telephone. In the drawing, as an example of a configuration of a mobile phone, a mobile phone having a dual mode of a CDMA system and an FM system is shown. The mobile phone shown in this figure includes a transmission (TX) circuit 100T that performs signal processing on a transmission signal, a reception (RX) circuit 100R that performs signal processing on a reception signal, and a transmission circuit 10R.
A modem 101 to which a transmission signal to be processed is modulated with respect to 0T and to which the reception signal processed in the reception system circuit 100R is input, a duplexer 107 for separating the transmission signal and the reception signal, and a transmission. A common antenna 108 for radiating a signal radio wave to be received and receiving a signal radio wave from a base station (not shown) is provided.

The transmission system circuit 100T converts the baseband transmission signal output from the modem 101 into a QPSK (Quadr
re Phase Shift Keying: 4 phase shift)
QPSK modulation circuit 1 for outputting F (intermediate frequency) transmission signal
02, a transmission-side variable amplifier (TX-AGCAMP) 103 for amplifying the IF transmission signal, and an amplified IF
A mixer 104 that mixes a transmission signal with a local oscillation signal from a local oscillator 121 to convert the signal into an RF (high frequency) transmission signal and outputs the RF signal, and a bandpass filter 105 for removing unnecessary signal components included in the RF transmission signal. And a power amplifier (PA) 1 for amplifying the RF transmission signal output from the band-pass filter 105 and outputting the amplified signal to the duplexer 107
06.

[0005] The receiving circuit 100R includes a duplexer 10
, A low-noise amplifier (LNA) 109 for amplifying the RF reception signal input through the RF signal 7, a band-pass filter 110 for removing unnecessary signal components included in the RF reception signal, and a local oscillator 121 for transmitting the RF reception signal. A mixer 111 for converting the received IF signal into a CDMA signal component by mixing the IF signal with a local oscillation signal from the receiver, a CDMA bandpass filter 112 for converting the input IF received signal into a CDMA signal component, and an input IF signal. FM band-pass filter 113 for converting a received signal into a signal component for FM
And the selectively input CDMA reception signal and F
A reception side variable amplifier circuit (RX-AGCAMP) 114 for amplifying the M reception signal and a QPSK demodulation circuit 115 for QPSK demodulating the amplified reception signal are provided.

The modem 101 includes a received signal strength detection circuit (RSSI) 116 for detecting the strength (received strength) of an input received signal, and received strength and strength reference data D1.
01, and a comparison circuit 117 that outputs a signal indicating the difference, and a transmission output correction circuit 119 for controlling the gain of the transmission-side variable amplification circuit 103.

Next, the operation of the portable telephone having the above configuration will be described.

First, the operation at the time of transmission will be described. The baseband transmission signal modulated by the modem 101 is
First, the signal is input to the QPSK modulation circuit 102 of the transmission system circuit 100T. The QPSK modulation circuit 102 performs QPSK modulation on the baseband transmission signal, converts the baseband transmission signal into, for example, a 130 MHz IF transmission signal, and outputs the IF transmission signal to the transmission-side variable amplification circuit 103. Next, the transmission-side variable amplification circuit 103 amplifies the IF transmission signal and outputs the amplified signal to the mixer 104. Mixer 104
Mixes the amplified IF transmission signal with the local oscillation signal from the local oscillator 121, converts it to, for example, an 800 MHz RF transmission signal, and outputs the RF transmission signal to the bandpass filter 105. After removing unnecessary signal components included in the RF transmission signal, the bandpass filter 105 outputs the signal to the power amplifier 106. The power amplifier 106 amplifies the RF transmission signal from which the unnecessary signal component has been removed, and outputs the amplified RF transmission signal to the duplexer 107. The RF transmission signal output to the duplexer 107 is radiated from the shared antenna 108 into space.

Next, the operation at the time of reception will be described. The signal radio wave captured by the common antenna 108 is converted into an electric RF reception signal via the duplexer 107 and output to the low noise amplifier 109 of the reception circuit 100R. The low noise amplifier 109 receives the input R
Amplify the F reception signal with a fixed gain,
Output to 10 After removing unnecessary signal components included in the RF reception signal, the band-pass filter 110
11 is output. The mixer 111 mixes the RF reception signal with the local oscillation signal from the local oscillator 121, and
The signal is converted into an IF reception signal of 5 MHz, and the band-pass filter 112 for CDMA and the band-pass filter 113 for FM
And output to The CDMA band-pass filter 112 and the FM band-pass filter 113 convert the input IF reception signal into a CDMA signal component and an FM signal component, respectively. The CDMA reception signal and the FM reception signal converted by the CDMA band-pass filter 112 and the FM band-pass filter 113 have only one of the signal components according to the setting mode. It is selectively output to the variable amplifier circuit 114. The reception-side variable amplification circuit 114 amplifies the selectively input CDMA reception signal or FM reception signal and outputs the amplified signal to the QPSK demodulation circuit 115. QPSK demodulation circuit 115 performs QPSK demodulation on the amplified received signal and outputs the result to modem 101.

The received signal input into the modem 101 is
The received signal strength detection circuit 116 detects the received signal strength. A signal indicating the reception strength detected by the reception signal strength detection circuit 116 is output to the comparison circuit 117. The comparison circuit 117 compares the reception intensity with the separately input intensity reference data D101, and outputs a signal indicating the difference to the reception-side variable amplification circuit 114 via a reception-side AGC voltage correction circuit (not shown). Also, the comparison circuit 117
Is also output to the transmission output correction circuit 119. A receiving-side AGC voltage correction circuit (not shown)
The reception-side AGC voltage V _RX-AGC is set so that the difference from the comparison circuit 117 becomes “0”, that is, the output of the reception signal strength detection circuit 116 matches the strength reference data D101.
To control the gain of the variable amplifier circuit 114 on the receiving side.

[0011] The transmission output correction circuit 119 is adapted to transmit the variable variable amplifier circuit 10 based on the signal indicating the difference input from the comparison circuit 117 and the transmission output correction data D102.
3 is controlled. The transmission output correction data D10
Reference numeral 2 denotes data corresponding to the line status between the mobile phone and a base station (not shown). Also, the transmission output correction circuit 119
Is controlled so that the modulated signal is inversely proportional to the level of the received signal and the transmission output correction data D102
Variable amplifier circuit 10 on the transmission side so that control according to
3 by outputting the transmission side AGC voltage V _TX-AGC .

As described above, in the CDMA mobile phone, the gain of the variable amplifier circuit 114 on the receiving side and the gain of the variable amplifier circuit 103 on the transmitting side are controlled in accordance with the signal level of the received signal. As a result, the signal level of the received signal is reflected in the transmission power, and communication of 40 or more users assigned to one frequency band is maintained.

[0013]

Here, as described above, in the CDMA type portable telephone, the signal level of the received signal is reflected in the transmission power, so that more than 40 users assigned to one frequency band can be used. In order to maintain communication, the high frequency stage of the receiving circuit 100R includes another method, for example, T
It is necessary to use a circuit having better linearity (a circuit in which distortion is less likely to occur) as compared with the DMA method. That is, in order to reflect the signal level of the received signal on the transmission power, the transmission-side variable amplification circuit 103 and the reception-side variable amplification circuit 114
Need to be operated in conjunction with each other.
AGC voltages V _RX-AGC and V _TX-AGC input to each amplifier circuit over a dynamic range of 0 dB or more;
There must be a good linearity relationship between the gain in each amplifier circuit.

However, in the conventional circuit, as described below, there is a problem that the relationship of linearity in each of the above-described amplifier circuits and the like is broken due to the influence of the communication environment such as jamming radio waves.

FIG. 15 is a diagram for explaining what is called "intermodulation spurious interference" in the receiving circuit 100R. Generally, unnecessary and harmful frequency components in a high-frequency circuit are called spurious. For example, when two or more signals having different frequencies are input to a high-frequency amplifier, intermodulation occurs between the input signals, and a spurious signal is generated at the output of the amplifier.

For example, as shown in FIG. 1, when a signal of a plurality of channels each having a signal band of W _RX (for example, 1.23 MHz) is received as the reception signal S _RX in the reception system circuit 100R, Two interfering signals 201,
It is assumed that 202 exists. In the illustrated example, the two interfering signals 201 and 202 are separated from the center frequency of one received signal S _RX by 900 kHz and 1700 kHz, respectively. Such two interference signals 201, 20
2 there are two spurious signals 2 on each side of each jamming signal due to the intermodulation of the two jamming signals 201 and 202.
03 and 204 occur. These two spurious signals 2
03 and 204 are two interference signals 201 and 20 respectively.
For example, the interference signal is generated at a position separated by a frequency interval between the two interference signals 201 and 202 (800 kHz in the example in the figure). For example, one of the spurious signals 203 and 204 generated in this manner (in the example of the figure, the spurious signal 203) falls within the band of the received signal S _RX ,
Decrease the receiving sensitivity. Such a phenomenon is intermodulation spurious interference. For example, for example, the third-order distortion characteristics of the low-noise amplifier 109, the mixer 111, the reception-side variable amplifier circuit 114, and the QPSK demodulation circuit 115 in the circuit shown in FIG. (Intermodulation) 3 characteristics ”).

FIG. 16 is a diagram for explaining signal interference called "single tone sensitivity suppression" in the receiving system circuit 100R. An example of this interference is:
As shown in FIG.
In some cases, the phase noise component 205 of the local oscillator 121 input to the mixer 111 falls into the signal band of the received signal S _RX and lowers the receiving sensitivity. Also,
As another example of this interference, as shown in the figure, one interference signal 201 saturates the received signal S _{RX in} the active circuit, and gives an error to the signal level and the phase of the signal. The figure shows a state where the signal S _RX ′ is saturated with the reception signal S _RX . These phenomena
This is signal interference called single tone sensitivity suppression. For example, the low noise amplifier 1 in the circuit shown in FIG.
09, the mixer 111, the reception-side variable amplification circuit 114, and the QPSK demodulation circuit 115 are generated due to output saturation characteristics (generally referred to as output compression points) and secondary distortion characteristics.

FIG. 17 is a diagram for explaining signal interference called suppression of the sensitivity of a receiving system due to a transmission signal. This interference is caused by the signal 206, which is generated by the transmission signal S _TX and one interference signal 201, as shown in FIG.
207 falls within the band of the reception signal S _RX to lower the reception sensitivity. In the figure, two signals 206 and 207 are generated on both sides of the interference signal 201 by the transmission signal S _TX and one interference signal 201,
One of the signals 206 falls within the signal band of the received signal _SRX . This signal jamming occurs, for example, in FIG.
Is generated due to a so-called cross modulation characteristic, which is one of the third-order distortion characteristics of the low noise amplifier 109, the mixer 111, the reception-side variable amplification circuit 114, and the QPSK demodulation circuit 115 in the circuit shown in FIG.

As can be understood from the above description, for example, if the reception signal is saturated in the reception system circuit 100R, an error occurs in the output signal of the comparison circuit 117, which affects the transmission power. , The mixer 111, the reception-side variable amplification circuit 114, and the QPSK demodulation circuit 115 require excellent output saturation characteristics (output compression points). In addition, the low-noise amplifier 109, the mixer 111, the reception-side variable amplification circuit 11
The 4th and QPSK demodulation circuits 115 are required to have an excellent third-order distortion characteristic over a dynamic range of 80 dB or more so that the reception sensitivity is not deteriorated by an interference signal.

FIG. 18 shows a performance standard (specifically, "IS" in the United States) in a receiving system circuit of a CDMA mobile phone.
(Interim Standard) -95 ". 9) shows an example of the distortion characteristic of the low noise amplifier 109 necessary to satisfy (). In the figure, the vertical axis indicates the input intercept point (dBm), and the horizontal axis indicates the signal level (dBm) of the received signal.
Here, the input intercept point expresses the third-order distortion characteristic described above. In the figure, the distortion characteristics of the low-noise amplifier 109 are shown in four states according to the presence or absence of a disturbing signal and the presence or absence of a transmission operation.
Specifically, the characteristic curve 211 shows the case where both the interference signal and the transmission operation are present, and the characteristic curve 212 shows the case where the interference signal is present but there is no transmission operation. A characteristic curve 213 indicates a case where there is no interference signal and a transmission operation is performed, and a characteristic curve 214 indicates a case where neither a disturbance signal nor a transmission operation is performed.

The performance criteria for preventing the reception sensitivity from being lowered by the interference signal in the CDMA type portable telephone set by IS-95 are as follows, for example. That is, (1) the received signal level is -101 dBm and one interference signal -30 dB
m, (2) the received signal level is -101 dBm and two interfering signals -43 dBm, (3) the received signal level is -90 dB
There is a performance criterion that the sensitivity is a value sufficient for communication under each condition of two interference signals -32 dBm at Bm and (4) two interference signals -21 dBm at a received signal level of -79 dBm.

As can be seen from the figure, the value of the input intercept point required for the low noise amplifier 109 to satisfy the IS-95 standard depends on the signal level of the received signal, the presence / absence of an interfering signal, and the transmission operation. It differs greatly depending on the presence or absence. Here, the conventional receiving system circuit 100
In R, the operating currents of the resistors, capacitors, transistors and the like constituting the circuit are always set to be constant irrespective of the reception state, so that the low-noise amplifier 109, the mixer 111, the reception-side variable amplification circuit 114 and the QPSK
The value of the input intercept point of the demodulation circuit 115 is
In the receiving state, set to the strictest conditions, IS-95
To meet the standards. Similarly, the other performances are set to the strictest conditions in the operating state so as to satisfy the IS-95 standard. For example, in the example shown in FIG. 18, the operating current flowing in the low noise amplifier 109 is set so as to satisfy the input intercept point shown by the characteristic curve 211.

By way of example, when considering the relationship between the value of the input intercept point and the operating current of the transistor constituting the receiving circuit 100R, it is generally found that 3
To achieve a dB higher input intercept point,
If the circuit conditions such as the load resistance are the same, the transistor needs twice the operating current. Therefore, in the example of FIG. 18, “transmission: no, interference signal:
Compared to the case of “absent”, “transmission: presence, interference signal: none”, “transmission: none, interference signal: presence” indicated by other characteristic curves
And "transmit: present, jamming signal: present", the input intercept point is higher and the required operating current is higher.

On the other hand, since a portable telephone is generally driven by a battery, if the current consumption is large, the consumption of the battery becomes large. And the battery must be replaced frequently.
Therefore, it is desired that the current consumption of the circuits in each section be as small as possible.

However, as described above, if the circuit performance is set so that the linearity, the third-order distortion characteristic, the output compression point, and the like are improved over a dynamic range of 80 dB or more in the receiving system circuit 100R, the current consumption in the circuit is reduced. There was a problem of becoming very large.

In particular, a CDMA mobile phone always operates in a signal receiving state (standby state) in order to check the level of a received signal even when transmission is not performed. Mixer 11
1 requires about twice or more the operating current as compared with the circuit used in the TDMA type mobile phone.
In addition, there is a problem that the current also increases in the other circuit parts, and the standby time becomes very short when the mobile phone is used. Also, for example, in a mobile phone operating in a dual mode of the CDMA system and the FM system, there is a circuit that commonly uses each system,
When the common circuit is operated after being optimized for the CDMA system, there is a problem that excessive performance is required for the operation of the FM system, and unnecessary current is consumed more than necessary.

The present invention has been made in view of the above problems, and has as its object to provide, for example, a receiving apparatus capable of changing an operation state so as to reduce power consumption in accordance with the presence or absence of jamming radio waves. To provide a communication device.

[0028]

According to a first aspect of the present invention, there is provided a receiving apparatus which operates according to a communication factor including at least one of the presence or absence of a transmission operation in a communication device, the presence or absence of an interference wave, and the signal level of a received signal. Is provided with a receiving circuit capable of changing the threshold value.

In this receiving apparatus, the operating state of the receiving circuit is changed in accordance with a communication factor including at least one of the presence or absence of a transmission operation in a communication device, the presence or absence of a jamming radio wave, and the signal level of a received signal.

According to a second aspect of the present invention, there is provided the receiving apparatus according to the first aspect, further comprising determining means for determining an operation state to be changed by the receiving circuit based on a communication factor, wherein the receiving circuit determines the operating state. The operation state is changed based on the operation state determined by the means.

In this receiving device, the operating state to be changed by the receiving circuit is determined by the determining means based on the communication factor. Also, the operation state of the receiving circuit is changed based on the operation state determined by the determination means.

According to a third aspect of the present invention, in the receiving apparatus according to the second aspect, the determining means has an association table for associating a communication factor with an operation state of the reception circuit, and the receiving means receives the information in accordance with the table contents of the association table. The circuit determines an operation state to be changed.

In this receiving device, the operating state to be changed by the receiving circuit is determined by the determining means in accordance with the contents of the association table that associates the communication factor with the operating state of the receiving circuit.

According to a fourth aspect of the present invention, in the receiving apparatus of the third aspect, the association table is configured such that the contents of the table can be changed from outside.

In this receiver, the contents of the association table can be changed according to, for example, the characteristics of the circuit elements of the receiving circuit.

According to a fifth aspect of the present invention, in the receiving apparatus of the first aspect, the receiving circuit includes a circuit for processing a high-frequency signal.

According to a sixth aspect of the present invention, in the receiving apparatus of the first aspect, the receiving circuit always detects the signal level of the received signal regardless of the presence or absence of substantial communication. As in

In this receiving apparatus, the operation for detecting the signal level of the received signal is always performed by the receiving circuit regardless of the presence or absence of substantial communication.

According to a seventh aspect of the present invention, in the receiving apparatus of the first aspect, the operation state is changed so that the receiving circuit consumes current according to a communication factor enough to satisfy required performance. It is like that.

In this receiving device, the receiving circuit changes the operating state so that current consumption is performed according to the communication factor enough to satisfy the required performance.

According to an eighth aspect of the present invention, in the receiving apparatus of the first aspect, the time required to change the operation state of the receiving circuit is changed in accordance with the difference in the operation state. It is.

In this receiver, the time required to change the operation state of the receiving circuit is appropriately changed according to the change in the operation state.

According to a ninth aspect of the present invention, in the receiving apparatus of the first aspect, a change in ambient temperature is included as a communication factor.

In this receiving apparatus, the operating state of the receiving circuit can be changed according to the ambient temperature change in addition to the presence or absence of the transmission operation in the communication device, the presence or absence of the interfering radio wave, or the signal level of the received signal. Is done.

According to a tenth aspect of the present invention, there is provided a communication device, comprising: a transmission circuit for performing signal processing on a transmission signal; And a receiving circuit capable of changing the operation state accordingly.

In this communication device, the transmission circuit performs signal processing on the transmission signal, and determines whether the operation state of the reception circuit is at least the presence or absence of the transmission operation in the transmission circuit, the presence or absence of interference, or the signal level of the reception signal. It is changed according to the communication factor including one.

[0047]

Embodiments of the present invention will be described below in detail with reference to the drawings.

FIG. 1 is a block diagram showing a configuration of a high-frequency stage of a mobile phone as a communication device according to an embodiment of the present invention. In the drawing, as an example of a configuration of a mobile phone, a mobile phone having a dual mode of a CDMA system and an FM system is shown. The mobile phone shown in this figure includes a transmission (TX) circuit 1 for performing signal processing on a transmission signal and a reception (RX) for performing signal processing on a reception signal.
A system circuit 2, a modem 3 to which a transmission signal to be processed is modulated and output to the transmission system circuit 1 and a reception signal processed in the reception system circuit 2 is inputted, and a separation of the transmission signal and the reception signal. , A common antenna 5 that radiates a signal radio wave to be transmitted and receives a signal radio wave from a base station (not shown), and a reception circuit control for controlling the operation state of each unit of the reception circuit 2. A part 6.

Here, the transmission system circuit 1 and the reception system circuit 2
Correspond to specific examples of the “transmitting circuit” and the “receiving circuit” in the present invention, respectively. The receiving system circuit 2 and the receiving circuit control unit 6 correspond to a specific example of the “receiving device” in the present invention.

The transmission system circuit 1 QPSK modulates the baseband transmission signal output from the modem 3 and outputs an IF (intermediate frequency) transmission signal.
Transmission side variable amplifier circuit (TX-
AGCAMP) 12, a mixer 13 that mixes the amplified IF transmission signal with a local oscillation signal from a local oscillator 16, converts the signal into an RF (high frequency) transmission signal, and outputs the RF signal, and an unnecessary signal component included in the RF transmission signal. And a power amplifier (PA) 15 for amplifying the RF transmission signal output from the band-pass filter 14 and outputting the amplified RF transmission signal to the duplexer 4. The power amplifier 15 is connected to a changeover switch 17 that is turned on / off according to the transmission control signal _DTX .

The reception system circuit 2 includes a low noise amplifier circuit section 21 having a low noise amplifier (LNA) 21a for amplifying an RF reception signal input through the duplexer 4, and an unnecessary signal component included in the RF reception signal. , A mixer circuit unit 23 having a mixer 23a for mixing an RF reception signal with a local oscillation signal from the local oscillator 16 and converting the RF reception signal into an IF reception signal, CDMA bandpass filter 24 for converting a received signal into a CDMA signal component
And an FM bandpass filter 25 for converting the input IF reception signal into an FM signal component, and a reception for amplifying the selectively input CDMA reception signal and FM reception signal. Side variable amplifier circuit (RX-AGC
AMP) a receiving-side variable amplifier circuit section 26 having 26a;
QPSK for QPSK demodulation of amplified received signal
And a QPSK demodulation circuit section 27 having a demodulation circuit 27a.

The low-noise amplifier circuit section 21, the mixer circuit section 23, the reception-side variable amplifier circuit section 26, and the QPSK demodulation circuit section 27 each include circuit setting data D1 described later.
Latch circuits 21b, 23b, 26b, 2 for latching 0
7b. Low noise amplifier 21a, mixer 2
3a, the reception-side variable amplification circuit 26a and the QPSK demodulation circuit 27a are respectively provided with latch circuits 21b, 23b,
Circuit setting data D latched by 26b and 27b
10, the electric performance (operating state) can be changed.

The modem 3 includes a low-pass filter 31 for passing a signal D2 of a predetermined frequency band of the received signal input from the QPSK demodulation circuit 27a, and a low-pass filter 31.
A broadband low-pass filter 32 for passing a signal D3 having a wider band, and a reception signal strength detection circuit (RSS) for detecting the strength (signal level) of the input reception signal.
I) A comparison circuit 34 that compares 33 with the reception intensity and intensity reference data D11 and outputs a signal D1 indicating the difference.
When a transmission output correction circuit 35 for controlling the gain of the transmission side variable amplifying circuit 12, the changeover switch 36 for switching whether to output a baseband transmission signal to the QPSK modulation circuit 11 in accordance with the transmission control signal D _TX And

The signal pass band of the low-pass filter 31 is
The band is set so that only the received signal required for communication is selected. For example, in the CDMA system of North American specifications, the cutoff frequency is set to 615 kHz. The signal pass band of the broadband low-pass filter 32 is set wider than that of the low-pass filter 31, and the cutoff frequency is set to 2.5 MHz, for example. By setting the signal pass bands of the low-pass filter 31 and the wide-band low-pass filter 32 as described above,
The 900 kHz offset and 1.7 MHz offset interfering signals pass through the wideband low-pass filter 32 but do not pass through the low-pass filter 31. Therefore, when the signal level of the signal D3 that has passed through the wide band low-pass filter 32 is higher than the signal level of the signal D2 that has passed through the low-pass filter 31 and is equal to or greater than a certain reference value, an interference signal is input to the receiving circuit 2. It means that. From the circuit setting table 61 described later, the signal D
Circuit setting data D10 corresponding to the presence / absence of jamming waves indicated by D2 and D3 is output.

The transmission control signal D _TX is a signal for determining the presence or absence of a transmission operation in the transmission circuit 1.
For example, it is represented by a digital on / off signal of 0 and 1, for example, when the signal value is “0”, it indicates that the transmission operation is off, and when the signal value is “1”, the transmission operation is Is on. However, it may be set to ON when it is "0" and to be OFF when it is "1". This transmission control signal D
_TX includes the changeover switches 17 and 36 and the reception circuit control unit 6
Is input to The transmission control signal D _TX is
And is used to turn on / off the power amplifier 15, for example.

[0056] mode switching signal D _FM is, a mobile phone CD
It is a signal for controlling which mode of the MA system or the FM system is operated, and is represented by, for example, a digital on / off signal of 0 or 1 and, for example, when the signal value is “0”. This indicates that the mode is the FM mode, and when the signal value is “1”, the mode is the CDMA mode. However, if it is "0", C
The mode may be set to the DMA mode, and if it is “1”, the mode may be set to the FM mode. The mode switching signal D _FM is generated in the modem 3, CDMA band-pass filter 24 and FM band-pass filter 25
Is input to the mode changeover switch provided at the next stage of the above and the receiving circuit control unit 6.

The signal D1 from the comparison circuit 34, the received signal D2 passed through the low-pass filter 31, and the signal D3 passed through the wide-band low-pass filter 32 are converted into analog / digital (A) signals (not shown) so that they can be digitally processed.
/ D) The signal is A / D converted by a converter to be a digital signal. The signals D1, D2, and D3 converted into digital signals are input to the receiving circuit control unit 6.

The receiving circuit control section 6 operates the low noise amplifier 21a, the mixer 23a, the receiving side variable amplifying circuit section 26a and the QPSK demodulating circuit 27a in the receiving circuit 2 in accordance with "communication factors" such as the presence or absence of a transmitting operation. The state can be controlled individually. The receiving circuit control unit 6 includes a circuit setting table 61 and a gain correction table 6
2 and an addition circuit 63. Receiving circuit controller 6
Is constituted by, for example, a one-chip integrated circuit (IC). The circuit setting table 61 and the gain correction table 62 are for determining the operating state of each part of the receiving system circuit 2 to be changed, and the contents of the tables can be changed from outside. The table contents of the circuit setting table 61 and the gain correction table 62 can be changed, for example, according to the variation in the characteristics of each device constituting the receiving circuit 2. However,
The table contents of the circuit setting table 61 and the gain correction table 62 may be fixed to fixed contents. It is desirable that the circuit setting table 61 and the gain correction table 62 be separate tables for the FM system and the CDMA system.

Here, the receiving circuit control section 6 corresponds to a specific example of “determining means” in the present invention. Further, the circuit setting table 61 and the gain correction table 62 correspond to a specific example of the “related table” in the present invention. In this embodiment, the “communication factor” refers to, for example, the presence or absence of a transmission operation, the presence or absence of jamming radio waves, the signal level of a received signal, and the like. The “communication factors” in the present embodiment also include factors such as ambient temperature.

The circuit setting table 61 includes communication factors such as the presence or absence of a transmission operation and the presence or absence of an interfering radio wave, and the operating states of the low-noise amplifier 21a, the mixer 23a, the reception-side variable amplification circuit 26a, and the QPSK demodulation circuit 27a in the reception system circuit 2. And various signals indicating communication factors are input. The signal indicating the communication factors include signal D1, D2, D3, the mode switching signal D _FM and transmit control signals D _TX. In this circuit setting table 61 is, for example, the mode when the switching signal D _FM is inputted, the mode switching signal D _FM
The table corresponding to the mode represented by is selected. Further, from the circuit setting table 61, for example, depending on the presence or absence of transmission operation represented by the transmission control signal D _TX, a low noise amplifier 21a, mixer 2
3a, the circuit setting data D10 that optimizes the current flowing through each of the receiving-side variable amplifier circuit 26a and the QPSK demodulation circuit 27a is determined and output to each circuit.

The gain correction table 62 is for correcting the gain of the variable amplifier circuit 26a on the receiving side, and is provided with the temperature data from the temperature sensor 64 and the circuit setting table 61.
From the circuit setting data D10. The gain correction table 62 is a circuit setting table 61
The gain correction value is output in synchronism with the circuit setting data D10 input from. In addition, the gain correction table 62 outputs a gain correction value corresponding to temperature data representing a temperature around the circuit input from the temperature sensor 64 in order to perform gain correction for temperature. The addition circuit 63 outputs the reception-side AGC voltage V _RX-AGC obtained by adding the gain correction value output from the gain correction table 62 and the output signal D1 from the comparison circuit 34 to the reception-side variable amplification circuit 26a. Has become. A specific example of the gain correction table 62 will be described later with reference to the drawings.

Here, the portable telephone according to the present embodiment is always in operation to detect the signal level of the received signal irrespective of the presence or absence of substantial communication. At this time, under the control of the reception circuit control unit 6, the operation state of each unit of the reception system circuit 2 is changed according to the signal level of the reception signal or the like so that the current consumption is reduced. Here, the “substantial communication” refers to communication involving a telephone call. In the present embodiment,
The “received signal” includes a signal for simply checking a signal level without an incoming call.

FIG. 2 is a diagram showing an example of the data structure of the circuit setting data D10 input to each part of the receiving system circuit 2. The circuit setting data D10 is, for example, serial data having an address, and is transmitted, for example, bit by bit. The circuit setting data D10 includes data D _LNA for the low noise amplifier 21a and data D _LNA for the mixer 23a.
_MIX and data D for the reception-side variable amplifier circuit 26a.
_{It has AGC} and data D _QPSK for the QPSK demodulation circuit 27a. Each data D _LNA , D _MIX , D _AGC , D _QPSK
Includes an address portion Dadd indicating address information and a setting data portion Ddata indicating substantial data. In the example shown in the figure, “0001”, “001”
The addresses “0”, “0011”, and “0100” correspond to the addresses of the low-noise amplifier 21a, the mixer 23a, the variable amplifier 26a on the receiving side, and the QPSK demodulator 27a, respectively. The setting data portion Ddat
A specific example of a will be described later in detail.

The low noise amplifier 21a, the mixer 23a,
Receiving side variable amplifier circuit 26a and QPSK demodulation circuit 27
a has its own address, and its own address and the address portion Dadd of the circuit setting data D10.
The latch circuit 2
The circuit setting data D10 for its own circuit is taken in via 1b, 23b, 26b, 27b.

FIG. 3 is a circuit diagram showing a configuration example of the low noise amplifier 21a. The low-noise amplifier 21a shown in the figure includes resistors R0 to R3, R5 and a switch SW1.
, Transistors T1 and T2, an inductor L1, a capacitor C1, and a SAW (Surface Acoustic Waves) filter F1. The power supply voltage Vcc is applied to the low noise amplifier 21a shown in FIG. Also,
The input signal LNA _IN is input to the low noise amplifier 21a shown in FIG.
An output signal LNA _OUT is output via the output terminal 3. Switch unit SW1 includes a switch S ₀ to S _3. The switches S _{0 to} S ₃ are, for example, CMOS (Metal-Oxide Semi)
conductor) It is composed of a switching element such as a transistor.

The switches S _{0 to} S of the switch section SW _1
3 are respectively arranged in parallel. Resistance R0-R
3, while being parallel arranged, one end is connected to a switch S ₀ to S _3. The other ends of the resistors R0 to R3 are connected to the collector terminal of the transistor T2. The emitter terminal of the transistor T2 is grounded. The base terminal of the transistor T2 is connected to one end of the resistor R5. The other end of the resistor R5 is connected to the input terminal 71 and the base terminal of the transistor T1.
The emitter terminal of the transistor T1 is grounded.
The collector terminal of the transistor T1 is connected to the inductor L1 and one end of the capacitor C1. The other end of the inductor L1 is connected to the input terminal 72. The other end of the capacitor C1 is connected to the input side of the SAW filter F1. The output side of the SAW filter F1 is connected to the output terminal 73.

The inductor L1 and the capacitor C1 are
This is provided for bias and impedance matching of the transistor T1. The resistor R5, the transistor T2 and the resistors R0 to R3 form a current mirror type bias circuit. Due to the action of the current mirror circuit constituted by the resistor R5, the transistor T2 and the resistors R0 to R3, the collector current Ic of the transistor T1 has a value proportional to the current flowing through the transistor T2.

The resistance value of the resistor R1 is different from that of the resistor R0.
For example, it is set to a value of 1/2. Further, the resistance value of the resistor R2 is set to, for example, 1/4 of the resistance R0. Further, the resistance value of the resistor R3 is set to, for example, 1/8 the value of the resistor R0. Note that the set value of each resistor is not limited to those described here, and may be set to other values. Switch S ₀ ~S
₃ is turned on or off by the circuit setting data D10. The low noise amplifier 21a shown in FIG.
In the current flowing through the transistor T2 will vary according to the on / off state of the switches S ₀ to S _3, further,
A current proportional to the current flowing through the transistor T2 flows as the collector current Ic of the transistor T1.

FIG. 4 is a circuit diagram of the low noise amplifier 2 shown in FIG.
2 shows an example of the relationship between the on / off states of the switches S _{0 to} S ₃ in 1a and the collector current Ic of the transistor T1. In the drawing, the on / off state of the switches S ₀ to S ₃ is determined by the set data portion Ddata of the circuit configuration data D10 shown in FIG. For example, when the setting data portion corresponding to the switches S _{0 to} S ₃ of the circuit setting data D10 is “0”, the switches S ₀ to S ₃
S ₃ is turned off. Also, when setting the data portion is "1", the switch S ₀ to S ₃ is turned off. However, it may be set to ON when it is "0" and to be OFF when it is "1". From the figure, for example,
When only the switch S ₀ is on _{(S 3, S 2, S} 1, S
It can be seen that a current of value I ₀ flows in ( ₀ = _{0, 0, 0,} 1). Also, in comparison with this case, the switches S ₀ to S ₀
When all S ₃ is turned on _{(S 3, S 2, S} 1, S 0 =
It can be seen that a current of 15 times the current of the value I ₀ flows through (1, ₁ , 1, ₁ ). In general, the operation of the high-frequency transistor improves the distortion performance (here, the third-order distortion intercept point) in proportion to the current.

FIG. 5 is a diagram showing an example of the contents of the circuit setting table 61 applied to the low noise amplifier 21a. The circuit setting table 61, so that the transmission ON / OFF (whether transmission operation), the state of the switch S ₀ to S ₃ in accordance with the signal level of the presence and the received signal of the interfering signal, shown in the drawing, They are stored in association with each other.

Here, in the table of FIG.
“X” corresponds to the transmission control signal D _TX and indicates whether or not there is a transmission operation. For example, when “TX” is “0”, it indicates that there is no transmission operation, and “TX”
Is "1", indicating that there is a transmission operation. In the table of FIG.
"S" indicates the presence or absence of an undesired signal. For example, when "UDS" is "0", there is no interference signal, and when "UDS" is "1", there is a transmission operation. As described above, the presence or absence of the interfering signal is determined by the wide band low-pass filter 3.
2 and the signal level of the signal D2 that has passed through the low-pass filter 31.

In the table shown in FIG. 7, the state of the switches S _{0 to} S ₃ indicates that the four bits (S ₃ , S ₂ , S ₁ , S ₁ , S ₁ , S ₂ , S _{3) 0} ).
In the drawing table, "0" indicates the "off" state of the switch S ₀ to S _3, "1" indicates the "on" state of the switch S ₀ to S _3. In the table of FIG. 3, the amplification factor (Ic / I ₀ ) of the operating current (collector current Ic of the transistor T1) in the low noise amplifier 21a is also shown. However, the amplification factors shown in the figure are for ease of explanation, and need not actually be included in the table contents of the circuit setting table 61.

In the table shown in the figure, “transmission: existence, interference signal: existence” (TX: 1, UDS: 1) and “transmission: existence,
In the case of "No interference signal: nothing" (TX: 1, UDS: 0),
Set state close to turn on almost all of the switches S ₀ to S _3, so that the operating current of the transistor T1 increases. This is already the "problem to be solved by the invention"
As described with reference to FIG. 18 in the section, “transmission: presence, interference signal: presence” and “transmission: presence, interference signal:
In the case of "none", a high input intercept point is required.

Further, in the table of FIG.
Interference signal: presence "(TX: 0, UDS: 1 ) and" transmission: No, interfering signal: No "(TX: 0, UDS: 0 ) in the case of a low bit of the switches S ₀ to S ₃ Only the switches S ₁ and S ₀ shown are set to be turned on, so that the operating current of the transistor T1 is reduced. This is because, as already described with reference to FIG. 18, in the case of “transmission: no, jamming signal: present” and “transmission: no, jamming signal: no”, a very high input intercept point is required. Because it is not done. In the mobile phone, since most of the standby time is in the transmission-off state, when the table is set as shown in FIG. 5, the operating current of the low noise amplifier 21a during the standby time can be reduced, and the standby time can be extended. .

FIG. 6 is a diagram showing an example of the contents of the gain correction table 62. The table contents shown in this figure are obtained by associating the circuit setting table 61 for the low noise amplifier 21a with the temperature data from the temperature sensor 64. In the table shown in this figure, for example,
When all of the switches S _{0 to} S ₃ are on (S ₃ , S ₂ , S
₁ , S ₀ = ₁ , ₁ , ₁ , ₁ ) correspond to the switches S _{0 to} S
_The gain correction value is set to be lower than when only the switches S ₁ and S ₀ represented by low bits out of ₃ are on. Further, in the table shown in this figure, for example, the gain correction value is set to be higher when the temperature is high than when the temperature is low. The gain correction table 62 outputs the gain correction value determined based on the contents of the table to the addition circuit 63. The gain correction value output to the addition circuit 63 is added to the output signal D1 from the comparison circuit 34, and output to the reception-side variable amplification circuit 26a as the reception _- side AGC voltage V _RX-AGC . The receiving side variable amplifying circuit 26a receives the input receiving side A
The gain is controlled by the GC voltage V _RX-AGC .

The contents of the tables shown in FIGS. 5 and 6 described above are tables in the case of operating in the CDMA system, and similar tables are stored for the FM mode. In the circuit setting table 61 and the gain correction table 62, whether to use any of the mode table is selected by the mode switching signal D _FM. For example, in the FM mode, even if the signal is limited, the communication quality is not deteriorated, so that the current of the low noise amplifier 21a and the like may be smaller than that in the CDMA system. In the FM mode, for example, table contents in consideration of such conditions are set.

FIGS. 7 and 8 show a low noise amplifier 21.
FIG. 6 is a diagram for explaining a switching time of an operation state in FIG. If the circuit is simply changed in response to a change in the reception state, there is a problem that the circuit generally operates as if it has oscillated. Therefore, in this embodiment, in order to solve this problem, the time required to change the operation state is changed according to the difference in the change in the operation state. More specifically, when the performance is relatively improved (when the operation state is such that a relatively large amount of current flows), the circuit state is changed in a short time, and conversely, the performance is relatively improved. When decreasing the operation state (when setting the operation state such that a relatively small amount of current flows), the operation state is changed in, for example, 10 to 1000 times as long as the time when the performance is improved. I have.

Here, in the example shown in FIG. 7, when changing to an operation state in which a relatively large amount of current flows, for example, “transmission: no, interference signal: no” (TX: 0, UDS:
0) from the state of “transmission: existence, jamming signal: existence” (TX:
The operation switching time of the circuit when changing to the state of 1, UDS: 1) is "1". On the other hand, when changing to an operation state in which a relatively small amount of current flows, for example, “transmission: present, interference signal: present” (TX: 1,
From UDS: 1), "Transmission: None, Interference signal: None"
When changing to the state of (TX: 0, UDS: 0), the operation switching time is set to 100 times.

Further, in the example shown in FIG.
At 2, t3, and t4, a change in communication factors such as the presence or absence of jamming radio waves occurs, and a time chart shows how much time has elapsed since the change of the communication factors before actually changing the operation state. Things. As shown in the figure, the time required for operation switching when changing to an operation state in which a relatively large current flows is indicated by a period T _UP , and the operation state is changed to a relatively small current flow. The time required for the operation switching at this time is indicated by a period T _DOWN . As shown in the figure, the period T _UP is set to be smaller than the period T _DOWN ,
The time required for operation switching when changing to an operation state in which a relatively small amount of current flows is longer than that required to change the operation state.

FIG. 9 is a circuit diagram showing a configuration example of the mixer 23a. The mixer 23a shown in FIG.
R3, switch section SW1 _MIX , transistor T21
To T31, resistors R21 to R25 and resistors R27 to R
32. The mixer 23a having the configuration shown in this figure is generally called a Gilbert mixer (Gilbert is the name of a developer of the mixer system). The configurations of the resistances R0 to R3 and the switch unit SW1 _MIX are basically the same as those of the low noise amplifier 21a shown in FIG.
This is the same as R3 and switch unit SW1.

The mixer 23a has input terminals 76, 7
7, an RF signal RF _IN is input. Further, the local oscillation signal OSC _IN from the local oscillator 16 is input to the mixer 23a via the input terminals 74 and 75. The RF signal RF _IN input to the mixer 23a is mixed with the local oscillation signal OSC _IN, and the difference component (frequency difference) is supplied to the IF output signal I / O via the buffer amplifier transistors T27 and T28.
The signals are output from the output terminals 79 and 80 as F _OUT .

The resistor R21 is provided as a negative feedback resistor. The resistors R22 to R25 are provided as bias resistors. Resistance R0 to R3, resistance R27
The transistor T31 forms a bias voltage generation unit. The resistors R28 and R29 are provided as load resistors. Transistors T29 and T30, resistor R3
1 and R32 form a constant current circuit. Resistance R30
Is a bias resistor. The mixer currents I ₁ , I ₂ and the buffer amplifier currents I ₃ , I ₄ depend on a bias voltage generation unit including resistors R0 to R3, a resistor R27, and a transistor T31.

The mixer 23a shown in this figure has a tendency that the higher the operating current, the better the third-order distortion. In general communication equipment, the mixer current (I ₁
+ I ₂ ) of about ₂ to 5 mA was sufficient, but CDMA
In the method, high strain characteristics are required, and 10 to 20 mA
In many cases. Generally, the third-order distortion is 3d
B To obtain a high value (excellent value), set the mixer current to 2
You need to shed twice as much.

Conventionally, the mixer currents I ₁ and I ₂ are fixedly set to values satisfying the strictest conditions of performance, but in the present embodiment, the switches S _{0 to} S ₃ are selected. in by turning on / off manner, when requiring high distortion performance, when setting the current I _1, I ₂ to a large value, it does not require a high strain performance, current I _1,
It is set to reduce the I _2. For example, transmission in the case of no interference signal off, there is no problem even distortion characteristics is low, is adapted to selectively turn on / off the switch S ₀ to S ₃ to lower the current. Specifically, when the distortion characteristic is good at 3dB lower value, the mixer current is adapted to selectively turn on / off the switch S ₀ to S ₃ as down to 1/2.

The resistors R0 to R3 are configured so that the current values of the currents I ₁ and I ₂ can be varied in combination with the switches S _{0 to} S ₃ . Further, when the current values of the currents I ₁ and I ₂ are reduced, since excellent strain characteristics are not required, the current values of the currents I ₃ and I ₄ can also be reduced. Therefore, the currents I ₃ and I ₄ are equal to the currents I ₁ and I ₂
Is controlled in conjunction with. In this case, the voltage of the resistor R30 is changed to the transistors T21 and T21.
Supplied from the voltage determining the bias of 22. Circuit setting table 6 applied to such a mixer 23a
The table contents of No. 1 are basically the same as the table contents applied to the low noise amplifier 21a shown in FIG. 5, although the detailed set values are different. The contents of the gain correction table 62 for such a mixer 23a are basically different from those of the low noise amplifier 21a shown in FIG.
The contents are almost the same as the contents of the table.

FIG. 10 is a circuit diagram showing another example of the configuration of the mixer 23a. The mixer 23a shown in FIG.
In which the portions corresponding to the resistors R28 and R29 in the circuit configuration shown in FIG. 14 are replaced with the switches SW2 and SW3 and the resistors R0 to R4, respectively, and the portion corresponding to the resistor R21 is replaced with the switch SW4 and the resistors R10 to R14. It has become. Other components are the same as those of the circuit shown in FIG. Switch SW
2, SW3's configuration, except that the resistor R0 and the switch S ₀ resistor in parallel to the side R4 are connected, the switch section S
This is the same as the configuration of W1 _MIX . Switch section SW4 is a switch S ₁₀ to S _13. Switch S ₁₀ to S ₁₃ of the switching unit SW4 are parallel arranged. Resistance R10~R13, together are in parallel arranged, one end is connected to a switch S ₁₀ to S _13. Switch S ₁₀ to S ₁₃ is composed of, for example, a switching element such as a CMOS transistor. The setting conditions for the switch section SW4 are described in the circuit setting table 61.
And the gain correction table 62.

[0087] Figure 11 includes a switch unit SW2 and the switch unit SW3, a current I ₁ ~I _4, shows the relationship between the combined resistance of the switch unit SW2 and the switch unit resistor connected SW3 R0 to R4. The switch SW
2. The setting conditions regarding SW3 are stored in the circuit setting table 61.
And the gain correction table 62.
As shown in the figure, for example, all the switches S ₀ to S ₃ is in the case of off, the combined resistance of the resistor R0 to R4, and only the resistor R4. Note that the resistance value of the resistor R4 is set to a relatively larger value than the other resistors R1 to R3.

FIG. 12 is a circuit diagram showing a configuration example of the reception-side variable amplifier circuit 26a. The receiving-side variable amplifier circuit 26a shown in FIG. 6 includes resistors R0 to R3 and a switch SW1.
_AGC , transistors T41 to T59, and resistors R41 to R41
R48, R49a, R49b, R50-R53, R55
To R57. The configurations of the resistors R0 to R3 and the switch unit SW1 _AGC are basically the same as those of the resistors R0 to R3 and the switch unit SW1 in the low noise amplifier 21a shown in FIG. Transistors T55 to T58
And the resistors R47, 48, 49a, and 49b constitute a constant current source 26-1 for DC bias. Further, the transistors T49 and T50 and the resistors R45 and R46
A constant current circuit 26-2 is formed. Further, the transistors T43 to T46 form an AGC operation part 26-3. The setting conditions relating to the switch unit SW1 _AGC include a circuit setting table 61 and a gain correction table 62.
Is stored in advance.

The receiving side variable amplifier circuit 26a shown in FIG.
, A power supply voltage Vcc is applied via an input terminal 81. In the receiving-side variable amplifier circuit 26a shown in this figure, the transistors T41 and T4
2, the input signal AGC _IN is input to the transistor T5
1 from the receiving circuit control unit 6 via the input terminal 82.
The GC voltage V _RX-AGC is input. Further, in the reception-side variable amplifier circuit 26a shown in this figure, an output signal AGC _OUT is output via an output terminal 83.

The transistors T41 and T42 are provided for amplification. In the AGC operation part 26-3 including the transistors T43 to T46, the transistor T43
By changing the ratio of the current flowing through 43 and T44,
An AGC function is realized. Transistors T45 and T46
The same applies to the ratio of the current flowing through. For example, when the same value as the current flowing through the transistor T41 flows through the transistor T44 (the current of the transistor T43 is 0), the gain is maximum. Further, when a current flows through the transistor T43, an operation is performed in which the gain decreases in accordance with the ratio of the current flowing through the transistors T43 and T44.

The transistors T47 and T48 are provided for a buffer amplifier. Transistor T4
7, T48 flows through transistors T49, T5
It is determined by a constant current circuit 26-2 having 0 and resistors R45 and R46. This transistor T43
To T47 are controlled by transistors T51 and T52 forming a differential amplifier circuit and their output buffer transistors T53 and T54.

[0092] AGC voltage V _RX-AGC is adapted to be input to one of the bases of the transistors T51, T52 forming a differential amplifier circuit for AGC voltage V _RX-AGC, transistors T51, T52 Current changes. The change in the current flows through the transistors T53 and T54,
This is provided to transistors T43 to T46. Resistance R52
Are provided for gain tilt correction. Resistance R5
0 and R51 are provided as load resistors.
The transistor T59 and the resistors R0 to R3 are circuits that generate a bias voltage.

In order to realize an AGC range of 80 dB or more required in the CDMA system, it is necessary to cascade three to four circuits shown in FIG.

FIG. 13 is a circuit diagram showing a configuration example of the QPSK demodulation circuit 27a. The QPSK demodulation circuit 27a shown in this figure includes a buffer amplifier 27-1 and a mixer circuit 2
7-2, 27-3, switch section SW1 _QPSK , and resistor R
0 to R3, R66 to R69, and a transistor T67. The buffer amplifier 27-1 includes transistors T81 to T88 and resistors R81 to R84. The mixer circuit 27-2 includes transistors T61 to T6
6 and resistors R61 to R65. The mixer circuit 27-3 includes transistors T71 to T76 and a resistor R7
1 to R75. QPSK demodulation circuit 2
7a includes resistors R0 to R3, a switch unit SW1 _QPSK ,
A resistor R66, 67, 68, 69 and a transistor T67
And Resistors R0 to R3, transistor T67
The resistor R66 forms a bias voltage generating section. The configurations of the resistors R0 to R3 and the switch unit SW1 _QPSK are basically the same as the resistors R0 to R3 and the switch unit SW1 of the low noise amplifier 21a shown in FIG. The setting conditions for the switch unit SW1 _QPSK are stored in the circuit setting table 61 and the gain correction table 62 in advance.

The local oscillator 71 is provided in the mixer circuit 27-2.
, A local oscillation signal is directly input. On the other hand, the local oscillation signal from the local oscillator 71 is input to the mixer circuit 27-3 via the 90-degree phase shift circuit 72. Input terminals 91 and 92 are connected to the transistors T65 and T66 of the mixer circuit 27-2 and the transistors T75 and T76 of the mixer circuit 27-3.
The IF signal IF _IN is input through the interface. The buffer amplifier 3 outputs a QPSK I signal I _OUT via output terminals 93 and 94, and outputs the output terminals 95 and 96.
Output the Q signal Q _OUT via the.

In this QPSK demodulation circuit 27a, 3
The secondary distortion characteristic depends on the operating current of the mixer circuits 27-2 and 27-3 and the operating current of the buffer amplifier 27-1. In the present embodiment, the mixer circuits 27-2, 27
The operating current and the operating current of the buffer amplifier 27-1 -3, resistors R0 to R3, the switch S ₀ of the bias voltage generating unit consisting of transistors T67 and a resistor R66 to S
Select and set according to ₃ . For example, in the signal reception state, if you do not need a high strain properties, the switch S ₀ by setting to S _3, the operation of the mixer circuit 27-2,27-3 current and buffer amplifier 2
The operating current of 7-1 is reduced.

Next, the operation of the portable telephone having the above configuration will be described.

First, the operation at the time of transmission will be described. The baseband transmission signal modulated by the modem 3 is first input to the QPSK modulation circuit 11 of the transmission system circuit 1. The QPSK modulation circuit 11 performs QPSK modulation on the baseband transmission signal, converts the baseband transmission signal into, for example, a 130 MHz IF transmission signal, and outputs the IF transmission signal to the transmission-side variable amplifier circuit 12. Next, the transmission-side variable amplification circuit 12 amplifies the IF transmission signal and outputs it to the mixer 13. The mixer 13 mixes the amplified IF transmission signal with the local oscillation signal from the local oscillator 16, converts it to, for example, an 800 MHz RF transmission signal, and outputs the RF transmission signal to the bandpass filter 14. The band-pass filter 14 removes an unnecessary signal component included in the RF transmission signal, and outputs the signal to the power amplifier 15. The power amplifier 15 amplifies the RF transmission signal from which the unnecessary signal component has been removed, and outputs the amplified RF transmission signal to the duplexer 4. The RF transmission signal output to the duplexer 4 is radiated from the shared antenna 5 into space.

The control of whether or not to perform the transmission operation is performed by the transmission control signal _DTX . The transmission control signal D _TX is, for example, a digital ON / OFF signal of 0,1.
It is represented by an off signal, generated in the modem 3 and input to the changeover switches 17 and 36 and the circuit setting table 61 of the receiving circuit control unit 6. Changeover switches 17, 36
_Are turned on / off based on the transmission control signal _DTX .

Next, the operation at the time of reception will be described. The signal radio wave captured by the common antenna 5 is converted into an electric RF reception signal via the duplexer 4 and output to the low noise amplifier 21a of the reception system circuit 2. The low noise amplifier 21 a amplifies the input RF reception signal and outputs the amplified signal to the bandpass filter 22. The bandpass filter 22 removes an unnecessary signal component included in the RF reception signal and outputs the signal to the mixer 23a. Mixer 23a
Mixes the RF reception signal with the local oscillation signal from the local oscillator 16, converts it to, for example, an 85 MHz IF reception signal, and outputs it to the CDMA bandpass filter 24 and the FM bandpass filter 25. The band-pass filter 24 for CDMA and the band-pass filter 25 for FM
The input IF reception signals are converted into CDMA signal components and FM signal components. CDMA bandpass filter 24 and FM bandpass filter 25
In the CDMA reception signal and the FM reception signal converted by the above, only one of the signal components is selectively output to the next-stage reception-side variable amplifier circuit 26a in accordance with the setting mode. The reception-side variable amplifier circuit 26a amplifies the selectively input CDMA reception signal or FM reception signal and outputs the amplified signal to the QPSK demodulation circuit 27a. Q
The PSK demodulation circuit 27a converts the amplified received signal into a QPS
K demodulation is performed and output to the modem 3.

[0102] The control of whether to operate in either mode of the portable telephone CDMA and FM system is performed by the mode switching signal D _FM. Mode switching signal D
_{The FM} is represented by, for example, digital on / off signals of 0 and 1, and a mode changeover switch provided at the next stage of the CDMA band-pass filter 24 and the FM band-pass filter 25, and the reception circuit control unit 6 It is input to the circuit setting table 61.

The received signal input to modem 3 is input to low-pass filter 31 and wide-band low-pass filter 32. The low-pass filter 31 has, for example, a cutoff frequency of 615 in accordance with the CDMA system of North American specifications.
kHz, and among the received signals input,
Only the signal D2 of a predetermined frequency band required for communication is passed. The wideband low-pass filter 32 has, for example, a cutoff frequency set to a value higher than that of the low-pass filter 31 (for example, 2.5 MHz), and passes a signal D3 having a band wider than that of the low-pass filter 31.
The reception signal D2 that has passed through the low-pass filter 31 is input to the reception signal strength detection circuit 33 and the circuit setting table 61 of the reception circuit control unit 6. The reception signal D3 that has passed through the wideband low-pass filter 32 is input to the circuit setting table 61 of the reception circuit control unit 6. The received signal D2 that has passed through the low-pass filter 31 and the signal D3 that has passed through the wideband low-pass filter 32 are converted into digital signals by an A / D converter (not shown) and input to the circuit setting table 61 so that they can be digitally processed. You.

The reception intensity (signal level) of the reception signal D2 input to the reception signal intensity detection circuit 33 is detected. A signal indicating the reception strength detected by the reception signal strength detection circuit 33 is output to the comparison circuit 34. The comparison circuit 34 compares the received signal strength with the separately input strength reference data D11 and outputs a signal D1 indicating the difference. The signal D1 indicating the difference from the comparison circuit 34 is supplied to the circuit setting table 61 of the reception circuit control unit 6 and the addition circuit 63.
Is input to The signal D1 is converted into a digital signal by an A / D converter (not shown) and input to the circuit setting table 61 and the adding circuit 63 so that the signal D1 can be digitally processed. The signal D1 indicating the difference from the comparison circuit 34 is also output to the transmission output correction circuit 35.

The transmission output correction circuit 35 controls the gain of the transmission side variable amplification circuit 12 based on the signal D1 indicating the difference input from the comparison circuit 34 and the transmission output correction data D12 separately input. Note that the transmission output correction data D12 is data according to the line condition between the mobile phone and a base station (not shown). Also, the transmission output correction circuit 3
5 is controlled so that the modulated signal is inversely proportional to the level of the received signal, and the transmission output correction data D12
Variable amplifier circuit 12 on the transmission side so that control according to
_Is output by outputting the transmission side AGC voltage V _TX-AGC .

Circuit setting table 61 of receiving circuit control section 6
The signal indicating the difference from the comparator circuit 34 D1, signal D2 for detecting the level of the received signal, the signal for detecting the interference signal D3, the mode switching signal D _FM and transmit control signals D _TX is transmitted It is input as a signal indicating a communication factor such as the presence / absence of an operation and the presence / absence of a jamming radio wave.

The circuit setting table 61 includes communication factors such as the presence or absence of a transmission operation and the presence or absence of a jamming radio wave, and the operation of the low-noise amplifier 21a, the mixer 23a, the reception-side variable amplification circuit 26a and the QPSK demodulation circuit 27a in the reception circuit 2. The circuit setting data D10 for determining the operation state of the low noise amplifier 21a and the like in the reception system circuit 2 is output to the low noise amplifier 21a and the like in association with the state. Note that, as described above, the circuit setting table 61 stores, for example, table contents as shown in FIG.
The circuit setting table 61 includes, for example, a mode switching signal D _FM
There is input, among the stored table selects the table corresponding to the mode represented by the mode switching signal D _FM. Further, the circuit setting table 61, for example, depending on the presence or absence of transmission operation represented by the transmission control signal D _TX, the current flowing through the circuit such as the low-noise amplifier 21a outputs a circuit setting data D10 as optimized . The low noise amplifier 21a and the like in the receiving system circuit 2 change the operation state based on the operation state set by the input circuit setting data D10. The change in the operation state is performed so that the operation state of each unit is optimized according to the signal level of the received signal and the like, and the current consumption is reduced.

Gain correction table 62 of receiving circuit control section 6
, Temperature data from the temperature sensor 64 and circuit setting data D10 from the circuit setting table 61 are input. The gain correction table 62 outputs a gain correction value in synchronization with the circuit setting data D10 input from the circuit setting table 61. Further, the gain correction table 62 outputs a gain correction value corresponding to the temperature data representing the temperature around the circuit input from the temperature sensor 64 in order to perform the gain correction for the temperature. As described above, the gain correction table 62 stores, for example, table contents as shown in FIG. The addition circuit 63 calculates the reception-side AGC voltage V _RX-AGC obtained by adding the gain correction value output from the gain correction table 62 and the output signal D1 from the comparison circuit 34,
Output to the receiving-side variable amplifier circuit 26a. The gain of the reception-side variable amplifier circuit 26a is controlled by the input reception-side AGC voltage V _RX-AGC .

Next, the operation of each part of the receiving system circuit will be described.

First, the operation of the low noise amplifier 21a having the configuration shown in FIG. 3 will be described. In the low noise amplifier 21a having the configuration shown in FIG. 3, the power supply voltage Vcc is applied to the input terminal 72. The input terminal 71 receives an input signal LNA _IN , and the output terminal 73 outputs an output signal LNA _OUT . Resistor R5, transistor T2
The current proportional to the current flowing through the transistor T2 flows through the collector current Ic of the transistor T1 due to the operation of the current mirror circuit constituted by the resistors R0 to R3.

The switches S _{0 to} S of the switch section SW _1
3 is turned on or off according to the signal level of the received signal or the like according to the circuit setting data D10 output from the circuit setting table 61. In low-noise amplifier 21a shown in FIG. 3, the current flowing through the transistor T2 will vary according to the on / off state of the switches S ₀ to S _3, further current proportional to the current flowing through the transistor T2 of the transistor T1 It flows as a collector current Ic.

The on / off states of the switches S _{0 to} S ₃ are as follows.
The setting data portion D of the circuit setting data D10 shown in FIG.
data. Also, the switches S _{0 to} S
The relationship between the on / off state of ₃ and the collector current Ic of the transistor T1 is, for example, as shown in FIG. As shown in FIG. 4, for example, when only the switch S ₀ is on (S ₃ , S ₂ , S ₁ , S ₀ = ₀ , ₀ , ₀ , ₁ ), the value I ₀ is used as the collector current Ic. Current flows.
In comparison with this case, when all switches S ₀ to S ₃ is turned on _{(S 3, S 2, S} 1, S 0 = 1,1,1,
In 1), 15 times the current of the value I ₀ flows. In general, the operation of the high-frequency transistor is proportional to the current, the distortion performance (here third order distortion intercept point) becomes better, when all the switches S ₀ to S ₃ is turned on, the strain performance of one It will be better. However, the current consumption at this time is the largest.

The table contents of the circuit setting table 61 applied to the low noise amplifier 21a are, for example, as shown in FIG. The circuit setting table 61, (presence of transmission operation) on / off of the transmission, the state of the switch S ₀ to S ₃ of the low-noise amplifier 21a corresponding to the signal level of the presence of the interfering signal and the received signal is associated with each It is memorized. As described with reference to FIG.
In the case of “jamming signal: present” and “transmitting: yes, jamming signal: no”, a high input intercept point is required. In this embodiment, as shown in the table of FIG. “Transmission: yes, jamming signal: yes” (TX: 1,
UDS: 1) and “transmission: present, jamming signal: no” (T
X: 1, UDS: 0), the switches S _{0 to} S ₃
Is set to a state close to ON, and the transistor T
1 increases the operating current.

Also, as described with reference to FIG.
In the case of “transmission: no, jamming signal: present” and “transmission: no, jamming signal: no”, the input intercept is not so high.
Since points are not required, in the present embodiment, as shown in the table of FIG. 5, “transmission: no, interference signal: presence” (TX: 0, UDS: 1) and “transmission:
No, interfering signal: No "(TX: 0, UDS: 0 ) in the case of the setting such that only the switch S _1, S ₀ which is represented by a low bit of the switches S ₀ to S ₃ is turned on Then, the operating current of the transistor T1 is reduced. In a general mobile phone, most of the standby time is in a transmission-off state. Therefore, when the above-described operation setting is performed in the low-noise amplifier 21a, the operating current of the low-noise amplifier 21a during the standby time can be reduced as compared with the related art. In addition, the standby time can be made longer than before.

In the low-noise amplifier 21a, the time required to change the operation state is changed according to the change in the operation state. More specifically, when the performance is relatively improved (when the operation state is such that a relatively large amount of current flows), the circuit state is changed in a short time, and conversely,
When the performance is relatively deteriorated (when the operation state is such that a relatively small amount of current flows), the operation state is changed in a time that is, for example, 10 to 1000 times longer than the time when the performance is improved. Do. More specifically, for example, FIG.
As shown in the above, when changing to an operation state in which a relatively large amount of current flows, for example, “transmission: no, interference signal:
From "No" (TX: 0, UDS: 0) to "Transmission: Yes,
The operation switching time of the circuit when changing to the state of "jam signal: present" (TX: 1, UDS: 1) is set to "1". On the other hand, when changing to an operation state in which a relatively small amount of current flows, for example, the state of “transmission: present, interference signal: present” (TX: 1, UDS: 1) is changed to “transmission:
When the state is changed to "No, no interference signal: No" (TX: 0, UDS: 0), the operation switching time is increased by 100 times. In this way, by changing the time required to change the operation state according to the difference in the change in the operation state, the circuit is simply changed in response to the change in the reception state, as in the case where the circuit is simply changed. Can be prevented from oscillating.

Table contents of the gain correction table 62 in which the circuit setting table 61 for the low-noise amplifier 21a is associated with the temperature data from the temperature sensor 64 are as shown in FIG. 6, for example. Low noise amplifier 21a
The contents of the gain correction table 62 relating to FIG.
As shown in, for example, when all of the switches S ₀ to S ₃ is turned on _{(S 3, S 2, S} 1, S 0 = 1,1,1,
1) is set such that the gain correction value is lower than when only the switches S ₁ and S ₀ represented by low bits among the switches S _{0 to} S ₃ are in the ON state. In addition, the contents of the gain correction table 62 for the low noise amplifier 21a are set such that, for example, the gain correction value is higher when the temperature is high than when the temperature is low.
The gain correction table 62 outputs the gain correction value determined based on the contents of the table to the adding circuit 63.
The gain correction value output to the adding circuit 63 is
Is added to the output signal D1 from the
_The signal is output to the reception-side variable amplifier circuit 26a as _RX-AGC .
The receiving-side variable amplifier circuit 26a receives the input receiving-side AGC
The gain is controlled by the voltage V _RX-AGC .

Next, the operation of the mixer 23a shown in FIG. 9 will be described.

In the mixer 23a having the configuration shown in FIG. 9, an RF signal RF _IN is input via input terminals 76 and 77.
The local oscillation signal OSC _IN from the local oscillator 16 is input via the input terminals 74 and 75. The RF signal RF _IN input to the mixer 23a is mixed with the local oscillation signal OSC _IN, and the difference component (frequency difference) is supplied to the IF output signal I / O via the buffer amplifier transistors T27 and T28.
It is output from the output terminals 79 and 80 as F _OUT .

In the mixer 23a, the mixer currents I ₁ and I ₂
And buffer amplifier currents I ₃ and I ₄ are equal to resistances R0 to R4.
3. It depends on a bias voltage generating section composed of a resistor R27 and a transistor T31. In the mixer 23a, when the operating current is increased, the third-order distortion tends to be excellent. In the present embodiment, the switch unit SW1
_If high distortion performance is required by selectively turning on / off the switches S _{0 to} S ₃ of the _MIX , the currents I ₁ and I ₂ are set to large values, and high distortion performance is not required. In such a case, the currents I ₁ and I ₂ are set to decrease. For example, when the transmission is without interference signal off, the distortion characteristics, so there is no problem even if low, to selectively turn on / off the switch S ₀ to S ₃ to lower the current.
Specifically, when the distortion characteristic may be a value lower by 3 dB, the switches S ₀ to S _{0 are set} so that the mixer current is reduced to １ ／.
Selectively turn on / off the S _3.

In the mixer 23a, when the current values of the currents I ₁ and I ₂ are reduced, excellent distortion characteristics are not required. Therefore, the current values of the currents I ₃ and I ₄ can be reduced. Therefore, in the mixer 23a, the currents I ₃ and I _3
4 is controlled in conjunction with the currents I ₁ and I ₂ . In this case, the voltage of the resistor R30 is equal to the voltage of the transistor T2.
1. Supplied from the voltage that determines the bias of T22. The table contents of the circuit setting table 61 applied to the mixer 23a are basically the same as the table contents applied to the low noise amplifier 21a shown in FIG. In addition, the table contents of the gain correction table 62 for such a mixer 23a are different from each other, though the detailed set values are different.
Basically, it is almost the same as the contents of the table relating to the low noise amplifier 21a shown in FIG.

Next, the operation of the mixer 23a shown in FIG. 10 will be described.

The mixer 23a having the configuration shown in FIG.
In relation to the values of the operating currents I ₁ and I ₂ , in terms of the mixer conversion gain and the DC voltage for connection to the next stage,
It is desirable to variably set the resistances R28 and R29, which are load resistances, according to communication factors. Therefore, the mixer 23a shown in FIG. 10, the current I ₁ in the switch section SW1 _MIX,
When you change the I _2, resistor shown in FIG. 9 R28, R2
The optimum value of the load resistance portion corresponding to 9 is selected and set by the switch unit SW2 and the switch unit SW3.
For example, when the currents I ₁ and I ₂ are large, the resistances R0 to R
Each switch is selected and set so that the combined resistance of No. 3 becomes a small value. For example, when the currents I ₁ and I ₂ are small, each switch is selected and set so that the combined resistance of the resistors R0 to R3 has a large value.

In the mixer 23a shown in FIG. 10, the emitter negative feedback resistors of the transistors T21 and T22 (FIG. 9)
Corresponds to the resistor R21. ) Relates to distortion characteristics, noise figure NF (Noise Figure), and gain. For example, when the resistance value of the negative feedback resistor is increased, the gain decreases and the noise figure NF deteriorates.
The strain characteristics are improved. Conversely, when the resistance value of the negative feedback resistor is small, the distortion characteristic is poor, but the gain is high and the noise figure NF is good. Therefore, when excellent distortion characteristics are required, a value having a large resistance value is selected at the expense of gain and noise figure NF (the sensitivity is deteriorated). In the present embodiment, when a high distortion characteristic is required, the negative feedback resistance is increased, and when a high distortion characteristic is not required, the switch unit SW4 is selectively set so as to reduce the negative feedback resistance. . In other words, by the switch unit SW4,
It allows optimization of gain, noise figure NF and distortion. The setting conditions for the switch SW4 are stored in the circuit setting table 61 and the gain correction table 62 in advance.

Next, the operation of the receiving-side variable amplifier circuit 26a shown in FIG. 12 will be described.

The receiving-side variable amplifier circuit 26a shown in FIG.
In this case, the power supply voltage Vcc is applied via the input terminal 81. In the reception-side variable amplifier circuit 26a, the input signal AGC _IN is input to the transistors T41 and T42, and the AGC voltage V _RX-AGC from the reception circuit control unit 6 is input to the transistor T51 via the input terminal 82. You. Furthermore,
In the receiving side variable amplifier circuit 26a, an output signal AGC _OUT is output via the output terminal 83.

AG provided with transistors T43 to T46
In the C operation part 26-3, the transistors T43 and T43
The AGC function is realized by changing the ratio of the current flowing through 44. The same applies to the current ratio flowing through the transistors T45 and T46. For example, the transistor T
When the same value as the current flowing through the transistor 41 flows through the transistor T44 (the current of the transistor T43 is 0), the gain is maximum. Further, when a current flows through the transistor T43, an operation is performed in which the gain is reduced in accordance with a current ratio flowing through the transistors T43 and T44.

The current flowing through the transistors T47 and T48 is determined by the constant current circuit 26-2 including the transistors T49 and T50 and the resistors R45 and R46. The currents of the transistors T43 to T47 are controlled by transistors T51 and T52 forming a differential amplifier circuit and their output buffer transistors T53 and T54.

The AGC voltage V _RX-AGC is input to one base of the transistors T51 and T52 forming a differential amplifier circuit, and changes the current of the transistors T51 and T52. The change in the current is given to transistors T43 to T46 via transistors T53 and T54.

In the AGC circuit portion composed of the transistors T41 to T46, the distortion characteristic depends on the current determined by the transistors T41 and T42 and the resistors R43 and R44. For example, when the current flowing through the transistors T41 and T42 is large, the distortion characteristic of the AGC circuit indicates a high (good) value. In the present embodiment, when the reception state does not require high distortion characteristics, the switch unit SW
1 _AGC switch S ₀ to S _3, the resistors R0 to R3, is operated to lower the current of the transistor T41, T42. Note that the receiving side variable amplifier circuit 2 shown in FIG.
The table contents of the circuit setting table 61 applied to 6a are basically different from those in FIG.
The table contents applied to the low noise amplifier 21a shown in FIG. Also, the table contents of the gain correction table 62 relating to such a reception-side variable amplifier circuit 26a are different from each other, though the detailed set values are different.
Basically, it is almost the same as the contents of the table relating to the low noise amplifier 21a shown in FIG.

In the receiving side variable amplifier circuit 26a, when the current of the transistors T41 and T42 is changed, the transistors T43 and T44 or the transistors T45 and T4
It is also necessary to change the voltage for AGC control input to the base of No. 6 according to the change in the current of the transistors T41 and T42. This is because the transistors T55,
The constant current circuit composed of T56 and resistors R47 and R48 has the same voltage (resistors R0 to R3, transistor T59, resistor R59) as that determining the current of transistors T41 and T42.
53 circuit).

The current of the transistors T47 and T48 forming the output buffer amplifier is obtained by connecting the bases of the transistors T49 and T50 which determine the current to the transistor T4.
1, connected in parallel to the bias voltage of T42 so as to prevent unnecessary current from flowing.

Next, the QPSK demodulation circuit 2 shown in FIG.
The operation of 7a will be described.

The local oscillation signal from the local oscillator 71 is directly input to the mixer circuit 27-2, and is also input to the mixer circuit 27-3 via the 90-degree phase shift circuit 72. The IF signal IF _IN is input to the transistors T65 and T66 of the mixer circuit 27-2 and the transistors T75 and T76 of the mixer circuit 27-3 via the input terminals 91 and 92. The buffer amplifier 3 has an output terminal 93,
An I signal I _{OUT of} QPSK is output via 94, and a Q signal Q _OUT is output via output terminals 95 and 96.

The operating current in the mixer circuits 27-2 and 27-3 and the operating current of the buffer amplifier 27-1 are determined by the switch SW1 _QPSK , the resistors R0 to R3, and the transistor T67.
And selecting, setting the switches S ₀ to S ₃ of the switch SW1 _QPSK in the bias voltage generating unit including a resistor R66. For example, in the signal reception state, if it does not need a high strain characteristic by setting the switches S ₀ to S _3, the operating current and the operating current of the buffer amplifier 27-1 of the mixer circuit 27-2,27-3 Lower.

The settings of the switches S _{0 to} S ₃ in the switch section SW 1 _QPSK are set in the circuit setting table 61.
And the gain correction table 62.
Here, the contents of the circuit setting table 61 applied to the QPSK demodulation circuit 27a are basically the same as the contents of the table applied to the low noise amplifier 21a shown in FIG. It is.
The contents of the gain correction table 62 for such a QPSK demodulation circuit 27a are basically the same as the contents of the table for the low noise amplifier 21a shown in FIG. 6, although the detailed set values are different.

As described above, according to the present embodiment, low-noise amplifier 21a, mixer 23a, reception-side variable amplification circuit 26a and QPSK in reception system circuit 2 are provided.
The operation state of the demodulation circuit 27a is changed according to a communication factor including at least one of the presence or absence of a transmission operation, the presence or absence of a jamming signal, and the signal level of a received signal. Thus, the operation state can be changed so that power consumption is reduced. This makes it possible to reduce the consumption of the battery, which is a power supply source, as compared with a conventional mobile phone, so that the so-called standby time and talk time can be made longer than before, and the frequency of battery replacement can be increased. Can be reduced. Further, for example, the operation state can be changed according to the difference between the modes of the CDMA system and the FM system.
Power consumption in the mode can be reduced.

Further, according to the present embodiment, the operation state to be changed by reception system circuit 2 is determined according to the table contents of circuit setting table 61 and gain correction table 62, and the contents of the table can be changed from outside. Therefore, the low noise amplifier 21 in the reception system circuit 2
a, mixer 23a, receiving-side variable amplifier circuit 26a and Q
The performance of each part of the PSK demodulation circuit 27a can be easily changed and set only by changing the contents of the circuit setting table 61 and the gain correction table 62. This allows
For example, when the receiving circuit 2 is manufactured by an IC, even if a difference in characteristics occurs between elements in the circuit, the table contents of the circuit setting table 61 and the gain correction table 62 are changed according to the difference in characteristics of the elements. Since it can be changed, the yield at the time of manufacturing the IC can be improved.
Further, it is possible to cope with the manufacture of a high-frequency system IC integrated on a large scale.

Further, according to the present embodiment, low-noise amplifier 21a, mixer 23a, reception-side variable amplification circuit 26a and QPSK demodulation circuit 27a in reception system circuit 2 are provided.
The time required to change the operating state of the device is changed in accordance with the difference in the operating state, so that, for example, a situation in which the circuit oscillates as the operating state changes is prevented. can do.

The present invention is not limited to the above embodiment, but can be variously modified. For example, in the above embodiment, a case has been described in which operation is performed in the dual mode of the CDMA system and the FM system.
The present invention can also be applied to a case in which only one of the MA system and the FM system operates. Also CD
The present invention is not limited to the MA system and the FM system, and can be applied to, for example, a TDMA system receiving circuit and a communication device.

[0139]

As described above, claims 1 to 9 are described.
According to the receiving device of any one of the above or the communication device of the tenth aspect, the communication state including at least one of the presence / absence of a transmission operation, the presence / absence of jamming radio waves, and the signal level of a reception signal, of the reception circuit. Since it is possible to change according to factors, for example, depending on the presence or absence of jamming radio waves,
There is an effect that the operation state can be changed so that power consumption is reduced.

In particular, according to the receiving device of the fourth aspect,
It has an association table that associates the communication factor with the operation state of the reception circuit, determines the operation state to be changed by the reception circuit according to the table contents of the association table, and enables the table contents of the association table to be changed from outside. , The performance of the receiving circuit part can be easily changed,
For example, there is an effect that the operation can be optimized according to the variation in the characteristics of the devices constituting the receiving circuit.

According to the receiving apparatus of the present invention, the time required to change the operating state of the receiving circuit is changed in accordance with the change in the operating state. This has the effect of preventing a situation where the receiving circuit performs an oscillating operation as the state is changed.

In particular, according to the receiving device of the ninth aspect, the communication factor includes a change in the surrounding temperature. For example, according to the device characteristics with respect to the temperature change of each device constituting the receiving circuit. The effect that operation can be performed is produced.

[Brief description of the drawings]

FIG. 1 is a block diagram showing a configuration of a high-frequency stage of a mobile phone as a communication device according to an embodiment of the present invention.

FIG. 2 is an explanatory diagram showing an example of a data structure of circuit setting data input to a receiving system circuit in the mobile phone shown in FIG.

FIG. 3 is a circuit diagram showing a configuration example of a low noise amplifier in the mobile phone shown in FIG.

4 is an explanatory diagram showing an example of a relationship between an operation changeover switch unit in the low noise amplifier shown in FIG. 3 and a current flowing in a circuit of the low noise amplifier.

FIG. 5 is an explanatory diagram showing an example of a circuit setting table applied to the low noise amplifier shown in FIG.

FIG. 6 is an explanatory diagram showing an example of a gain correction table applied to the low noise amplifier shown in FIG.

7 is an explanatory diagram showing a switching time of an operation state in the low noise amplifier shown in FIG.

FIG. 8 is another explanatory diagram showing a switching time of an operating state in the low noise amplifier shown in FIG. 3;

FIG. 9 is a circuit diagram showing one configuration example of a mixer in the mobile phone shown in FIG.

FIG. 10 is a circuit diagram showing another configuration example of the mixer in the mobile phone shown in FIG.

11 is an explanatory diagram showing an example of a relationship between an operation changeover switch unit in the mixer shown in FIG. 10 and a current flowing in a circuit of the mixer.

FIG. 12 is a circuit diagram illustrating a configuration example of a reception-side variable amplifier circuit in the mobile phone illustrated in FIG. 1;

13 is a circuit diagram showing a configuration example of a QPSK demodulation circuit in the mobile phone shown in FIG.

FIG. 14 is a block diagram showing a circuit configuration of a high frequency stage of a conventional general mobile phone.

FIG. 15 is an explanatory diagram showing signal interference called intermodulation spurious interference in a receiving circuit of a conventional mobile phone.

FIG. 16 is an explanatory diagram showing signal interference called single tone sensitivity suppression in a receiving circuit of a conventional mobile phone.

FIG. 17 is an explanatory diagram showing sensitivity suppression by a transmission signal, which occurs in a receiving circuit of a conventional mobile phone.

FIG. 18 is a characteristic diagram for describing a distortion characteristic required for a receiving circuit of a conventional mobile phone.

[Explanation of symbols]

D _FM mode switching signal D _TX transmission control signal D10 Circuit setting data SW1 switch unit 1 transmission system circuit 2 reception system circuit 3 modem 4 duplexer 5 shared antenna 6 reception circuit control unit 16 local oscillator 21 low noise amplifier circuit unit 21a low noise amplifier (LNA) ) 21b, 23b, 26b, 27b Latch circuit 23 Mixer circuit unit 23a Mixer 24 Bandpass filter for CDMA 25 Bandpass filter for FM 26 Receiving side variable amplifying circuit unit 26a Receiving side variable amplifying circuit (RX-AGCAMP) 27 QPSK demodulation circuit Section 27a QPSK demodulation circuit 31 Low-pass filter 32 Wide-band low-pass filter 33 Received signal strength detection circuit (RSSI) 61 Circuit setting table 62 Gain correction table 63 Addition circuit 64 Temperature sensor

Claims (10)

[Claims] An apparatus for receiving a signal applied to a communication device that transmits and receives a signal, wherein the communication device includes at least one of the presence or absence of a transmission operation in the communication device, the presence or absence of a jamming wave, and the signal level of a received signal. A receiving device comprising a receiving circuit capable of changing an operation state according to a factor. 2. The apparatus according to claim 1, further comprising: a determination unit configured to determine an operation state to be changed by the reception circuit based on the communication factor, wherein the reception circuit operates based on the operation state determined by the determination unit. The receiving apparatus according to claim 1, wherein the state is changed. 3. The method according to claim 2, wherein the determining unit has an association table that associates the communication factor with an operation state of the receiving circuit.
3. The receiving apparatus according to claim 2, wherein an operation state to be changed by the receiving circuit is determined according to table contents of the association table. 4. The receiving device according to claim 3, wherein the contents of the association table are changeable from outside. 5. The receiving device according to claim 1, wherein said receiving circuit includes a circuit for processing a high-frequency signal. 6. The receiving apparatus according to claim 1, wherein said receiving circuit is always in operation to detect a signal level of a received signal regardless of whether or not there is substantial communication. 7. The receiving apparatus according to claim 1, wherein the receiving circuit changes an operation state such that current consumption according to the communication factor enough to satisfy required performance is performed. 8. The receiving apparatus according to claim 1, wherein the receiving circuit changes a time required to change the operation state according to a difference in change in the operation state. 9. The receiving apparatus according to claim 1, wherein the communication factor includes a change in ambient temperature. 10. A transmission circuit that performs signal processing on a transmission signal, and sets an operation state according to a communication factor including at least one of the presence or absence of a transmission operation in the transmission circuit, the presence or absence of interfering radio waves, and the signal level of a reception signal. A communication device comprising: a reception circuit that can be changed.