EP3214695A1 - Mobile radio antenna - Google Patents

Abstract

The present invention relates to a mobile radio antenna, in particular for a mobile radio base station, with at least one dipole radiator and with a disposed on the dipole radiator dielectric body, which is characterized in that the height H of the dielectric body in the main emission at least 30% of maximum thickness D of the dielectric body in a cross section perpendicular to the main emission direction.

Description

The present invention relates to a mobile radio antenna having a dipole radiator and having a dielectric body disposed on the dipole radiator. Furthermore, the present invention relates to a mobile radio antenna arrangement having a plurality of antennas, with a first subgroup of first antennas and a second subgroup of second antennas. Each of these is preferably a mobile radio antenna for use at a mobile radio base station.

The use of dielectric rod antennas has hitherto been known only from the field of radar technology.

So it is from the publication " Grzegorz Adamiuk et al., IEEE transactions on antennas and propagation, Volume 56, No. 2, February 2010 a UWB antenna is known in which a dual-polarized, composed of two slit radiator radiator is disposed in a dielectric body in the form of a cone.

The publication " To Mario Leib et al., IEEE Transactions on Microwave Theory and Techniques, Vol. 59, No. 4, pp. 1082-1089, April 2011 also shows a UWB antenna with a rod dielectric radiator powered by a slot antenna.

The publications " Wideband Dual-Circular-Polarized Dielectric Rod Antenna for Applications in V-band Frequencies ", MW Rousstia et al., Proceedings of ICT.OPEN 2013, 27-28 November 2013, Eindhoven, Eindhoven University of Technology, 2013 , " Rousstia et al., Proceedings of the 10th European Radar Conference, (EuRAD), 9-11 October 2013, Nuremberg, IEEE, pages 359-362 , such as " NEW METHOD FOR ULTRA WIDE BAND AND HIGH GAIN RECTANGULAR DIELECTRIC ROD ANTENNA DESIGN ", Jingping Liu et al., Progress In Electromagnetics Research C, Vol. 36, pp. 131-143, 2013 also show the use of dielectric rod-shaped bodies in the field of radar technology.

In the mobile sector, it is only known in array antennas from a plurality of dipole radiators to arrange thin dielectric plates with low relative permittivity on the individual dipole radiators.

Furthermore, in the mobile sector dielectric resonator antennas are known in which the dielectric body itself is used as a radiator, which is usually fed via a slot.

The object of the present invention is to improve the properties of mobile radio antennas and in particular their applicability in mobile radio antenna arrangements with high single radiator density.

This object is achieved by a mobile radio antenna according to claim 1 and by a mobile radio antenna arrangement according to claim 7. Advantageous embodiments of the present invention are the subject of the dependent claims.

In a first aspect, the present invention shows a mobile radio antenna, in particular a mobile radio base antenna for a mobile radio base station, with at least one dipole radiator and with a dielectric body arranged on the dipole radiator. The present invention is characterized in that the height H of the dielectric body in the main emission direction is at least 30% of the maximum thickness D of the dielectric body in a cross section perpendicular to the main emission direction.

As a result of the dimensioning according to the invention, the dielectric body acts as a waveguide for the mobile radio signals radiated by the dipole radiator and thereby shifts the radiation plane of the dipole radiator. The displacement of the radiation plane in particular means changing and / or shifting the effective radiation aperture and / or shifting the phase center of the radiation in the main emission direction. This enables a multiplicity of new fields of application of the combination of dipole radiator and dielectric body, in particular in the area of mobile radio antenna arrangements with a plurality of antennas.

In this case, the height H of the dielectric body is preferably at least 50% of the maximum thickness D of the dielectric body, more preferably the height H of the dielectric body is at least 70% of the maximum thickness D of the dielectric body. This results in a correspondingly larger shift in the abstraction level.

In possible embodiments, the height H of the dielectric body may be more than 85% of the maximum thickness D of the dielectric body, or even more than 150%. At the top, the height H of the dielectric body is at least not limited in principle. However, with respect to the intended application, H <6 * D, more preferably H <3 * D, is preferred.

Preferably applies to antennas with a horizontal half width between 55 ° and 100 °, in particular for antennas with a horizontal half width of 65 ° + - 10 ° or 90 ° + - 10 ° while H <3 * D. Alternatively or additionally applies to antennas with a horizontal half-width between 23 ° and 43 ° while H <6 * D and / or H> 2 * D. This takes into account the increasing height bundling effect of the dielectric body.

Furthermore, it is conceivable for beamforming and / or beamshaping applications in which a plurality of antennas can be flexibly interconnected and / or operated separately, to use dielectric bodies with different heights for the individual antennas.

According to the invention, the height H of the dielectric body in the main emission direction of the dipole radiator is measured. The thickness D is in the cross section of the dielectric body, d. H. measured in a plane perpendicular to the main emission direction of the dipole radiator. The dielectric body does not have to have a symmetrical design. The height of the dielectric body is considered to be the longest extent of the dielectric body in the main emission direction of the dipole radiator, and the thickness of the dielectric body in a height plane to be the longest extent in the cross section, i. H. in a plane perpendicular to this main emission direction. The maximum thickness D of the dielectric body is thus the greatest thickness in a cross section of the dielectric body considered over all height levels.

The mobile radio antenna according to the invention is preferably connectable via signal lines to a mobile radio base station in order to receive and / or transmit mobile radio signals. In this case, the mobile radio antenna according to the invention is preferably used in a frequency band which is in the range between 100 MHz and 10 GHz, preferably between 500 MHz and 6 GHz. Alternatively or additionally, the antenna may have a resonant frequency range which is between 100 MHz and 10 GHz, preferably between 500 MHz and 6 GHz. In principle, they are Higher frequencies are also conceivable, in particular if the dipole radiator is a printed circuit dipole.

The dielectric body according to the invention may initially be made of any dielectric material. For example, the dielectric body may be made of a homogeneous dielectric material. For example, the dielectric body may be a solid plastic body.

Alternatively, however, the dielectric body may be made of a first material having a higher relative permittivity and a second material having a lower relative permittivity. For example, the first material may be embedded as granules in the second material or vice versa. Alternatively, the second material may be gaseous and bubble-shaped embedded in the first material. In particular, air bubbles may be provided in the first material.

Regardless of the material used, the dielectric body preferably has an effective relative permittivity ∈ _r of more than 2, more preferably of more than 2.5. The effective relative permittivity ε _r may, for example, be between 2 and 4, more preferably between 2.5 and 3.5.

For example, it can be used solid material with a relative permittivity in this area, or material with a higher relative permittivity and embedded air holes. Furthermore, for example, material having a higher relative permittivity than granules may be embedded in a material having a lower relative permittivity.

The material of the dielectric body can have an approximately constant permittivity, or a gradient of permittivity.

The dielectric body preferably has an axis of symmetry pointing in the main emission direction. This results in a particularly uniform far-field diagram.

In this case, the symmetry is particularly preferably an axial symmetry and / or a rotational symmetry. In this case, the dielectric body is particularly preferably rotationally symmetrical with respect to an axis of symmetry aligned in the main emission direction of the dipole radiator, ie. H. it has a round cross-section. In this case, the maximum thickness D corresponds to the maximum diameter of a cross section of the dielectric body.

Alternatively, the dielectric body can be axially symmetrical with respect to an axis of symmetry aligned in the main emission direction of the dipole radiator, for example with a cross-sectional area in the form of a preferably regular polygon, for example a quadrangle or square. In this case, the maximum thickness D corresponds to the maximum diagonal of a cross section of the dielectric body. The dielectric body preferably has a rod region. The thickness of the dielectric body deviates in this rod region preferably by a maximum of 30% and more preferably by a maximum of 15% from the maximum thickness D. Therein, the thickness of the dielectric body in a height plane is understood to be its greatest extent in this height level. Alternatively or additionally, the cross-sectional area of the dielectric body in the rod region preferably deviates by a maximum of 30% and more preferably by a maximum of 15% from the maximum cross-sectional area of the dielectric body.

The dielectric body preferably has, at least in the rod region in each height plane, a cross section which consists of a circle or a preferably regular polygon, eg a quadrangle, hexagon, octagon, etc. In principle, however, any shape with waveguide function and / or Aperturverschiebungsfunktion is conceivable.

Particularly preferably, the dielectric body in the rod region has a thickness which is constant in the height direction and / or a cross section which remains constant in the height direction. The rod region has in particular a cylindrical shape, preferably a circular cylindrical shape or cuboidal shape.

Preferably, the height of the rod region is between 50 and 100%, more preferably between 65 and 100% of the height H of the dielectric body.

Alternatively or additionally, the dielectric body may have a lens area. In the lens region, the dielectric body preferably has a cross section which changes in the height direction. Preferably, the cross-sectional area of the dielectric body in the lens region changes by at least 30% and more preferably by at least 50% with respect to the maximum cross-sectional area of the dielectric body.

More preferably, the lens portion has the shape of a truncated cone or a truncated counter-cone or a truncated pyramid or a truncated counter-pyramid. Preferably, the smallest diameter or the smallest diagonal of the cut-off cone or counter-cone or the cut pyramid or counter-pyramid is between 30 and 80% of the maximum diameter or the maximum diagonal of the cut cone or counter-cone or the truncated pyramid or counter-pyramid preferably between 40 and 70%.

The height of the lens region is preferably between 5% and 50%, preferably between 10% and 35%, of the height H of the dielectric body.

The dielectric body preferably has both a rod region and a lens region. In this case, the lens region is preferably arranged on the side of the rod region facing away from the dipole radiator. Alternatively, the dielectric body may have only a rod portion having a slightly varying elevation in the height direction.

Regardless of the specific shape of the dielectric body, it is preferably arranged in the main emission direction on the dipole radiator. Further preferably, no dielectric body is provided in the area of the dipole radiator itself, i. H. the dipole radiator is not embedded in the dielectric body but arranged in the main emission direction on the dielectric body.

In this case, according to the invention, the dielectric body can be placed directly on the dipole radiator and in particular can be in contact therewith, or can be arranged over a narrow gap of preferably not more than 2 mm away from it.

If the dielectric body has an axis of symmetry, this preferably coincides with the axis of symmetry of the dipole radiator. The axis of symmetry of a dipole radiator is understood to be an axis extending in the main emission direction, with respect to which the dipole segments forming the dipole radiator are arranged symmetrically.

The dipole radiator according to the invention is preferably a dual-polarized dipole radiator. The inventors have recognized that a dielectric body can be used as a waveguide for both polarizations of such a radiator. Preferably, the two polarizations of the radiator are orthogonal to one another and / or have separate ports for the supply of mobile radio signals.

Preferably, the two dipoles of the dual-polarized dipole radiator have the same axis of symmetry, wherein the two dipoles are preferably arranged crosswise with respect to the common axis of symmetry. For example. it can be a dipole square.

The dipole radiator preferably has a base region which extends in the main emission direction and dipole segments arranged on the base region, which preferably extend perpendicular to the main emission direction.

The dipole radiator used according to the invention may comprise one or more additional radiators, which may also be based on other radiating principles. In particular, one or more additional radiators can be integrated in the dipole radiator. For example. For example, the dipole radiator can have one or more slots, which act as slot radiators, so that the dipole radiator used according to the invention is electrically a combination of dipole radiator and slot radiator.

und/oder $$0,5*\frac{\lambda }{\sqrt{\pi \left({\epsilon }_r-1\right)}}\le \mathrm{D}\le 2,5*\frac{\lambda }{\sqrt{\pi \left({\epsilon }_r-1\right)}}\mathrm{.}$$

In a preferred embodiment of the present invention, the following relationship exists between the maximum thickness D and the height H of the dielectric body, the wavelength λ of the center frequency of the lowest resonance frequency range of the antenna and the relative permittivity ε _{r of} the dielectric body: $$0.5*\frac{\lambda }{\sqrt{\pi \left({\epsilon }_r-1\right)}}\le \mathrm{H}$$

and or $$0.5*\frac{\lambda }{\sqrt{\pi \left({\epsilon }_r-1\right)}}\le \mathrm{D}\le 2.5*\frac{\lambda }{\sqrt{\pi \left({\epsilon }_r-1\right)}}\mathrm{,}$$

und/oder $$0,75*\frac{\lambda }{\sqrt{\pi \left({\epsilon }_r-1\right)}}\le \mathrm{D}\le 2,5*\frac{\lambda }{\sqrt{\pi \left({\epsilon }_r-1\right)}}\mathrm{oder}\le 1,25*\frac{\lambda }{\sqrt{\pi \left({\epsilon }_r-1\right)}}\mathrm{.}$$

Particularly preferred is the following relationship: $$0.75*\frac{\lambda }{\sqrt{\pi \left({\epsilon }_r-1\right)}}\le \mathrm{H}$$

and or $$0.75*\frac{\lambda }{\sqrt{\pi \left({\epsilon }_r-1\right)}}\le \mathrm{D}\le 2.5*\frac{\lambda }{\sqrt{\pi \left({\epsilon }_r-1\right)}}\mathrm{or}\le 1.25*\frac{\lambda }{\sqrt{\pi \left({\epsilon }_r-1\right)}}\mathrm{,}$$

bevorzugt $$\mathrm{D}\le 1,25*\frac{\lambda }{\sqrt{\pi \left({\epsilon }_r-1\right)}}\mathrm{.}$$

Preferably applies to antennas with a horizontal half width between 55 ° and 100 °, in particular for antennas with a horizontal half width of 65 ° + - 10 ° or 90 ° + - 10 ° $$\mathrm{D}\le 1.5*\frac{\lambda }{\sqrt{\pi \left({\epsilon }_r-1\right)}}.$$

prefers $$\mathrm{D}\le 1.25*\frac{\lambda }{\sqrt{\pi \left({\epsilon }_r-1\right)}}\mathrm{,}$$

Alternatively or additionally applies to antennas with a horizontal half width between 23 ° and 43 ° or for antennas with a relative bandwidth of more than 40% $$\mathrm{D}\le 2.5*\frac{\lambda }{\sqrt{\pi \left({\epsilon }_r-1\right)}}\mathrm{,}$$

This takes into account that for a very high concentration or bandwidth, a larger diameter multiplier may be needed compared to the wavelength.

In the context of the present invention, a resonant frequency range refers to a coherent frequency range of the radiator which has a return loss of better than 6 dB or better 10 dB or better 15 dB. The selected limit value of the return loss depends on the specific application of the antenna. The center frequency is defined as the arithmetic mean of the highest and lowest frequencies in the resonant frequency range.

The resonant frequency range and thus the center frequency are determined according to the invention preferably with respect to the impedance position in the Smith chart, assuming subsequent elements for optimal impedance matching and / or impedance transformation.

In the context of the use of the antenna according to the invention, the lowest resonant frequency range is preferably understood to be the lowest resonant frequency range of the antenna used for transmitting and / or receiving.

It has been found that a particularly effective shift of the Abstrahlebene can be achieved by the above dimensions, since the dielectric body works particularly well as a waveguide.

The directivity of the dielectric body can be influenced by the use of different body shapes and sizes. Furthermore, a combination with a conductive and / or metallic element is conceivable in order to influence the properties of the antenna.

According to the invention, a conductive and / or metallic element is preferably arranged in and / or on the dielectric body. In particular, the bundling effect can be influenced by such metallic elements.

In a first variant, the conductive and / or metallic element may be a coating of an inner or outer surface of the dielectric body. In a second variant, it may be a conductive and / or metallic disk arranged in or on the dielectric body. Both variants can be combined with each other.

Alternatively or additionally, it can be provided that the conductive and / or metallic element surrounds an outer circumference of the dielectric body. In particular, this may be a metallization of the outer circumference of the dielectric body. Alternatively, the conductive and / or metallic element may extend in a plane perpendicular to the main radiation direction. Particularly preferred in this case, a metallic disc is used, which extending in a plane perpendicular to the main radiation direction of the dipole radiator. Such a metallic disc can be arranged, for example, between a rod part and a lens part of the dielectric body.

The conductive and / or metallic element can be used in particular to improve the bundling effect in frequency ranges in which the bundling effect of the dielectric body is less strong.

According to the invention, the conductive and / or metallic element has a bundling effect, which is maximal for a frequency f _met . Furthermore, the dielectric body preferably has a bundling effect, which is maximal for a frequency f _diel . According to the invention, the frequencies f _met and f _{diel differ here} . The bundling effect of the conductive and / or metallic element and the bundling effect of the dielectric body are thereby maximum for different frequency range, so that the far field characteristics of the antenna according to the invention are improved by the combination of dielectric body and conductive and / or metallic element over a wider frequency range.

Preferably, the frequency f _{met is} smaller than the frequency f _diel . The conductive and / or metallic element is thus optimized for smaller frequencies, the dielectric body for larger frequencies.

Alternatively or additionally, the frequency f _{met may be} smaller than the center frequency f _{res of} the lowest resonance frequency range of the antenna, and the frequency f _diel greater than this center frequency f _res .

Furthermore, alternatively or additionally, a certain distance between the two frequencies f _diel and f _met may preferably exist. The following relationship preferably applies here: $$\left|{\mathrm{f}}_{\mathrm{diel}}-{\mathrm{f}}_{\mathrm{mead}}\right|/{\mathrm{f}}_{\mathrm{diel}}>\mathrm{0}.\mathrm{1}*{\mathrm{f}}_{\mathrm{diel}}.\mathrm{more\; preferred}\left|{\mathrm{f}}_{\mathrm{diel}}-{\mathrm{f}}_{\mathrm{mead}}\right|/{\mathrm{f}}_{\mathrm{diel}}>\mathrm{0}.\mathrm{2}*{\mathrm{f}}_{\mathrm{diel}}\mathrm{,}$$

The antenna according to the invention preferably has a reflector, on which the dipole radiator is arranged. The reflector preferably has a conductive reflector plane which is perpendicular to the main emission direction of the dipole radiator.

In one possible embodiment, the reflector may have a subreflector. Preferably, this subreflector is designed as a reflector frame. In a particularly preferred embodiment, the edge length of the reflector frame is greater than the maximum thickness D of the dielectric body.

In a further possible embodiment, the distance between the dipole radiator and the reflector can be between 0.05 λ and 0.5 λ, preferably between 0.1 λ and 0.4 λ. Λ is the wavelength of the center frequency of the lowest resonant frequency range of the antenna.

In a further possible embodiment, the reflector may have a bundling effect, which is a maximum for a frequency f _ref . Furthermore, the dielectric body preferably has a bundling effect which is maximal for a frequency f _diel , wherein the two frequencies f _ref and f _diel do not coincide. As a result, the bundling effect is achieved over a larger frequency range, since the reflector and the dielectric body optimally bundle for different frequency ranges.

According to a first sub-variant, the frequency f _{ref may be} smaller than the frequency f _diel , ie the reflector is designed for lower frequencies than the dielectric body.

In a second sub-variant, the frequency f _{ref may be} smaller than the center frequency f _{res of} the lowest resonance frequency range of the antenna, and the frequency f _{diel may be} greater than the center frequency f _res .

In a third sub-variant, there may be a certain distance between the frequency components f _diel and f _ref . In particular, it is preferred that | f _{diel -f ref} | / f _diel > 0.1 * f _diel , more preferably | f _diel - f _ref | / f _diel > 0.2 * f _diel .

The above-mentioned embodiments and variants with regard to the reflector can each be realized on their own. Preferably, however, the variants are combined with one another.

The antennas according to the invention can be used in particular together with other antennas as part of an antenna arrangement.

The present invention in a second aspect comprises a mobile radio antenna arrangement having a plurality of antennas, in particular for a mobile radio base station, having a first subgroup of one or more first antennas and a second subgroup of one or more second antennas. The first antennas each comprise a dipole radiator with a first dielectric body arranged on the dipole radiator, the height H _{1 of} the first dielectric body being at least 30% of the maximum thickness D of the first dielectric body. The second antennas each comprise a radiator without a dielectric element or with another, second dielectric element. In this case, in particular, a plurality of first antennas are preferably used.

The inventors of the present invention have recognized that the use of dielectric bodies in mobile radio antenna arrangements with a plurality of antennas allows the remote field values of the mobile radio antenna arrangement to be influenced. In particular, by using the dielectric bodies only in a first subset of radiators, or by using different dielectric bodies for different subgroups of radiators, the effective radiation level of the respective radiators of the subgroup can be changed.

In this case, a plurality of first antennas are preferably provided, the dipole radiators of the first antennas having identical resonance frequency ranges. In particular, the first antennas can be used for operation in the same mobile radio frequency band. In a preferred embodiment, the dipole radiators of the first antennas are identical.

Alternatively or additionally, it may be provided that the dipole radiators of the first antennas have the same emission level and / or height H _S1 over a common reflector. This allows a simple interconnection of the dipole radiator of the first antennas and thus the first antennas.

Furthermore, it can be provided according to the invention that a plurality of second antennas are provided, wherein the radiators of the second antennas have identical resonance frequency ranges. As a result, the second antennas can be used for operation in the same mobile radio frequency band. In a preferred embodiment, the radiators of the second antennas are identical.

Alternatively or additionally, the emitters of the second antennas may have the same emission level and / or height H _S2 over a common reflector. As a result, a simple interconnection of the radiator of the second antennas and thus the second antennas is possible.

Furthermore, it can be provided that the first dielectric bodies of the first antennas each have the same height H ₁ . Furthermore preferably, the first dielectric bodies are designed to be identical to one another. The first dielectric bodies thus influence the radiation characteristics of the radiators of the first antennas in the same way.

Furthermore, it can be provided that the second dielectric bodies, insofar as they are used, each have the same height H ₂ . Further preferably, the second dielectric bodies are identical to each other. Also by this The second dielectric bodies influence the radiation of the radiators of the second antennas in the same way.

Preferably, the first dielectric bodies differ from the second dielectric bodies when used, in particular with regard to their height. The first and second dielectric bodies thus influence the radiation of the dipole radiators of the first antennas and the radiators of the second antennas in different ways.

Particularly preferred is an embodiment in which only first dielectric body are used and the radiators of the second antenna have no dielectric element.

In a preferred embodiment of the present invention, the dipole radiators of the first antennas are dual-polarized dipole radiators. This optimally utilizes the space within the mobile radio antenna arrangement.

Furthermore, the emitters of the second antennas can be dual-polarized emitters. Alternatively or additionally, the emitters of the second antennas may be dipole emitters. In particular, this may be the dual-polarized dipole radiators in the emitters of the second antennas. However, the present invention is also used with other radiators of the second antennas.

The first subgroup of antennas of the antenna arrangement according to the invention may have separate ports for transmitting and / or receiving mobile radio signals. In particular, the first subset of antennas can thus be used separately from the second subset of antennas for transmitting and / or receiving mobile radio signals.

Alternatively, however, the first subgroup and the second subgroup of antennas of the antenna arrangement according to the invention may also have common ports for transmitting and / or receiving mobile radio signals

According to the invention, it may be provided that the antennas of the first and / or the antennas of the second subgroup each form one or more group antennas and have common ports for transmitting and / or receiving mobile radio signals.

In particular, the first antennas of the first subgroup can be interconnected to one or more array antennas. In particular, the first antennas of the first subgroup can be connected to one or more common ports via one or more phase shifters.

In the same way, the second antennas of the second subgroup can form one or more array antennas, and in particular can communicate with one or more common ports via one or more phase shifters.

In an alternative embodiment, the antennas of the first subgroup may each have separate ports for transmitting and / or receiving mobile radio signals. Alternatively or additionally, the antennas of the second subgroup may each have separate ports for transmitting and / or receiving mobile radio signals. Beamforming or beamshaping applications are possible with the separate ports of each antenna. In particular, the individual antennas can preferably be connected together to form different group antennas and / or operated individually for separate channels.

The use of dielectric bodies according to the invention has advantages in many different antenna arrangements. Depending on the design of the antenna arrangement, the dielectric bodies can be used to move the radiation levels of the respective subgroups of antennas away from one another to move or toward each other or to increase the radiation level of lower arranged radiators in order to improve their emission characteristics.

In a first variant of the mobile radio antenna arrangement according to the invention, the dielectric bodies shift the radiation planes of the first antennas and the second antennas away from one another. In particular, the first dielectric bodies can be used to move the emission plane of the first antennas away from the emission planes of the second antennas. This reduces the coupling of the first antennas and the second antennas in the mobile radio antenna arrangement according to the invention.

Such a shift of the radiation levels is used in particular when the dipole radiators of the first antennas and the radiators of the second antennas are arranged in a common plane and / or have the same height H _S over a common reflector. In this case, the emitters of the first and second antennas would have the same levels of abstraction per se. By using the dielectric bodies, however, it is achieved that the first antennas have a different emission level than the second antennas. In particular, the emission level of the first antennas is raised above the emission level of the second antennas.

The displacement V of the radiation plane through the first dielectric body and the height H _{S of} the dipole radiators of the first antennas over a common reflector preferably have the following relation: 0.5 H _S > V. Alternatively or additionally, the height H _{1 of} the first dielectric Body and the height H _{S of} the dipole radiators of the first antennas on a common reflector the following relationship: 0.5 H _S > H ₁ .

In this case, the displacement of the emission planes according to the invention can be used in particular in a mobile radio antenna arrangement in which the dipole radiators of the first antennas and the radiators of the second antennas have the same resonant frequency ranges and / or the same structure. Depending on specific purpose, the first and the second antennas for the same or different mobile bands can be used. Even if the dipole radiators of the first antennas and the radiators of the second antennas have the same resonant frequency ranges and / or the same structure, the resonant frequency ranges of the individual antennas formed by the radiators and the dielectric bodies can nevertheless differ, since the use of the dielectric bodies also Influence on the resonant frequency ranges of the antenna formed by the radiator and dielectric body.

An inventive shift of the radiation levels can be used both when the antennas of the first and the second subgroup each form one or more array antennas, as well as when the antennas of the first and the second subgroup each have separate ports for transmitting and receiving mobile radio signals exhibit. In a further possible embodiment, the first and the second antennas can be or are connected together to form one or more array antennas.

In a further embodiment variant of the present invention, the dielectric bodies move the emission planes of the first antennas and the second antennas toward one another. Thus, the first dielectric bodies may be used to move the radiation plane of the first antennas toward the radiation plane of the second antennas.

Such a succession movement of the planes of abstraction is used in particular when the dipole radiators of the first antennas and the radiators of the second antennas are arranged in different planes and / or have different heights H _S1 and H _S2 above a common reflector. In such an arrangement, the dipole radiators of the first antennas and the radiators of the second antennas have, in principle, different levels of emission. This distance between the radiation levels of the radiators can be reduced by the use of dielectric bodies.

In a preferred embodiment, the still remaining distance A between the planes of abstraction has the following relation to the height H _{S1 of} the first dipole radiators over a common reflector: A> 0.5 H _S1 , preferably A> 0.2 H _S1 . In this case, the distance A can also be completely 0, ie the levels of abstraction are equalized to one another.

Such a succession movement of the radiation levels is preferably used when the dipole radiators of the first antennas and the radiators of the second antennas have the same resonant frequency ranges and / or have the same structure. Preferably, such a configuration is furthermore used when the dipole radiators of the first antennas and the radiators of the second antennas are connected together to form one or more array antennas. In particular, this makes it possible to match the emission level of the individual radiators of a group antenna formed by dipole radiators of the first antennas and radiators of the second antennas.

In a third variant of the present invention, which can be combined with the first and / or the second variant, the dipole radiators of the first antennas are arranged in a first plane and the second antennas have metal structures which are arranged in a second plane above the first plane are. In this case, it is provided that the first dielectric bodies extend at least to the second level of the metal structures of the second antennas and / or raise the radiation plane of the dipole radiators of the first antennas at least to the second level. The use of the dielectric bodies thus prevents the metal structures of the second antennas from impairing the emission characteristic of the dipole radiators of the first antennas in a manner which was frequently encountered in the prior art.

Such a configuration is used in particular when the height H _{S1 of} the dipole radiators of the first antennas above a common reflector is smaller than the height H _{S2 of} the radiators of the second antennas above the common reflector.

Furthermore, such a configuration can be used, in particular, when the center frequency of the lowest resonant frequency range of the dipole radiators of the first antennas is higher than the center frequency of the lowest resonant frequency range of the radiators of the second antennas or if the first antennas are used for radiating in a higher frequency band than the second antennas. In this case, the radiators of the second antennas are usually larger than the dipole radiators of the first antennas, and therefore protrude beyond the dipole radiators of the first antennas. Due to the inventive displacement of the radiation plane of the dipole radiator of the first antennas by the use of the first dielectric body whose radiation power can be significantly improved because they are less affected by the emitters of the second antenna.

In one possible embodiment, the radiators of the second antennas may be designed as dipole radiators and arranged in a plane above the plane of the dipole radiators of the first antennas. In particular, the radiators of the second antennas may have bases which are higher than the bases of the dipole radiators of the first antennas, so that the dipole segments of the radiators of the second antennas arranged on the pedestals are arranged above the dipole segments of the radiators of the first antennas. In this case, the first dielectric bodies are designed such that they protrude at least as far as the dipole segments of the dipole radiators of the second antennas and preferably beyond them. In this case, the first and the second antennas are preferably used for different frequency bands and / or have different resonance frequency ranges.

The second antennas may consist of a plurality of dipoles, which are arranged in the form of a square and / or cross and / or a T.

In a further embodiment which can be combined with the embodiment described above, in the region of the radiators of the second antennas be arranged third radiator. These third radiators preferably have the same resonance frequency range and / or are used for the same frequency band as the dipole radiators of the first antennas. Alternatively or additionally, the dipole radiators of the first antennas and the radiators of the second antennas may have different resonance frequency ranges and / or be used for different frequency bands.

Due to the arrangement of the third emitters in the area of the emitters of the second antennas, these emitters usually can not have the same plane as the dipole emitters of the first antennas. In particular, the third radiators can be arranged on radiators of the second antennas, and thus arranged on a different plane than the dipole radiators of the first antennas. Still alternatively or additionally, the dipole radiators of the first antennas are disposed between the radiators of the second antennas.

In such an embodiment, the first dielectric bodies have a dual function. On the one hand, they improve the emission possibilities of the first antennas, since the emitters of the second antennas less hinder their emission due to the shift in the emission plane of the dipole radiators of the first antennas. Furthermore, the first dielectric bodies approximate the radiation plane of the dipole radiators of the first antennas to the radiation level of the third radiators.

In one possible embodiment, the radiators of the second antennas can have radiator elements which extend parallel and / or perpendicularly and / or obliquely to the emission direction. In this case, the third radiator can be arranged within the radiator elements extending parallel and / or perpendicular and / or obliquely to the emission direction. Alternatively or additionally, the third emitters may be dual polarized emitters.

The dipole radiators of the first antennas and the third radiators can be of the same design.

The last-described embodiment of a mobile radio antenna arrangement can be used in particular when the dipole radiators of the first antennas and the third radiators are connected together to form a group antenna and / or can be interconnected. In particular, the dipole radiators of the first antennas and the third radiators can be combined via one or more phase shifters to form one or more array antennas.

The mobile radio antenna arrangement according to the invention preferably comprises at least one column or row of antennas, wherein the first and second antennas are arranged alternately in the column or row and / or wherein the second antennas are arranged between two columns or rows of first antennas. In particular, the array antenna can have a plurality of columns and rows, wherein the first and the second antennas are alternately arranged in the plurality of columns and rows and / or wherein the second antennas are arranged between a plurality of columns and rows of first antennas.

The mobile radio antenna arrangement may further comprise a housing, within which the first and the second antennas are arranged. Furthermore, the mobile radio antenna arrangement preferably has ports via which the mobile radio antenna arrangement can be connected to a mobile radio base station. Furthermore, phase shifters can be provided in the housing, via which antennas of the mobile radio antenna arrangement are interconnected to form group antennas.

In a mobile radio antenna arrangement according to the second aspect of the present invention, the first antennas used are preferably mobile radio antennas, as described in more detail in accordance with the first aspect of the present invention.

This relates in particular to the design and / or dimensioning of the first dielectric bodies of the first antennas, which is preferably carried out as described above with regard to the first aspect.

Although the second antennas may in principle also be constructed in accordance with the first aspect of the present invention. Preferably, however, the second antennas do not have dielectric bodies and accordingly are not configured according to the first aspect of the present invention.

Figur 1:

ein erstes Ausführungsbeispiel einer erfindungsgemäßen Mobilfunkantenne,

Figur 2:

eine vergleichende Darstellung zwischen einer Mobilfunkantenne gemäß dem Stand der Technik und dem ersten Ausführungsbeispiel in Figur 1,

Figur 3:

die E-Feld-Verteilung bei einer Sendefrequenz von 2,6 GHz bei dem in Figur 1 dargestellten Ausführungsbeispiel,

Figur 4:

das in Figur 1 dargestellte Ausführungsbeispiel der vorliegenden Erfindung, wobei die maximale Dicke D und die Höhe H des dielektrischen Körpers eingezeichnet sind,

Figur 5:

vier Ausführungsbeispiele erfindungsgemäßer Mobilfunkantennen mit dielektrischen Körpern unterschiedlicher Höhe,

Figur 6:

zwei Diagramme, welche den S-Parameter in Abhängigkeit von der Frequenz und den Antennengewinn in Abhängigkeit vom Abstrahlwinkel für die in Figur 5 gezeigten vier Ausführungsbeispiele zeigen,

Figur 7:

vier Diagramme, welche die E-Feld-Verteilung für das letzte der in Figur 5 gezeigten Ausführungsbeispiele mit einer Höhe H des dielektrischen Körpers von 200mm zeigen, und zwar getrennt für den ersten und den zweiten Port bei einer Sendefrequenz von 2,6 GHz,

Figur 8:

das erste und das letzte Ausführungsbeispiel aus den in Figur 5 gezeigten vier Ausführungsbeispielen mit zwei Darstellungen des Antennengewinns bei einer Sendefrequenz von 2,6GHz,

Figur 9:

eine Formel und ein Diagramm, welche die Abhängigkeit der maximalen Dicke eines Stabbereiches und eines Linsenbereiches von der Wellenlänge der Mittenfrequenz und der relativen Permittivität zeigen,

Figur 10:

eine Mobilfunkantenne gemäß dem Stand der Technik und zwei Ausführungsbeispiele von Mobilfunkantennen gemäß der vorliegenden Erfindung, sowie ein Diagramm, welches die Direktivität und den Gain für die einzelnen Ports zeigt,

Figur 11:

ein Diagramm, welches die Breite des Antennendiagramms für die in Figur 10 gezeigten Mobilfunkantennen wiedergibt,

Figur 12:

ein weiteres Ausführungsbeispiel einer erfindungsgemäßen Mobilfunkantenne mit einem metallischen Element und/oder einer metallischen Beschichtung,

Figur 13:

eine Mobilfunkantenne gemäß dem Stand der Technik und drei Ausführungsbeispiele von erfindungsgemäßen Mobilfunkantennen, deren dielektrische Körper sich im Hinblick auf die Ausgestaltung des Linsenbereichs unterscheiden,

Figur 14a:

ein Diagramm, welches die Fernfeld-Nutzpolarisation bei einer Frequenz von 2,6 GHz für die in Figur 13 gezeigten Mobilfunkantennen wiedergibt,

Figur 14b:

ein Diagramm, welches die Fernfeld-Kreuzpolarisation bei einer Frequenz von 2,6 GHz für die in Figur 13 gezeigten Mobilfunkantennen wiedergibt,

Figur 15:

ein erstes Ausführungsbeispiel einer erfindungsgemäßen Antennenanordnung,

Figur 16:

das in Figur 15 gezeigte erste Ausführungsbeispiel einer erfindungsgemäßen Antennenordnung mit zwei Vergleichs-Antennenanordnungen und einem Diagramm, welches den Gewinn für die Antennenanordnungen in Abhängigkeit von der Frequenz wiedergibt,

Figur 17:

zwei Diagramme, welche die Direktivität der in Figur 16 gezeigten Antennenanordnungen wiedergeben, wobei die Breite bei 3dB und 10dB in Abhängigkeit von der Frequenz wiedergegeben ist,

Figur 18:

ein zweites Ausführungsbeispiel einer erfindungsgemäßen Antennenanordnung,

Figur 19:

eine perspektivische Darstellung des in Figur 18 dargestellten zweiten Ausführungsbeispiels,

Figur 20:

ein drittes Ausführungsbeispiel einer erfindungsgemäßen Antennenanordnung und

Figur 21:

eine perspektivische Darstellung des in Figur 20 dargestellten dritten Ausführungsbeispiels einer Antennenanordnung.

The present invention will now be described in more detail with reference to embodiments and drawings. Showing:

FIG. 1:

A first embodiment of a mobile radio antenna according to the invention,

FIG. 2:

a comparative representation between a mobile radio antenna according to the prior art and the first embodiment in FIG. 1 .

FIG. 3:

the E-field distribution at a transmission frequency of 2.6 GHz at the in FIG. 1 illustrated embodiment,

FIG. 4:

this in FIG. 1 illustrated embodiment of the present invention, wherein the maximum thickness D and the height H of the dielectric body are located,

FIG. 5:

Four embodiments of mobile radio antennas according to the invention with dielectric bodies of different heights,

FIG. 6:

two diagrams showing the S-parameter as a function of the frequency and the antenna gain as a function of the radiation angle for the in FIG. 5 show four embodiments shown

FIG. 7:

Four diagrams showing the E-field distribution for the last one in FIG. 5 shown embodiments with a height H of the dielectric body of 200mm, separated for the first and the second port at a transmission frequency of 2.6 GHz,

FIG. 8:

the first and the last embodiment of the in FIG. 5 4 embodiments shown with two representations of the antenna gain at a transmission frequency of 2.6 GHz,

FIG. 9:

a formula and a graph showing the dependence of the maximum thickness of a rod region and a lens region on the wavelength of the center frequency and the relative permittivity,

FIG. 10:

a mobile radio antenna according to the prior art and two embodiments of mobile radio antennas according to the present invention, as well as a diagram showing the directivity and the gain for each port,

FIG. 11:

a diagram showing the width of the antenna diagram for the in FIG. 10 reproduces the mobile radio antennas shown,

FIG. 12:

a further embodiment of a mobile radio antenna according to the invention with a metallic element and / or a metallic coating,

FIG. 13:

a mobile radio antenna according to the prior art and three embodiments of mobile radio antennas according to the invention, whose dielectric bodies differ with regard to the design of the lens area,

FIG. 14a:

a diagram showing the far-field payload polarization at a frequency of 2.6 GHz for the in FIG. 13 reproduces the mobile radio antennas shown,

FIG. 14b:

a diagram showing the far-field cross-polarization at a frequency of 2.6 GHz for the in FIG. 13 reproduces the mobile radio antennas shown,

FIG. 15:

A first embodiment of an antenna arrangement according to the invention,

FIG. 16:

this in FIG. 15 1 shows a first embodiment of an inventive antenna arrangement with two comparison antenna arrangements and a diagram which shows the gain for the antenna arrangements as a function of the frequency,

FIG. 17:

two diagrams showing the directivity of in FIG. 16 reproduced antenna arrangements, wherein the width at 3dB and 10dB is reproduced in dependence on the frequency,

FIG. 18:

A second embodiment of an antenna arrangement according to the invention,

FIG. 19:

a perspective view of the in FIG. 18 illustrated second embodiment,

FIG. 20:

A third embodiment of an antenna arrangement according to the invention and

FIG. 21:

a perspective view of the in FIG. 20 illustrated third embodiment of an antenna arrangement.

FIGS. 1 to 3 show a first embodiment of a mobile radio antenna according to the invention. This is preferably a mobile radio antenna which can be connected via signal lines to a mobile radio base station in order to receive and / or transmit mobile radio signals.

The exemplary embodiment of the mobile radio antenna consists of a dipole radiator 1, on which a dielectric body 2 is arranged. The dipole radiator 1 has a base 3 which carries dipole segments 4. The dipole segments 4 extend in a plane perpendicular to the main emission direction of the mobile radio antenna. The base 3, however, extends in the main emission direction.

The dipole radiator 1 is arranged on a reflector 10 which is plate-shaped and extends in a plane perpendicular to the main emission direction and thus parallel to the plane of the dipole segments 4. Through the base 3, the dipole segments 4 are held at a height H _S above the reflector 10.

In the exemplary embodiment, the dipole radiator 1 is a dual-polarized dipole radiator. The first polarization is formed by a first dipole formed by two opposite dipole segments 4, the second polarization by two further, also opposite dipole segments 4. The two polarizations are orthogonal and crosswise to each other. In the exemplary embodiment, the dipole radiator is designed as a dipole square, in which the four dipole segments are arranged around a common axis and occupy four sectors of a square.

In the exemplary embodiment, the two polarizations of the dipole radiator are used separately for transmitting and / or receiving mobile radio signals, and have separate ports 12 and 13 for this purpose.

On the dipole radiator 1, a dielectric body 2 is arranged according to the invention. The dielectric body 2 has an underside with which it is arranged on the plane formed by the dipole segments 4 of the dipole radiator 1.

The underside of the dielectric body may include mechanical attachment areas for attachment to the dipole. These may e.g. as noses and / or grooves protrude into the area of the dipole. The underside of the dielectric body is preferably planar at least except for the mechanical fastening regions, and / or extends parallel to the plane of the dipole segments 4 or a plane which is perpendicular to the main emission direction of the antenna.

Preferably, the underside of the dielectric body is placed directly on the dipole segments 4, or only separated by a narrow air gap of preferably not more than 2 and both preferably at most 1 mm.

At the in FIG. 1 In the exemplary embodiment shown, the dielectric body comprises a rod region 8 and a lens region 9. In the rod region 8, the dielectric body exhibits a cross section which is constant in the main emission direction, which is the cross section in a plane perpendicular to the main emission direction. In the lens region 9, which is arranged in the emission direction on the side facing away from the dipole radiator side of the rod portion 8, the dielectric body, however, has a changing in the main emission direction cross-section.

In the exemplary embodiment, the dielectric body has a rotational symmetry. The symmetry axis of the dielectric body runs parallel to the main emission direction of the dipole radiator 1 and coincides with the symmetry axis of the dipole radiator 1.

In the rod region 8, the dielectric body is designed as a solid circular cylinder. The lens region 9 is designed in the embodiment as a counter-cone. As will be shown in more detail below, however, other shapes are also conceivable for the lens region. Furthermore, the lens area 9 can also be dispensed with completely, so that the entire dielectric body is designed as a dielectric rod.

The dielectric body according to the present invention is used to displace the emission plane 6 of the dipole radiator in the main emission direction, so that the emission plane 7 of the antenna formed from dipole radiator 1 and dielectric body 2 is arranged above the emission plane 6 of the dipole radiator 1 itself. As will be described in more detail below, this shift in the emission level enables a multitude of applications, in particular if the mobile radio antenna according to the invention is combined with other antennas in an antenna arrangement.

In the exemplary embodiment, the antenna further has a sub-reflector frame 11, which is arranged on the plate-shaped main reflector 10 and surrounds the antenna. The subreflector frame improves the directivity.

The inventive shift of the Abstrahlebene is characterized by the in FIG. 3 occupied E-field diagrams occupied. As can be seen from these diagrams, the region of the strongest E-field distribution and thus in the plane of emission of the dipole segments of the dipole radiator 1 is displaced in the emission direction by the dielectric body placed on the antenna, at least by the height of the rod region 8 of the dielectric body 2.

In FIG. 4 Once again, the dimensions of the dielectric body are shown schematically. In particular, the maximum thickness D of the dielectric body 2, ie its maximum extent in a plane perpendicular to the main emission direction, and the height H of the dielectric body, ie a maximum extent in the emission direction, are shown.

According to the present invention, dielectric bodies are used in which the height H is at least 30% of the maximum thickness D. Preferably, the height H is at least 50% of the maximum thickness D, further preferably at least 70% of the maximum thickness D. In this way, according to the invention, a corresponding displacement of the radiation level is achieved.

Alternatively or additionally, the height of the bar area 8, i. the maximum extension of the rod region in the main emission direction, at least 20% of the maximum thickness D, preferably at least 30% of the maximum thickness D, furthermore preferably at least 40% of the maximum thickness D.

The height H of the dielectric body or of the rod region of the dielectric body is at least in principle not limited. FIG. 5 shows four different embodiments, which differ with respect to the height H of the dielectric body. In all embodiments, the dielectric body has a diameter D of 50 mm. The height H is 50 mm, 75 mm, 100 mm or 200 mm in the four embodiments. In the four embodiments, a dielectric body was used which consists exclusively of a rod region and has no lens region.

FIG. 6 shows in the upper diagram the S parameter in copolarization as a function of the frequency in a frequency range between 1.7 GHz and 2.7 GHz. It becomes clear that the course of the S-parameter depends on the height H. Furthermore, the height H also has an influence on the position of the resonant frequency range, with larger heights tending to broaden the resonant frequency range.

The diagram in FIG. 6 Below shows the far-field diagram for the different heights of the dielectric body. The longer the dielectric body becomes, the higher the directivity in the main beam direction becomes, that is, at phi = 0 degrees, and the more local minima and maxima are formed in the far field diagram.

The increasing number of local minima / maxima is due to constructive and / or destructive superposition of electromagnetic fields. It can be assumed that the local minima and maxima by different emission points along the axis of the dielectric body to conditions come, ie a part of the energy is radiated along the body (radiating modes) and a part of the energy passed on (bound modes).

FIG. 7 shows the electric field in V / m for the frequency 2.6 GHz and for a dielectric body with the height H of 50 mm and 200 mm. At both body levels, the electric field completely penetrates the dielectric bodies. Further, the electric field in the body having a height H of 200 mm repeats periodically along the Z-axis, that is, in the main radiation direction. This illustrates the waveguide function and the displacement of the phase center of the radiation along the z-axis and thus in the main emission direction.

Fig. 7 shows the electric field for the antenna port 1 and thus the polarization 1, and for the antenna port 2 and thus in the polarization 2. Both fields are orthogonal to each other, whereby a high isolation or decoupling between the two antenna ports is achieved.

FIG. 7 shows, on the one hand, that the height H of the dielectric body must not fall below a certain minimum height if the dielectric body is to function as a waveguide.

At the same time, the side lobes, which increase with increasing length, are also explained. These can be explained by the imperfect conduction of the field through the dielectric body and the partial emission at the respective field maxima.

In FIG. 8 Again, the antenna gain in copolarization at 2.6 GHz for a height of 50 mm and a height of 200 mm of the dielectric body is shown in three dimensions. As can be clearly seen, the directivity of the main lobe is significantly increased by the extension of the dielectric body, but side lobes are added.

The claimed relationship between the height H of the dielectric body and the thickness D of the dielectric body according to the invention is obtained by considering the dielectric body as a rod radiator. FIG. 9 shows the dependence of the thickness of such a rod radiator on the wavelength of the center frequency of the resonant frequency range and the effective relative permittivity ε _r in a rod radiator.

On the left are the formulas for the diameter d _{max, conductor of} the rod area and thus the maximum thickness of the dielectric body and the diameter d _{min, peak} reproduced at the thinnest point of the lens area. On the right, this dependency is shown graphically in a diagram. The maximum thickness of the dielectric body can therefore not be chosen arbitrarily, but must be chosen depending on the wavelength and the relative permittivity.

bevorzugt $$0,75*\frac{\lambda }{\sqrt{\pi \left({\epsilon }_r-1\right)}}\le \mathrm{D}\le 1,25*\frac{\lambda }{\sqrt{\pi \left({\epsilon }_r-1\right)}}\mathrm{.}$$

For the purposes of the present invention, the maximum thickness D of the dielectric body, in particular the maximum thickness of the rod area, is selected in the following range: $$0.5*\frac{\lambda }{\sqrt{\pi \left({\epsilon }_r-1\right)}}\le \mathrm{D}\le 1.5*\frac{\lambda }{\sqrt{\pi \left({\epsilon }_r-1\right)}}.$$

prefers $$0.75*\frac{\lambda }{\sqrt{\pi \left({\epsilon }_r-1\right)}}\le \mathrm{D}\le 1.25*\frac{\lambda }{\sqrt{\pi \left({\epsilon }_r-1\right)}}\mathrm{,}$$

bevorzugt $$0,75*\frac{\lambda }{\sqrt{\pi \left({\epsilon }_r-1\right)}}\le \mathrm{H}$$

For the height H, at least as a lower limit, a comparable dependence on the wavelength and the relative permittivity applies: $$0.5*\frac{\lambda }{\sqrt{\pi \left({\epsilon }_r-1\right)}}\le \mathrm{H}$$

prefers $$0.75*\frac{\lambda }{\sqrt{\pi \left({\epsilon }_r-1\right)}}\le \mathrm{H}$$

This also results in the claimed relationship between the height H of the dielectric body and the maximum thickness D.

The influence of the maximum thickness D of the dielectric body on the waveguiding properties and thus the radiation characteristic of the antenna resulting from the dipole and the dielectric body will now be described again with reference to FIG Figures 10 and 11 shown in more detail. Top in FIG. 10 Here, on the one hand, a comparative example without dielectric body (000) and two examples 001 and 002, each with dielectric bodies of different sizes, are shown.

In the exemplary embodiment, the reflector has a length and a width of 144 mm, the sub-reflector a length and width of 97 mm and a height of 21 mm. The used dipole radiator in all versions is the identical radiator, with a resonant frequency range between 1.7 and 2.7 GHz.

In Example 001, the dielectric body has a diameter and thus a maximum thickness D in the sense of the present invention of 90 mm and a height H of 80 mm, in Example 002 a diameter and thus a maximum thickness D in the sense of the present invention of 50 mm and a height H of 50 mm. The relative permittivity of the material used is 2.8 each.

In the diagram in FIG. 10 Below is the gain and directivity for the three antennas versus frequency. The diagram shows an improvement in directivity and gain when using a dielectric body. The effect is for Example 002, ie the dielectric body with the smaller diameter D, for higher frequencies significantly more pronounced than for lower frequencies.

Furthermore, the use of the dielectric body having the smaller diameter D also causes the resonance frequency range to be changed. While the entire frequency range between 1.8 and 2.7 is usable for the larger dielectric body, the smaller dielectric body in Example 002 restricts the usable range to frequencies between 2.1 and 2.7. Therefore, for lower frequencies, the smaller dielectric body no longer works as a waveguide due to its small diameter. However, no diagram is included for this.

The diagram in FIG. 11 now shows the opening angle at 10 dB or 3 dB for the three examples. Again, the lower opening angle when using the dielectric body according to the invention again shows.

The dielectric body preferably has an effective relative permittivity of greater than 2, more preferably greater than 2.5.

This can be achieved, for example, by fabricating the dielectric body from a solid material having a corresponding relative permittivity. Instead, the body could also be made of a material having a higher relative permittivity of e.g. 6, and have air holes which again reduce the effective relative permittivity of the dielectric body. Instead, a material with a low relative permittivity could be used, in which a granulate with a high relative permittivity is injected. For example, it could be incorporated into a matrix material having a relative permittivity of 1 and a granulate having a relative permittivity of 30.

The effective relative permittivity is constant in a preferred embodiment over the extent of the dielectric body.

However, a material with a gradient of relative permittivity could be used to influence the emission properties.

To influence the radiation properties, the following adjustments are also conceivable:

In FIG. 12 the height H _{S of} the dipole or the dipole segments 4 is shown above the reflector 10. As is known, the reflector has the highest bundling effect for frequencies for whose wavelength λ the relationship H _S = λ / 4 holds.

Further, as shown above, the bundling effect of the dielectric body depends on the maximum thickness D and the diameter of the dielectric body, respectively. According to the invention, the distance H _S between the dipole and the reflector can now be optimally designed for low frequencies, while the maximum thickness D or the diameter of the dielectric cone is optimally designed for high frequencies.

The radiation properties of the antenna can furthermore be influenced by the use of metallic and / or conductive objects in the region of the dielectric body. For example, one or more metal discs or plates 14 may be mounted in the dielectric body or on the dielectric body. In particular, a metal disk, which is perpendicular to the main emission direction, can be integrated into the dielectric body or attached to its underside. Alternatively or additionally, it is conceivable to provide the surface of the dielectric body with a surface metallization 15. In this case, the surface metallization 15 is preferably arranged exclusively on the outer circumference of the dielectric body. Also by such metallic and / or conductive elements, the directivity of the antenna can be influenced. Preferably, the electrical and conductive elements are designed so that their bundling effect is optimal for a different frequency range than the bundling effect of the distance H _S between the dipole and the reflector, and / or the bundling effect of the dielectric body.

The influence of the lens area is determined by the Figures 13 and 14 again examined closer. In FIG. 13 four embodiments 000 to 003 are shown. Embodiment 000 is a comparative example without a dielectric body. The exemplary embodiment 001 has a lens area configured as a countercone, that embodiment 002 has a lens area embodied as a cone, and that the embodiment 003 is designed without a lens area.

Figure 14a shows the far-field diagram of the antenna for the Nutzpolarisation, FIG. 14b for the cross polarization. It can be seen that, as already shown above, the directivity and the gain in the emission direction can be increased by the use of the dielectric body. However, the different lens shapes for examples 001 and 002 have virtually no influence on the diagrams. The slightly different embodiment of the diagram for example 003 is more likely to be explained by the greater effective height H of the dielectric body and the amplification of the secondary maxima already discussed above at higher altitudes.

The change in the emission plane according to the invention can be used, in particular in group antenna arrangements with a high single radiator density, to change the far-field characteristic. In particular, the dielectric bodies according to the invention are thereby used only in a part of the antennas, so that their emission level is shifted to a height which is in a preferred relation to the emission level of the remaining emitters.

FIG. 15 shows a first embodiment of a mobile radio antenna arrangement according to the invention with a first group of first antennas 21, which are designed as antennas according to the invention and consist of a dipole radiator with a dielectric body 23 and a second subset of second antennas 22, which have no dielectric body. In the exemplary embodiment, the dipole radiators of the first antennas 21 and the second antennas 22 identical. By using the dielectric bodies 23 in the first antennas 21, the emission plane of these antennas is shifted with respect to the second antennas.

The dipole radiators of the first antennas and the second antennas are arranged on a common reflector 10 and would therefore have the same radiation plane without the dielectric bodies 23. The displacement of the aperture or the radiation level of the individual radiators therefore reduces the mutual coupling of the individual antennas. As a result, the near-field coupling and consequently the far-field values such as the aperture angle and the directivity of the antenna can be improved.

In the exemplary embodiment, the antenna arrangement has a plurality of rows 24, 24 ', 24 "and a plurality of columns 25, 25', 25". The first antennas 21 with a dielectric body 23 and the second antennas 22 without such a dielectric body alternate in both the rows and in the columns.

FIG. 16 shows as Comparative Example V000 an antenna arrangement in which all antennas without dielectric body are executed and as Comparative Example V001 an embodiment in which all the antennas have a dielectric body. This in FIG. 15 illustrated embodiment of the antenna arrangement according to the invention is shown as example V002.

Down in FIG. 16 is the Dielektivität and the profit of the individual examples as a function of the frequency shown. In FIG. 17 the width of the far field diagram is shown at 10dB and 3dB. As can be seen clearly from both diagrams, the exemplary embodiment according to the invention has both the best directivity at least in the area of the main lobe and the best gain in the area of the main lobe.

At the in FIG. 15 In the exemplary embodiment shown, the first and the second antennas can be configured jointly as a group antenna. In particular, a row or a column of antennas can be connected via a phase shifter to a common port or, since these are dual-polarized antennas, to two common ports. In this case, a phase compensation is preferably carried out between the first and second antennas of such a group antenna in order to compensate for the effects of the dielectric body on the phase position within the array antenna.

Alternatively, however, the first antennas may also form one or more array antennas below, while the second antennas each form one or more separate array antennas below. In this case, preferably the first antennas within a column or row are connected via a phase shifter to one or more common ports, and the second antennas within a column or row are connected via one or more phase shifters with one or more ports.

In a further embodiment, the individual antennas may also each have separate ports in order to be flexibly interconnected, for example, for beamforming or beamshaping applications, or to be able to be operated separately. In this case, the antenna arrangement is preferably an active antenna arrangement, in which each of the individual antennas is assigned a separate amplifier.

However, the antenna arrangement according to the invention may also be a passive antenna without an amplifier.

At the in FIG. 15 illustrated embodiment of a mobile radio antenna arrangement according to the invention come as spotlights dual polarized dipole radiator used. In particular, these emitters are designed as already described above with respect to FIG FIG. 1 shown embodiment is shown in more detail. The first and the second antennas differ in the embodiment solely by the use of a dielectric body according to the present invention in the first antennas, while the dipole radiators are made identical. The dielectric bodies are preferably designed as described above.

In FIG. 18 a second embodiment of an antenna arrangement according to the invention is shown.

Top in FIG. 18 First, an antenna according to the prior art is shown. This has first antennas 31 and second antennas 32. The first antennas are used for transmitting and / or receiving in a higher frequency band, the second antennas 32 for transmitting and / or receiving in a lower frequency band. The first antennas and second antennas are each dipole radiators. Since the dipole radiators of the second antennas are designed for lower frequencies, they have a greater distance from the common reflector 10 than the dipole radiators of the first antennas. Thus, the radiation plane 6 of the first antennas 31 lies below the plane 34 of the dipole segments of the second antennas. This leads to the prior art that the emission power of the first antennas is significantly affected.

This effect is prevented according to the invention in that dielectric bodies 33 are arranged on the first antennas 31 with an otherwise identical structure, which raises the radiation plane of the first antennas 31 from the emission plane 6 of their dipole radiators via the plane 34 of the dipole segments of the second antennas 32. As a result, the emission characteristic of the first antennas 31 is no longer negatively influenced by the presence of the second antennas. The displacement V and, equivalently, the height H of the dielectric bodies 33 in this exemplary embodiment is thus greater than the distance K between the emission plane 6 of the dipole radiators of the first antennas 31 and the emission plane 34 of the dipole radiators of the second antennas.

At the in FIG. 18 In the exemplary embodiment shown, the dipole radiators of the first antennas are in turn dual-polarized dipole radiators. In particular, these are designed as already described above with regard to in FIG. 1 shown embodiment has been shown.

The dipoles of the second antennas 32, on the other hand, are designed as VH poles, i. spaced-apart dipoles 32 and 32 'are used, each with orthogonal polarizations. These are interconnected via a 180 ° hybrid coupler to form an X-pole.

The second antennas can be used, for example, as a low-band antenna for the mobile radio frequency band between 698 and 960 MHz, the first antennas as a high-band antenna for the frequency range between 1710 and 2690 MHz.

As in FIG. 19 which the in FIG. 18 shown embodiment shown again in a perspective view, the first antennas are arranged in four columns of two antennas, wherein the second antennas are arranged between the rows thus formed.

The dipoles of the second antennas 32 can also be arranged in a square, wherein in each case a first antenna 31 is located within such a square. Furthermore, further first antennas 31 may be arranged between such squares of second antennas 32. Alternatively or additionally, the second antennas 32 may also be arranged in the form of a cross.

A third embodiment of an antenna arrangement according to the invention is in Figures 20 and 21 shown. Top in FIG. 20 again, an antenna according to the prior art is shown, while below the dielectric body equipped embodiment of the present invention is shown.

The antenna arrangement according to the invention has first antennas 41, second antennas 42 and third antennas 43. The first antennas 41 and the third antennas 43 are used for transmission in the same frequency band, while the second antennas 42 are used for transmission in a lower frequency band.

In this case, the third antennas 43 are arranged in the region of the second antennas 42, and offset in the emission direction relative to the first antennas 41 upwards. The second antennas 42 also have metal elements which extend into a plane above the emission plane 45 of the dipole radiators of the first antennas 41.

In the exemplary embodiment, the second antennas are antennas with sidewalls 47 and 48 running obliquely to the main emission direction, between which slots 49 are formed, which act as slit radiators. The oblique side walls 47 and 48 together form a kind of funnel. Between these funnel-shaped antennas, the dipole radiators of the first antennas 41 are arranged. Alternatively, the second antennas could also consist of dipole radiators, which are arranged in a square.

In the case of an antenna according to the prior art, therefore, the radiation of the first antennas is considerably impaired by the metallic elements of the second antennas 42 arranged above in the emission direction. Furthermore, the dipole radiators of the first antennas 41 and the dipole radiators of the third antennas 43 have different emission planes 45 and 46.

Both problems are solved according to the invention by the use of dielectric bodies 44 on the dipole radiators of the first antennas 41. The height H of the dielectric bodies corresponds to the distance between the radiation plane 46 of the dipole radiators of the third antennas and the radiation plane 45 of the dipole radiators of the first antennas.

On the one hand, this results in the first and the third antennas having essentially the same level of abstraction. Furthermore, the radiation plane of the first antennas is lifted above the plane of the metallic elements of the second antennas, so that their radiation properties are no longer adversely affected.

The dipole radiators of the first and third antennas can be dual-polarized dipole radiators. In particular, the dipoles of the two polarizations are arranged crossed to one another. The dipole radiator can be designed as this with respect to the embodiment in FIG. 1 was described in more detail.

The dipole radiators of the first and the third antennas may be of identical design and / or have the same resonant frequency ranges. They usually have only slight differences in the base area with regard to their attachment.

Preferably, the first and the third antennas are used for transmitting and / or receiving in the same frequency band. The first and the third antennas can be interconnected to one or more array antennas and in particular via one or more phase shifter with one or more common ports in combination.

The second antennas are preferably used for transmitting and / or receiving in a lower frequency band than the first and / or the third antennas. Preferably, the second antennas are connected together to form one or more array antennas and, in particular, can communicate with one or more ports via one or more phase shifters.

The second antennas 42 and the first antennas 41 are arranged on a common reflector 10. The third antennas are arranged within the second antennas, and preferably have their own sub-reflector, which also is disposed within the second antenna 42. The first antennas may further comprise frame-shaped subreflectors 11.

Regardless of the specific embodiment, antennas used in the mobile radio antenna arrangements according to the invention are preferably first antennas, as described in more detail above with regard to the antennas according to the invention. In particular, this applies to the design and / or the design of the dielectric body.

Claims (15)

Mobile radio antenna, in particular for a mobile radio base station, with at least one dipole radiator and with a dielectric body arranged on the dipole radiator,
characterized,
that the height H is in a cross section of the dielectric body in the main direction at least 30% of the maximum thickness D of the dielectric body perpendicularly to the main emission direction. Mobile radio antenna according to one of the preceding claims, wherein the height H of the dielectric body is at least 50% of the maximum thickness D of the dielectric body, preferably at least 70% of the maximum thickness D of the dielectric body, and / or wherein the dielectric body has an effective relative permittivity ε _r > 2 and preferably has an effective relative permittivity ε _r > 2.5. A mobile radio antenna according to claim 1, wherein the dipole radiator is a dual-polarized dipole radiator and / or wherein the dielectric body has an axis of symmetry pointing in the main radiating direction, which is preferably an axial symmetry and / or rotational symmetry, and / or wherein the dielectric body has a rod region and / or a lens region, wherein the height of the rod region is preferably between 50% and 100%, more preferably between 65% and 100% of the height H of the dielectric body, and / or wherein Lens region is preferably arranged on the side facing away from the dipole radiator side of the rod region and / or wherein preferably the height of the lens region between 5% and 50%, preferably between 10% and 35% of the height H of the dielectric body. A mobile radio antenna according to any one of the preceding claims, wherein for the maximum thickness D and the height H of the dielectric body the following relationship exists with the wavelength λ of the center frequency of the lowest resonant frequency range of the antenna and the effective relative permittivity ε _{r of} the dielectric body: $$0.5*\frac{\lambda }{\sqrt{\pi \left({\epsilon }_r-1\right)}}\le \mathrm{H}$$

and or $$0.5*\frac{\lambda }{\sqrt{\pi \left({\epsilon }_r-1\right)}}\le \mathrm{D}\le 25*\frac{\lambda }{\sqrt{\pi \left({\epsilon }_r-1\right)}}$$

prefers $$0.75*\frac{\lambda }{\sqrt{\pi \left({\epsilon }_r-1\right)}}\le \mathrm{H}$$

and or $$0.75*\frac{\lambda }{\sqrt{\pi \left({\epsilon }_r-1\right)}}\le \mathrm{D}\le 2.5*\frac{\lambda }{\sqrt{\pi \left({\epsilon }_r-1\right)}}\mathrm{or}\le 1.25*\frac{\lambda }{\sqrt{\pi \left({\epsilon }_r-1\right)}}$$

Mobile radio antenna according to one of the preceding claims, wherein in / and or on the dielectric body, a conductive and / or metallic element is arranged, wherein the conductive and / or metallic element is preferably a coating of an inner or outer surface of the dielectric body , and / or around a conductive and / or metallic disc arranged in or on the dielectric body,
and / or wherein the conductive and / or metallic element surrounds an outer circumference of the dielectric body or extends in a plane perpendicular to the main emission direction,
wherein preferably the conductive and / or metallic element has a bundling effect which is maximal for a frequency f _met and wherein the dielectric body has a bundling effect which is maximal for a frequency f _diel , where f _met ≠ f _diel ,
more preferably f _met <f _diel ,
and / or wherein preferably the following relationship exists with the center frequency f _{res of} the lowest resonant frequency range of the antenna: f _met <f _res <f _diel ,
and / or wherein further preferred: | f _dl - f _met | / f _diel > 0.1 * f _diel , preferably | f _dl - f _met | / f _diel > 0.2 * f _diel . Mobile radio antenna according to one of the preceding claims, with a reflector on which the dipole radiator is arranged,
wherein the antenna has a subreflector, which is preferably designed as a reflector frame, wherein the edge length of the reflector frame is preferably equal to or greater than the maximum thickness D of the dielectric body,
and / or wherein the distance between the reflector and the dipole radiator is between 0.05 λ and 0.5 λ, preferably between 0.1 λ and 0.4 λ, wherein it is λ is the wavelength of the center frequency of the lowest resonant frequency range of the antenna,
and / or wherein the reflector has a bundling effect which is at a maximum for a frequency f _ref and wherein the dielectric body has a bundling effect which is maximal for a frequency f _diel , where f _ref ≠ f _diel ,
preferably f _ref <f _diel ,
and / or wherein preferably the following relationship to the center frequency f _{res of} the lowest resonance frequency _{band of} the antenna is: f _ref <f _res <f _diel ,
and / or where preferred | f _diel - f _ref | / f _diel > 0.1 * f _diel , preferably | f _diel - f _ref | / f _diel > 0.2 * f _diel . Mobile radio antenna arrangement having a plurality of antennas, in particular for a mobile radio base station, having a first subgroup of one or more first antennas and a second subgroup of one or more second antennas,
characterized,
that the first antenna each comprise a dipole radiator having a disposed on the dipole radiators first dielectric body, wherein the height H ₁ of the first dielectric body is at least 30% of the maximum thickness D of the first dielectric body, and that the second antennas, respectively a radiator without a dielectric element or with another, second dielectric element. Mobile radio antenna arrangement according to claim 7, wherein the dipole radiators of the first antennas are dual-polarized dipole radiators and / or wherein the radiators of the second antennas are dual-polarized radiators and / or dipole radiators. A mobile radio antenna arrangement according to claim 7 or 8, wherein the dipole radiators of the first antennas have identical resonance frequency ranges and are preferably identical, and / or have the same radiating plane and / or height H _S1 over a common reflector, and / or wherein the radiators of the second Antennas have identical resonance frequency ranges and are preferably identical and / or have the same level of abstraction and / or height H _S2 over a common reflector, and / or wherein the first dielectric body have the same height H ₁ and are preferably identical and / or wherein the second dielectric body have the same height H ₂ and are preferably identical. A mobile radio antenna arrangement according to any one of claims 7 to 9, wherein the dielectric bodies shift the radiation planes of the first antennas and the second antennas away from each other, preferably the dipole radiators of the first antennas and the radiators of the second antennas are arranged in a common plane and / or the same Have height H _S over a common reflector, wherein preferably the displacement V of the radiation levels and the height H _{S of} the dipole radiator of the first antenna above a common reflector have the following relationship: 0.5 H _S <V, and / or preferably Dipole radiator of the first antennas and the radiators of the second antennas have the same resonant frequency ranges and / or the same structure. Mobile radio antenna arrangement according to one of claims 7 to 9, wherein the dielectric bodies to move the radiation levels of the first antennas and the second antennas to each other, preferably the dipole radiator of the first antennas and the radiators of the second antennas are arranged in different planes and / or different heights H _S1 and H _{S2 have} over a common reflector, wherein preferably the remaining distance A between the planes of abstraction has the following relation to the height H _{S1 of} the dipole radiators of the first antennas over a common reflector: A <0.5 H _S1 , preferably A < 0.2 H _S1 , and / or wherein preferably the dipole radiators of the first antennas and the radiators of the second antennas have the same resonant frequency ranges and / or the same structure. Mobile radio antenna arrangement according to one of claims 7 to 11, wherein the dipole radiators of the first antennas are arranged in a first plane and the second antennas have metal structures arranged in a second plane above the first plane, wherein the first dielectric bodies extend at least to the second level of the metal structures of the second antennas and / or raise the radiation plane of the dipole radiators of the first antennas at least to the second plane, and / or wherein the height H _{S1 of} the dipole radiators of the first antennas above a common reflector is smaller than the height H _{S2 of} the radiators of the second antennas above a common reflector, and / or wherein the center frequency of the lowest resonance frequency range of the dipole radiators of the first antennas is higher as the center frequency of the lowest resonance frequency range of the radiators of the second antennas. The mobile radio antenna arrangement according to claim 12, wherein the radiators of the second antennas are dipole radiators and arranged in a plane above the plane of the dipole radiators of the first antennas, the dipole radiators of the first antennas and the radiators of the second antennas preferably having and / or for different resonant frequency ranges different frequency bands are used, and / or wherein the second antenna preferably has a plurality of dipoles, which are arranged in a square and / or cross and / or T,
or
wherein third radiators are arranged in the area of the radiators of the second antennas, which preferably have the same resonant frequency range and / or are used for the same frequency band as the dipole radiators of the first antennas, and / or where the dipole radiators of the first antennas and the radiators of the second antennas preferably have different resonant frequency ranges and / or are used for different frequency bands, the emitters of the second antennas preferably have radiator elements which extend parallel and / or perpendicular and / or oblique to the emission direction, the third emitters preferably within the parallel and / or arranged perpendicular and / or obliquely to the emission direction radiating elements are arranged, wherein it is preferably in the third emitters to dual-polarized dipole radiator. A mobile radio antenna arrangement according to any one of claims 7 to 13, at least one column or row of antennas, the first and second antennas being arranged alternately in the column or row, and / or the second antennas being arranged between two columns or rows of first antennas, wherein the array antenna preferably has a plurality of columns and rows, wherein the first and the second antennas are arranged alternately in the plurality of columns and rows and / or wherein the second antennas are arranged between a plurality of columns and rows of first antennas. Mobile radio antenna arrangement according to one of claims 7 to 13, wherein the first antennas of the mobile radio antenna are formed by mobile radio antennas according to one of claims 1 to 8.

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