CN117411497B - Full duplex phased array and radio frequency decoupling network thereof - Google Patents
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Abstract
The invention discloses a full duplex phased array and a radio frequency decoupling network thereof, wherein the full duplex phased array comprises a transmitting subarray and a receiving subarray which are staggered with each other, an additional decoupling reference unit is added in the receiving subarray of an antenna, under the premise of consistent receiving function, the coupling difference between the decoupling reference unit and the receiving unit is constructed through array position arrangement, the radio frequency decoupling network adjusts the amplitude and the phase of a reference channel of the radio frequency decoupling network at the front end according to the difference, so that the amplitude of a self-interference signal in the reference channel is the same as or similar to that of the receiving channel, the phase is opposite, and the two channels are combined to eliminate the self-interference signal, and meanwhile, the interested receiving signal can be reserved, thereby realizing the full duplex communication function.
Description
Technical Field
The present invention relates to the field of wireless communication technology, and more particularly, to a full duplex phased array and a radio frequency decoupling network thereof.
Background
The use of modern society data has grown in blowout, which has prompted the mobile communications demand to grow very much from place to place. 6G is a new generation mobile communication technology developed towards the mobile communication demand after 2030, and aims to remarkably improve the communication performances such as peak rate, time delay, traffic density, mobility, spectrum efficiency and the like and realize the ultimate goal of everything interconnection. Full duplex communication is one of the key technologies of the 6G enhanced wireless air interface, and is the most effective technical approach for improving the spectrum efficiency. As an emerging wireless link communication scheme, the wireless link communication system can simultaneously transmit and receive independent data streams in the same frequency band of a communication system, avoids spectrum resource waste caused by orthogonality between signal transmission and reception in half-duplex communication, and can directly improve spectrum efficiency to be twice as high as the original one. In addition to improving the gain of data throughput, the full duplex technology can avoid wireless access collision, reduce congestion and end-to-end delay, and the like, and meet the exponentially growing user data and diversified business demands in future mobile communication scenes.
A conventional phased array architecture is shown in fig. 1, where the transmit subarray and the receive subarray are aligned along the x-axis, and the transmit-receive array elements are aligned.
At present, the most central problem faced by full duplex communication systems is that the transmitter signal can generate significant self-interference to the receiver. In the case where the received signal is weak and the self-interference signal is strong, the self-interference signal not only floods the target received signal, but also directly saturates the receiving link. The full duplex phased array is required to process the problem of self-interference from a plurality of transmitting units to a plurality of receiving units, and the complexity of modeling and cancellation is greatly increased; meanwhile, phased arrays are often applied to scenes with higher link budget, and higher transmit-receive isolation is required under the requirements of higher radiation power and receiving sensitivity.
In order to solve the problem of self-interference in a full duplex system, students at home and abroad put forward various solutions to cover a plurality of links such as antenna propagation, analog circuits, digital terminals and the like. In practical full duplex applications, it is difficult for a single decoupling scheme to reduce self-interference to a sufficiently low level, and common systems combine multiple technical means to suppress the self-interference signal step by step. For example, a 28GHz full duplex phased array published by Kyutae Park et al in 2021 on IEEE microwave theory and technology journal (IEEE Transactions on Microwave Theory and Techniques) processes self-interference signals aiming at two links of antenna propagation and radio frequency circuits, the cross polarization of a transceiver sub-array improves the original transceiver isolation by 10dB, the radio frequency cancellation channel of a 2 tap further brings 10dB isolation, finally, the transceiver isolation of more than 57dB in the 1GHz bandwidth is obtained, and the self-interference can be reduced to the noise level by further realizing 15.5dB inhibition in the digital domain.
Although the digital signal processing can effectively inhibit the self-interference of the receiving and transmitting, in order to ensure the receiver is unsaturated, the self-interference signal is inhibited to be within the dynamic range of the ADC, and the self-interference inhibiting means of the radio frequency front end is very important. The radio frequency cancellation method is a common self-interference suppression means, and uses the low-power signal extracted from the transmitting end to process amplitude, phase and time delay, and then combine with the receiving channel to cancel the self-interference signal. In a single-shot single-receive system, a single-channel radio frequency canceller can improve isolation by 10-30 dB, but complex coupling of antennas is difficult to completely simulate when the cancellation channel is processed, and the relative bandwidth realized by the prior art is basically below 5%. On the other hand, the multi-array element coupling in the full duplex phased array scene is more complex, and the application and the final effect of the cancellation technology are limited.
Disclosure of Invention
The primary purpose of the invention is to provide a full duplex phased array, which solves the problems of low isolation degree and narrow bandwidth of the radio frequency cancellation technology of the current full duplex system; it is a secondary object of the present invention to provide a full duplex phased array radio frequency decoupling network.
In order to solve the technical problems, the technical scheme of the invention is as follows:
in one aspect, the invention provides a full duplex phased array, which comprises a transmitting subarray and a receiving subarray which are separated, wherein the interval between the transmitting and receiving subarrays is smaller than that of a conventional array, the interval is smaller than half wavelength, the transmitting subarray comprises a plurality of transmitting array elements which are uniformly arranged along the horizontal direction, the receiving subarray comprises a plurality of receiving array elements which are uniformly arranged along the horizontal direction and at most two reference array elements, wherein the receiving array elements in the receiving subarray and the transmitting array elements of the transmitting subarray are staggered in the horizontal direction, each receiving array element is positioned between two adjacent transmitting array elements in the horizontal direction, the reference array elements are arranged at the head part and/or the tail part of the receiving subarray, and the reference array elements are only adjacent to one transmitting array element in the horizontal direction.
In the above technical means, the transmitting array elements and the receiving array elements are placed in a staggered manner, and because electromagnetic waves continuously attenuate along the propagation path, the coupling of the antenna elements with larger distance therebetween is weaker, so that the receiving array elements only consider self-interference signals of two adjacent transmitting array elements to the receiving array elements, the coupling strength of the reference array elements by the transmitting antenna is lower, only consider self-interference signals of two adjacent transmitting array elements to the receiving array elements, and the function of receiving external signals is basically consistent, and the coupling difference between the decoupling reference units and the receiving units is constructed through array position arrangement.
Further, the distances between two adjacent array elements in the transmitting subarray and two adjacent array elements in the receiving subarray are both D, and the distance between the receiving array elements in the receiving subarray and the two adjacent transmitting array elements in the horizontal direction is D/2.
Furthermore, the transmitting array element, the receiving array element and the reference array element are all formed by adopting antennas with the same structure.
Furthermore, the array elements of the transmitting subarray and the array elements of the receiving subarray share a dielectric substrate respectively, and are tightly coupled with each other.
Furthermore, decoupling structures are added between two adjacent array elements in the transmitting subarray and two adjacent array elements in the receiving subarray.
Another aspect of the present invention provides a radio frequency decoupling network of a full duplex phased array as described above, where the decoupling network obtains reference signals for cancellation from a receiving subarray, where the decoupling network includes a plurality of receiving channels corresponding to the receiving array elements one by one and reference channels corresponding to the reference array elements one by one, where each receiving channel is connected to one receiving array element, each reference channel is connected to one reference array element, each receiving channel performs signal amplification and phase shift scanning on a receiving signal of the receiving array element connected thereto, each reference channel performs amplitude modulation and phase modulation on a receiving signal of the reference array element connected thereto, and after combined cancellation is performed on an output signal of each receiving channel and an output signal of one reference channel, a receiving signal of interest in each receiving channel is obtained.
Further, each receiving channel comprises an amplifier and an adjustable phase shifter, wherein the input end of the amplifier receives a receiving signal of a corresponding receiving unit, the output end of the amplifier is connected with the input end of the adjustable phase shifter, and the output end of the adjustable phase shifter outputs an output signal of the receiving channel. Wherein the amplifier may be in the form of a low noise amplifier, a variable gain amplifier, etc., which may also be cascaded with an attenuator.
Further, each of the reference channels contains amplitude and phase adjustment devices, which may be implemented by an amplifier, which may be in the form of a low noise amplifier, a variable gain amplifier, etc., an adjustable attenuator, and an adjustable phase shifter. The input end of the amplifier receives a receiving signal of a corresponding decoupling reference unit, the output end of the amplifier is connected with the input end of the adjustable attenuator, the output end of the adjustable attenuator is connected with the input end of the adjustable phase shifter, and the output end of the adjustable phase shifter outputs an output signal of the reference channel. The relative positions of the adjustable attenuator and the adjustable phase shifter may be interchanged.
Further, the reference channel performs amplitude modulation and phase modulation on the received signal of the reference array element connected with the reference channel, and the method comprises the following steps:
the amplitude of the received signal of the reference array element is adjusted to be the same as or similar to the amplitude of the output signal of the corresponding receiving channel, and the phase of the received signal of the reference array element is adjusted to be opposite to the phase of the output signal of the corresponding receiving channel.
Further, the device also comprises a combiner, and the output signal of each receiving channel and the output signal of one reference channel are combined and counteracted by the combiner.
Furthermore, the radio frequency cancellation network can be combined with a traditional radio frequency cancellation architecture, namely a low-power copy of a transmitting signal is obtained from a transmitting end of a transmitting subarray, and after the low-power copy of the transmitting signal is combined with an output signal of the radio frequency decoupling network, a final output signal is obtained, decoupling effects of the radio frequency decoupling network and the radio frequency cancellation architecture can be overlapped, and the suppression performance on self-interference signals is further improved.
Compared with the prior art, the technical scheme of the invention has the beneficial effects that:
according to the invention, an additional decoupling reference unit is added in the receiving subarray of the antenna, under the premise of consistent receiving function, the coupling difference between the decoupling reference unit and the receiving unit is constructed through array position arrangement, and according to the difference, amplitude and phase adjustment are carried out on a reference channel of the radio frequency decoupling network at the front end, so that the amplitude of a self-interference signal in the reference channel is similar to that of the receiving channel, the phase is opposite, and the two channels are combined to eliminate the self-interference signal, and simultaneously, the external receiving signal can be reserved, thereby realizing the full-duplex communication function.
Drawings
FIG. 1 is a schematic diagram of a conventional full duplex phased array structure;
fig. 2 is a schematic diagram of a full duplex phased array structure of a decoupling reference unit according to an embodiment of the present invention when receiving a sub-array header;
fig. 3 is a schematic diagram of a full duplex phased array structure of a decoupling reference unit provided in an embodiment of the present invention when receiving a tail of a sub-array;
fig. 4 is a schematic diagram of a full duplex phased array structure of a decoupling reference unit according to an embodiment of the present invention when receiving the head and tail of a subarray;
fig. 5 is a schematic structural diagram of a radio frequency decoupling network according to an embodiment of the present invention;
FIG. 6 is a schematic diagram of coupling distribution during scanning of an emission sub-array according to an embodiment of the present invention;
fig. 7 is a schematic diagram of a Vivaldi antenna structure according to an embodiment of the present invention;
fig. 8 is a schematic diagram of a full duplex phased array structure using Vivaldi antennas according to an embodiment of the present invention;
FIG. 9 is a graph showing matching performance of the full duplex phased array of FIG. 7 provided by an embodiment of the invention;
FIG. 10 is a graph showing the radiation performance of the full duplex phased array of FIG. 7 provided by an embodiment of the invention;
FIG. 11 is a schematic diagram of a radiation direction at 0.8GHz of the transmit subarray of the full-duplex phased array of FIG. 7 provided by an embodiment of the invention;
FIG. 12 is a schematic diagram of a radiation direction at 1.5GHz of a transmit subarray of the full-duplex phased array of FIG. 7 provided by an embodiment of the invention;
FIG. 13 is a schematic diagram of a receive subarray of the full duplex phased array of FIG. 7 at 0.8GHz in radiation direction provided by an embodiment of the invention;
FIG. 14 is a schematic diagram of a receive subarray of the full duplex phased array of FIG. 7 at 1.5GHz radiation direction provided by an embodiment of the invention;
fig. 15 is a schematic diagram of amplitude of different coupling types between transmit-receive array elements of the full duplex phased array of fig. 7 according to an embodiment of the invention;
FIG. 16 is a schematic diagram of the total coupling amplitude of the entire transmit subarray of the full duplex phased array of FIG. 7 to a single receive unit provided by an embodiment of the present invention;
FIG. 17 is a schematic diagram of the total coupled phase of the entire transmit subarray of the full duplex phased array of FIG. 7 to a single receive unit provided by an embodiment of the present invention;
fig. 18 is a schematic diagram of a radio frequency decoupling network corresponding to the full duplex phased array of fig. 7 provided by an embodiment of the invention;
fig. 19 is a schematic diagram of decoupling effects of the radio frequency decoupling network of fig. 15 according to an embodiment of the present invention;
fig. 20 is a schematic diagram of distribution and phase information of coupling 1 between arrays when the phased array according to the embodiment of the present invention performs beam scanning;
FIG. 21 is a radiation pattern of an emissive subarray according to an embodiment of the present invention at scan angles of 0, + -15, and+ -30, respectively;
FIG. 22 is a radiation pattern of a receive subarray according to an embodiment of the present invention with scan angles of 0, + -15, and+ -30, respectively;
fig. 23 is a schematic diagram of transmit-receive isolation of a phased array with different beam scanning angles according to an embodiment of the present invention.
In the figure, 1 is a dielectric substrate, 2 is a feed microstrip line, 3 is a radiation slot line, and 4 is a sawtooth slot structure.
Detailed Description
The drawings are for illustrative purposes only and are not to be construed as limiting the present patent;
for the purpose of better illustrating the embodiments, certain elements of the drawings may be omitted, enlarged or reduced and do not represent the actual product dimensions;
it will be appreciated by those skilled in the art that certain well-known structures in the drawings and descriptions thereof may be omitted.
The technical scheme of the invention is further described below with reference to the accompanying drawings and examples.
Example 1
The embodiment provides a full duplex phased array, as shown in fig. 2 to 4, including separate transmitting subarrays and receiving subarrays, where the transmitting subarrays include a plurality of transmitting array elements uniformly arranged along a horizontal direction, the receiving subarrays include a plurality of receiving array elements uniformly arranged along a horizontal direction and at most two reference array elements, where the receiving array elements in the receiving subarrays and the transmitting array elements of the transmitting subarrays are staggered in the horizontal direction, so that each receiving array element is located between two adjacent transmitting array elements in the horizontal direction, when there is only one reference array element, the reference array element can be located at the head or tail of the receiving subarray, when there are two reference array elements, the reference array elements are located at the head and tail of the receiving subarray, and the reference array elements are adjacent to only one transmitting array element in the horizontal direction, when there are three array elements, the reference array elements can be located at positions near the head and tail of the receiving subarray and after the head and tail of the receiving subarray
As shown in fig. 2 to 4, the coupling of different types is described by coupling 1, coupling 2, etc. from strong to weak, and is represented by C1, C2, etc., the external received signal is represented by S, and the weaker signal is ignored, so that the signals received by all receiving units are the sum of the coupling and the external received signal:
Y Rx =2C1+S
and the coupling is weaker at the edge position of the decoupling reference cell position array, and the total signal received by the decoupling reference cell position array is:
Y Ref =C1+S
therefore, the pure external receiving signal can be obtained by amplitude modulation of the signal received by the decoupling reference unit and then cancellation of the signal received by the receiving unit.
Example 2
The embodiment provides a radio frequency decoupling network of a full duplex phased array according to embodiment 1, as shown in fig. 5, where fig. 5 shows that the full duplex phased array has a decoupling reference unit, and the decoupling reference unit is disposed at a header of a receiving sub-array, and the radio frequency decoupling network obtains reference signals for cancellation from the receiving sub-array, where the reference signals include a plurality of receiving channels corresponding to the receiving array elements one by one and reference channels corresponding to the reference array elements, each receiving channel is connected to one receiving array element, each reference channel is connected to the reference array element, each receiving channel performs signal amplification and phase shift scanning on a received signal of the receiving array element connected to the receiving channel, and the reference channels perform amplitude modulation and phase modulation on the received signal of the reference array element connected to the receiving channel, and after the output signal of each receiving channel and the output signal of one reference channel are combined and cancelled, the interested received signal in each receiving channel is obtained.
Each receiving channel comprises an amplifier and an adjustable phase shifter, wherein the input end of the amplifier receives a receiving signal of a corresponding receiving unit, the output end of the amplifier is connected with the input end of the adjustable phase shifter, and the output end of the adjustable phase shifter outputs an output signal of the receiving channel. In this embodiment, the amplifier may be in the form of a low noise amplifier, a variable gain amplifier, or the like, or may be cascaded with an attenuator.
Each reference channel comprises an amplitude and phase adjusting device, and the amplitude and phase adjusting device can be realized through a low-noise amplifier, an adjustable attenuator and an adjustable phase shifter, wherein the input end of the low-noise amplifier receives a receiving signal of a corresponding decoupling reference unit, the output end of the low-noise amplifier is connected with the input end of the adjustable attenuator, the output end of the adjustable attenuator is connected with the input end of the adjustable phase shifter, and the output end of the adjustable phase shifter outputs an output signal of the reference channel. The same function can also be achieved by a variable gain amplifier and an adjustable phase shifter.
The system also comprises a combiner, wherein the output signal of each receiving channel and the output signal of one reference channel are combined and counteracted by the combiner.
The reference signal is subjected to double amplification and inversion at the receiving endThe signal of the reference channel can be expressed as Y REF ’=-2C1-2/>S, the process of combining cancellation with the receiving channel can be expressed as:
Y Res =2C1+S-(2/>C1+2/>S)=-S
through the above-mentioned cancellation process, the final rf output signal is a pure external received signal.
When the phased array is scanned, assuming that the transmitting array elements are sequentially phase shifted by 0, θ,2θ, … …, nθ, respectively, fig. 6 depicts the distribution and phase information of the strongest coupling (C1) between the transceiver units at this time, the coupling 1 of the transmitting unit 1 to the decoupling reference unit and the receiving unit 1 may be denoted as C1, the coupling 1 of the transmitting unit 2 to the receiving unit 1 and the receiving unit 2 may be denoted as C1 +.θ, and the coupling 1 of the transmitting unit 2 to the receiving unit 2 and the receiving unit 3 may be denoted as C1 +.2θ. The total coupling signal of each receiving unit is C1σ∠0.5θ、C1/>σ∠1.5θ、C1/>Sigma is 2.5θ … …, wherein sigma is an amplitude coefficient, and the coupling signal of the decoupling reference unit is still C1. For the receiving unit 1, the combiner cancellation procedure can be expressed as:
Y Res1 =C1σ∠0.5θ+S-(C1/>σ∠0.5θ+S/>σ∠0.5θ)= S(1-σ∠0.5θ)
i.e. the decoupling reference cell amplitude is sigma-fold amplified, phase shifted pi +0.5 theta. For the receiving unit 2, the combiner cancellation procedure can be expressed as:
Y Res2 =C1σ∠1.5θ+S-(C1/>σ∠1.5θ+S/>σ∠1.5θ)=S(1-σ∠1.5θ)
i.e. the decoupling reference cell amplitude is sigma-fold amplified, phase shifted pi +1.5 theta. The remaining receiving units and so on. In summary, when the phased array scans, the receiving and transmitting coupling signals can be basically eliminated, and signals are received to a certain extent, and only the amplitude modulation and phase modulation link of the reference channel is required to be supplemented with corresponding amplitude and phase.
The full duplex phased array and the radio frequency decoupling network in the embodiment can be further overlapped to improve the isolation performance by combining with other full duplex technologies. For example, the full duplex phased array and the radio frequency decoupling network in this embodiment are combined with a conventional radio frequency cancellation architecture, where a conventional radio frequency cancellation circuit obtains a reference signal from the front end of the transmitter, and combines the reference signal with the output end of the radio frequency reference network to form a final received signal.
In a specific embodiment, a transmitting signal in the front end of a transmitter is transmitted to a transmitting sub-array through a beam forming network to be transmitted, a low-power copy of the transmitting signal is obtained at the transmitting end of the transmitting sub-array to be used as a reference signal, the low-power copy of the transmitting signal is combined with an output signal of a radio frequency decoupling network to obtain a final output signal, and decoupling effects of the radio frequency decoupling network and a radio frequency cancellation architecture can be overlapped to further improve the suppression performance on self-interference signals.
Example 3
This embodiment continues to provide the following embodiments on the basis of embodiment 2 of embodiment 1:
the embodiment provides a full duplex phased array, two decoupling reference units are arranged at two ends of a receiving subarray, and the receiving subarrays are staggered. Each array element can adopt various antenna types, such as Vivaldi antennas, microstrip antennas, dipole antennas and the like, and the embodiment adopts the Vivaldi antennas to realize the array, wherein the Vivaldi antennas are broadband antennas, and the overall structure of the Vivaldi antennas is shown in fig. 7 and consists of three parts, namely a dielectric substrate 1, a feed microstrip line 2 and a radiation slot line 3. The phased array formed by Vivaldi antennas is shown in fig. 8, and the transmitting subarray is positioned in front and comprises 6 transmitting antenna units and two blind pixels; the receiving sub-array is positioned at the rear and comprises 5 receiving antenna units, 2 reference receiving units and two blind pixels, and the distance between the receiving sub-arrays is only 50mm (0.167 wavelength at 1 GHz). The blind pixels are used for improving impedance matching of the array elements at the edges of the transceiver subarrays, and meanwhile, the difference of performances of the reference receiving unit and the receiving unit in the aspects of coupling, receiving and the like can be reduced, and the signal input port of the blind pixels is connected with a matching load and does not bear radiation. The antennas of the transceiver subarray share a dielectric substrate, are tightly coupled with each other, and in order to improve isolation of array elements in the subarray and reduce E-plane coupling, a sawtooth slotting structure 4 is added between adjacent array elements.
Fig. 9 and 10 respectively describe matching and radiation performance of the Vivaldi antenna array, and the-10 dB matching bandwidth of each array element covers 0.8-1.5 ghz, and the forward gain of the antenna array is greater than 9dB in this range. Fig. 11 and 12 depict radiation patterns of the transmitting sub-array at 0.8GHz and 1.5GHz, respectively, and fig. 13 and 14 depict radiation patterns of the receiving sub-array at 0.8GHz and 1.5GHz, respectively, both of which are forward radiation, and the side lobes and back radiation are weaker. The patterns of different frequencies have consistency, the wave beams at high frequencies are more concentrated than those at low frequencies, and meanwhile, the antenna array has higher radiation gain in the whole matching bandwidth, which shows that the antenna array can well work at 0.8-1.5 GHz.
Since electromagnetic waves are continuously attenuated along the propagation path, the coupling of antenna units with larger mutual distance is weaker, the coupling is classified according to the distance between the receiving units and the receiving units, the coupling with the nearest distance and the strongest energy is expressed as coupling 1 (C1), the coupling with the next distance is expressed as coupling 2 (C2), and so on, namely, the coupling is respectively marked as C1, C2, C3 and C4 … … from strong to weak, and the graph 15 shows the amplitude of different coupling types between the receiving units and the receiving units, wherein the coupling 1 is stronger than the coupling 2 by 8dB, the coupling 2 is stronger than the coupling 3 by 10dB and the coupling 3 is stronger than the coupling 4 by 10dB in the whole frequency band. The external received signal is denoted by S. Ignoring weaker signals than C1, the signals received by all receiving units being the sum Y of the coupled and outer received signals Rx =2C1+S, and due to the edge position of the array, the total signal received by the two decoupled reference cells is Y Ref =c1+s. Fig. 16 and 17 show the total coupling amplitude and phase of the entire transmitting sub-array to a single receiving antenna, respectively, wherein the coupling amplitude of the five receiving units is about-17 dB, the coupling amplitude of the decoupling reference unit is about-23 dB, and the phases within the operating frequency band are substantially identical. The antenna array architecture is proved to realize the differentiation of coupling, and meanwhile, the phases are basically consistent, so that the subsequent cancellation process is facilitated. The receiving end amplifies and inverts the double of the reference signal, the signal of the reference channel is Y Ref ’=-2/>C1-2/>S, the signal after combining and counteracting is Y Res =2/>C1+S-(2/>C1+2/>S) = -S, i.e. a clean received signal.
The embodiment also provides a corresponding decoupling circuit for the front end of the radio frequency, as shown in fig. 18, 5 receiving channels are connected with 5 receiving units of the antenna array, each receiving channel is composed of a low noise amplifier and an adjustable phase shifter, the amplifying function of the received signal and the phase scanning function of the phased array are respectively realized, and the 5 receiving channels are combined by using a 1-division 2-power divider and a 1-division 3-power divider to obtain the total received signal. The 2 reference channels are composed of a low noise amplifier, an adjustable attenuator and an adjustable phase shifter, and the reference channels are respectively subjected to amplitude modulation and phase modulation and then are combined to obtain a total reference signal. In the decoupling network, the amplitude of the reference channel is adjusted to be consistent with the receiving channel, the phase is adjusted to be opposite to the receiving channel, and then the combiner is utilized to combine with the received signal for cancellation. The decoupling effect of the network is shown in fig. 19, and the transceiving coupling in the range of 0.8 GHz-1.5 GHz can be reduced from-10 dB to-40 dB.
The decoupling design works equally well when the phased array is beam scanned, maintaining high transmit-receive isolation of the system, and the same decoupling network design is used when the beam is scanned as when it is not scanned, as shown in fig. 18. When the phase shifts of the transmitting array elements are 0, θ,2θ, … …, and 5θ, respectively, fig. 20 depicts the distribution and phase information of the coupling 1 between the arrays at this time, the coupling generated by the transmitting 1 pair of reference 1 and the receiving 1 is C1, the coupling generated by the transmitting 2 pair of receiving 1 and the receiving 2 is C1 ++θ … …, and the coupling generated by the transmitting 2 pair of receiving 1 and the receiving 2 is C1 ++5θ. For reception 1, the combiner cancellation process may be denoted as Y Res1 =C1σ∠0.5θ+S-(C1/>σ∠0.5θ+S/>Sigma < 0.5θ) =s (1-sigma < 0.5θ), sigma is the amplitude coefficient; for receive 2, the combiner cancellation process may be denoted as Y Res2 =C1/>σ∠1.5θ+S-(C1/>σ∠1.5θ+S/>Sigma < 1.5θ) =s (1-sigma < 1.5θ), the remaining receiving units and so on. As a result of this calculation, the decoupling scheme is still able to cancel the self-interference signal, but loses some of the externally received signal relative to the case without scanning. When the decoupling network utilizes the reference 1 to cancel the self-interference signal of the receiving unit 1, the signal needs to be amplified by sigma times and phase-shifted by pi+0.5θ; when the reference 1 is used for canceling the self-interference signal of the receiving 2, the signal needs to be amplified by sigma times and phase-shifted by pi+1.5θ; when the reference 2 is used for canceling the self-interference signal of the receiving 5, the signal needs to be amplified by sigma times and phase-shifted by pi-0.5 theta.
The radiation patterns of the transmitting sub-array and the receiving sub-array at scanning angles of 0, ±15° and ±30° are shown in fig. 21 and fig. 22, respectively, and the scanning loss in the range of ±30° is less than 0.8dB. When the beam scanning angles of the transmitting array are +/-15 degrees and +/-30 degrees respectively, as shown in fig. 23, the transceiving coupling of the system is stabilized below-40 dB in the frequency band of 0.8 GHz-1.5 GHz, and the isolation robustness of the design in phased array scanning is proved. The same or similar reference numerals correspond to the same or similar components;
the terms describing the positional relationship in the drawings are merely illustrative, and are not to be construed as limiting the present patent;
it is to be understood that the above examples of the present invention are provided by way of illustration only and not by way of limitation of the embodiments of the present invention. Other variations or modifications of the above teachings will be apparent to those of ordinary skill in the art. It is not necessary here nor is it exhaustive of all embodiments. Any modification, equivalent replacement, improvement, etc. which come within the spirit and principles of the invention are desired to be protected by the following claims.
Claims (10)
1. The full duplex phased array is characterized by comprising a separated transmitting subarray and a receiving subarray, wherein the transmitting subarray comprises a plurality of transmitting array elements which are uniformly arranged along the horizontal direction, the receiving subarray comprises a plurality of receiving array elements which are uniformly arranged along the horizontal direction and at least 1 reference array element, wherein the receiving array elements in the receiving subarray and the transmitting array elements of the transmitting subarray are staggered in the horizontal direction, each receiving array element is positioned between two adjacent transmitting array elements in the horizontal direction, the reference array element is arranged at the head part and/or the tail part of the receiving subarray, and the reference array element is only adjacent to one transmitting array element in the horizontal direction.
2. The full duplex phased array of claim 1, wherein the distance between two adjacent array elements in the transmit subarray and two adjacent array elements in the receive subarray is D, and the distance between a receiving array element in the receive subarray and two adjacent transmit array elements in the horizontal direction is D/2.
3. The full duplex phased array of claim 2, wherein the transmit array element, the receive array element, and the reference array element all use the same antenna configuration.
4. A full duplex phased array as claimed in claim 3, wherein a dielectric substrate is shared between each of the transmit subarray elements and each of the receive subarray elements and is tightly coupled to each other, and decoupling structures are added between adjacent two of the transmit subarrays and adjacent two of the receive subarrays to reduce E-plane coupling.
5. A full duplex phased array radio frequency decoupling network as claimed in any one of claims 1 to 4, wherein reference signals for cancellation are obtained from a receiving sub-array, the decoupling network comprising a plurality of receiving channels in one-to-one correspondence with the receiving array elements and reference channels in one-to-one correspondence with the reference array elements, wherein each of the receiving channels is connected to one of the receiving array elements, each of the reference channels is connected to one of the reference array elements, each of the receiving channels performs signal amplification and phase shift scanning on the received signal of the receiving array element connected thereto, each of the reference channels performs amplitude modulation and phase modulation on the received signal of the reference array element connected thereto, and the output signal of each of the receiving channels is combined with the output signal of one of the reference channels to cancel the received signal of interest in each of the receiving channels, as the output signal of the radio frequency decoupling network.
6. The full duplex phased array radio frequency decoupling network of claim 5, wherein each of the receive paths comprises an amplifier and an adjustable phase shifter, wherein the input of the amplifier receives the receive signal of the corresponding receive unit, and wherein the output of the amplifier is coupled to the input of the adjustable phase shifter, and wherein the output of the adjustable phase shifter outputs the output signal of the receive path.
7. The full duplex phased array radio frequency decoupling network of claim 5, wherein each of said reference channels comprises amplitude and phase adjustment devices, implemented by an amplifier, an adjustable attenuator and an adjustable phase shifter, wherein the input of said amplifier receives the received signal of the corresponding decoupled reference cell, the output of said amplifier is connected to the input of said adjustable attenuator, the output of said adjustable attenuator is connected to the input of said adjustable phase shifter, and the output of said adjustable phase shifter outputs the output signal of said reference channel.
8. The full duplex phased array radio frequency decoupling network of claim 7, wherein the reference channel amplitude and phase modulates the received signals of the reference array elements connected thereto, comprising:
the amplitude of the received signal of the reference array element is adjusted to be the same as or similar to the amplitude of the output signal of the corresponding receiving channel, and the phase of the received signal of the reference array element is adjusted to be opposite to the phase of the output signal of the corresponding receiving channel.
9. The full duplex phased array radio frequency decoupling network of claim 5, further comprising a combiner, the output signal of each of the receive channels and the output signal of one of the reference channels being combined by the combiner.
10. The full duplex phased array radio frequency decoupling network of claim 6, wherein a low power copy of the transmit signal is obtained from the transmit end of the transmit sub-array, and the low power copy of the transmit signal is combined with the output signal of the radio frequency decoupling network to obtain a final output signal.
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Citations (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| KR20110115465A (en) * | 2010-04-15 | 2011-10-21 | 국방과학연구소 | Method of beam nulling in phase arrangement antenna |
| US9395727B1 (en) * | 2013-03-22 | 2016-07-19 | Google Inc. | Single layer shared aperture beam forming network |
| CN106063135A (en) * | 2014-03-07 | 2016-10-26 | 华为技术有限公司 | Interference elimination device and method |
| CN110361739A (en) * | 2018-04-09 | 2019-10-22 | 株式会社万都 | Radar equipment and its antenna equipment |
| JP2020153871A (en) * | 2019-03-20 | 2020-09-24 | パナソニックＩｐマネジメント株式会社 | Radar device |
| CN116054853A (en) * | 2023-01-13 | 2023-05-02 | 电子科技大学 | Robust phased array self-interference digital domain suppression method |
| CN117176260A (en) * | 2023-08-29 | 2023-12-05 | 大连理工大学 | Phased array antenna leakage interference elimination device and method based on microwave photons |
Family Cites Families (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US8837332B2 (en) * | 2010-12-13 | 2014-09-16 | Nec Laboratories America, Inc. | Method for a canceling self interference signal using passive noise cancellation for full-duplex simultaneous (in time) and overlapping (in space) wireless transmission and reception on the same frequency band |
| JP2017147574A (en) * | 2016-02-16 | 2017-08-24 | 富士通株式会社 | Wireless communication device and antenna arrangement method |
-
2023
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Patent Citations (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| KR20110115465A (en) * | 2010-04-15 | 2011-10-21 | 국방과학연구소 | Method of beam nulling in phase arrangement antenna |
| US9395727B1 (en) * | 2013-03-22 | 2016-07-19 | Google Inc. | Single layer shared aperture beam forming network |
| CN106063135A (en) * | 2014-03-07 | 2016-10-26 | 华为技术有限公司 | Interference elimination device and method |
| CN110361739A (en) * | 2018-04-09 | 2019-10-22 | 株式会社万都 | Radar equipment and its antenna equipment |
| JP2020153871A (en) * | 2019-03-20 | 2020-09-24 | パナソニックＩｐマネジメント株式会社 | Radar device |
| CN116054853A (en) * | 2023-01-13 | 2023-05-02 | 电子科技大学 | Robust phased array self-interference digital domain suppression method |
| CN117176260A (en) * | 2023-08-29 | 2023-12-05 | 大连理工大学 | Phased array antenna leakage interference elimination device and method based on microwave photons |
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